Wireless Transmitting Method

TECHNICAL FIELD [0001] The present invention relates to wireless transmitting devices and methods of wireless transmission and in particular wireless transmitting devices and methods of wireless transmission for transmitting signals to wireless receiving devices using multiple transmission antennas.

This application claims the priority of Japanese Patent Application No. 2005-253194 filed in Japan on September 1, 2005 and Japanese Patent Application No. 2005-367860 filed in Japan on December 21, 2005, the contents of which are incorporated herein by reference.

BACKGROUND OF THE INVENTION [0002] Recently, methods have been provided, mainly adapted for multi-carrier broadcast systems in which a plurality of blocks are separated along a frequency and time axis, and which carry out a series of signals transmitted to users from wireless broadcast devices in block units. Here, regions that are secured to users for communication and that are defined along the frequency and time axis are called assignment slots, and the blocks that serve as the basis for determining assignment slots are referred to as fragments.

[0003] In the above, methods are provided that, in order to transmit broadcast signals, group transmission signals and control signals, blocks whose ranges are extended towards the frequency axis are assigned to produce frequency diversity effects. thereby reducing errors regardless of the low reception power. In addition, ways are provided to order

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Transmission of unicast signals in one-to-one communications between wireless transmitting devices and wireless receiving devices, blocks whose ranges are reduced in the direction of the frequency axis are assigned to produce multi-user diversity effects (multiuser diversity), thereby improving the receiving power of wireless receiving devices.

[0004] FIG. 16A and 16B depict relationships related to signals transmitted from a wireless transmitting device to a wireless receiving device with respect to time (horizontal axis) and frequency (vertical axis). In FIG. 16A the horizontal axis represents time, and the vertical axis represents frequency. Transmission times from t₁ to this are listed on the timeline. In the present, the same length of time is set for times from t₁ to vol₃. Transmission frequencies from f₁ to f₅ are summarized on the frequency axis. Hereby the same scope F_Cfrequency is set for frequencies from f₁ to f₅. With reference to transmission times from t₁ to vol₃ and transmission frequency from f₁ to f₅, fifteen fragments of K are compiled₁ to K₁₅ as shown in FIG. 16A. [0005] In addition, five fragments from K₁ to K₅ are connected as shown in FIG. 16B and are then evenly divided into six slots along the time axis, thereby comparing the communication slots s1 to s6 each having a time length equal to t₁/ 6 and a frequency range of 5f₁. Communication slots p₁ and p₄ are assigned to the first user; communication gaps p₂ and p₅ are assigned to a second user; and communication gaps p₃ and p₆ are assigned to the third user. This makes it possible for the first to third users to obtain frequency diversification effects.

[0006] Then fragment K₁₀ is assigned to the fourth user as a communication slot p₁₁. Fragments of K₇, K₈ and K₉ are connected so as to form communication gaps from p₈ to p₁₀each having a length of time equal to t₂ and a frequency range of 3f₁ and which are assigned to the fifth user. In addition, fragment K₆ is assigned to the sixth user as a communication slot p₇. This makes it possible for

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From the fourth to the sixth user to achieve multi-user diversification effects, which makes it possible for the fifth user to obtain a frequency diversification effect.

[0007] Furthermore, the Ku fragment is assigned to the seventh user as a communication slot p₁₂. This makes it possible for this user to achieve the effect of diversifying many users. In addition, Ki fragments₃and K₁₅ are assigned to the eighth user as communication slots p₁₉ and p₂₆. This makes it possible for this user to achieve the effect of diversifying many users.

In addition, two fragments of K₁₂ and K₁₄ are evenly divided into six slots, thereby forming slots from p₁₃ to p₁₈ and p₂₀ to p₂₅. Communication slots p₁₃, p₁₆, p₂₀ and p₂₃ are assigned to the ninth user; communication gaps p₁₄, p₁₇, p₂₁ and p₂₄ are assigned to the tenth user; and communication gaps p₁₅, p₁₈, p₂₂ and p₂₅ are assigned to the eleventh user. This makes it possible for the ninth to eleventh users to obtain frequency diversity effects separately.

Non-Patent Document 1: Contribution to 3GPP, R1-050249, "Downlink Multiple Access Scheme for Evolved UTRA", [Obtained August 17, 2005], Internet (URL:

<a href="ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/TSGR1_40bis/Docs/R1-050249.zip">ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/TSGR1_40bis/Docs/R1050249.zip</a>)

Non-Patent Document 2: Contribution to 3GPP, R 1-050590, "Physical Channels and Multiplexing in Evolved UTRA Downlink", [Obtained August 17, 2005], Internet (URL: <a href="ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/R1_Ad_Hocs/LTE_AH_June-05/Docs/R1-050590.zip">ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/R1_Ad_Hocs/LTE_AH_June05/Docs/R1-050590.zip</a>)

DISCLOSURE OF THE INVENTION

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PROBLEMS TO BE SOLVED BY THE INVENTION [0008] In order to obtain the effects of frequency diversification in the aforementioned known traditional methods, it is necessary to increase the scatter coefficients or reduce the coding coefficients in error correction coding in response to frequency changes of the transfer function in propagation paths.

[0009] FIG. 17A and 17B and FIG. 18A and 18B are graphs showing delay profiles and transfer functions with respect to signals that are propagated through multiple propagation paths having different delay times so as to achieve wireless receiving devices.

[0010] FIG. 17A and 18A show delay profiles representing transmission signals that are propagated through multiple propagation paths so as to achieve a wireless receiving device in terms of time (horizontal axis) and power (vertical axis). FIG. 17B and 18B show transfer functions for performing frequency processing on delay profiles with respect to frequency (horizontal axis) and power (vertical axis).

[0011] FIG 17A shows the appearance of six delay waves from w11 to w16, and FIG. 18A depicts the appearance of three delay waves from w21 to w23. They differ from each other in maximum delay times t1 and t2.

[0012] When the maximum delay time t1 is long as shown in FIG. 17A and 17B, i.e. when relatively fast frequency changes (fast power changes in the frequency direction) occur in the transfer function, it is expected that an adequate frequency diversification effect will be produced regardless of the low spreading coefficients and high code rate in error correction coding . However, when the maximum delay time t2 is small as shown in FIG 18A and 18B, i.e. when there are relatively moderate frequency changes in the transfer function, it is not expected to produce an adequate frequency diversification effect when the spreading factor is small and the coding factor in correction-coded coding error is high; hence it is necessary

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EP 2 280 495 B1 to increase the spreading factor and to reduce the code rate in the error correction coding.

[0013] D1 and D2 in FIG. 17B and FIG 18B show signals, i.e. data. This means that in FIG. 17B, ​​the dispersion ratio of the spectrum spreading technology is set to "4" with respect to the D1 and D2 data, thereby assigning four subcarriers from a11 to a14 to the D1 data. Similarly, four subcarriers from a₁₅ to a₁₃ are assigned to the D2 data. In this case, the transfer function has fast frequency changes; hence, subcarrier receiving power a₁₃ relating to data D1 significantly decreases so that the subcarrier's receiving power a₁₆ referring to D2 data also drops significantly. Thus, there is no reception failure with respect to the Di and D2 data.

[0014] In FIG. 18B the scattering ratio is set to "8" so as to assign eight subcarriers from a₂₁ to a₂₈ to data D1. In this case, the transfer function has slow frequency changes such that the subcarrier's receiving power a₂₄ significantly decreases, and the subcarrier receiving power a₂₃ and a₂₅ decreases slightly, while the data dispersion ratio is increased compared to the case of FIG. 17B so that there is no receiving failure with respect to D1 data. The above mentioned scattering ratio values ​​are described for simplicity and are not necessarily limited. Document US 2005/163236 A1 shows transmission symbols in a multi-antenna communication system in which at least part of the frame is delayed in at least one antenna.

[0015] The present invention is considered with reference to the above-mentioned conditions in which the object of the invention is to provide a wireless transmission device and method of wireless transmission that can produce an adequate frequency diversification effect without controlling the spreading factor and the code rate in the error correction coding on the transmission side wireless.

MEASURES TO SOLVE THE PROBLEM

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[0016] According to the present invention, a method of transmitting control according to claim 1 is provided. A preferred feature is summarized in claim 2.

EFFECT OF THE INVENTION [0017] With respect to the delay time T matched to the communication signal that indicates either the frequency diversity transmission or the multiple user diversification transmission, the transmission signals provided to the n transmission antennas are each delayed by a delay time (n-1) T or less.

[0018] Thus, by properly setting the delay time T based on the condition whether the transmission signals are subjected to frequency diversification transmission or multi-user diversification transmission, it is possible to produce frequency diversification effects and multi-user diversity effects without being affected by propagation path conditions.

BRIEF DESCRIPTION OF THE DRAWINGS [0019]

FIG 1 is a schematic view showing that the signals transmitted by the wireless transmission device according to the first embodiment of the present invention are propagated through a plurality of propagation paths so as to reach the wireless receiving device.

FIG 2A is a graph showing a delay profile used on signals that are propagated through a plurality of propagation paths having different delay times so as to reach a wireless receiving device.

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FIG 2B is a graph showing transfer functions that is generated by performing frequency processing on the delay profile shown in FIG 2A.

FIG 3A is a graph showing another delay profile used on signals that are propagated through multiple propagation paths having different delay times so as to reach a wireless receiving device.

FIG. 3B is a graph showing the transfer functions of a wireless receiving device which is generated by performing frequency processing on the delay profile shown in FIG. 3A.

FIG. 3C is a graph showing the transfer functions of another wireless receiving device in a different position that is generated by performing frequency processing on the delay profile shown in FIG. 3A.

FIG. 4A is a graph showing the maximum delay time (n-1) T in the delay profile.

FIG. 4B is a graph showing the relationship between the maximum delay time (n-1) T shown in FIG. 4A and frequency changes.

FIG. 5A is a graph showing the next maximum delay time (n-1) T in the delay profile.

FIG. 5B is a graph showing the relationship between the maximum delay time (n-1) T shown in FIG 5A and frequency changes.

FIG. 6A is an illustration showing a wireless transceiver system in which the same signal having no time delay is transmitted via multiple antennas of the wireless transmission device.

FIG. 6B is a graph showing an example of a reception signal in the system shown in FIG. 6A.

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FIG. 6C is a graph showing another example of a reception signal in the system shown in FIG 6A.

FIG. 7A is an illustration showing a wireless transmitting / receiving system in which the same signal is used with different delay times and is then transmitted via multiple transmit antennas of the wireless transmission device.

FIG. 7B is a graph showing an example of a reception signal in the system shown in FIG. 7A.

FIG. 7C is a graph showing another example of a reception signal in the system shown in FIG 7A.

FIG. 8 is a block diagram showing the configuration of the physical layer of a wireless transmission device according to a second embodiment of the present invention.

FIG. 9A shows an example of a signal that is produced by applying a circular delay to a transmit signal in accordance with the third embodiment of the present invention.

FIG. 9B shows another example of a signal that is produced by applying a circular delay to a transmission signal in accordance with the third embodiment of the present invention.

FIG. 10 is a block diagram showing the configuration of the physical layer of a wireless transmission device according to a third embodiment of the present invention.

FIG. 11 is an illustration explaining the operation of the circular delay introduction section 119-1 in the third embodiment of the present invention.

FIG. 12 is a block diagram showing the configuration of the physical layer of a wireless transmission device according to the fourth embodiment of the present invention.

FIG. 13 is a block diagram showing the configuration of the physical layer of a wireless transmission device according to the fifth embodiment of the present invention.

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FIG. 14 is a table showing the relationship between the maximum delay time (n-1) T between transmit antennas and the frequency bandwidth Fc of the fragment in relation to each physical channel. FIG. 15 is a table showing another relationship between the maximum delay time (n-1) T between transmit antennas and the frequency bandwidth Fc of the fragment in relation to each physical channel.

FIG. 15A is a graph showing the relationship between signals that are transmitted from a wireless transmitting device to a wireless receiving device, in terms of time (horizontal axis) and frequency (vertical axis).

FIG. 16B is a graph showing communication slots that are assigned to the time-frequency space shown in FIG. 16A.

FIG. 17A is a graph showing a delay profile adapted to signals that are propagated through multiple propagation paths having different delay times so as to achieve a wireless receiving device.

FIG. 17B is a graph showing a transfer function that is generated by performing frequency processing on the delay profile shown in FIG. 17A.

FIG. 18A is a graph showing a delay profile adapted to signals that are propagated by propagation paths having different delay times so as to achieve a wireless receiving device.

FIG. 18B is a graph showing a transfer function that is generated by performing frequency processing on the delay profile shown in FIG 18A.

DESCRIPTION OF THE REFERENCE MARKINGS [0020]

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2-4

5, 6

7, 8, 9, 10 11a, 11b, 111a, 111b, 211a, 211b 12-1, 12-2, 12-3, 112-1 to 112-3, 212-1 to 212-3, from 312 -1 to 312-3

15, 215 16 from 19-1 to 19-3 from 119-1 to 119-3 20

110

219

220

310

319

320 wireless transmitting device transmitting antenna delayer wireless receiving device user dependent signal processor antenna dependent signal processor coding section with error correction coding modulator subcarrier assignment section IFFT parallel-serial converter input section GI input section delay input section input circular delays mixer filter C / A converter memory phase rotation section delay input section weight calculation section weighted reproduction section delay input and directivity control section

THE BEST WAY TO IMPLEMENT THE INVENTION

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EP 2 280 495 B1 (First Embodiment of the Invention) [0021] FIG. 1 is a schematic illustration showing that the signals transmitted from the wireless transmitting device 1 are propagated through multiple propagation paths so that they reach the wireless receiving device 7. The wireless transmitting device 1 has a plurality of transmission antennas from 2 to 4, which are suitably applied with different delay times 0, T and 2T and from which signals are transmitted. The wireless receiving device 7 receives the signals transmitted from the wireless transmitting device 1. FIG. 1 shows an example in which the wireless transmission device 1 is equipped with three transmission antennas 2 to 4.

[0022] Many transmit antennas are assumed to be transmit antennas installed in a wireless transmission device located in a cellular base station in which three types of transmit antennas are provided for different sectors of the same base station and for different base stations . The following description is given for a situation in which they belong, for example, to the same sector, but a different system may also be used. That is, n transmit antennas belong to different sectors, or n transmit antennas belong to different base stations.

In the figure, retarders 5 and 6 introduce a time delay T through which, as described above, the time delay T is introduced into the transmission antenna 3 and the time delay 2T is introduced into the transmission antenna 4.

[0023] FIG. 2A and 2B show the delay profile and transfer function with respect to signals that are propagated by multiple (three) propagation paths having different delay times so that they reach the wireless receiving device. FIG. 2A shows a delay profile showing that transmission signals are propagated through multiple propagation paths having different delay times so that they reach the wireless receiving device in terms of time (axis

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EP 2 280 495 B1) and power (vertical axis). As shown in FIG. 2A delay profile immediately has a maximum delay wave shape of 2T + d_max; hence, compared to a structure in which the same signal is transmitted via each transmit antenna, the maximum delay wave shape becomes very large. Here, dmax denotes the arrival time differences between the fast propagation path and the slow propagation path when the radio waves approach the receiving antenna from the transmitting antenna.

[0024] FIG. 2B shows the transfer function that is produced by performing frequency processing on the delay profile of FIG 2A with respect to frequency (horizontal axis) and power (vertical axis). In the delay profile, the increasing maximum delay time of 2T + dmax indicates rapid frequency changes of the transfer function. Thus, as shown in FIG. 2B (similarly to FIG. 17B), data D1 and D2 are broadcast with a broadcast ratio of "4" and are assigned to subcarriers. It is preferred that the spreading factor or the error correction coding coefficients are controlled in response to frequency changes of the transfer function in the wireless transmitting device 1, in which the above-mentioned method recognizes that the delay time 2T is previously approved by the wireless transmitting device 1; hence, it is possible to determine the spreading factor or the code rate of the error correction coding regardless of changes in the frequency of the propagation paths. In order to create the effects of diversification of many users, it is beneficial that the maximum delay time of 2T + dmax, which appears immediately in the delay profile, is not so much increased. Multi-user diversification effects will be described with reference to FIG. from 3A to 3C.

[0025] FIG. 3A to 3C show the delay profile and transfer functions with respect to signals that are propagated through a plurality of propagation paths having different delay times so as to achieve a wireless receiving device. FIG. 3A shows a delay profile adapted to transmit signals that are propagated through multiple (three) propagation paths having different delay times so that they reach the wireless transmission device in terms of time (axis

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EP 2 280 495 B1) and power (vertical axis). FIG. 3B shows the transfer function with respect to the wireless receiving device used by user u1. FIG. 3C shows the transfer function with respect to the wireless receiving device used by the user u2. Since u1 and u2 wireless user receiving devices differ in location, their immediate transfer functions differ.

[0026] Assuming that the left region is connected to frequency channel b1 and the right channel is connected to frequency channel b2 in FIG. 3B and 3C, user u1 obtains good quality on frequency b2 while user u2 obtains good quality on frequency b1. Thus, data D1 to D4 are transmitted to user u1 via frequency channel b2. Data D1 to D4 are subjected to spectrum spreading. Data D1 to D4 are transmitted to user u2 via frequency channel b1. In this case, data D1 to D4 are subjected to spectrum spreading.

[0027] As described above, by utilizing the quality difference between the frequency channels at some point, it is possible to create multi-user diversification effects to improve transmission efficiency for different users who perform communications using different frequency channels.

However, when the maximum delay time is 2T + d_max is greatly increased, fast frequency changes occur in the transfer function, thereby reducing the quality differences between frequency b1 and frequency b2.

Thus, in order to generate adequate multi-user diversification effects, it is important to reduce the maximum delay time of 2T + d_max as shown in FIG. 3A.

[0028] FIG. 4A and 4B and FIG. 5A and 5B show the relationship between the maximum delay time (n-1) T and frequency changes. When the arrival time difference (n-1) T occurs between the incoming waves w31 and w32 as shown in FIG. 4A, transfer function of this propagation path

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EP 2 280 495 B1 is shown in FIG. 4B. That is, the frequency difference between the power amplitude drops (vertical axis) is defined as F = 1 / (n-1) T.

When multiple delay waves appear from w41 to w42 as shown in FIG. 5A, the arrival time difference (n-1) T appears between the first arrival arrival w41 and the last arrival arrival wave w42 so that the frequency difference between the power amplitude drops (vertical axis) is defined as F = 1 / (n-1) T as shown in FIG. 5B.

[0029] In this regard, the frequency diversification effect differs from the multi-user diversification effect in terms of frequency changes of their respective transfer functions; hence, in order to produce a frequency diversification effect, the maximum delay time (n-1) T is set as (n-1) T&gt; 1 / Fc where Fc is the bandwidth of the fragment which is the basic region protected by the user for communication and defined in relation to the frequency axis and time axis, thereby creating an environment that easily produces a frequency diversification effect.

[0030] On the other hand, in order to create a multi-user diversification effect, the maximum delay time (n-1) T is set to (n-1) T &lt;1 / Fc, where Fc is the fragment's bandwidth, thus creating an environment easily producing a multi-user diversification effect. In the further part of the description, the inequality (n-1) T &lt;1 / Fc includes (n-1) T = 0. Hereinafter, the delay times introduced into the transmit antennas are each represented as (n-1) multiples of T where T is assumed to be constant while it is possible to change T depending on each of the transmit antennas. In order to create a multi-user diversification effect, it is possible to reduce the maximum delay time by reducing the number of transmit antennas used for transmission instead of setting the inequality (n-1) T &lt;1 / Fc.

As described above, in response to determining whether the transmission signals are subject to frequency diversification transmission or multi-user diversification transmission (i.e. (n-1) T&gt; 1 / Fc or (1-n) T &lt;1 / Fc), it is possible to produce frequency diversification effect or effect

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EP 2 280 495 B1 to diversify many users without being affected by the conditions of the propagation paths.

[0031] As shown in FIG. 16A, with respect to the first user who performs communication via the communication slot s1, which is formed by joining multiple successive fragments in the frequency direction and a user who has assigned discontinuous fragments such as the ninth user who has assigned communication slots s₁₃, p₁₆, p₂₀ and p₂₃, BW bandwidth (i.e. BW = 5F for the first user, and BW = 3F for the ninth user) of the communication slot immediately assigned to the user determines the basis for realizing the effect of frequency diversification; hence, by setting the maximum delay time to (n-1) T&gt; 1 / BW, it is possible to create a frequency diversification effect.

For example, the delay time T is set such that the maximum delay time (n-1) T between the transmitting antennas is in the range (n-1) T&gt; 1 / BW when the communication signal indicates the frequency diversification effect, while the delay time T is set so that the maximum delay time (n-1) T between the transmitting antennas is in the range (n-1) T &lt;1 / F_c. Although no illustration is provided when a subcarrier partially contained in many fragments is assigned to a certain user, the BW bandwidth of the user-assigned communication slot represents the frequency difference between subcarriers that deviate at most within subcarriers immediately assigned to the user.

Determining whether signals are subject to frequency diversification or multi-user diversification transmissions can be changed based on the types of transmit signals (e.g. pilot signals, control signals, broadcast / group transmission signals, etc.), the movement speeds of wireless receiving devices (where frequency diversification is selected for high movement speeds and the diversification of many users is chosen for low movement speeds), etc.

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[0032] FIG. 6A to 6C are explanatory drawings for a situation in which the same signal having no delay time is transmitted via multiple antennas of the wireless transmission device 8. It is assumed that as shown in FIG. 6A, the wireless transmitting device 8 is equipped with a plurality of (three) transmitting antennas that are arranged in parallel and which do not have horizontal directionality. As a result of the e11 and e12 leafs indicated by the ellipses shown in FIG. 6A, there is a direction setting up a wireless receiving device 9 that receives receiving signals with a high reception level in all frequency bands (see FIG. 6B) and a direction setting up a wireless receiving device 10 which receives reception signals with a low reception level in relation to all frequency bands (see FIG. 6C).

[0033] FIG. 7A to 7C are explanatory drawings in which the same signal is applied with correspondingly different delay times and is then transmitted by multiple transmitting antennas of the wireless transmitting device 8. It is assumed that the wireless transmitting device 8 is equipped with multiple (three) transmitting antennas not having directionality, which are arranged in parallel. As a result of the e21 to e26 leaflets in narrow bands, there appears a frequency band providing a high level of reception and a frequency band ensuring a low level of reception within the reception signals, while the average level of reception is kept essentially constant regardless of directions; hence, it is possible to provide substantially the same quality with respect to both reception levels of the wireless receiving device 9 (see FIG. 7B) and the receiving level of the wireless receiving device 10 (see FIG. 7C). Thus, the method in which signals are applied with different delay times and are then transmitted via the transmitting antennas of the wireless transmitting device 8, compensates for the disadvantages of the methods which is described with reference to FIGs. 6A to 6C and in which the same signal is transmitted via multiple transmit antennas.

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EP 2 280 495 B1 (Second Embodiment) [0034] A second embodiment of the present invention will be described with respect to the structure of a wireless transmission device. Similar to the wireless transmission device 1 of the first embodiment (see FIG. 1), the wireless transmission device of the present embodiment has a plurality of transmission antennas.

The wireless transmitting device described below is a wireless transmitting device in which different delay times are input into transmission antennas for transmitting signals in which delay times are entered in time regions.

Signals with different delay times introduced in connection with the transmit antennas are described in the present embodiment in such a way that a signal which is delayed by T with respect to the transmit signal currently transmitted from the first transmit antenna is transmitted via the second transmit antenna, and similarly, the nth transmit antenna transmits a signal delayed by (n-1) T.

[0035] FIG. 8 is a block diagram showing the configuration of the physical layer of the wireless transmission device of the present embodiment. The physical layer represents part of the configuration of the wireless transmission device, in particular, which receives transmission signals that performs signal processing into a form suitable for wireless transmission, and which transmits signals to a wireless frequency converter to convert frequency into wireless frequencies.

As shown in FIG. 8, the physical layer includes user-dependent signal processors 11a and 11b and antenna-dependent signal processors 12-1, 12-2 and 12-3. The user-dependent signal processor 11a (similar to the user-dependent signal processor 11b) performs signal processing on signals to be sent to a wireless receiving device used by each

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EP 2 280 495 B1. The antenna dependent signal processor 12-1 (similar to the antenna dependent signal processor 12-2 and 12-3) performs signal processing for each transmitting antenna.

[0036] The user-dependent signal processor 11a includes an error correction coding section 13, modulator 14, subcarrier assignment section 15, section 16 (IFFT) (Inverse Fast Fourier Transform), parallel-serial processing section 17, GI input interval 18 Guard Interval), and sections 19-1, 19-2 and 19-3 for entering the delay.

The error correction coding section 13 performs the error correction coding on the transmission signals. Modulator 14 performs modulation processing such as QPSK (Quadrature Phase Shift Keying) and 16QAM (Quadrature Amplitude Modulation) on the output of Section 13 error correction coding.

[0037] The subcarrier assignment section 15 assigns the modulator 14 output signal to the respective subcarriers based on the subcarrier assignment information indicated by the higher order layer. Section 16 IFFT performs frequency-time processing on the output signal of section 15 subcarrier assignment.

The parallel-serial processing section 17 performs parallel-serial processing on the output of the IFFT section 16. The GI input section 18 introduces protective gaps into the output signal of the parallel-serial processing section 17. The delay introduction section 19-1 introduces various delays into the output signal of the GI insertion section 18 in combination with transmit antennas. [0038] The output signals of the 19-1 to 19-3 delay input section are provided to the antenna-dependent signal processors 121, 12-2 and 12-3, respectively. The 19-1 to 19-3 delay input sections provide different delays (e.g., 0, S, and 2S). Here S = T / (sample time). Sample time represents the minimum time interval between digital signals that

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EP 2 280 495 B1 are processed in GI insertion section 18, delay input sections 19-1 to 19-3, and mixing section 20.

Thus, entering a delay value of S samples in sections 19-1 to 19-3 of entering the delay indicates that the delay time T is entered at the output terminal of the D / A converter 22. The user-dependent signal processor 11a is used to some extent; in other words, it is used in either a frequency diversification region or a multi-user diversification region; hence, it receives a communication signal (frequency difference / multiple user communication signal) directing the use of either the frequency diversification region or the multiple user diversification region from the higher order layer controlling the physical layer. The user-dependent signal processor 11a selectively uses either the frequency diversification region or the multi-user diversification region based on the communication signal, thereby operating to change the delay time T. The user-dependent signal processor 11b has a structure similar to the user-dependent signal processor 11a, but it differs from it in terms of its user.

[0039] The antenna dependent signal processor 12-1 includes a mixing section 20, a filter 21 and a C / A (Digital / Analog) converter 22.

The mixing section 20 adds and mixes signals that are output to the antenna dependent signal processor 12-1 from the user dependent signal processors 11a and 11b. Filter 21 extracts signals only from a predetermined band from the output signal of the mixing section. The C / A converter 22 performs digital to analog conversion on the output signal of the filter 21.

Both antenna dependent signal processors 12-2 and 12-3 have similar structures to the antenna dependent signal processor 12-1. The output signal of the antenna dependent signal processor 12-1 is transmitted to a wireless frequency converter (not shown) for performing frequency conversion on frequency

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EP 2 280 495 B1 wireless from which it is provided to many (three) transmit antennas, thereby transmitting wireless signals.

(Third Embodiment) [0040] A third embodiment of the present invention will be described with respect to another structure of a wireless transmission device. The wireless transmitting device of the present embodiment is a wireless transmitting device which introduces different delay times into the transmission antennas so as to transmit signals in which the delay times are applied in relation to the time regions.

The wireless transmission device supports signals that are used with protective intervals for symbols (valid symbol spacing) of transmission signals. Signals applied with different delay times for the transmitting antennas are focused on predetermined portions (valid symbol spacing) of the transmitting signals that are currently transmitted via the first transmitting antenna outside the guard intervals; hence, only valid symbol intervals are delayed by T and are then transmitted via a second transmit antenna; similarly, only valid symbol intervals are delayed by (n-1) T and are then transmitted via the nth transmit antenna.

[0041] Thus, the transmit antennas transmit signals that have introduced guard intervals according to valid symbol intervals; hence, unlike the second embodiment, there is no deviation in the symbol's time synchronization in the transmission antennas. Entering the delay time described above is referred to in the following description as "entering the circular delay". By means of processing to introduce circular delay, delay wave protection is advantageous compared to the second embodiment which describes that delay times are entered into the transmission antennas.

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[0042] FIGS. 9A and 9B show examples of signals that are produced by introducing circular delays in the transmitting signals in the present embodiment. FIG. 9A shows the signal transmitted via the first antenna, and FIG. 9B shows the signal transmitted via the second antenna. FIG. 9A and 9B show that the valid symbol spacing corresponds to four samples and the protective distance corresponds to one sample in which, with respect to the valid symbol spacing, one sample is delayed in the second antenna compared to the first antenna. Symbol units do not have any symbol time synchronization deviation with respect to the first antenna and the second antenna; hence, even when a circular delay is introduced into it, it is confirmed that the protective distance effect is maintained to intensify the action against interference in adjacent symbols.

[0043] FIG. 10 is a block diagram showing the configuration of the physical layer of a wireless transmission device according to the present embodiment. As shown in the figure, the physical layer includes user-dependent signal processors 111a and 111b and antenna-dependent signal processors 112-1, 112-2 and 112-3.

The user-dependent signal processor 111a (similar to the user-dependent signal processor 111b) performs signal processing in connection with the wireless transmission device used by each user. Antenna dependent signal processor 112-1 (similar to antenna dependent signal processors 112-2 and 112-3) performs overweighting of signals in relation to the intended transmitting antenna.

The structure of the user-dependent signal processor 111a is substantially identical to the structure of the user-dependent signal processor 11a (FIG. 8) described in the second embodiment, while the difference between them lies in the fact that the GI insertion section 18 is not provided and instead of the section from 19-1 to 19-3 input delay, circular input delay sections 119-1 to 119-3 are provided.

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EP 2 280 495 B1

User-dependent signal processor 111a shares the same functions as section 13 of error correction coding, modulator 14, section 15 of subcarrier assignment, section 16 of IFFT, and section 17 of parallel-serial processing included in the second embodiment (see FIG. 8); hence, they are designated by the same reference signs and their description will be omitted.

[0044] The circular delay input section 119-1 introduces various circular delay into the output signal from the parallel-serial processing section 17 in combination with transmit antennas. The output signals from the 119-1 to 119-3 circular input delay section are provided to the antenna-dependent signal processors 112-1, 112-2 and 112-3. In addition, circular delay delay sections 119-1 to 119-3 provide different delays (e.g., 0, S, and 2S). Where, S = T / (sample time).

The user-dependent signal processor 111a is used to some extent. Because it is used in either the frequency diversification region or the multi-user diversification region, it receives a communication signal directing the use of either the frequency diversification region or the multi-user diversification region via higher-order physical layer control. The user-dependent signal processor 111a selectively uses either the frequency diversification region or the multiple user diversification region based on the communication signal, thereby operating to change the delay time T.

The user-dependent signal processor 111b has a similar structure as the user-dependent signal processor 111a, but differs from it in terms of the user.

[0045] FIG. 11 is an illustration explaining the circular delay introduction section 119-1, which is described as an example of the present embodiment. The circular delay input section 119-1 is equipped with memory 110. To enter a circular delay with the size of k samples, data D11 is sequentially entered from address k + 1 to address n of memory 110 (this

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EP 2 280 495 B1 is entered 1, 2, 3, ..., (nk)); then the D11 data sequence is entered into address 1 (i.e., (nk-4-1), (n-k + 2), (nk + 3), ..., n), thus entering n data samples D11. Then, sequentially deriving from address 1 of memory 110, it is possible to derive D12 data, which is created by entering a circular delay of k samples for n D11 data samples (i.e., (n-k + 1), (nk + 2) , (n-k + 3), ..., n, 1,2, ..., (nk)).

FIG. 9A shows an example of a signal that is created by entering a circular delay of zero sample size for four sample size data, and FIG. 9B shows an example of a signal that is created by providing a circular delay of one sample size.

[0046] The structure of the antenna dependent signal processor 112-1 (FIG. 10) is substantially identical to the structure of the antenna dependent signal processor 12-1 (FIG. 8) described in the second embodiment in which the difference between them is that section 18 of the GI insertion is provided.

The functions of the mixing section 20, GI input section 1, filter 21 and D / A converter 22 contained in the antenna dependent signal processor 112-1 are identical to those included in the second embodiment (FIG. 8); hence, they are designated by the same reference signs and their description will be omitted.

Both user-dependent 112-2 and 112-3 signal processors have a structure similar to the antenna-dependent structure of the 112-1 signal processor. The output signals of the antenna dependent signal processors 1121, 112-2 and 112-3 are provided to a wireless frequency converter (not shown) to perform frequency conversion to wireless frequencies from which they are supplied to many (three) transmit antennas, thereby transmitting wireless signals.

(Fourth embodiment)

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[0047] A fourth embodiment of the present invention will be described with respect to the structure of the next wireless transmission device. The wireless transmission device according to the present embodiment is a wireless transmission device in which different delay times are introduced into the transmission antennas so as to transmit signals, the delay times being entered with respect to the frequency region.

The present embodiment deals with signals that are used with guard intervals with respect to symbols (valid symbol intervals) of transmission signals, wherein, similar to the wireless transmission device of the third embodiment (FIG. 10), it includes circular delays.

[0048] FIG. 12 is a block diagram showing the configuration of the physical layer of the wireless transmission device of the present embodiment. As shown in the figure, the physical layer includes user dependent signal processors 211a and 211b, subcarrier assignment section 215, and antenna dependent signal processors 212-1, 212-2 and 212-3.

The user-dependent signal processor 211a (similar to the user-dependent signal processor 211b) performs signal processing with respect to the wireless transmission device used by each user. The subcarrier assignment section 215 assigns the user-dependent signal processor output signal 211a to each subcarrier. Antenna dependent signal processor 232-1 (similar to antenna dependent signal processors 212-2 and 212-3) performs signal processing with respect to the recommended antenna.

[0049] Each of the user-dependent signal processors 211a and 211b includes an error correction coding section 13 and a modulator 14. The functions of the error correction coding section 13 and the modulator 14 are substantially identical to those described in the second embodiment

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EP 2 280 495 B1 (FIG. 8); hence, they are marked with the same reference signs, and their description will be omitted.

The output signals of the user dependent signal processors 211a and 211b are assigned to respective subcarriers in section 215 of the subcarrier assignment based on the subcarrier assignment information indicated by the higher order layer; then they are delivered to antenna dependent signal processors 212-1, 212-2 and 212-3.

[0050] Antenna-dependent signal processor 212-1 includes phase rotation section 219, IFFT section 16, parallel-serial processing section 17, GI input section 18, filter 21 and C / A converter 22. Functions of IFFT section 16, section 17 processing parallel-serial, GI input section 18, filter 21, and D / A converter 22 are identical to the functions of the second embodiment (FIG. 8); hence, they are marked with the same reference signs, and their description will be omitted.

The phase rotation section 219 rotates the output signal of section 215 of the subcarrier assignment by phase 0_m for each subcarrier, the oasis then outputs it to section 16 of the IFFT. Both antenna-dependent signal processors 212-2 and 213 have a structure similar to the structure of the user-dependent signal processor 212-1.

[0051] The output signals of the antenna dependent signal processors 212-1, 212-2 and 212-3 are provided to a wireless frequency converter (not shown) to perform frequency conversion to wireless frequencies from which they are provided to a plurality of transmit antennas, including thus outputting wireless signals.

In this embodiment, the rotation of phase 0_m in section 219 phase rotation is set to 0_m= 2NF_m'(N-1) T. Here, f_m is the frequency difference between the 0th subcarrier and the mth subcarrier, which is defined as fm = m / T, so that (n-1) T represents the time of the circular delay on the nth antenna with respect to the first antenna. Ts represents the time of valid symbol for an OFDM symbol.

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[0052] The delay input section 220 consists of phase rotation section 219 and IFFT section 16. The phase rotation used by the phase rotation section 219 is subjected to frequency-time processing in section 16 of the IFFT so that it is considered as a time delay at the output of section 16 of the IFFT.

The user-dependent signal processor 211a is utilized in a portion that is used either in the frequency diversification region or in the multi-user diversification region in which it receives a communication signal indicating whether to use the frequency diversification region or the multi-user diversification region of the higher-order layer physical. Based on the communication signal, the user-dependent signal, the processor 211a selectively uses the frequency diversification region or the multi-user diversification region, thereby operating to change the delay time T. [0053] The wireless transmitting devices of the second to fourth embodiments are each provided with a delay input section for delaying the transmission signals provided to n (n is an integer greater than or equal to two) of the broadcast antennas for a maximum delay time (n-1) T according to with a delay time T matched to the communication signal indicating whether the transmission signals are subject to frequency diversification transmission or multiple diversification transmission users.

Thus, by appropriately setting the delay time T based on determining whether transmission signals are subjected to frequency diversification transmission or multi-user diversification transmission, it is possible to create a frequency diversification effect and a multi-user diversification effect without being affected by propagation path conditions.

(Fifth Embodiment) [0054] A fifth embodiment of the present invention will be described with respect to the structure of another wireless transmission device.

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EP 2 280 495 B1

The wireless transmitting device of the present embodiment is a wireless transmitting device that introduces different delay times into signals that are then transmitted via transmit antennas in a frequency diversification region when using appropriate weights for the transmit antennas so as to perform directional control in the diversification region many users wherein delay times are used and directional control is performed in the frequency region.

The present examples support signals that are generated by introducing guard intervals with transmission signals with respect to symbols (valid symbol intervals), where, like the third and fourth embodiments, it introduces circular delays into the signals.

[0055] FIG. 13 is a block diagram showing the configuration of the physical layer of the wireless transmission device of the present embodiment. As shown in the figure, the physical layer includes user dependent signal processors 211a and 211b, subcarrier assignment section 215, weight calculation section 310, and antenna dependent signal processors 312-1, 312-2 and 312-3. The structures of the user dependent signal processor 211a and the subcarrier assignment section 215 are similar to the structures of the fourth embodiment (FIG 12); hence, they are marked with the same reference signs, and their description will be omitted.

[0056] The antenna dependent signal processor 312-1 (similar to the antenna dependent signal processors 312-2 and 312-3) performs signal processing with respect to the recommended transmit antennas. The antenna-dependent signal processor 312-1 includes a weight multiplication section 319, IFFT section 16, parallel-serial processing section 17, GI input section 18, filter 21, and C / A 22 converter. The functions of IFF section 16, parallel-serial processing section 17, GI input section 18, filter 21, and C / A 22 converter are identical to those of the first example

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EP 2 280 495 B1; hence, they are marked with the same reference signs, and their description will be omitted.

[0057] Section 319 weight multiplication performs weight multiplication on the output signal from subcarrier assignment section 215 with respect to subcarriers, and outputs the results to section 16 IFFT. Both antenna dependent signal processors 312-2 and 312-3 have a structure similar to the antenna dependent signal processor 312-1.

The output signals of the antenna dependent signal processors 312-1, 312-2 and 312-3 are supplied to a wireless frequency converter (not shown) for performing frequency conversion to wireless frequencies, from which the results are delivered to the transmitting antennas, thus outputting wirelessly signals.

[0058] The specified subcarrier is used to some extent. That is, it is used either in the frequency diversification region or in the multi-user diversification region. Section 319 of weight multiplication is informed about whether to use either the frequency diversification region or the multi-user diversification region of the higher-order layer controlling the physical layer, based on what phase rotation 0_m is introduced to introduce different delay times to antennas in the frequency diversification region, while multiplication using the weight in m is performed to control directionality in the multi-user diversification region.

[0059] The delay input and directivity control section 320 consists of weight multiplication section 319 and IFFT section 16. When phase rotation is introduced through weight multiplication section 319, it is considered as the exit time of section 16 IFFT because section 16 IFFT performs frequency-time processing. On the other hand, when the weight multiplication section carries out the multiplication using the weights in_m, section 16 IFFT performs processing

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Frequency-time so that the output signal from the IFFT section 16 output from the transmit antenna is subjected to directional control.

[0060] When the weight multiplication section 319 rotates the phase by 0_m, similar to the fourth embodiment, it sets 0_m= 2NF_m'(N-1) T. Here f_m is the frequency difference between the 0th subcarrier and the mth subcarrier, with fm = m / Ts; and (n-1) T represents the circular delay time on the nth antenna with respect to the first antenna. Ts represents the time of valid symbol for an OFDM symbol.

In order to carry out reproduction using the weight in_m, the following weight is adjusted to perform directional control. Assuming a linear array of n antennas whose distance is equal to half the carrier frequency wavelength, the weight Wm is calculated according to the following equation (1):

[0061] [Equation 1]

<img file="PL2280495T3_D0001.tif" />

[0062] Weight w_m represents the weight vector used in section 319 of weight multiplication, in which, in equation (1), the first to last term describe the weights used in the first to the nth antenna.

In equation (1) expressing the weight of w_m, n is the number of antennas, in this embodiment, n = 3; 0 is the direction in which the main stream is directed; ak is the ratio between the frequency used for transmission and the frequency which is measured based on 0.

With respect to the main direction 0 of the stream, the measured value generated by the wireless transmitting device or the terminal of the counter 55 / 51P29970EN00

A communicator is provided to the weight calculation section 310 in which it is used to calculate the weight in_m. Equation (1) shows an example of calculation for the weight in m, which can be calculated by another method. Calculation methods including θ and w_m are described in the "Technical Report RCS2004-229" (published by the Corporate Institute of Electronic Information and Telecommunication in November, 2004) and similar documents.

[0063] The delay input and directivity control section 320 introduces delays with a maximum delay time (n-1) T or less between the transmit antennas when the communication signal indicates frequency diversification, while it performs the multiplication to produce the weight in m so as to perform control directionality when the communication signal indicates the diversification of many users.

As described in the first embodiment, the delay input and directivity control section 320 sets the delay time T such that the maximum delay time (n-1) T between transmit antennas is in the range (n-1) T&gt; 1 / Fc when the communication signal indicates frequency diversification.

As described in the first embodiment, the delay input and directivity control section 320 sets the delay time T such that the maximum delay time (n-1) T is in the range (n-1) T&gt; 1 / BW when the communication signal indicates frequency diversification .

[0064] The above-mentioned description informs that the section 319 of the weight multiplication of the delay input and directional control section is instructed by the higher order layer controlling the physical layer to use either the frequency diversification region or the multi-user diversification region based on which performs phase rotation θ_ηso as to introduce different delay times for the antennas in the frequency diversification region while it performs the multiplication to produce the weight in m so as to carry out directional control in the multi-user diversification region; however, it is possible to use another way of using both phase rotation θ_η and weight

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In m in a multi-user diversification region in such a way that, as described in the fourth embodiment, phase 0 rotation_m is provided for both the frequency diversification region and the multi-user diversification region before producing the main stream kierunku direction, and then the directional control is performed using the weight in m after the main stream direction θ is generated in the multi-user diversification region. Similar to the fourth embodiment, the delay time T varies with θ_η in accordance with the region of frequency diversification and the region of diversification of many users. Thus, in the stage prior to creating the main stream direction θ, it is possible to produce the same multi-user diversification effect as in the fourth embodiment, while after creating the main stream direction θ, it is expected that a larger multi-user diversification effect will be created by accurately performing directionality control using weight in m. In addition, by using the physical layer configuration of the wireless transmission device shown in FIG 13 rather than the fourth embodiment, it is possible to implement improved characteristics as a result of directional control by slightly increasing the circuit structure.

[0065] As described above, the delay input and directivity control section 320 introduces delays with a maximum delay time (n-1) T or less between transmit antennas when the communication signal indicates frequency diversification while it provides a delay with maximum delay time (n- 1) T or less between the transmitting antennas, or it performs the multiplication to produce the weight in m, to perform directionality control when the communication signal indicates the diversification of multiple users, [0066] The wireless transmission device performing the above-mentioned processing has the structure shown in FIG. 13, wherein, when the communication signal indicates multi-user diversification, the delay input and directivity control section introduces

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Or delay with a maximum delay time (n-1) T or less between the transmitting antennas, or it multiplies to produce the weight in m so as to perform directional control. [0067] As described in the first embodiment, the delay input and directivity control section sets the delay time T such that the maximum delay time (n-1) T between transmit antennas is in the range (n-1) T&gt; 1 / Fc when the communication signal indicates frequency diversification while it sets the delay time T such that the maximum delay time is in the range (n-1) T &lt;1 / Fc when the communication signal indicates the diversification of many users yes, that the delay is introduced between the transmitting antennas.

As described in the first embodiment, the delay input and directivity control section sets the delay time T such that the maximum delay time (n-1) T between the transmitting antennas is in the range (N-1) T&gt; 1 / BW when the communication signal indicates frequency diversification.

[0068] The above-mentioned second to fifth embodiments are described in relation to the case in which the number of users is two and the number of antennas is three, wherein the number of users and the number of antennas are not necessarily limited to these numbers.

In the aforementioned fourth and fifth embodiments, it is possible to transmit signals that are multiplied using specific scramble codes depending on antennas, sectors, and base stations, to transmit antennas.

(Sixth Embodiment) [0069] This embodiment will be described with reference to various maximum delay times (n-1) T depending on physical channels. The above-mentioned first to fifth embodiments are described assuming that one-to-one communication is carried out with respect to one particular fragment at a given time,

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(N-1) T&gt; 1 / Fc is set to produce a frequency diversification effect, while (n-1) T &lt;1 / Fc is set to produce multi-user diversification effects.

[0070] Normally, in communications other than one-to-one communications, a known signal referred to as pilot channels is transmitted to a wireless transmission device to estimate the propagation path; alternatively, a control channel is used to pass different types of parameters before data communication. The present embodiment will be described with reference to the method of setting the maximum delay time (n-1) T in these physical channels.

[0071] In the UTRA &amp; O UTRAN Development developed in 3GPP (3rd Generation Partnership Project), DCPCH (Downlink Common Pilot Channel) common pilot channels, Downlink Dedicated Pilot Channel (DDPCH) and dedicated download link synchronization channels are provided. DSCH (Downlink Synchronization Channel), DCCCH (Downlink Common Control Channel) downlink Shared Control Channel (DSCSCH) and control / signaling channels (Multicast / Broadcast Channel).

[0072] The common DCPCH pilot channels correspond to the CPICH pilot channels in W-CDMA (Wideband Code Division Multiple Access), which are used to estimate the conditions of the downlink propagation path, cellular search and measurement of propagation path losses in uplink transmission power control in AMCS (Adaptive Modulation and Coding Scheme).

Dedicated DDPCH pilot channels are used to carry out transmissions towards individual mobile stations via transmission antennas such as adaptive antenna arrays, whose propagation (directivity) paths differ from the propagation paths of antennas with shared antennas; alternatively, they can be used to enhance shared DSPCH downlink common pilot channels in conjunction with mobile stations having low reception quality.

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[0073] DSCH download link synchronization channels correspond to SCH synchronization channels in W-CDMA, and they are used for cellular search of mobile stations, wireless signal frames OFDM (Orthogonal Frequency Division Multiplexing) signals, time slots, transmission intervals TTI (Transmission Timing Interval) and OFDM symbol time synchronization. The DCCCH common control channels contain common control information such as broadcast information (corresponding to BCH broadcast channels) corresponding to the primary common control physical PCCPCH channels, the secondary common control physical S -CCPCH channels and the PICH notification indicator channels in W-CDMA, with packet notification indicator information PI (corresponding to PICH notification indicator channels) means the occurrence of packet calls, wherein the packet notification information (corresponding to the PCH notification channels) corresponds to the packet calls, and the downlink access information (corresponding to the FACH downlink access channels).

[0074] DSCSCH shared downlink control signaling channels correspond to HS-DSCH connected to HS-SCCH shared control channels, dedicated DPCCH downlink control channels, AICH acquisition indicators contained in HS-PDSCH high speed shared downlink physical channels in HSPDA (High Speed ​​Downlink Packet Access), however, they are shared by many mobile stations and are used for the transmission of information (modulation methods, distributed coding, etc.) which is required for mobile stations to perform demodulation in relation to HS-DSCH high-speed download link shared information which is required for performing error correction decoding and HARQ processing, and for scheduling information on wireless resources (frequency, time).

[0075] DSDCH downlink shared data channels correspond to HS-DSCH high speed downlink shared channels

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EP 2 280 495 B1 and dedicated DPDCH downlink data channels contained in high speed HS-PDSCH shared HSPDA downlink channels in HSPDA, which are used to transmit the data packet towards higher-order mobile stations.

Group / broadcast channels are used to broadcast information signals.

The abovementioned physical channels W-CDMA and HSDPA are described in the document "Tachikawa Keiji, W-CDMA Mobile Communication Method, ISBN4-6 21-04894-5" and the like.

[0076] FIG. 14 and 15 are tables describing the relationship between the maximum delay time (n-1) T between transmit antennas and the frequency bandwidth Fc of the fragments in combination with the physical channels. As shown in the figures, it is preferred to set (n-1) T &lt;1 / Fc regardless of the frequency diversification region and the multi-user diversification region with respect to common pilot pilot channels, common control channels and dedicated control channels. It is preferable to set (n-1) T&gt; 1 / Fc regardless of the frequency diversification region and the multiple user diversification region with respect to downlink synchronization channels.

With respect to dedicated pilot channels, it is preferable to set (n-1) T&gt; 1 / Fc in the frequency diversification region and set (n1) T &lt;1 / Fc in the multi-user diversification region. Dedicated pilot signals are assumed to be transmitted via transmit antennas, with the delay introduction section for delaying the transmit signals supplied to n transmit antennas with a maximum delay time (n-1) T or less sets the delay time T such that the maximum delay time (n-1) T is in the range (n-1) T&gt; 1 / Fc when the communication signal, which indicates whether fragments containing dedicated pilot channels are subjected to frequency diversification transmission or multi-user diversification transmission, indicates frequency diversity while it sets the delay time T so that

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Perform directional control using the weights derived from the weight calculation section or to specify the maximum delay time (n-1) T as (n-1) T &lt;1 / Fc when the communication signal indicates the diversification of multiple users. Group / broadcast channels are used only in the frequency diversification region; hence, setting (n-1) T&gt; 1 / Fc is preferred.

[0077] The reasons why the above-mentioned settings are carried out are that the common pilot channels are used to notify the signal intensities experienced by the terminals, hence it is undesirable for the delay time to vary with respect to the fragments, whereas it is necessary to the wireless transmission device knew the signal strength in relation to the fragments in the case of (n-1) T &lt;1 / Fc in order to diversify many users, hence it is preferred to set (n-1) T &lt;1 / Fc in such a way that the maximum delay time does not change with respect to the fragments.

Dedicated pilot channels are used to calculate the estimated propagation path values ​​used to demodulate data signals. Thus, it is preferable to perform communication by setting (n-1) T&gt; 1 / Fc in the frequency diversification region and setting (n-1) T &lt;1 / Fc in the multi-user diversification region. [0078] Downlink synchronization channels are used for frame synchronization, where estimation of propagation paths is not necessary, and it is preferable to secure accurate reception in the event of low reception power; hence, it is preferable to set (n-1) T&gt; 1 / Fc to produce a frequency diversification effect. In particular, it is possible that the same signal is transmitted using the same time and the same frequency via downlink synchronization channels over multiple sectors and multiple antennas contained in a single base station. Thus, the signals are used with different delays with respect to the antennas and are transmitted via multiple sectors and multiple antennas contained in a single base station via downlink synchronization channels;

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Therefore, it is expected that a high frequency diversification effect that is higher than the frequency diversification effect of another physical channel will be created.

[0079] It is assumed that the common control channels and the dedicated control channels use the estimated propagation path values ​​that are generated by the common pilot channels; hence, it is preferred that they are set to a maximum delay time which is identical to that for common pilot channels, and are subjected to transmission.

However, it is preferable to secure accurate reception on common control channels and dedicated control channels in the event of low reception power; hence, it is preferable to create a frequency diversification effect, and, above all, to improve the control channel reception performance, when common control channels, dedicated control channels and group / broadcast channels are included in the same fragment, it is preferable to carry out transmission via common channels pilot by setting (n-1) T&gt; 1 / F_c, thereby producing a frequency diversity effect on the control channels.

[0080] When the same fragment is used for the diversification of multiple users, it is necessary to carry out notification of signal intensities occurring in the current transmission matched to the diversification of multiple users (communication with (n-1) T &lt;1 / Fc); hence, it is preferred to perform the transmission by setting (n-1) T &lt;1 / Fc.

For this reason, it is possible to set a relationship between the maximum delay time (n-1) T between the transmitting antennas and the fragment's frequency bandwidth Fc, which is identical to the relationship shown in FIG. 15, for each physical channel.

In order to create a frequency diversification effect, it is preferable to perform communication by setting (n-1) T&gt; 1 / Fc.

[0081] The above-mentioned embodiment is described so that the maximum delay time is in the range (n-1) T &lt;1 / Fc in the multi-user diversification region while the wireless transmitting device

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The embodiment described in the fifth embodiment may use the weight in m, which is produced by the weight calculation section 310, in a multi-user diversification region.

The aforementioned second to fifth embodiments are each described so that a wireless transmission device having n transmit antennas transmits signals with a prescribed recommended delay time for each of n send antennas; however, this structure is not limited. For example, when a wireless transmission device having n transmit antennas chooses to use multi-user diversification, it is possible to transmit signals with the recommended delay time T 'entered for each of the transmit antennas (where j is an integer, 1 &lt;j &lt;n) within n transmitting antennas. In the above-mentioned structure compared to the structure in which the signals are transmitted using all n transmit antennas, the maximum delay time (j-1) T 'introduced to the signals transmitted via the j transmit antennas is reduced so as to further reduce the changes propagation paths; hence, it is possible to create a good multi-user diversification effect. In particular, in the case of j = 1, it is possible to reduce the circumference of the delay section circuit.

The present embodiment is described with the assumption that the maximum delay time is set to (n-1) T&gt; 1 / Fc to produce a frequency diversification effect, while, as described in the first embodiment, when the transmission is carried out using a physical channel, which has assigned fragments that fall in many frequency directions, BW bandwidth assigned to the physical channel forms the basis for creating a frequency diversification effect; hence, it is possible to create a frequency diversification effect by setting the maximum delay time to (n-1) T&gt; 1BW.

[0083] By using a wireless transmission device according to the above-mentioned embodiments of the present invention, which

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EP 2 280 495 B1 selects the use of either frequency diversification or the diversification of multiple users in the transmission of signals from n transmit antennas so as to vary the delay times introduced into signals transmitted via n transmit antennas based on the result of the selection; hence, it is possible to create a frequency diversification effect or a multi-user diversification effect without being affected by propagation path conditions.

[0084] In the above-mentioned embodiments, programs performing the functions of error correction coding section 13, modulator 14, subcarrier assignment sections 15 and 215, IFFT section 16, parallel-serial processing section 17, GI input section 18, sections 19-1 for 19-3 input delay, sections 119-1 to 119-3 input circular delay, mixing section 20, filter 21, C / A 22 converter, phase rotation section 219, weight calculation section 310 and weight multiplication section 319 shown in FIG. 8, 10, 12 and 13 are stored on a computer-readable storage medium such that programs stored on the storage medium are loaded into the computer system and are then executed to control the wireless transmission device. Here, the computer system includes OS and hardware such as peripherals.

[0085] Computer-readable recording media are referred to as flexible disks, magneto-optical disks, ROMs, portable media such as CDROMs and storage devices such as hard disks contained in computer systems. In addition, the computer-readable storage medium includes media for dynamic storage of programs in short periods of time, such as communication lines such as the Internet, networks and telephone lines used to transmit programs, as well as volatile memories for storing programs during the recommended period of time, which are included in computer system for server and client. The aforesaid programs are designed to implement parts of the above mentioned functions; alternatively, they are designed to be implemented

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EP 2 280 495 B1 of the above-mentioned functions via a connection to programs that are previously stored in a computer system.

[0086] The invention is described in detail by way of embodiments with reference to drawings in which its exact structure is not necessarily limited to the embodiments; hence, it includes designs that do not depart from the spirit of the present invention.

INDUSTRIAL APPLICABILITY [0087] The present invention is applicable to wireless transmission devices and wireless transmission methods that transmit signals to wireless reception devices using multiple transmission antennas, wherein delay times are appropriately set based on determining whether the transmission signals are transmitted. frequency diversification or multi-user diversification transmission; hence, it is possible to create frequency diversification effects and multi user diversification effects without being affected by propagation path conditions.