Transmission control method

TECHNICAL FIELD [0001] The present invention relates to wireless transmission devices and methods for wireless transmission, in particular to wireless broadcast devices and wireless transmission methods for transmitting signals to wireless receiving devices using a plurality of transmission antennas.

The present application claims the priority of Japanese Patent Application No. 2005-253194 filed in Japan on September 1, 2005 and Japanese Patent Application No. 2005-367860 filed in Japan on December 21, 2005, the contents of which are incorporated herein by reference.

BACKGROUND [0002] Recently, methods have been provided, mainly adapted for multi-carrier transmission systems in which a plurality of blocks are distributed along frequency and time axis and which perform scheduling of signals transmitted to users from wireless broadcast devices in block units. Here, regions that are secured for users to communicate and which are defined along the frequency and time axis are called assignment slots, and the blocks serving as the basis for determining assignment slots are referred to as fragments.

[0003] In the above, there are provided methods which, for transmission of broadcast signals, group transmission signals and control signals, blocks whose ranges are extended in the direction of the frequency axis are assigned to produce frequency diversity effects, thus reducing errors regardless of the low reception power. In addition, methods are provided for which purpose

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Transmitting unit signals (unicast) in one-to-one communication between wireless transmitting devices and wireless receiving devices, blocks whose ranges are reduced in the direction of the frequency axis are assigned so as to generate multiuser diversity effects, thus improving the reception power in wireless receiving devices.

[0004] FIG. 16A and 16B show dependencies relating to signals transmitted from a wireless transmission device to a wireless reception device with respect to time (horizontal axis) and frequency (vertical axis). In FIG. 16A, the horizontal axis represents the time and the vertical axis represents the frequency. Transmission times from t1 to t3 are set in the timeline. Herein, the same length of time is set for times t1 to t3, respectively. The transmission frequencies f1 to f5 are set on the frequency axis. In this same frequency range FC is set for frequencies f1 to f5. Regarding transmission times t1 to t3 and transmission frequencies f1 to f5, fifteen fragments K1 to K15 are arranged as shown in FIG. 16A.

[0005] In addition, five fragments from K1 to K5 are connected as shown in FIG. 16B and are then evenly distributed to up to six slots along the time axis, thereby juxtaposing communication slots s1 to s6 each having a time length of t1 / 6 and a frequency range of 5f1. Communication slots s1 and s4 are assigned to the first user; communication slots s2 and s5 are assigned to the second user; and the communication slots s3 and s6 are assigned to the third user. This makes it possible for the first to third user to obtain frequency diversity effects.

[0006] Next, the fragment K10 is assigned to the fourth user as the communication slot s11. Fragments K7, K8 and K9 are combined to form communication slots s8 to s10, each of which has a length of time equal to t2 and a frequency range equal to 3f1 and which are assigned to the fifth user. In addition, the fragment K6 is assigned to the sixth user as the communication slot s7. This makes it possible for

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From the fourth to the sixth user, obtaining the multiuser diversity effects, which makes it possible for the fifth user to obtain the frequency diversity effect.

[0007] Furthermore, the fragment K11 is assigned to the seventh user as the communication slot s12. This makes it possible for the user to achieve the effect of multi-user diversification. In addition, fragments K13 and K15 are assigned to the eighth user as communication slots s19 and s26. This makes it possible for the user to achieve the effect of multi-user diversification.

In addition, the two fragments K12 and K14 are evenly divided into six slits, thus creating gaps from s13 to s18 and s20 to s25. Communication slots s13, s16, s20 and s23 are assigned to the ninth user; communication slots s14, s17, s21 and s24 are assigned to the tenth user; and the communication slots s15, s18, s22 and s25 are assigned to the eleventh user. This makes it possible for the ninth to eleventh user to receive separately the effects of frequency diversity.

Non-patent 1 document: Contribution to 3GPP, R1-050249, "Downlink Multiple Access Scheme for Evolved UTRA", [Acquired on August 17, 2005], Internet (URL: <a href="ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/TSGR1_40bis/Docs/R1-">ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/TSGR1_40bis/Docs/R1-</a>

050249.zip)

Non-patent 2 document: Contribution to 3GPP, R 1-050590, "Physical Channels and Multiplexing in Evolved UTRA Downlink", [Acquired on August 17, 2005], Internet (URL: <a href="ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/R1_Ad_Hocs/LTE_AH_June-">ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/R1_Ad_Hocs/LTE_AH_June-</a>

05 / Docs / R1-050590.zip)

Document by Bauch G. and others: "Orthogonal Frequency Division Multiple Access with Cyclic Delay Diversity", 2004 ITG Workshop on Smart Antennas (Munich, Germany, 18-19 March 2004) reveals that cyclical

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Delay diversification is a simple transmission diversity technique for systems with OFDM encoding with multiple transmitting antennas. Cyclic delay diversification does not require either a stretched guard interval or the modification of a standard OFDM receiver. Bauch et al. Discusses the problem of selecting cyclical delays and proposes a solution that allows the use of full spatial diversity in channels with flat atrophy and frequency-selective channels with an unknown delay spread. As a result, spatial diversification is converted into frequency diversification between neighboring subcarriers. This imposes some restrictions on channel coding and interleaving scheme. In addition, they are directed at the aspects of many users and propose an interleaving and multiple access strategy, which ensures that all users get the maximum possible benefit of diversification using FEC codes with limited constraint length. Performance comparison reveals that spatio-temporal block codes outperform cyclic delay diversification at the cost of greater complexity and less flexibility.

DISCLOSURE OF THE INVENTION

PROBLEMS TO BE SOLVED BY INVENTION [0008] In order to achieve frequency diversity effects in the above-mentioned traditional methods, it is necessary to increase scattering rates or reduce coding rates in the error correction encoding in response to frequency variations of the transfer functions in propagation paths.

[0009] FIG. 17A and 17B and FIG. 18A and 18B are graphs showing delay profiles and transfer functions with respect to signals that are propagated by a plurality of propagation paths having different delay times so as to achieve wireless receiving devices.

[0010] FIG. 17A and 18A show delay profiles representing transmission signals that are propagated by a plurality of propagation paths such that

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A wireless receiving device is achieved with respect to time (horizontal axis) and power (vertical axis). FIG. 17B and 18B show the transfer functions for performing frequency conversion on delay profiles with respect to frequency (horizontal axis) and power (vertical axis).

[0011] FIG. 17A shows the appearance of six delay waves w11 to w16, and FIG. 18A shows the appearance of three delay waves from w21 to w23. They differ from each other by the maximum delay times t1 and t2.

[0012] When the maximum delay time t1 is long as shown in FIG. 17A and 17B, i.e. when relatively fast frequency variations (rapid changes in power in the frequency direction) occur in the transfer function, it is expected that an adequate frequency diversity effect will be produced independent of the low spreading factor and high code rate in the error correction coding. . However, when the maximum delay time t2 is small as shown in FIGs. 18A and 18B, i.e. when there are relatively moderate frequency variations in the transfer function, an adequate frequency diversity effect is not expected when the scattering factor is small and the code rate in the correction coding errors is high; hence,

[0013] D1 and D2 in FIG. 17B and FIG 18B show signals, i.e. data. That is, in FIG. 17B, ​​the spectrum spreading ratio is set to "4" with respect to data D1 and D2, thereby assigning four subcarriers from a11 to a14 to data D1. Similarly, the four subcarriers from a15 to a18 are assigned to data D2. In this case, the transfer function has fast frequency changes; hence, the pickup power of the subcarrier A13 relating to the D1 data drops significantly so that the pickup power of the subcarrier? 16 relating to the D2 data also drops significantly. Thus, there is no failure of reception with respect to data D1 and D2.

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[0014] In FIG. 18B the scattering ratio is set to "8" so as to assign eight subcarriers from a21 to a28 to data D1. In this case, the transfer function has slow frequency variations such that the pickup power of the subcarrier a24 drops significantly, and the pickup power of the subcarriers a23 and a25 decreases to a small extent while the ratio of data scattering is increased compared to the case of FIG. 17B such that there is no reception failure with respect to data D1. The aforementioned values ​​of the scattering ratios are described for simplicity and are not necessarily limited.

[0015] The present invention is considered with reference to the above-mentioned conditions, wherein the object of the invention is to provide a wireless transmission device and a wireless transmission method that can produce an adequate frequency diversity effect without controlling the scattering factor and code rate in the error correction coding on the transmission side wireless.

PROBLEM SOLUTIONS [0016] In accordance with the present invention, a method for controlling a transmission according to claim 1 is provided. Preferred features are set out in claims 2 and 3.

EFFECT OF THE INVENTION With reference to the delay time T suited to a communication signal that indicates either a frequency diversity transmission or a multi-user diversity transmission, the transmission signals delivered to the n transmit antennas are each delayed by a delay time (n-1) T or less.

[0018] Thus, appropriately setting the delay time T based on the condition that the transmission signals are subjected to the transmission of diversification

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It is possible to generate frequency diversity effects and diversity effects of many users without being affected by the conditions of the propagation path.

BRIEF DESCRIPTION OF THE DRAWINGS [0019]

FIG 1 is a schematic view showing that the signals transmitted by the wireless transmission device according to the first embodiment of the present invention are propagated through a plurality of propagation paths so as to achieve a wireless reception device.

FIG. 2A is a graph showing the delay profile applied to signals that are propagated through multiple propagation paths having different delay times so as to achieve a wireless reception device.

FIG. 2B is a graph showing the transfer function that is produced by performing frequency conversion on the delay profile shown in FIG. 2A.

FIG. 3A is a graph showing a further delay profile applied to signals that are propagated by a plurality of propagation paths having different delay times so as to achieve a wireless reception device.

FIG. 3B is a graph showing the transfer function of a wireless receiving device that is produced by performing frequency conversion on the delay profile shown in FIG. 3A.

FIG. 3C is a graph showing the transfer function of another wireless receiving device in another

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A position that is generated by performing frequency conversion on the delay profile shown in FIG. 3A.

FIG. 4A is a graph showing the maximum delay time (n-1) T in the delay profile.

FIG. 4B is a graph showing the relationship between the maximum delay time (n-1) T shown in FIG. 4A and frequency changes.

FIG. 5A is a graph showing the next maximum delay time (n-1) T in the delay profile.

FIG. 5B is a graph showing the relationship between the maximum delay time (n-1) T shown in FIGURE 5A and frequency changes.

FIG. 6A is an illustration showing a wireless transceiver / receiver system in which the same signal lacking time delay is transmitted via a plurality of antennas of a wireless transmission device.

FIG. 6B is a graph showing an example of a reception signal in the system shown in FIG. 6A.

FIG. 6C is a graph showing another example of a reception signal in the system shown in FIG. 6A.

FIG. 7A is an illustration showing a wireless transceiver / receiver system in which the same signal is used with different delay times and is then transmitted via a plurality of transmission antennas of a wireless transmission device.

FIG. 7B is a graph showing an example of a reception signal in the system shown in FIG. 7A.

FIG. 7C is a graph showing another example of a reception signal in the system shown in FIG. 7A.

FIG. 8 is a block diagram showing the configuration of a physical layer of a wireless transmission device according to a second embodiment of the present invention.

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FIG. 9A shows an example of a signal that is generated by applying a circular delay on a transmission signal in accordance with the third embodiment of the present invention.

FIG. 9B shows another example of a signal that is produced by applying a circular delay on a transmission signal in accordance with the third embodiment of the present invention.

FIG. 10 is a block diagram showing the configuration of a physical layer of a wireless transmission device according to the third embodiment of the present invention.

FIG. 11 is an illustration explaining the operation of the section 119-1 of introducing a circular delay in the third embodiment of the present invention.

FIG. 12 is a block diagram showing the configuration of a physical layer of a wireless transmission device according to a fourth embodiment of the present invention.

FIG. 13 is a block diagram showing the configuration of a physical layer of a wireless transmission device according to a fifth embodiment of the present invention.

FIG. 14 is a table showing the relationship between the maximum delay time (n-1) T between the transmit antennas and the bandwidth of the Fc bandwidth with respect to each physical channel. FIG. 15 is a table showing another relationship between the maximum delay time (n-1) T between transmit antennas and the bandwidth of the Fc bandwidth with respect to each physical channel.

FIG. 16A is a graph showing the relationship between signals that are transmitted from a wireless transmission device to a wireless receiving device with respect to time (horizontal axis) and frequency (vertical axis).

FIG. 16B is a graph showing communication slots that are assigned to the time-frequency space shown in FIG 16A.

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FIG. 17A is a graph showing a delay profile adapted to signals that are propagated by multiple propagation paths having different delay times so as to achieve a wireless reception device.

FIG. 17B is a graph showing the transfer function that is produced by performing frequency conversion in the delay profile shown in FIG. 17A.

FIG. 18A is a graph showing a delay profile adapted to signals that are propagated by propagation paths having different delay times so as to achieve a wireless reception device.

FIG. 18B is a graph showing the transfer function that is produced by performing frequency conversion on the delay profile shown in FIG. 18A.

DESCRIPTION OF LAYOUT DECLARATIONS [0020]

<td>1</td><td>wireless transmitting device</td>

<td>2-4</td><td>broadcast antenna</td>

<td>5,6</td><td>inhibitor</td>

<td>7, 8, 9, 10</td><td>wireless receiving device</td>

<td>11a, 11b, 111a,</td><td></td>

<td>111b, 211a, 21b</td><td>user-dependent signal processor</td>

<td>12-1, 12-2, 12-3,</td><td></td>

<td>from 112-1 to 112-3,</td><td></td>

<td>from 212-1 to 212-3,</td><td></td>

<td>from 312-1 to 312-3</td><td>signal processor dependent on the antenna</td>

<td>13</td><td>the error correction coding section</td>

<td>14</td><td>modulator</td>

<td>15, 215</td><td>the subcarrier assignment section</td>

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<td>16</td><td>IFFT section</td>

<td>17</td><td>parallel-serial converter</td>

<td>18</td><td>GI input section</td>

<td>from 19-1 to 19-3</td><td>Delay entry section</td>

<td>from 119-1 to 119-3</td><td>a section for entering circular delay</td>

<td>20</td><td>mixer</td>

<td>21</td><td>filter</td>

<td>22</td><td>D / A converter</td>

<td>110</td><td>memory</td>

<td>219</td><td>Phase rotation section</td>

<td>220</td><td>Delay entry section</td>

<td>310</td><td>the weight calculation section</td>

<td>319</td><td>the section of weighted reproduction</td>

<td>320</td><td>delay entry section</td>

<td></td><td>directional control</td>

and

BEST MODE FOR CARRYING OUT THE INVENTION (First Embodiment of the Invention) [0021] FIG. 1 is a schematic illustration showing that the signals transmitted from the wireless transmission device 1 are propagated by a plurality of propagation paths so as to reach a wireless receiving device 7. The wireless transmission device 1 has a plurality of transmission antennas 2 to 4, which are respectively used with different delay times. 0, T and 2T and from which signals are transmitted. The wireless receiving device 7 receives signals transmitted from the wireless transmission device 1. FIG. 1 shows an example in which the wireless transmission device 1 is equipped with three transmitting antennas from 2 to 4.

[0022] It is assumed that a plurality of transmission antennas is transmit antennas installed in a wireless transmitting device located

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In a cellular network base station in which three types of transmit antennas are provided with respect to different sectors of the same base station and with respect to different base stations. The following description is given in relation to the situation in which they belong, for example, to the same sector, but it is also possible to use a different arrangement. That is, n transmit antennas belong to different sectors, or n transmit antennas belong to different base stations.

In the figure, the delay 5 and 6 introduce a time delay T, through which, as described above, the time delay T is introduced into the transmitting antenna 3, and the time delay 2T is introduced into the transmitting antenna 4.

[0023] FIG. 2A and 2B show a delay profile and a transfer function with respect to signals that are propagated by a plurality of (three) propagation paths having different delay times so that they reach a wireless reception device. FIG. 2A shows a delay profile showing that the transmission signals are propagated by a plurality of propagation paths having different delay times so that they reach the wireless reception device with respect to time (horizontal axis) and power (vertical axis). As shown in FIG. 2A, the delay profile immediately has a maximum delay waveform of 2T + dmax; hence, compared to the structure in which the same signal is transmitted via each transmit antenna, the maximum delay waveform becomes very large. Here,

[0024] FIG. 2B shows a transfer function that is generated by performing frequency conversion on the delay profile of FIG. 2A with respect to frequency (horizontal axis) and power (vertical axis). In the delay profile, increasing the maximum delay time 2T + dmax indicates fast frequency changes of the transfer function. Thus, as shown in FIG. 2B (similar to FIG. 17B), data D1 and D2 are broadcast with a broadcast ratio of "4" and are assigned to subcarriers. favorable

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It is contemplated that the dissipation factor or code rate of the error correction encoding be controlled in response to frequency variations of the transfer function in the wireless transmission device 1 in which the above-mentioned method acknowledges that the delay time 2T is previously validated by the wireless transmission device 1; hence, it is possible to determine the scattering factor or code rate of coding with error correction regardless of the frequency variation of the propagation paths. In order to generate multi-user diversity effects, it is preferred that the maximum delay time 2T + dmax, which immediately appears in the delay profile, is not increased as much. The multi-user diversity effects will be described with reference to FIG. from 3A to 3C.

[0025] FIG. from 3A to 3C show a delay profile and transfer functions with respect to signals that are propagated by a plurality of propagation paths having different delay times so as to achieve a wireless reception device. FIG. 3A shows a delay profile adapted to transmit signals that are propagated by a plurality of (three) propagation paths having different delay times so that they arrive at a wireless transmission device with respect to time (horizontal axis) and power (vertical axis). FIG. 3B shows the transfer function with respect to the wireless receiving device used by the user u1. FIG. 3C shows the transfer function with respect to the wireless receiving device used by the user u2.

[0026] Assuming that the left region is connected to frequency channel b1 and the right channel is connected to frequency channel b2 in FIG. 3B and 3C, the u1 user obtains good quality in the frequency b2 channel, while the u2 user obtains good quality in the b1 frequency channel. Thus, data from D1 to D4 are transmitted to user u1 via frequency channel b2. Data from D1 to D4 are subject to spectrum scattering. Data from

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D1 to D4 are transmitted to user u2 via frequency channel b1. In this case, data from D1 to D4 are subject to spectrum scattering. [0027] As described above, by utilizing the quality difference between frequency channels at some point, it is possible to generate multiuser diversity effects to improve transmission performance for different users who communicate using different frequency channels.

However, when the maximum delay time 2T + dmax is greatly increased, rapid frequency changes occur in the transfer function, thereby reducing the quality differences between the frequency channel b1 and the frequency channel b2.

Thus, in order to generate adequate multiuser diversity effects, it is important to reduce the maximum delay time 2T + dmax as shown in FIG. 3A.

[0028] FIG. 4A and 4B and FIG. 5A and 5B show the relationship between the maximum delay time (n-1) T and the frequency changes. When the time difference of arrival (n-1) T appears between incoming waves w31 and w32 as shown in FIG. 4A, the transfer function of this propagation path is shown in FIG. 4B. That is, the frequency difference between power amplitude declines (vertical axis) is defined as F-1 / (n-1) T.

When multiple delay waves from w41 to w42 appear as shown in FIG. 5A, the time difference of arrival (n-1) T appears between the first arrival wave w41 and the last arrival wave w42, so that the frequency difference between power amplitude declines (vertical axis) is defined as F = 1 / (n-1) T as shown in FIG. 5B.

[0029] Accordingly, the frequency diversity effect differs from the multi-user diversity effect in terms of frequency variations in their respective transfer functions; hence, in order to produce a frequency diversity effect, the maximum delay time (n-1) T is set as (n-1) T&gt; 1 / Fc where Fc is the frequency bandwidth of the fragment, which is the basic region protected by the user for communication and specified in

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With respect to the frequency axis and timeline, thereby creating an environment that easily generates the frequency diversity effect.

[0030] On the other hand, in order to create a multi-user diversity effect, the maximum delay time (n-1) T is set as (n-1) T &lt;1 / Fc, where Fc is the bandwidth of the fragment, thereby creating an environment easily generating the effect of multi-user diversification. In the following description, the inequality (n-1) T &lt;1 / Fc includes (n-1) T = 0. Hereinafter, the delay times introduced into the transmit antennas are each represented as (n-1) multiples of T where T is assumed to be constant while it is possible to change T depending on each of the transmission antennas. In order to create a multi-user diversity effect, it is possible to reduce the maximum delay time by reducing the number of transmit antennas used for transmission instead of setting inequalities (n-1) T &lt;1 / Fc.

As described above, in response to determining if the transmission signals are subject to frequency diversity or multi-user diversity diversification transmission (i.e. (n-1) T&gt; 1 / Fc or (1-n) T &lt;1 / Fc), it is possible to generate the effect of frequency diversification or the diversification effect of many users without being affected by the propagation path conditions.

[0031] As shown in FIG. 16A, with respect to a first user who communicates via a communication slot s1 that is formed by combining multiple consecutive portions in the frequency direction and a user who has non-contemporaneous fragments assigned, such as a ninth user who has communication slots s13, s16 assigned, s20 and s23, the bandwidth BW (i.e., BW = 5F for the first user, and BW = 3F for the ninth user) the communication slot immediately assigned to the user determines the basis for implementing the frequency diversity effect; hence, by setting the maximum delay time to (n-1) T&gt; 1 / BW, it is possible to produce a frequency diversity effect.

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For example, the delay time T is set such that the maximum delay time (n-1) T between transmission antennas is in the range (n-1) T&gt; 1 / BW when the communication signal indicates the frequency diversity effect, while the delay time T is set so that the maximum delay time (n-1) T between the transmission antennas is in the range (n-1) T &lt;1 / Fc. Although no illustration is provided when the subcarrier partially included in multiple fragments is assigned to a certain user, the bandwidth BW of the communication slot assigned to the user represents the frequency difference between subcarriers which deviate from each other at most within the subcarriers immediately assigned to the user.

Determining whether signals are subject to frequency diversity transmission or multi-user diversification transmission can be changed based on the types of transmission signals (eg pilot signals, control signals, broadcast / group broadcast signals, etc.), the speed of the wireless receiving devices (where diversification frequency is selected in the case of high speed of movement, and the diversification of many users is selected in the case of low speed of movement), etc.

[0032] FIG. 6A to 6C are explanatory drawings for a situation in which the same signal having no delay time is transmitted via multiple antennas of the wireless transmission device 8. It is assumed that as shown in FIG. 6A, the wireless transmission device 8 is provided with a plurality of (three) transmission antennas that are arranged in parallel and that do not have directionality in the horizontal direction. As a result of the presence of the lobes e11 and e12 indicated by the ellipses shown in FIG. 6A, there is a direction in which the wireless receiving device 9 receives reception signals with a high reception level with respect to all frequency bands (see FIG 6B) and the direction of the wireless receiver device 10,

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[0033] FIG. 7A to 7C are explanatory drawings in which the same signal is applied with correspondingly different delay times and is then transmitted over a plurality of transmission antennas of the wireless transmission device 8. It is assumed that the wireless transmission device 8 is equipped with many (three) transmit antennas not having directionality, which are arranged in parallel. As a result of the presence of lobes e21 to e26 in narrow bands, a frequency band appears there providing a high level of reception and a frequency band ensuring a low level of reception within receiving signals, whereas the average reception level is kept constant regardless of the directions; hence, it is possible to provide substantially the same quality with respect to both reception levels of the wireless receiving device 9 (see FIG 7B) and the reception level of the wireless receiving device 10 (see FIG 7C). Thus, the method in which the signals are applied with different delay times and are then transmitted via the transmission antennas of the wireless transmission device 8 compensates for the disadvantages of the method which is described with reference to FIGs. 6A to 6C and wherein the same signal is transmitted via multiple transmit antennas.

(Second Embodiment) [0034] A second embodiment of the present invention will be described with reference to the structure of a wireless transmission device. Similar to the wireless transmission device 1 of the first embodiment (see FIG 1), the wireless transmitting device of the present embodiment has a plurality of transmission antennas.

The wireless transmitting device described below is a wireless transmitting device in which different delay times are input into transmit antennas for transmitting signals in which delay times are input in time regions.

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Signals with different delay times introduced in connection with the transmit antennas are described in the present embodiment in such a way that a signal that is delayed by T relative to the transmission signal currently being transmitted from the first transmission antenna is transmitted via the second transmission antenna, and similarly, the n-th transmitting antenna transmits a signal delayed by (n-1) T.

[0035] FIG. 8 is a block diagram showing the physical layer configuration of the wireless transmission device of this embodiment. The physical layer represents a part of the wireless transmission device configuration, in particular, which receives the transmission signals that performs signal processing into a form suitable for wireless transmission, and which transmits signals to the wireless frequency converter to convert the frequency into wireless frequencies.

As shown in FIG. 8, the physical layer includes user-dependent signal processors 11a and 11b and antenna-dependent signal processors 12-1, 12-2 and 12-3. The user-dependent signal processor 11a (similar to the user-dependent signal processor 11b) performs the signal processing on signals to be transmitted to the wireless receiving device used by each user. The antenna-dependent signal processor 12-1 (similar to the antenna-dependent signal processor 12-2 and 12-3) performs signal processing with respect to each transmit antenna.

[0036] The user-dependent signal processor 11a includes an error correction coding section 13, a modulator 14, a subcarrier assignment section, a 16 (IFFT) section (an Inverse Fast Fourier transform), a parallel serialization section 17, a GI input section 18 (Interval Protective (Guard Interval)), and Sections 19-1, 19-2 and 19-3 entering the delay.

The error correction coding section 13 performs error correction coding on the transmission signals. The modulator 14 performs modulation processing such as QPSK (Squared Keying with Offset

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Phases (Quadrature Phase Shift Keying)) and 16QAM (Kwadraturowa Modulation

Amplitudes (Quadrature Amplitude Modulation)) on the output signal of the error correction coding section.

[0037] The subcarrier assignment section assigns the output of the modulator 14 to the respective subcarriers based on the subcarrier assignment information indicated by the higher order layer. Section 16 of the IFFT performs frequency-time processing on the output signal of the subcarrier assignment section.

Parallel-serial processing section 17 carries out parallel-serial processing on the output signal of the IFFT section 16. The GI input section 18 introduces guard intervals to the output signal of the parallel-serial processing section. The delay entry section 19-1 introduces different delays to the output signal of the GI input section 18 in conjunction with the transmission antennas.

[0038] The output signals from 19-1 to 19-3 of the delay input are provided to the antenna-dependent signal processors 121, 12-2 and 12-3, respectively. Sections 19-1 to 19-3 introduce delays providing different delays (e.g., 0, S, and 2S). Here S = T / (sample time). The time of the sample represents the minimum time interval between the digital signals that are processed in the GI input section 18, the sections 19-1 through 19-3 for delay entry and the mixing section.

Thus, entering a delay of S samples in sections 19-1 to 19-3 of the delay entry indicates that the delay time T is input at the output end of the D / A converter 22. The user-dependent signal processor 11a is used in a certain bit; in other words, it is used either in the frequency diversity region or multi-user diversification region; hence, it receives a communication signal (a communication signal to vary the frequency / difference of multiple users) directing the use of either a frequency diversity region or a multi-user diversity region from a higher order layer controlling a physical layer. The user-dependent signal processor 11a selectively uses either the diversification region

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A frequency diversity region or multi-user diversity region based on a communication signal, thereby operating to change the delay time T.

The user-dependent signal processor 11b has a structure similar to the user-dependent signal processor 11a, but differs from that of its user.

[0039] The antenna-dependent signal processor 12-1 comprises a mixing section, a filter 21 and a D / A converter (Digital / Analog) 22.

The mixing section adds and mixes the signals that are output to the antenna-dependent signal processor 12-1 from the user-dependent signal processors 11a and 11b. The filter 21 extracts signals from only a predetermined band from the output section of the mixing section. The D / A converter 22 carries out processing from digital to analog form on the output signal of the filter 21.

Both antenna-dependent signal processors 12-2 and 12-3 have similar structures to the antenna-dependent signal processor 12-1. The output signal of the antenna-dependent signal processor 12-1 is passed to a wireless frequency converter (not shown) for converting the frequency into wireless frequencies from which it is supplied to a plurality of (three) transmit antennas, thereby transmitting wireless signals.

(Third Embodiment) [0040] A third embodiment of the present invention will be described with reference to another structure of a wireless transmission device. The wireless transmitting device of the present embodiment is a wireless transmitting device that introduces different delay times to transmit antennas so as to transmit signals in which delay times are applied with respect to time regions.

The wireless transmitting device supports signals that are used with guard intervals with respect to symbols (important symbol intervals) of the transmission signals. Signals applied with different delay times in

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With regard to transmission antennas, they are focused on predetermined parts (important symbol intervals) of the transmission signals that are currently transmitted via the first transmission antenna in addition to the guard intervals; hence, only important symbol intervals are delayed by T and are then transmitted via the second transmission antenna; similarly, only important symbol intervals are delayed by (n-1) T and are then transmitted via the n-th transmission antenna.

[0041] Thus, the transmission antennas transmit signals that have guard intervals inserted according to important symbol intervals; hence, in contrast to the second embodiment, there is no deviation in the timing of the symbol in the transmitting antennas.

The introduction of the delay time described above is referred to in the following description as "entering a circular delay". By processing to introduce a circular delay, securing delay waves is advantageous compared to a second embodiment that describes that delay times are introduced into the transmit antennas.

[0042] FIGs. 9A and 9B show examples of signals that are generated by introducing circular delays to transmission signals in the present embodiment. FIG. 9A shows a signal transmitted via the first antenna, and FIG. 9B shows the signal transmitted via the second antenna. FIG. 9A and 9B show that a valid symbol interval corresponds to four samples and the guard interval corresponds to one sample in which, with respect to an important symbol interval, one sample is delayed in the second antenna compared to the first antenna. In the symbol units there is no deviation of symbol time synchronization with respect to the first antenna and the second antenna; flock, even if the circular delay is introduced to it, it is confirmed that

[0043] FIG. 10 is a block diagram showing the configuration of the physical layer of a wireless transmission device according to the present

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In one embodiment. As shown in the figure, the physical layer comprises user-dependent signal processors 111a and 111b and antenna-dependent signal processors 112-1, 112-2 and 112-3.

A user-dependent signal processor 111a (similar to a user-dependent signal processor 111b) performs signal processing in combination with a wireless transmission device used by each user. The antenna-dependent signal processor 112-1 (similar to the antenna-dependent signal processors 112-2 and 112-3) performs overweighting of the signals with respect to the transmitted transmit antenna.

The structure of the user-dependent signal processor 111a is substantially identical to the structure of the user-dependent signal processor 11a (FIG 8) described in the second embodiment, whereas the difference between them lies in that the GI entry section 18 is not provided and instead of the section from 19-1 to 19-3, the delay is provided by sections 119-1 to 119-3 of the introduction of a circular delay.

The user-dependent signal processor 111a shares the same functions as the error correction section 13, the modulator 14, the subcarrier section 15, the IFFT section 16, and the parallel serial processing section included in the second embodiment (see FIG. 8); hence, they are marked by the same reference signs and their description will be omitted.

[0044] Section 119-1 of introducing a circular delay introduces a different circular delay to the output signal from parallel-serial conversion section 17 in combination with transmission antennas. The output signals from the sections 119-1 to 119-3 of the inputting of the circular delay are provided to the antenna-dependent signal processors 112-1, 112-2 and 112-3. In addition, sections 119-1 to 119-3 introduce a circular delay providing different delays (e.g., 0, S and 2S). Here, S = T / (sample time).

The user-dependent signal processor 111a is used in a certain piece. Because it is used either in the region

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In a frequency diversity diversification or in a multi-user diversity region, it receives a communication signal that directs the use of either a frequency diversity region or a multi-user diversity region through higher-order control of the physical layer. The user-dependent signal processor 111a selectively uses either a frequency diversity region or a multi-user diversity region based on a communication signal, thus operating to change the delay time T.

The user-dependent signal processor 111b has a similar structure as the user-dependent signal processor 111a, but differs from it for the user.

[0045] FIG. 11 is an illustration explaining the section 119-1 of introducing a circular delay which is described as an example of the present embodiment. The circular input delay section 119-1 is provided with memory 110. In order to enter a circular delay of k samples, the data D11 is sequentially input from the address k + 1 to the address n memory 110 (i.e., 1, 2, 3 are entered, ..., (nk)); then the data subsequence D11 is entered into address 1 (i.e., (n-k + 1), (n-k + 2), (nk + 3), ..., n) are entered, thus entering n data samples D11. Then, sequentially deriving memory address 1 from address 1 1, it is possible to output data D12, which is created by entering a circular delay of k samples for n data samples D11, (i.e., (n-k + 1), (nk + 2) , (n-k + 3), ..., n, 1, 2, ..., (nk)).

FIG. 9A shows an example of a signal that is formed by entering a circular delay of zero specimens for data of the size of four samples, and FIG. 9B shows an example of a signal that is created by giving a circular delay of one sample size.

[0046] The structure of the signal-dependent signal processor 112-1 (FIGURE 10) is substantially identical to that of the antenna-dependent signal processor 12-1 (FIGURE 8) described in the second embodiment, wherein the difference between them is that, that a GI entry section 18 is provided therein.

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EP 2 164 187 B1

Functions of the mixing section, the GI input section 18, the filter 21 and the D / A converter 22 included in the antenna dependent signal processor

112-1 are identical to those contained in the second embodiment (FIG.

8); hence, they are marked by the same reference signs and their description will be omitted.

Both user-dependent signal processors 112-2 and 112-3 have a structure similar to the antenna-dependent structure of the signal processor 112-1. The output signals of the antenna-dependent signal processors 1121, 112-2 and 112-3 are provided to a wireless frequency converter (not shown) for converting frequency into wireless frequencies from which they are supplied to a plurality of (three) transmit antennas, thereby transmitting wireless signals.

(Fourth Embodiment) [0047] A fourth embodiment of the present invention will be described with reference to the structure of another wireless transmission device. The wireless transmitting device according to the present embodiment is a wireless transmitting device in which different delay times are introduced into the transmission antennas so as to transmit signals, wherein delay times are entered with respect to the frequency region.

The present embodiment deals with signals that are used with guard intervals with respect to the symbols (important symbol intervals) of the transmission signals, wherein similar to the wireless transmission device of the third embodiment (FIGURE 10), circular delays are included therein.

[0048] FIG. 12 is a block diagram showing the configuration of the physical layer of the wireless transmission device of this embodiment. As shown in the figure, the physical layer includes user-dependent signal processors 211a and 211b, assignment section 215

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And sub-carriers, and antenna-dependent signal processors 212-1, 212-2 and

212-3.

The user-dependent signal processor 211a (similar to the user-dependent signal processor 211b) performs signal processing with respect to the wireless transmission device used by each user. The subcarrier assignment section 215 assigns an output signal of a user-dependent signal processor 211a to each subcarrier. The antenna-dependent signal processor 212-1 (similar to antenna-dependent signal processors 212-2 and 212-3) performs signal processing with respect to the recommended antenna.

[0049] Each of the user-dependent signal processors 211a and 211b comprise an error correction coding section 13 and a modulator 14. The functions of the error correction coding section 13 and the modulator 14 are substantially identical to those described in the second embodiment (FIGURE 8); hence, they are marked with the same reference numerals and their description will be omitted.

The output signals of the user-dependent signal processors 21a and 211b are assigned a respective subcarrier in the subcarrier section subcarrier 215 based on the subcarrier assignment information indicated by the higher order layer; then, they are supplied to the antenna-dependent signal processors 212-1, 212-2 and 212-3.

The antenna-dependent signal processor 212-1 comprises a phase rotation section 219, an IFFT section 16, a parallel-serial processing section 18, a GI input section 18, a filter 21 and a D / A converter 22. Functions of the IFFT section 16, processing section 17 parallel-serial, GI input section 18, filter 21 and D / A converter 22 are identical to those of the second embodiment (FIGURE 8); hence, they are marked with the same reference numerals and their description will be omitted.

The phase rotation section 219 rotates the output signal s of the subcarrier section 215 by phase 0_m for each subcarrier and then derives it to IFFT section 16. Both processors dependent on the antenna

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The signals 212-2 and 213 have a structure similar to the structure of the user-dependent signal processor 212-1.

[0051] The output signals of the antenna-dependent signal processors 212-1, 212-2 and 212-3 are provided to a wireless frequency converter (not shown) for performing frequency conversion into wireless frequencies from which they are delivered to multiple transmission antennas, including by itself by outputting wireless signals.

In the present embodiment, rotation of the phase θ_π in phase 219, the phase rotation is set to θ_m= 2πf_m· (N-1) T. Here, f_m means the frequency difference between the 0-subcarrier and the m-subcarrier, it being defined as fm = m / Ts, such that (n-1) T represents the time of circular delay on the nth antenna with respect to the first antenna. Ts represents the time of the valid symbol for the OFDM symbol.

[0052] The delay introduction section 220 consists of a phase rotation section 219 and an IFFT section 16. The phase rotation applied by the phase turn section 219 is subjected to a frequency-time conversion in the IFFT section 16 so that it is considered a time delay at the output of the IFFT section 16.

The user-dependent signal processor 211a is used in a piece that is used either in the frequency diversity region or in a multi-user diversity region in which it receives a communication signal indicating whether to use a frequency diversity region or a multi-user diversity region from a higher layer controlling a layer physical. Based on the communication signal, the user-dependent signal processor 211 selectively uses a frequency diversity region or a multi-user diversity region, thereby operating to change the delay time T.

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A communication signal indicating whether the transmission signals are subject to transmission of frequency diversity or multi-user diversity diversification.

Thus, by appropriately setting the delay time T based on determining whether the transmission signals are subject to frequency diversity transmission or multi-user diversity transmission, it is possible to generate the frequency diversity effect and the diversification effect of many users without being affected by the propagation path conditions.

(Fifth Embodiment) [0054] A fifth embodiment of the present invention will be described with reference to the structure of another wireless transmission device. The wireless transmitting device according to the present embodiment is a wireless transmitting device that introduces different delay times to signals which are then transmitted via transmit antennas in a frequency diversity region when applying appropriate weights to transmit antennas so as to perform direction control in a diversification region. a plurality of users, wherein delay times are used and direction control is implemented in the frequency region.

The present examples support signals that are generated by inputting guard intervals to transmit signals with respect to symbols (valid symbol intervals), wherein, similar to the third and fourth embodiments, it introduces circular delays to signals.

[0055] FIG. 13 is a block diagram showing the configuration of the physical layer of the wireless transmission device of this embodiment. As shown in the figure, the physical layer includes user-dependent signal processors 211a and 211b, subcarrier assignment section 215, weight calculation section 310, and antenna-dependent processors

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312-1, 312-2 and 312-3 signal signals. The structures of the user-dependent signal processor 211a and the subcarrier assignment section 215 are similar to the structures of the fourth embodiment (FIG 12); hence, they are marked with the same reference numerals and their description will be omitted.

[0056] The antenna-dependent signal processor 312-1 (similar to antenna-dependent signal processors 312-2 and 312-3) performs signal processing with respect to the recommended transmit antennas.

The antenna-dependent signal processor 312-1 includes a mass multiplication section 319, an IFFT section 16, a parallel-serial processing section 18, a GI input section 18, a filter 21 and a D / A converter 22. Functions of the IFFT section 16, section 17 parallel-serial processing the input section GI, the filter 21 and the converter C / A 22 are identical to the functions of the first embodiment; hence, they are marked with the same reference numerals and their description will be omitted.

[0057] The mass multiplication section 319 performs weight multiplication on the output signal from the subcarrier section subcarrier 215 with respect to subcarriers, and outputs the results to the IFFT section 16. Both antenna-dependent signal processors 312-2 and 312-3 have a structure similar to the antenna-dependent signal processor 312-1.

The output signals of the antenna-dependent 312-1, 312-2 and 312-3 signal processors are provided to a wireless wireless frequency converter (not shown) for performing frequency conversion into wireless frequencies from which the results are delivered to the transmit antennas, thereby outputting wirelessly signals.

[0058] A particular subcarrier is used in a certain fragment. That is, it is used either in the frequency diversity region or in the multi-user diversification region. The weighting multiplication section 319 is informed of whether to use or region

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Frequency diversity diversification or multi-user diversification region from a higher-order layer controlling a physical layer, based on what phase 0 rotation_m is introduced to introduce different delay times into antennas in the frequency diversity region, whereas multiplication using the weight in m is carried out in order to control directionality in a multi-user diversity region.

[0059] The delay introduction section 320 and the direction control consist of a weight multiplication section 319 and an IFFT section 16. When the phase rotation is entered via the weight multiplication section 319, it is considered as the output time of the IFFT section 16, because the IFFT section 16 performs frequency and time-to-time processing. On the other hand, when the weight multiplication section performs multiplexing using weights in m, the IFFT section 16 performs frequency-time processing such that the output signal from the IFFT section 16 outputted from the transmission antenna is subjected to a direction control.

[0060] When the weighting multiplication section 319 rotates the phase by 0_msimilar to the fourth embodiment, it sets θ_m= 2πf_m· (N-1) T. Here f_mmeans the frequency difference between the 0th subcarrier and the mth subcarrier, where fm = m / Ts; a (n-1) T represents the circular delay time on the nth antenna with respect to the first antenna. Ts represents the time of the valid symbol for the OFDM symbol.

For multiplication using the weight in m, the following weight is set to perform direction control. Assuming a linear array of n aerials whose distance is equal to half the wavelength of the carrier frequency, the weight wm is calculated according to the following equation (1):

[Equation 1]

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EP 2 164 187 B1

<img file="PL2164187T3_D0001.tif" />

<img file="PL2164187T3_D0002.tif" />

[0062] The weight wm represents the weight vector used in the weighting multiplication section 319, in which in the equation (1), the first to the last term describe the weights used in the first to the nth antenna.

In equation (1) expressing the weight in m, n denotes the number of antennas, in the present embodiment, n = 3; θ indicates the direction in which the main stream is directed; ak is the ratio between the frequency used for transmission and the frequency which is measured based on θ.

With respect to the main direction θ of the flow, the measured value generated by the wireless transmission device or the counter of the message counter is provided to the section 310 of the weight calculation in which it is used to calculate the weight in m. The equation (1) shows an example of the calculation for the weight wm, which can be calculated by means of another method. The calculation methods for θ and wm are described in "Technical Report RCS2004-229" (published by the Corporate Institute of Electronic Information and Telecommunication in November, 2004) and similar documents.

[0063] The delay entry and direction control section 320 introduces delays with a maximum delay time (n-1) T or less between the transmission antennas when the communication signal indicates frequency diversity while it performs multiplexing to generate a weight in m so as to perform control directivity when the communication signal indicates the diversification of many users.

As described in the first embodiment, the delay entry section 320 and the direction control function sets the delay time T so that the maximum delay time (n-1) T between the transmission antennas falls within

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(N-1) T&gt; 1 / Fc when the communication signal indicates frequency diversity.

As described in the first embodiment, delay entry section 320 and direction control means set the delay time T such that the maximum delay time (n-1) T is in the range (n-1) T&gt; I / BW when the communication signal indicates frequency diversity .

[0064] The above-mentioned description informs that the mass injection section 319 of the delay entry section and the direction control is instructed by the higher order control layer of the physical layer to use either the frequency diversity region or the multi-user diversity region based on which performs phase 0 rotation._mso as to introduce different delay times to antennas in a frequency diversity region, while it multiplies to produce a weight in m so as to perform direction control in a multi-user diversity region; however, it is possible to use a different method of using both Phase 0 rotation_m and weights in m in the multi-user diversity region such that, as described in the fourth embodiment, rotation of phase 0_m it is provided with respect to both the frequency diversity region and the multi-user diversity region prior to generating the main flow direction, and then the direction control is carried out using the weight in m after generating the main flow direction in the multi-user diversity region. Similarly to the fourth embodiment, the delay time T varies with 0m according to the frequency diversity region and the multi-user diversity region. Thus, in the step preceding the creation of the main flow direction, it is possible to produce the same multi-user diversity effect as in the fourth embodiment, while after generating the main flow direction, it is expected that a greater effect of multi-user diversification will be created by precisely executing directional control using the weight in m. In addition, using rather the configuration of the physical layer

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In the case of the wireless transmission device shown in FIG. 13 than the fourth embodiment, it is possible to realize the improvement of the characteristics as a result of the directivity control by slightly increasing the circuit structure.

[0065] As described above, the delay entry section 320 and the direction control introduce delays with a maximum delay time (n-1) T or less between the transmission antennas when the communication signal indicates frequency diversity while it provides a delay with a maximum delay time (n-). 1) T or less between transmitting antennas, or it multiplies to create a weight in m so as to perform direction control when the communication signal indicates multi-user diversification, [0066] The wireless transmitting device performing the above-mentioned processing has the structure shown in FIG. 13, wherein, when the communication signal indicates the diversification of many users, the delay entry and direction control sections introduce delays with a maximum delay time (n-1) T or less between the transmission antennas, or it performs a multiplication to create a weight in m so as to perform a direction control. [0067] As described in the first embodiment, the delay entry and direction control section sets the delay time T such that the maximum delay time (n-1) T between the transmission antennas is in the range (n-1) T&gt; 1 / Fc when the communication signal indicates frequency diversity, while it sets the delay time T so that the maximum delay time is in the range (n-1) T &lt;1 / Fc when the communication signal indicates the diversity of multiple users so that a delay is introduced between the transmit antennas.

As described in the first embodiment, the delay entry and direction control section sets the delay time T such that the maximum delay time (n-1) T between the transmission antennas is in the range (N-1) T&gt; 1 / BW when the communication signal indicates frequency diversification.

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[0068] The above-mentioned second to fifth embodiments are described with reference to the case in which the number of users is two and the number of antennas is three, wherein the number of users and the number of antennas are not necessarily limited to these numbers.

In the above-mentioned fourth and fifth embodiments, it is possible to transmit signals which are subjected to multiplication by using specific cryptographic codes dependent on antennas, sectors, and base stations, to transmit antennas.

(Sixth Embodiment) [0069] This embodiment will be described with reference to various maximum delay times (n-1) T dependent on physical channels. The above-mentioned embodiments from the first to the fifth are described assuming that one-to-one communication is carried out with reference to one specific fragment at a given moment, where (n-1) T&gt; 1 / Fc is set to produce the effect of diversification frequency, while (n-1) T &lt;1 / Fc is set to produce the effect of multi-user diversity.

[0070] Normally, in communications other than one-to-one communication, a known signal referred to as a pilot channel is transmitted to a wireless transmission device to estimate the propagation path; alternatively, a control channel is used to provide various types of parameters before data communication. This embodiment will be described with reference to the method of setting the maximum delay time (n-1) T in these physical channels.

[0071] In the UTRA &amp; UTRAN Development developed in 3GPP (3rd Generation Partnership Project), common DCPCH downlink pilot channels (Downlink Dedicated Pilot Channel), dedicated downlink DDPCH (Downlink Dedicated Pilot Channel) channels, synchronizing downlink download channels are provided. DSCH (Downlink Synchronization Channel), common control channels DCCCH (Downlink Common Control

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EP 2 164 187 B1

Channel), shared linking signaling download channels

DSCSCH (Downlink Shared Control Channel), and broadcast / group broadcast channels (Multicast / Broadcast Channel).

The common DCPCH pilot channels correspond to the CPICH pilot channels in W-CDMA (Wideband Code Division Multiple Access), which are used to estimate the conditions of the downlink propagation path, the cellular search and the measurement of propagation path losses in uplink transmission power control in AMCS (Adaptive Modulation and Coding Scheme).

The dedicated DDPCH pilot channels are used to carry out transmissions towards individual mobile stations via transmit antennas such as adaptive antenna arrays whose propagation paths are different from the propagation paths of antennas with shared antennas; alternatively, they may be used to reinforce the shared DSPCH download joint pilot channels in connection with mobile stations having low reception quality.

[0073] The DSCH download synchronization channels correspond to SCH synchronization channels in W-CDMA, wherein they are used for mobile cellphone search, wireless OFDM signal frames (Orthogonal Frequency Division Multiplexing), time slots, TTI transmission time intervals (Transmission Timing Interval ) and OFDM symbol time synchronization. The common control channels DCCCH contain common control information such as broadcast information (corresponding to broadcast channels BCH) corresponding to the original common control physical channels PCCPCH, secondary common control physical channels S-CCPCH and PICH notification channel channels in W-CDMA,

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To the downlink (corresponding to the access channels to the FACH download link).

[0074] The DSCSCH downlink shared signaling channels correspond to HS-DSCH connected to the HS-SCCH shared control channels, dedicated DPCCH download control channels, AICH acquisition indicators included in the shared high-speed download channels HS-PDSCH in HSPDA (High Speed ​​Downlink Packet Access), which are shared by many mobile stations and are used for information transmission (modulation methods, distributed coding, etc.) which is required for mobile stations to perform demodulation in relation to shared downlink channels with a large HS-DSCH speed, information that is required to perform error correction decoding and HARQ processing,and scheduling information about wireless resources (frequency, time).

[0075] The shared DSDCH download data channels correspond to the HS-DSCH high-speed downlink shared channels and the dedicated DPDCH download data channels included in the physical HS-PDSCH high-speed common download channels in the HSPDA, wherein they are used for transmission a data packet towards mobile stations from higher-order layers.

Group / broadcast channels are used to broadcast information signals.

The above-mentioned physical channels W-CDMA and HSDPA are described in the document "Tachikawa Keiji, W-CDMA Mobile Communication Method, ISBN4-621-04894-5" and the like.

[0076] FIG. 14 and 15 are tables describing the relationship between the maximum delay time (n-1) T between transmitting antennas and the bandwidth of the Fc frequency bands in combination with physical channels. As shown in the figures, it is preferable to set (n-1) T &lt;1 / Fc irrespective of the frequency diversity region and the multi-user diversity region with respect to common

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Control pilot channels, common control channels and dedicated control channels. The (n-1)&gt; 1 / Fc setting is preferred irrespective of the frequency diversity region and the multi-user diversity region with respect to synchronizing downlink channels.

With respect to dedicated pilot channels, it is preferable to set (n-1) T&gt; 1 / Fc in the frequency diversity region and set (n1) T &lt;1 / Fc in the multi-user diversity region. Dictated pilot signals are assumed to be transmitted via transmit antennas, wherein the delay entry section for delaying the transmission signals provided to the n transmit antennas with a maximum delay time (n-1) T or less sets the delay time T so that the maximum delay time (n-1) T is in the range (n-1) T&gt; 1 / Fc when a communication signal that indicates whether fragments containing dedicated pilot channels are subject to frequency-diversity transmission or multi-user diversification transmission, indicates frequency diversification, while it sets the delay time T to execute a direction control using scales derived from the weight calculation section or to determine the maximum delay time (n-1) T as (n-1) T &lt;1 / Fc when the communication signal indicates the multiversion of multiple users . Group / broadcast channels are used only in the frequency diversity region; hence, it is preferable to set (n-1) T&gt; 1 / Fc.

[0077] The reasons why the aforementioned settings are carried out are that joint pilot channels are used to notify the signal strengths experienced by the terminals, hence it is undesirable that the delay time varies with respect to the fragments, whereas it is necessary to the wireless transmitting device knew the intensity of the signals in relation to the fragments in the case of (n-1) T &lt;1 / Fc in order to diversify many users, hence it is preferable to set (n-1) T &lt;1 / Fc in such a way that the maximum time the delay did not change with respect to fragments.

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EP 2 164 187 B1

Dedicated pilot channels are used to calculate the estimated values ​​of propagation paths used to demodulate data signals. Thus, it is preferable to communicate by setting (n-1) T&gt; 1 / Fc in the frequency diversity region and setting (n-1) T &lt;1 / Fc in the multi-user diversity region.

[0078] Synchronizing downlink channels are used to synchronize the frame, whereby estimation of propagation paths is not necessary, and it is advantageous to secure accurate reception in the case of low reception power; hence, it is preferable to set (n-1) T&gt; 1 / Fc to produce a frequency diversity effect. In particular, it is possible that the same signal is transmitted using the same time and the same frequency via synchronizing downlink channels through a plurality of sectors and a plurality of antennas contained in a single base station. Same, the signals are applied with different delays in relation to the antennas and are transmitted via a plurality of sectors and a plurality of antennas contained in a single base station via synchronizing downlink channels; hence, it is expected that a high frequency diversification effect will be generated that is higher than the frequency diversity effect of another physical channel.

[0079] It is assumed that the joint control channels and dedicated control channels use estimated values ​​of propagation paths that are generated by means of common pilot channels; hence, it is preferred that they be set to the maximum delay time, which is identical to that for the common pilot channels, and have been transmitted.

However, it is advantageous to secure accurate reception in common control channels and dedicated control channels in the case of low reception power; hence, it is advantageous to produce a frequency diversity effect, wherein, in the first place, to improve the reception efficiency of control channels, when shared control channels, dedicated control channels and group / broadcast transmission channels are included in the same fragment, it is preferable to carry out

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Transmission via common pilot channels by setting (n-1) T&gt; 1 / Fc, thereby generating a frequency diversity effect in the control channels.

[0080] When the same fragment is used to diversify many users, it is necessary to perform a notification of the signal strengths present in the current transmission matched to the multiuser diversity (communication with (n-1) T &lt;1 / Fc); hence, it is preferable to carry out the transmission by setting (n-1) T &lt;1 / Fc.

For this reason, it is possible to set the relationship between the maximum delay time (n-1) T between the transmission antennas and the bandwidth of the Fc portion of the fragment, which is identical to the relationship shown in FIG. 15, for each physical channel.

In order to generate the frequency diversity effect, it is advantageous to carry out communication by setting (n-1) T&gt; 1 / Fc.

[0081] The above-mentioned embodiment is described such that the maximum delay time is in the (n-1) T &lt;1 / Fc range in the multi-user diversity region, while the wireless transmitting device described in the fifth embodiment can use the weight in m , which is generated by the weight calculation section 310 in a multi-user diversity region.

The embodiments mentioned above from the second to the fifth are each described so that a wireless transmitting device having n transmission antennas transmits signals with a recommended delay time entered for each of the transmitting antennas; however, this structure is not limited. For example, when a wireless transmission device having n transmission antennas selects the use of multiple user diversity, it is possible to transmit signals with the introduced delay time T 'for each of the transmission antennas (where j is an integer, 1 &lt;j &lt;n) within n transmit antennas. [0082] In the above-mentioned structure compared to the structure in which the signals are transmitted using all n transmit antennas, the maximum delay time (j-1) T 'introduced to the signals

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The transmitting antennas transmitted via j are reduced so as to further reduce the propagation path changes; hence, it is possible to create a good multi-user diversification effect. In particular, with j = 1, it is possible to reduce the circumference of the delay section.

This embodiment is described with the assumption that the maximum delay time is set to (n-1) T&gt; 1 / Fc to produce the frequency diversity effect, whereas, as described in the first embodiment, when the transmission is performed using a physical channel, which has assigned fragments located in many frequency directions, the BW bandwidth assigned to the physical channel forms the basis for generating the frequency diversity effect; hence, it is possible to produce a frequency diversity effect by setting the maximum delay time to (n-1) T&gt; 1 / BW.

[0083] By using a wireless transmission device according to the above-mentioned embodiments of the present invention that chooses to use either frequency diversity or multi-user diversity in transmission of signals from n transmitting antennas so as to vary the delay times introduced into signals transmitted via n transmission antennas based on the result choice; hence, it is possible to generate the effect of frequency diversity or the diversification effect of many users without being affected by the conditions of propagation paths.

[0084] In the above-mentioned embodiments, programs performing the functions of error correction coding section 13, modulator 14, section 15 and 215 subcarrier assignments, IFFT section 16, parallel serialization section 17, GI input section 18, sections 19-1 for a delay of 19-3, a section 119-1 to 119-3 for entering a circular delay, a mixing section, a filter 21, a D / A converter 22, a phase rotation section 219, a weight calculation section 310, and a weighting multiplication section 319 shown in FIGS. . 8, 10, 12 and 13 are stored on

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Computer-readable storage medium such that the programs stored on the storage medium are loaded into the computer system and are then executed to control the wireless transmission device. Here, the computer system includes OS and hardware such as peripherals.

[0085] Computer-readable recording media are referred to as flexible discs, magneto-optical disks, ROMs, portable media such as CDROMs and storage devices such as hard disks included in computer systems. In addition, the computer-readable storage medium includes carriers for dynamically storing programs in short periods of time, such as communication lines such as the Internet, networks and telephone lines used to transmit programs as well as fleeting memories for storing programs over a prescribed period of time that are included in the a computer system serving the server and the client. The above-mentioned programs are designed to carry out some of the aforementioned functions; alternatively,

[0086] The invention is described in detail by way of exemplary embodiments with reference to the drawings, in which its exact structure is not necessarily limited to the embodiments; hence, it includes designs that do not depart from the scope of the present invention as defined in the appended claims.

INDUSTRIAL APPLICABILITY [0087] The present invention can be applied to wireless transmission devices and wireless transmission methods that transmit signals to wireless receiving devices using a plurality of transmission antennas, wherein delay times are appropriately set based on whether the transmission signals are transmitted frequency diversification or transmission

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Diversifying many users; hence, it is possible to generate frequency diversity effects and diversification effects of many users without being affected by the propagation path conditions.