Transmission control method and apparatus using delays in multiple antenna systems

ES 2 380 451 T3

DESCRIPTION

Wireless transmission method.

Technical field

The present invention relates to wireless transmission devices and wireless transmission methods and in particular to wireless transmission devices and wireless transmission methods for transmitting signals to wireless receiving devices through the use of plural transmitting antennas.

The present application claims priorities of Japanese Patent Application No. 2005-253194 filed in Japan on September 1, 2005 and Japanese Patent Application No. 2005-367860 filed in Japan on December 21, 2005, the contents of which are incorporated herein by reference.

Previous technique

Recently, methods are provided, mainly adapted for multi-carrier transmission systems, in which a plurality of blocks are divided along the frequency and time axes that perform scheduling on the signals transmitted to the users from the wireless transmission devices to the block units. Here, the regions that are secured for users to carry out communications and that are defined along the frequency and time axes are referred to as allocation bands, and blocks that serve as the basis for determining the allocation bands are referred to as fragmented encodings.

In the foregoing, methods are provided which, in order to transmit broadcast signals, multicast signals, and control signals, blocks whose ranges are expanded in the direction of the frequency axis are assigned in order to produce frequency diversity effects. , thus reducing errors regardless of the low reception power. In addition, methods are provided which, in order to transmit unicast signals in one-to-one communications between wireless transmission devices and wireless deception device, blocks whose ranges are reduced in the direction of the frequency axis are allocated in order to produce multi-user diversity effects, thus improving the reception power in wireless receiving devices.

Figures 16A and 16B show the relationships with respect to signals transmitted from a wireless transmitting device to a wireless receiving device with respect to time (horizontal axis) and frequency (vertical axis). In FIG.16A, the horizontal axis represents time, and the vertical axis represents frequency. Transmission times fe at₃ they fit on the time axis. Here, the same length of time is set to times Í1 at₃ respectively. The transmission frequencies f1 to fs are adjusted to the frequency axis. Here, the same frequency range F₆, set the frequencies fe to f5. With reference to the transmission times fe to fe, and the transmission frequencies fe to f5, fifteen fragmented encodings K1 to K15 are set as shown in Figure 16A.

Additionally, five fragmented encodings K1 to K₅, is connected as shown in FIG. 16B and are then divided equally into six strips along the time axis, thus establishing the communication strips s1 as₈, each of which has a time duration of 6fe and a frequency range of 5fe. The communication strips s1 as₄, are assigned to a first user; communication slots s2 and s5 are assigned to a second user; and the communication slots s3 to s6 are assigned to a third user. This makes it possible for the first to third users to obtain frequency diversity effects.

Then, the K10 chunk encoding is assigned to a fourth user as a communications slot su. The fragmented encodings K7, K₃, K9 are connected in order to form communication strips s₃ as ™, each of which has a time duration of t₂ and a frequency range of 3f and assigned to a fifth user. Additionally, the chunk encoding k6 is assigned to a sixth user as a communication slot s7. This makes it possible for the fourth to sixth user to obtain multi-user diversity effects, and this makes it possible for the fifth user to obtain a frequency diversity effect.

[0007] Additionally, the K11 chunk encoding is assigned to a seventh user as an s12 communication slot. This makes it possible for the user to obtain a multi-user diversity effect. Additionally, the K13 and K15 chunks are assigned to an eighth user as communication slots s19 and s26. This makes it possible for the user to obtain a multi-user diversity effect.

Additionally, the two fragmented encodings K12 and K1₄ are equally divided into six stripes, thus forming stripes s1₃ to s1₈ and s20 to s25. Communication stripes s1₃, s1₈, s20 and s23 are assigned to a ninth user; the communication strips su, s-17, s₂1 and s24 are assigned to a tenth user; and the communication strips s1₅, s1₈, s22,

ES 2 380 451 T3 and S25 are assigned to an eleventh user. This makes it possible for the 9th to the 11th user to obtain frequency diversity effects individually.

Non-patent Document 1: Contribution to 3GPP, R1-050249, “Downlink Multiple Access Scheme for Evolved UTRA”, [Retrieved August 17, 2005] Internet (URL: ftp://ftp.3gpp.org/TSG_RL1/TSGR1_40bis/ Does / R1- 050249.zip)

Non-patent Document 2: Contribution to 3GPP, R1-050590, “Physical Channels and Multiplexing in Evolved UTRA. Downlink ”. [Retrieved August 17, 2005], Internet (URL:

ftp://ftp.3gpp.org./TSG_RAN/WG1_RL1/R1_Ad_Hoes/LTE_AH_june-05/Docs/R1-0.50590.zip)

Description of the invention

Problems to be solved by the invention

In order to obtain the frequency diversity effects in the aforementioned conventionally known methods, it is necessary to increase the dispersion coefficients or reduce the coding coefficients in the coding that corrects the error in response to the frequency variations of the functions of transfer in the paths of propagation.

FIGS. 17A and 17B and FIGS. 18A and 18B are graphs showing delay profiles and transfer functions relative to signals propagating through plural propagation paths that have different delay times in order to reach wireless receiving devices.

FIGS. 17A and 18A show delay profiles showing transmission signals, propagating through plural propagation paths in order to reach a wireless receiving device, with respect to time (horizontal axis) and power (vertical axis). FIGS. 17B and 18B show the transfer functions to perform frequency conversion on the delay profiles with respect to frequency (horizontal axis) and power (vertical axis).

FIG. 17A shows the appearance of six lag waveforms W11 to w-ιβ, and FIG 18A shows the appearance of three lag waveforms w21 to w23. They differ from each other with respect to the maximum delay times t1 and t2.

When the maximum delay time t1 is long as shown in FIGS. 17A and 17B, that is, when relatively fast frequency variations (rapid power variations in the frequency direction) occur in the transfer function, an adequate frequency diversity effect is expected to reduce regardless of the dispersion coefficients small and high coding coefficients in the coding that corrects the error. However, when the maximum delay time t2 is small as shown in FIGS. 18A and 18B, that is, when relatively moderate frequency variations occur in the transfer function, an adequate frequency diversity effect is not expected to occur when the dispersion coefficient is small and the coding coefficient in the coding that corrects the error is high; thus, it is necessary to increase the dispersion coefficient and reduce the coding coefficient in the coding that corrects the error.

D1 and D2 in FIG. 17B and 18B show the signals, i.e. data. That is, in FIG. 17B, ​​the spreading index of the technology that spreads the spectrum is set to "4" with respect to the D1 and D2 data, thus assigning four subcarriers an to a-i4 to the D1 data. Similarly, the four subcarriers a-is to a-is are assigned to the D2 data. In this case, the transfer function has rapid frequency variations; in this way, the reception power of the sub-carrier a13 in relation to the data D1 noticeably decreases such that the reception power of the sub-carrier a16 in relation to the data D2 also noticeably decreases. Therefore, reception failures do not occur with respect to the D1 and D2 data.

In FIG. 18B, the dispersion index is set to "8" in order to assign eight subcarriers to₂1 to a28 to data D1. In this case, the transfer function has slow frequency variations in such a way that the reception power of the subcarrier a24 decreases markedly, and the reception power of the subcarrier a23 and a25 decreases slightly, while the dispersion index of the data is increased compared to the case of FIG. 17B such that reception failures do not occur with respect to the D1 data. The aforementioned values ​​of dispersion indices are described for convenience and are not necessarily limited. US 2005/163236 A1 describes transmission symbols in a multiple antenna communication system in which at least a portion of a frame is delayed by at least one transmission antenna.

ES 2 380 451 T3

The present invention is made in consideration of the above-mentioned circumstances, wherein it is an object of the invention to provide a wireless transmission device and a wireless transmission method that can produce a suitable frequency diversity effect without controlling the dispersion coefficient and a coding coefficient in the coding that corrects the error on the wireless transmission side.

Means to solve the problem

In accordance with the present invention, a transmission control method is provided according to claim 1. A preferable feature is set forth in claim 2.

Effect of the invention

With reference to the delay time T suitable for the communication signal, indicating transmission of frequency diversity or transmission of multi-user diversity, the transmission signals supplied to the n transmission antennas are each delayed by the transmission times. delay (n-1) T or less.

Thus, by properly setting the delay time that based on the condition of whether the transmission signals are subjected to frequency diversity transmission or multi-user diversity transmission, it is possible to produce frequency diversity effects and multi-user diversity effects. unaffected by the condition of a propagation path.

Brief description of the drawings.

FIG. 1 is a schematic illustration showing that signals transmitted by a wireless transmitting device according to the first embodiment of the present invention propagate through plural propagation paths in order to reach a wireless receiving device.

FIG. 2A is a graph showing the delay profile applied to signals propagating through plural propagation paths having different delay times in order to reach a wireless receiving device.

FIG. 2B is a graph showing a transfer function that occurs by frequency conversion on the delay profile shown in FIG. 2A.

FIG. 3A is a graph showing another delay profile applied to signals propagating through plural propagation paths having different delay times in order to reach a wireless receiving device.

FIG. 3B is a graph showing a transparency function of the wireless receiving device, which is produced by performing frequency conversion on the delay profile shown in FIG. 3A.

FIG. 3C is a graph showing a transfer function of another wireless receiving device located at a different position that occurs when frequency conversion is performed on the delay profile shown in FIG. 3A.

FIG. 4A is a graph showing the maximum delay time (n-1) T in a delay profile.

FIG. 4B is a graph showing the relationship between the maximum delay time (n-1) T shown in FIG. 4A and frequency variations.

FIG. 5A is a graph showing another maximum delay time (n-1) T in a delay profile.

FIG. 5B is a graph showing the relationship between the maximum delay time (n-1) T shown in FIG. 5A and frequency variations.

FIG. 6A is an illustration showing the wireless transmission / reception system, in which the same signal that does not have a delay time is transmitted via plural antennas of a wireless transmission device.

FIG. 6B is a graph showing an example of a receive signal in the system shown in FIG.6A.

FIG. 6C is a graph showing another example of a receive signal in the system shown in FIG. 6.

ES 2 380 451 T3

FIG. 7A is an illustration showing a wireless transmitting / receiving system, in which the same signal is applied with different delay times and transmitted via plural transmitting antennas of a wireless transmitting device.

FIG. 7B is a graph showing an example of a receive signal in the system shown in FIG. 7A.

FIG. 7C is a graph showing another example of the reception signal in the system shown in FIG. 7A.

FIG. 8 is a block diagram showing the configuration of a physical layer of the wireless transmission device according to a second embodiment of the present invention.

FIG. 9A shows an example of a signal that is produced by applying a running delay to a transmission signal in accordance with a third embodiment of the present invention.

FIG. 9B shows another example of a signal that is produced by applying a running delay to a transmission signal in accordance with the third embodiment of the present invention.

FIG. 10 is a block diagram showing the configuration of a physical layer of a wireless transmission device according to the third embodiment of the present invention.

FIG. 11 is an illustration for explaining the operation of a flow retarding section 111-1 in the third embodiment of the present invention.

FIG. 12 is a block diagram showing the configuration of a physical layer of a wireless transmission device according to a fourth embodiment of the present invention.

FIG. 13 is a block diagram showing the configuration of a physical layer of a wireless transmission device according to a fifth embodiment of the present invention.

FIG. 14 is a table showing the relationship between the maximum delay time (n-1) T between the transmitting antennas and the frequency bandwidth Fc of a fragmented encoding with respect to each physical channel.

FIG. 15 is another table showing the relationship between the maximum delay time (n-1) T between the transmitting antennas and the bandwidth of the frequency Fc of a fragmented encoding with respect to each physical channel.

FIG. 15A is a graph showing the relationship between signals, which are transmitted from a wireless transmitting device to a wireless receiving device, with respect to time (horizontal axis) and frequency (vertical axis).

FIG. 16B is a graph showing communication slots that are assigned to a frequency time slot shown in FIG. 16A.

FIG. 17A is a graph showing the delay profile adapted to signals propagating through plural propagation paths having different delay times in order to reach a wireless receiving device.

FIG. 17B is a graph showing a transfer function that occurs by frequency conversion on the delay profile shown in FIG. 17A.

FIG. 18A is a graph showing a delay profile adapted to signals propagating through propagation paths having different delay times in order to reach a wireless receiving device.

FIG. 18B is a graph showing a transfer function that occurs by frequency conversion on the delay profile shown in FIG. 18.

ES 2 380 451 T3

Best Mode of Carrying Out the Invention (First Embodiment)

FIG. 1 is a schematic illustration showing that signals transmitted from a wireless transmitting device 1 propagate through plural propagation paths in order to reach a wireless receiving device 7. The wireless transmitting device 1 has plural transmitting antennas 2 to 4, which apply respectively to different delay times 0, T and 2T and of which the signals are transmitted. The wireless receiving device 7 receives signals transmitted from a wireless transmitting device 1. FIG. 1 shows an example in which the wireless transmission device 1 is equipped with three transmission antennas 2 to 4.

Suppose that the plural transmitting antennas are transmitting antennas installed in a wireless transmitting device provided in a base station by mobile phones, wherein the three types of transmitting antennas are supplied with respect to different sectors of the same base station and with relative to different base stations. The following description is given with respect to the situation in which they belong to the same sector, for example, but it is possible to employ another constitution. That is, the n transmit antennas belong to different sectors, or the n transmit antennas belong to different base stations.

In the figure, delays 5 and 6 apply a delay time T, by means of which, as described above, the delay time T is applied to the transmitting antenna 3, and the delay time 2T is applied to the transmitting antenna 4.

FIGS. 2A and 2B show a delay profile and a transfer function with respect to the signals, which propagate through plural propagation signals, (3) that have different delay times in order to reach a wireless receiving device. FIG. 2A shows the delay profile showing that transmission signals propagate through plural propagation paths that have different delay times in order to reach the wireless receiving device with respect to time (horizontal axis) and power (vertical axis). As shown in FIG. 2A, the delay time instantaneously has a maximum delay waveform of 2T + dmax; thus, compared to the constitution in which the same signal is transmitted via each transmitting antenna, the maximum waveform and delay becomes very long. Here D_maxrepresents a time-of-arrival difference between a fast-propagating path and a slow-propagating path when waves arrive at a receiving antenna from a transmitting antenna.

FIG.2B shows a transfer function that occurs when frequency conversion is performed on the delay profile of FIG. 2A with respect to frequency, (horizontal axis) and power (vertical axis). In the delay profile, increasing the maximum delay time 2T + dmax indicates rapid frequency variations of the transfer function. Therefore, as shown in FIG. 2B (similar to FIG. 17B), the data D1 and D2 are scattered with a scattering index of “4” and are assigned with subcarriers, it is preferable that the scattering coefficient or the coding coefficients of the error correcting coding be controlled in response to the frequency variations of the transfer function in the wireless transmission device 1, wherein the above-mentioned method establishes that the delay time 2T is recognized in advance by the wireless transmission device 1, in this way, it is possible to determine the dispersion coefficient or the coding coefficient of the coding that corrects the error without import frequency variations or propagation paths. In order to produce multi-user diversity effects, it is preferable that the maximum delay time 2T + dmax, which appear instantaneously in the delay profile, is not greatly increased. Multi-user diversity effects will be described with reference to FIGS. 3A to 3C.

FIGS. 3A to 3C show a delay profile and transfer functions with respect to the signals propagating through the plural propagation paths having different delay times in order to reach a wireless receiving device 3. FIG. 3A shows the delay profile adapted in such a way that the transmission signals propagating through the plural propagation paths (3) have different delay times in order to reach the wireless receiving device with respect to time (axis horizontal) and power (vertical axis). FIG. 3B shows a handover function relative to the wireless receiving device used by a user ul. FIG.3C shows a transfer function in relation to the wireless receiving device used by a user u2. Because the wireless receiving devices of users u1 and u2 differ from each other in location, the instant transfer functions of the same differ from each other.

Suppose the left region is connected to a frequency channel b1 and a right channel is connected to a frequency channel b2 in FIGS. 3B and 3C, user u1 enjoys good quality on frequency channel b2, while user u2 enjoys good frequency quality on channel b1. Therefore, the data D1 to

D4 are transmitted to user u1 on frequency channel b2. Data D1 to D4 are subjected to scattering of the

ES 2 380 451 T3 spectrum. Data D1 to D4 is transmitted to user u2 on frequency channel b1. In this case, the data D1 to D4 are spectralized.

As described above, by using a quality difference between frequency channels at a certain time, it is possible to produce multi-user diversity effects to improve transmission efficiency with respect to different users conducting communications using different frequency channels.

However, when the maximum delay time 2T + dmax is greatly increased, rapid frequency variations occur in the transfer function, thus reducing the quality difference between the frequency channel b1 and the frequency channel b2.

Therefore, in order to produce suitable multi-user diversity effects, it is important to reduce the maximum delay time 2T + dmax as shown in FIG. 3A.

FIGS. 4A and 4B and FIGS. 5A and 5B show the relationships between the maximum delay time (n-1) T and the frequency variations. When an arrival time difference (n-1) T appears between arrival waves w31 and w32 as shown in FIG. 4A, a transfer function of this propagation path is shown in FIG. 4B. That is, a frequency difference between the power amplitude drops (vertical axis) is defined as F = 1 / (n-1) T.

When the plural delay zones w41 to w43 appear as shown in FIG. 5A, an arrival time difference (n-1) T appears between the first arrival wave w41 and the last arrival wave w43, such that the frequency difference between the power amplitude drops (vertical axis) is defined as f = 1 / (n-1) T, as shown in FIG. 5B.

In this regard, the frequency diversity effect differs from the multi-user diversity effect in terms of frequency variations of the appropriate transfer functions thereof; thus, in order to produce the frequency diversity effect, the maximum delay time (n-1) T is set as (n-1) T> / 1Fc. where Fc denotes a frequency bandwidth of a fragmented encoding, which is a basic region secured by the user for communication and defined with respect to the frequency axis and the time axis, thus creating an environment that easily produces the effect of frequency diversity.

In contrast, in order to produce the multi-user diversity effect, the maximum delay time (n-1) T is set as (n-1) T <1 / Fc, where Fc denotes a frequency bandwidth of fragmented encoding, thus creating an environment that easily produces the effect of multi-user diversity. In the following description, an inequality of (n-1) T <1 / Fc comprises (n-1) T = 0. In the following description, the delay times applied to the transmitting antennas are each represented as (n-1) multiples of T where T is assumed to be a constant, while it is possible to change T with respect to each of the antennas. of transmission. In order to produce the multi-user diversity effect, it is possible to reduce the maximum delay time by reducing the number of transmitting antennas used for transmission instead of setting the inequality of (n-1) T <1 / Fc.

As described above, in response to a determination of whether the transmission signals undergo frequency diversity transmission or multi-user diversity transmission (i.e., (n-1) T> 1 / F_c o (In) T <1 / Fc it is possible to produce the frequency diversity effect or the multi-user diversity effect without being affected by the propagation path conditions.

As shown in FIG. 16A, with respect to the first user who carries out communication via the communication slot s1 that occurs when connecting consecutive fragmented encodings in the frequency direction and the user to whom the discontinuous fragmented encodings are assigned such as the ninth user to whom the communication bands s13, s16, s20 and s23 are assigned, the bandwidth BW (that is, BW = 5F for the first user, and BW = 3F for the ninth user) of a communication slot instantly assigned to the user defines the basis for the realization of frequency diversity effect; in this way, by setting the maximum delay time as (n-1) T> I / BW, it is possible to produce the frequency diversity effect.

For example, the delay time T is set such that the maximum delay time (n-1) T between the transmitting antennas falls within a range of (n-1) T> I / BW when the signal of communication indicates the effect of frequency diversity, while the delay time T is set in such a way that the maximum delay time (n-1) T between the transmitting antennas falls within a range of (n-1) T <1 / Fc. Although no illustration is provided, when a subcarrier partially included in the plural fragmented encodings is allocated to a certain user, the BW bandwidth of a communication slot allocated to the user represents a frequency difference between the subcarrier, which are deviated by one of the other maximum within sub-carriers instantly assigned to the user.

ES 2 380 451 T3

The determination from which signals are subjected to frequency diversity transmission or multi-user diversity transmission can be changed based on the types of transmission signals (eg, pilot signals, control signals, broadcast / multicast signals, and the like. ), moving the speeds of the wireless receiving devices (where the frequency diversity is selected in case of a high speed of movement, and multi-user diversity is selected in case of low speed of movement), and the like.

FIGS. 6A to 6C are explanatory drawings for the situation in which the same signal having no delay time is transmitted via plural antennas of a wireless transmission device 8. Suppose, as shown in Fig. 6A, the device Wireless transmission antenna 8 is equipped with plural transmission antennas (three), which are arranged in parallel and have no directivity in the horizontal direction. Due to the occurrence of the lobes e11 and e12 indicated by ellipses shown in FIG. 6A, there is an address that has a wireless receiving device 9 that receives the reception signals with a high reception level with respect to all the bands of frequency (see FIG. 6B) and an address that has a wireless reception device 10 that receives reception signals with a low reception level with respect to all frequency bands (see FIG.6C).

FIGS. 7A to 7C are explanatory drawings in which the same signal is applied with different delay times respectively and is then transmitted via the plural transmitting antennas of the wireless transmitting device 8. Suppose that the wireless transmitting device 8 It is equipped with plural transmitting antennas (three) having no directivity, which are arranged in parallel. Due to the occurrence of lobes e21 to e26 in narrow bands, a frequency band occurs that ensures a high reception level and a frequency band that ensures a low reception level within the reception signals, while a reception level average remains substantially constant regardless of indications; in this way, it is possible to ensure substantially the same quality with respect to both the reception level of a wireless reception device 9 (see FIG. 7B) and the reception level of a wireless reception device 10 (see FIG. 7C). Therefore, the method, in which the signals with different delay times are applied and transmitted via the transmitting antennas of the wireless transmission device 8, compensates for the drawbacks of the methods, which are described with reference to FIGS. 6A to 6C and in which the same signal is transmitted via plural transmitting antennas.

(Second Embodiment)

A second embodiment of the present invention will be described with respect to the constitution of a wireless transmission device. Similar to the wireless transmission device 1 of the first embodiment (see FIG. 1), the wireless transmission device of the present embodiment has plural transmission antennas.

The wireless transmission device described below is a wireless transmission device in which different delay times are applied to transmitting antennas to transmit signals, where the delay times are imparted to a region of time.

The signals applied with different delay times relative to the transmitting antennas are described in the present embodiment in such a way that a signal, which is delayed T with respect to a transmitting signal actually transmitted from a first transmitting antenna, is transmits via a second transmitting antenna, and similarly, an nth transmitting antenna transmits a signal delayed by (n-1) T.

FIG. 8 is a block diagram showing the configuration of a physical layer of the wireless transmission device of the present embodiment. The physical layer represents a portion of the wireless transmission device configuration, in particular, that receives transmission signals, performs signal processing in a wireless transmittable form, and sends signals to a wireless frequency converter to effect conversion. frequency in wireless frequencies.

As shown in FIG. 8, the physical layer includes user-dependent signal processors 11a and 11b and antenna-dependent signal processors 12-1, 12-2, and 12-3. User-dependent signal processor 11a (similar to user-dependent signal processor 11b) performs signal processing on signals to be transmitted to a wireless receiving device used by each user. The antenna-dependent signal processor 12-1 (similar to the antenna-dependent signal processors 12-2 and 12-3) performs signal processing with respect to each of the transmitting antennas.

The user-dependent signal processor 11a includes an error-correcting encoding section 13, a modulator 14, a sub-carrier mapping section 15, an IFFT (Fast Inverse Fourier Transform) section 16, a parallel-conversion section. series 17, a section that imparts GI (Guard Interval) 18, some sections that impart delay 19-1, 19-2, and 19-3.

ES 2 380 451 T3

The error-correcting coding section 13 performs the error-correcting coding on the transmission signals. Modulator 14 performs modulation processing such as QPSK (Quadrature Phase Shift Keying) and 16 QAM (Quadrature Amplitude Modulation) at the output of the coding section that corrects error 13.

The subcarrier allocation section 15 assigns the output of modulator 14 to the appropriate subcarriers based on the subcarrier allocation information indicated by a high order layer. IFFT section 16 performs frequency-time conversion at the output of subcarrier allocation section 15.

The parallel-series conversion section 17 performs parallel-series conversion at the output of the IFFT section 16. The GI-imparting section 18 imparts guard intervals at the output of the parallel-series conversion section 17. The delay-imparting section 19-1 imparts different delays to the output of the section imparted by GI 18 relative to the transmit antennas.

The outputs of delay imparting sections 19-1 through 19-3 are supplied to antenna dependent signal processors 12-1, 12-2, and 12-3 respectively. Sections imparting delay 19-1 through 19-3 provide different delays (for example 0, S, and 2s) Here, S = T / (sample time). The sample time represents a minimum time interval between the digital signals, which are processed in the GI imparting section 18, the delay imparting sections 19 -1 to 19-3, and the mixing section 20.

Therefore, imparting a delay of S samples in the delay imparting sections 19-1 through 19-3 indicates that the time delay T is imparted at the output terminal of the D / A converter 22. The user dependent signal processor 11a is used in some chunky encoding; in other words, it is used in a frequency diversity region or in a multi-user diversity region; in this way, it receives a communication signal (frequency div / multi-user div communication signal) that directs the use of the frequency diversity region or the multi-user diversity region from the high-order layer that controls the physical layer . The user-dependent signal processor 11a selectively uses the frequency diversity region or the multi-user diversity region based on the communication signal, thus operating to change the delay time T.

The user-dependent signal processor 11b has a constitution similar to that of the user-dependent signal processor 11a, but differs from it in terms of the user thereof.

The antenna dependent signal processor 12-1 includes a mixing section 20, a filter 21, and a D / A (Digital / Analog) converter 22.

The mixing section 20 adds together and mixes more to the signals, which are output to the antenna-dependent signal processor 12-1 from the user-dependent signal processors 11a and 11b. The filter 21 extracts the signals of the prescribed band only from the output of the mixing section 20. The D / A converter 22 performs a digital-to-analog conversion at the output of the filter 21.

Both the antenna-dependent signal processors 12-2 and 12-3 have similar constitution to that of the antenna-dependent signal processor 12-1. The output of the antenna-dependent signal processor 12-1 is sent to a wireless frequency converter (not shown) to effect frequency conversion to wireless frequencies, of which this is supplied to plural transmitting antennas (three), transmitting so wireless signals.

(Third Realization)

A third embodiment of the present invention will be described with respect to another constitution of a wireless transmission device. The wireless transmission device of the present embodiment is a wireless transmission device that applies different delay times to transmitting antennas in order to transmit signals, wherein the delay times are applied with respect to the time region.

The wireless transmission device handles signals, which are applied with guard intervals with respect to the symbols (valid symbol intervals) of the transmission, signals. The applied signals with different delay times with respect to the transmitting antennas are focused on the prescribed portions (valid symbol interval) of the transmitting signals, which are in fact transmitted via a first transmitting antenna except for the intervals guard; in this way, only the valid symbol slots are delayed by T and are then transmitted via a second transmitting antenna; similarly, only valid symbol intervals are delayed by (n-1) T and are then transmitted via an nth transmitting antenna.

ES 2 380 451 T3

Therefore, the transmitting antennas transmit signals, which are applied with guard intervals corresponding to the valid symbol intervals; thus, unlike the second embodiment, no symbol time deviation times occur at the transmitting antennas. A method that imparts the lag time described above is referred to as "running lag impact" in the following description. By way of processing to impart circulating delay, the lock delay waves are advantageous compared to the second embodiment which describes that the delay times are applied to the transmitting antennas.

FIGS. 9A and 9B show examples of signals that are produced by imparting flow delays to the transmission signals in the present embodiment. FIG. 9A shows a signal transmitted via a first antenna, and FIG. 9B shows a signal transmitted via a second antenna. FIGS. 9A and 9B show that the valid symbol interval corresponds to four samples and the guard interval corresponds to one sample, where relative to the valid symbol interval, a sample lags behind in the second antenna compared to the first antenna. . No symbol time deviation occurs in symbol units with respect to the first antenna and the second antenna; thus, even when the flow delay is applied to it, it is recognized that a guard interval effect to intensify against interferences with adjacent symbols is maintained.

FIG.10 is a block diagram showing the physical layer configuration of the wireless transmission device according to the present embodiment. As shown in the figure, the physical layer includes user-dependent signal processors 111a and 111b and antenna-dependent signal processors 1121, 112-2, and 112-3.

User-dependent signal processor 111a (similar to user-dependent signal processor 111b) performs signal processing in relation to a wireless transmission device for each user. The antenna-dependent signal processor 112-1 (similar to the antenna-dependent signal processors 112-2 and 112-3) performs signal processing relative to the prescribed transmit antenna.

The constitution of the user-dependent signal processor 111a is substantially identical to the constitution of the user-dependent signal processor 11a (FIG. 8) described in the second embodiment, while a difference between these rests in that the GI-imparting section 18 does not is supplied, and the sections that impart circulating delay 119-1 through 119-3 are supplied in place of the section that impart delay 19-1 through 19-3.

The user dependent signal processor 111a shares the same functions as the error-correcting encoding section 13, modulator 14, subcarrier allocation section 15, IFFT section 16, and parallel-serial conversion section 17 incorporated in the second embodiment (see FIG. 8); thus, they are designated by the same reference numerals, and the description thereof is omitted.

The circulating delay imparting section 119-1 imparts different circulating delays at the output of the parallel-series conversion section 17 relative to the transmitting antennas. The outputs of the circulating delay imparting sections 119-1 through 119-3 are supplied to antenna dependent signal processors 112-1, 112-2, and 112-3. In addition to the sections that impart circulating delay 119-1 to 119-3 they provide different delays (for example 0, S, and 2S). Where, S = T / (sample time).

The user dependent signal processor 11a is used in some chunky encoding. Because it is used in the frequency diversity region or the multi-user diversity region, it receives a communication signal that directs the use of the frequency diversity region or the multi-user diversity region by means of the high order controlling the physical layer. The user-dependent signal processor 11a selectively uses the frequency diversity region or the multi-user diversity region based on the communication signal, thus operating to change the delay time T.

The user-dependent signal processor 111b has a similar constitution as the user-dependent signal processor 11a, but differs from it in terms of the user.

FIG. 11 is an illustration to explain the circulating lag imparting section 119-1, which is described as an example of the present embodiment. The circulating delay imparting section 119-1 is equipped with a memory 110. In order to impart a circulating lag of k samples, the data D11 is input sequentially in an address k + 1 to the address n of memories 110 (i.e. 1, 2, 3 ..., (nk) are input) ; then a subsequence of the D11 data is entered at address 1 (i.e. (nk-4-1), (n-k + 2), (nk + 3) ..., n) are entered), thus entering n samples of the D11 data. Then, by sequentially outputting from address 1 of memory 110, it is possible to output data D12, which occurs by imparting a circulating delay of each samples to the n samples of data D11, (i.e. (n-k + 1 ), (n-k + 2), (n-k + 3), n, 1,2, (nk)).

ES 2 380 451 T3

FIG. 9A shows an example of the signal, which is produced by imparting a circulating delay of a zero sample to the data of four samples, and FIG. 9 shows an example of the signal, which is produced by imparting a circulating delay of a sample.

The constitution of the antenna-dependent signal processor 112-1 (FIG. 10) is substantially identical to the constitution of the antenna-dependent signal processor 12-1 (FIG. 8) described in the second embodiment, wherein a difference between these it rests that the GI 18 imparting section is supplied for this.

The functions of the mixing section 20, the GI imparting section 18, the filter 21, and the D / A converter 22 included in the antenna-dependent signal processor 112-1 are identical to those incorporated in the second embodiment (FIG .8); thus, they are designated by the same reference numeral, and the description thereof is omitted.

Both the antenna dependent signal processor 112-2 and 112-3 have a constitution similar to that of the antenna dependent signal processor 112-1. The outputs of the antenna dependent signal processors 112-1, 112-2 and 112-3 are supplied with a wireless frequency converter (not shown) to effect the frequency conversion and wireless frequencies, of which they are supplied to plural transmitting antennas (three), thus transmitting wireless signals.

(Fourth Realization)

A fourth embodiment of the present invention will be described with reference to the constitution of another wireless transmission device. The wireless transmission device of the present embodiment is a wireless transmission device in which different delay times are applied to transmitting antennas in order to transmit signals, where the delay times are applied with respect to the frequency region. .

The present embodiment deals with signals that are applied with the guard intervals with respect to the symbols (valid d symbol intervals) of the transmission signals, where similar to the wireless transmission device of the third embodiment (FIG.10 ), traffic delays are imparted to them.

FIG. 12 is a block diagram showing the physical layer configuration of the wireless transmission device of the present embodiment. As shown in the figure, the physical layer includes user-dependent signal processors 211a and 211b, a subcarrier allocation section 215, and antenna-dependent signal processors 212-1, 212-2, and 212-3.

User dependent signal processor 211 a (similar to user dependent signal processor 211b) performs signal processing with respect to the wireless transmission device used by each user. The subcarrier allocation section 215 allocates the output of the user dependent signal processor 211 to each subcarrier. User-dependent signal processor 232-1 (similar to antenna-dependent signal processors 212-2 and 112-3) performs signal processing relative to a prescribed antenna.

Each of the user-dependent signal processors 211a and 211b includes an error-correcting coding section 13 and a modulator 14. The functions of the error-correcting coding section 13 and modulator 14 are substantially identical to those described. in the second embodiment (FIG.8); thus, they are designated by the same reference numerals, and the description thereof is omitted. The outputs of the user dependent signal processors 211a and 211b are assigned with appropriate subcarriers in the subcarrier assignment section 215 based on the subcarrier assignment information indicated by the high order layer; then, they are supplied to the antenna dependent signal processors 212-1, 212-2, and 212-3.

The antenna dependent signal processor 212-1 includes a phase rotation section 219. An IFFT section 176, a parallel-series conversion section 17, a GI imparting section 18, a filter 21, and a D / D converter. A 22. The functions of the IFFT section 16, the parallel-series conversion section 17, the GI imparting section 18, the filter 21, and the D / A converter 22 are identical to those of the second embodiment (FIG. 8); thus, they are designated by the same reference numerals, and the description thereof is omitted.

The phase rotation section 219 rotates the output of the subcarrier allocation section 215 in phase by 0m with respect to each subcarrier and then outputs this to the IFFT section 16. Both the antenna-dependent signal processors 212- 2 and 212-3 have a constitution similar to the constitution of the antenna dependent signal processor 212-1.

The output of the antenna dependent signal processors 212-1, 212-2, and 212-3 are supplied to a wireless frequency converter (not shown) to effect frequency conversion into frequencies.

ES 2 380 451 T3 wireless, of which are supplied to the plural transmitting antennas, thus omitting the wireless signals.

In the present embodiment, the rotation of fas® m in the phase rotation section 219 is set as 0m = 2nfm. (N-1) T. Here, fm denotes a frequency difference between the 0-th subcarrier and the m-th subcarrier, where it is defined as fm = m / t, such that (n-1) T represents a circulating delay time on the nth antenna relative to the first antenna. Ts represents a valid symbol time for an OFDM symbol.

A delay-imparting section 220 is constituted by phase rotation section 219 and IFFT section 16. The phase rotation applied to phase rotation section 219 is subjected to frequency-time conversion in IFFT section 16, of such that this is considered as a time delay at the output of the IFFT section

16.

The user-dependent signal processor 211a is used in a certain fragmented coding, which is used in the frequency diversity region or the multi-user diversity region, where it receives a communication signal indicating whether the use of the frequency region the frequency diversity or multi-user diversity region of the high order layer controls the physical layer. Based on the communication signal, the user-dependent signal, the processor 211a selectively uses the frequency diversity region or the multi-user diversity region, thus operating to change the delay time T.

The wireless transmission devices according to the second to fourth embodiments are each equipped with a delay-imparting section to delay the transmitted signals supplied to n (n is an integer of two or more) transmit antennas by a maximum delay time. (n-1) T according to the delay time T appropriate to a communication signal that indicates whether the transmission signals are subjected to frequency diversity transmission or transmission of multi-user diversity.

Thus, by appropriately setting the delay time T based on determining whether the transmission signals are subjected to frequency diversity transmission or multi-user diversity transmission, it is possible to produce the effect of frequency diversity and the effect of multi-user diversity without being affected by the conditions of the propagation paths.

(Fifth Realization)

A fifth embodiment of the present invention will be described with respect to the constitution of another transmission device. The wireless transmission device of the present embodiment is a wireless transmission device that applies different delay times to the signals, which are then transmitted via transmitting antennas, in the region of frequency diversity while applying appropriate weights to the antennas. transmission in order to effect directivity control in the multi-user diversity region, where delay times are applied and directivity control is performed in the frequency region.

The present embodiment deals with signals that are produced by imparting guard intervals to the transmission signals with respect to symbols (valid symbol intervals), where, similar to the third and fourth embodiments, it imparts circulating delays to the signals.

FIG. 13 is a block diagram showing the configuration of a physical layer of the wireless transmission device of the present embodiment. As shown in the figure, the physical layer includes user dependent signal processors 211a and 211b, a subcarrier allocation section 215, a weight calculation section 310, and antenna dependent signal processors 312-1, 312 -2, and 312-3. The constitutions of the user dependent signal processor 211a and the subcarrier allocation section 215 are similar to those of the fourth embodiment (FIG. 12); thus, they are designated by the same reference numerals, and the description thereof is omitted.

The antenna-dependent signal processor 312-1, (similar to the antenna-dependent signal processors 312-2 and 312-3) performs signal processing with respect to the prescribed transmit antenna.

The antenna dependent signal processor 312-1 includes a weighted multiplier section 312, an IFFT section 16, a parallel-series conversion section 17, a GI imparting section 18, a filter 21, and a D / A converter 22. . The functions of the IFFT section 16, the serial-parallel conversion section 17, the GI imparting section 18, the filter section 21, and the D / A converter 22 are identical to those of the first embodiment; thus, they are designated by the same reference numerals, and the description thereof is omitted.

ES 2 380 451 T3

[0057] The weighted multiplication section 319 performs the weighted multiplication at the output of the subcarrier allocation section 215 with respect to the subcarriers, and outputs the results to the IFFT section 16. Both the antenna-dependent signal processors 312-2, and 312-3 have a constitution similar to that of the antenna dependent signal processor 312-1.

The output of antenna dependent signal processors 312-1, 312-2, 312-3 are supplied to a wireless frequency converter (not shown) to effect frequency conversion to wireless frequencies, of which the results are supplied to transmitting antennas, thus pulling out wireless signals.

A specific subcarrier is used in some chunky encoding. That is, it is used in the frequency diversity region or in the multi-user diversity region. The weighted multiplication section 319 is informed of the determination whether to use the frequency diversity region or the multi-user diversity region of the high-order layer controlling the physical layer, based on which the rotation m is entered with in order to apply different delay times to antennas in the frequency diversity region, while the multiplication using a weight Wm is carried out in order to effect directivity control in the multi-user diversity region.

A section that imparts delay and directivity control 320 is constituted by the weighted multiplication section 319 and the IFFT section 16. When phase rotation is introduced by means of a weighted multiplication section 319, it is considered as a time in the output of IFFT section 16 because IFFT section 16 performs frequency-time conversion. On the other hand, when the weighted multiplication section performs multiplication using the weights Wm, the IFFT section 16 performs frequency-time conversion in such a way that the output to the IFFT section 16 output from the transmitting antenna is subjected to directivity control.

When the weighted multiplication section 319 rotates the phases S by m, similar to the fourth embodiment, it sets Sm = 2nfm. (N-1) T. Here, fm denotes a frequency difference between the 0-th subcarrier and the m-th subcarrier, where fm = m / Ts; and (n-1) T represents a circulating delay time in an nth antenna relative to the first antenna. Ts represents a valid symbol time for an OFDM symbol.

In order to carry out multiplication using the weight Wm, the next weight is set in order to carry out directivity control. Assuming a linear array of n antennas whose distance is half a wavelength of a carrier frequency, the weight Wm is calculated according to the following equation (1).

[Equation 1]

<img file="ES2380451T3_D0001.tif" />

The weight Wm represents a vector of a weight used in the weighted multiplication section 319, where in equation (1), the first and last terms describe the weights used in the first antennae.

In equation (1) expressing the weight Wm, n denotes the number of antennas, where in the present embodiment, n = 3; θ denotes a direction in which the main beam is directed; and k denotes an index between the frequency used for transmission and the frequency that is measured based on θ.

With respect to the direction of the main beam an average value produced by the wireless transmission device or a terminal of the counter communicator is supplied to the weight calculation expression 310, in which this is used for the calculation of the weight of Wm. Equation (1) represents an example of the calculation for the weight Wm that can be calculated via another method. The calculation methods related to Wm are described in "technical report rcs2004-229" (published by the Corporate Institute Electronic Information and Telecommunication in November, 2004) and the like.

The directivity control and delay imparting section 320 imparts a maximum delay time delay (n1) T or less between the transmitting antennas when the communication signal indicates frequency diversity, while it performs multiplication to produce the weight Wm in order to effect directivity control when the communication signal indicates multi-user diversity.

ES 2 380 451 T3

As described in the first embodiment, the directivity control and delay imparting section 220 sets the delay time T such that the maximum delay time (n-1) T of the transmitting antennas falls within a range of (n-1) T&gt; 1 / fc when the communication signal indicates frequency diversity.

As described in the first embodiment, the section that imparts delay and directivity control 320 sets the delay time T such that the maximum delay time (n-1) T falls within the range of (n-1) T &gt; 1 / BW when the communication signal indicates frequency diversity.

The above-mentioned description teaches that the weighted multiplication section 319 of the section that imparts delay and directivity control 320 is instructed by the high-order layer that controls the physical layer to use the frequency diversity region or the multi-user diversity region. , based on which it applies a phase rotation θ _m in order to impart different delay times to the antennas in the frequency diversity region, while it performs multiplication to produce the weight Wm in order to effect directivity control in a multi-user diversity region; However, it is possible to use another method to utilize both the phase rotation θ m and the weight Wm in the multi-user diversity region such that as described in the fourth embodiment, the phase rotation) m is imparted with respect to both the frequency diversity region as the multi-user diversity region before the main beam direction θ occurs, and then directivity control is performed using the weight Wm after the main beam direction θ occurs in the multi-user diversity region. Similar to the fourth embodiment, the delay time T varies relative to θm according to the region of frequency diversity and the region of multi-user diversity. Thus, in the stage before the main beam direction occurs, it is possible to produce the same multi-user diversity effect as in the fourth embodiment, whereas after the main beam direction θ occurs, it is expected that a Greater multi-user diversity effect by strictly performing directivity control using Wm weight. Additionally, by using the physical layer configuration of the wireless transmission device shown in FIG. 13 instead of the fourth embodiment, it is possible to effect an improvement of the characteristics due to directivity control by slightly increasing the constitution of the circuit.

As described above, the directivity control and delay imparting section 320 imparts a maximum delay time delay (n-1) T or less between the transmitting antennas when the communication signal indicates frequency diversity, while this imparts a delay of the maximum delay time (n-1) T or less between the transmitting antennas, or it performs multiplication to produce the weight Wm in order to effect directivity control when the communication signal indicates multi-user diversity.

The wireless transmission device that performs the aforementioned processing has the constitution shown in FIG. 13, where, when the communication signal indicates multi-user diversity, the section that imparts delay and directivity control imparts a delay to the maximum delay time (n-1) T or less between the transmitting antennas, or it performs a delay. multiplication to produce the weight Wm in order to effect directivity control.

As described in the first embodiment, the section that imparts delay and directivity control sets the delay time T in such a way that the maximum delay time (n-1) T between the transmitting antennas falls to a range of (n -1) T&gt; 1 / Fc when the communication signal indicates frequency diversity, while it sets the delay time T such that the maximum delay time falls within a range of (n-1) T &lt;1 / Fc when the communication signal indicates multi-user diversity such that a delay is applied between the transmitting antennas.

As described in the first embodiment, the section that imparts delay and directivity control sets the delay time T such that the maximum delay time (n-1) T between the transmitting antennas falls within a range of ( n-1) T&gt; 1 / BW when the communication signal indicates the frequency diversity.

The aforementioned second to fifth embodiments are described with respect to the case in which the number of users is two and the number of antennas is three, while the number of users and the number of antennas are not necessarily limited to these numbers.

In the aforementioned fourth to fifth embodiments, it is possible to transmit signals, which are subjected to multiplication using specific random codes dependent on antennas, sectors, and base stations, to the transmitting antennas.

(Sixth Realization)

The present embodiment will be described with respect to variations of the maximum delay times (n-1) T dependent on the physical channels. The aforementioned first to fifth embodiments are described under the assumption that a 1-to-1 communication is effected in relation to some fragmented encoding in

ES 2 380 451 T3 certain instant, where (n-1) T&gt; 1 / F_c is set to produce the frequency diversity effects, while (n-1) T &lt;1 / Fc is set to produce the multi-user diversity effect.

Normally, in communications other than a 1 to 1 communication, a signal known as pilot channels is transmitted to a wireless transmission device in order to estimate a propagation path; alternatively, a control channel is used to report various types of parameters prior to data communication. The present embodiment will be described with respect to the method of setting the maximum delay time (n-1) T on these physical channels.

UTRA &amp; OUTRAN evolved, examined in 3 GPP (Third Generation Partnership Project), DCPCH common pilot channels are supplied (Downlink Common Pilot Channel dedicated pilot channel DDPCH (Downlink Dedicated Pilot Channel), Link synchronization channels Downlink DSCH (Downlink Synchronization Channel, Common Control Channels DCCCH (Downlink Common Control Channel), downlink shared control signaling channels DSCSCH (Downlink Shared Control Channel), and multicast / broadcast channels (Multicast / Broadcast Channel).

The DCPCH common pilot channels correspond to CPICH pilot channels in W-CDMA (Broadband Code Division Multiple Access), which are used for the estimation of the conditions of the downlink propagation paths, the search for cells, and the measurement of propagation path losses in uplink transmission power control in AMCS (Adaptive Modulation and Coding Scheme).

Dedicated DDPCH pilot channels are used to transmit to individual mobile stations via transmitting antennas such as adaptive array antennas whose propagation paths (directivities) differ from those of shared path antennas; alternatively, they can be used for the purpose of reinforcing common shared DSPCH downlink pilot channels relative to mobile stations having poor reception qualities.

The downlink synchronization channels DSCH correspond to synchronization channels SCH in WCDMA, where they use for search of cells of mobile stations, "tireless" frames of OFDM signals (Orthogonal Frequency Division Multiplexing), time slots, intervals transmission time TTI (Transmission Time Interval), or OFDM symbol time synchronization.

DCCCH common control channels include common control information such as broadcast information (corresponding to BCH broadcast channels) corresponding to PCCPCH primary common control physical channels, S-CCPCH secondary common control physical channels, and signal indicator channels. PICH radio messaging in W-CDMA, packet radio messaging indicator PI information, (corresponding to PCH radio messaging channels) corresponding to packet calls, and downlink access information (corresponding to the FACH downlink access channels).

DSCSCH downlink shared control signaling channels correspond to HS-DSCH HS-SCCH connected shared control channels, DPCCH downlink dedicated control channels, AICH acquisition indicators included in HS high-speed physical downlink shared channels -PDSCH in HSPDA (High Speed ​​Downlink Packet Access), where they are shared by several mobile stations and are used for the transmission of the information (modulation methods, dispersion coding, etc.) that is necessary for the mobile stations to carry out demodulation in relation to the shared link channels HS-DSCH high-speed downstream, the information that is necessary for error-correcting decoding and HARQ processing, and wireless resource planning information (frequency, time).

DSDCH downlink shared data channels correspond to HS-DSCH high-speed downlink shared channels and DPDCH downlink dedicated data channels included in HS-PDSCH high-speed physical downlink shared channels in HSPDA, where they use for the transmission of packet data towards the mobile stations of higher order layers.

Multicast / broadcast channels are used to broadcast information signals.

The aforementioned physical channels of W-CDMA and HSDPA are described in "Tachikawa Keiji, W-CDMA Mobile Communication Method. ISBN4-62 1-04894-5 "and the like.

FIG. 14 and FIG. 15 are tables that describe the relationships between the maximum delay time (n-1) T between the transmitting antennas and the frequency bandwidth Fc of the fragmented encodings in relation to the

ES 2 380 451 T3 physical channels. As shown in the figures, it is preferable to set (n-1) T &lt;1 / Fc regardless of frequency diversity region and multi-user diversity region with respect to common pilot channels, common control channels, and dedicated control channels. It is preferable to set (n-1) T&gt; 1 / Fc regardless of the frequency diversity region of the multi-user diversity region with respect to the downlink sync channels.

With respect to dedicated pilot channels, it is preferable to set (n-1) T&gt; 1 / Fc in the frequency diversity region and to set (n-1) T &lt;1 / Fc, in the multi-user diversity region. Suppose that the dedicated pilot signals are transmitted via transmitting antennas, where the delay-imparting section for the delayed transmitting signals supplied to the n transmitting antennas by the maximum delay time (n1) T or less sets the time delay T such that the maximum delay time (n-1) T falls within a range of (n-1) T&gt; 1 / Fc when a communication signal, which indicates whether the fragmented encodings that include dedicated pilot channels are subjected to the transmission of frequency diversity or the transmission of multi-user diversity, indicate frequency diversity, while this establishes the delay time of T in order to effect control of effectiveness using the weights outputs from the weight calculation section or to define the maximum delay time (n-1) T as (n-1) T &lt;1 / Fc, when communication signals indicate multi-user diversity. Multicast / broadcast channels are used in the frequency diversity region only; thus, it is preferable to set (n-1) T&gt; 1 / Fc.

The reasons why the aforementioned configurations were carried out are that the common pilot channels are used for the notification of the signal intensities observed by the terminals, in this way, it is understandable that the delay times vary with respect to the fragmented encodings. , Although it is necessary for wireless transmission devices to know the signal strengths with respect to the fragmented encodings in the case of (n-1) T &lt;1 / Fc in order to effect multi-user diversity, in this way, it is preferable to set ( n-1) T &lt;1 / Fc so that the maximum delay time does not vary with respect to the fragmented encodings.

The dedicated pilot channels are used for calculations of the estimated values ​​of the propagation paths used for demodulation of the data signals. Therefore, it is preferable to effect communication by setting (n-1) T&gt; 1 / Fc in the frequency diversity region and by setting (n-1) T &lt;1 / Fc in the multi-user diversity region.

Downlink synchronization channels are used for frame synchronization, where estimation of propagation paths is not necessary, and it is preferable to ensure accurate reception in case of low reception power; thus, it is preferable to set (n-1) T&gt; 1 / Fc in order to produce the frequency diversity effect. In particular, there is a possibility that the same signal is transmitted using the same time and frequency via downlink synchronization channels via plural sectors and plural antennas included in a base station. Therefore, the signals with different delays with respect to the antennas are applied if they are transmitted via plural sectors and plural antennas included in a base station via downlink synchronization channels; thus, it is expected to produce a high frequency diversity effect, which is greater than the other physical channel.

Common control channels and dedicated control channels are presumed to use estimated propagation path values, which occur via common pilot channels; thus, it is preferable that they set the maximum delay time, which is identical to that of the common pilot channels, and be subjected to transmission.

However, it is preferable to ensure accurate reception on common control channels and dedicated control channels in case of low reception power; thus, it is preferable to produce the frequency diversity effect, wherein, in consideration of improving the reception performance of the control channels first, when the common control channels, the dedicated control channels, and the multicast channels / broadcast are included in the same fragmented coding, it is preferable to transmit via the common pilot channels by setting (n-1) T&gt; 1 / Fc, thus producing the effect of frequency diversity in the control channels.

When the same snippet coding is used for multi-user diversity, it is necessary to report on the signal strengths emerging in the present transmission suitable for multi-user diversity (communication low (n-1) T &lt;1 / Fc); thus, it is preferable to effect transmission when setting (n-1) T &lt;1 / Fc.

For this reason, it is possible to establish the relationship between the maximum delay time (n-1) T between the transmitting antennas and the frequency bandwidth Fc of the chunked coding, which is identical to the relationship shown in FIG. 15 with respect to each physical channel.

ES 2 380 451 T3

In order to produce the effect of frequency diversity, it is preferable to effect communication by setting (n1) T&gt; 1 / Fc.

The aforementioned embodiment was described in such a way that the maximum delay time falls within a range of (n-1) T &lt;1 / Fc in the multi-user diversity region, while, the wireless transmission device described in the fifth embodiment you can use the weight Wm that is produced by the weight calculation section 310, in the multi-user diversity region.

The aforementioned second to fifth embodiments are each described such that the wireless transmitting device having n transmitting antennas transmits applied signals with a prescribed delay time with respect to each of the n transmitting antennas; but this constitution is not restrictive. For example, when the wireless transmitting device having n transmitting antennas is selected using multi-user diversity, it is possible to transmit signals applied at the prescribed delay time T 'with respect to each of the transmitting antennas j (where j is a integer, j &lt;n) within the n transmitting antennas.

In the aforementioned constitution compared to the constitution in which the signals are transmitted using all the n transmitting antennas, a maximum delay time (j &lt;1) T 'applied to the signals transmitted via the transmitting antennas j decreases in order to further reduce the variations of the propagation paths; in this way, it is possible to produce a good multi-user diversity effect. In the case of j = 1, in particular, it is possible to reduce the circuit scale of the delay section.

The present embodiment is described under the precondition that the maximum delay time is set as (n-1) T&gt; 1 / Fc in order to produce the frequency diversity effect, while, as described for the first embodiment, when transmission is effected using a physical channel, which is allocated with chunky encodings resting on plural frequency directions, the BW bandwidth allocated to the physical channel forms the basis for producing the frequency diversity effect; in this way, it is possible to produce the frequency diversity effect by setting the maximum delay time to (n-1) T &lt;1BW.

By using the wireless transmission device, according to the above-mentioned embodiments of the present invention, which select the use of frequency diversity or multi-user diversity in transmitting signals from n transmitting antennas in order to vary the delay times applied to the signals transmitted via the n transmitting antennas based on the selection result; in this way, it is possible to produce the frequency diversity effect or the multi-user diversity effect without being affected by the conditions of the propagation paths.

In the above-mentioned embodiments, the programs that perform the functions of the error-correcting coding section 13, the modulator 14, the subcarrier assignment sections 15 and 215, the IFFT section 16, the parallel-serial conversion section 17 , the GI imparting section 18, the delay imparting sections 19-1 to 19-3, the circulating delay imparting sections 119-1 to 119-3, the mixing section 20, the filter 21, the D / A converter 22, the phase rotation section 219, in the weight calculation section 310, and the weighted multiplication section 319 shown in Figures 8, 10, 12 and 13 and stored on a computer-readable storage medium, such that programs stored on the storage medium are loaded into a computer system and then executed in order to control the wireless transmission device. Here, the computer system includes OS and equipment such as peripheral devices.

Computer-readable recording medium is referred to as floppy disks, magneto-optical disks, portable ROM media such as CD-ROM, and storage devices such as hard disks built into the computer system. Additionally, the computer-readable storage medium encompasses means for dynamically retaining programs in a short period of time, such as communication lines such as the Internet, networks, telephone lines used to transmit programs as well as volatile memories for retain programs for a prescribed period of time, which are incorporated into a computer system that serves as the server and the client. The aforementioned programs are designed to perform a part of the aforementioned functions; alternatively they are designed to perform the aforementioned functions by way of combination with programs that are stored in the computer system in advance.

The invention is described in detail by way of the embodiments with reference to the drawings, where the detailed constitution thereof is not necessarily limited to the embodiments; thus, it encompasses designs that do not deviate from the spirit of this invention.

ES 2 380 451 T3

Industrial application

The present invention is applicable to wireless transmission devices and wireless transmission method, which transmit signals to wireless reception devices through the use of plural transmission antennas, wherein the delay times are appropriately set based on determining whether the transmission signals are subjected to frequency diversity transmission or multi-user diversity transmission; in this way, it is possible to produce frequency diversity effects and multi-user diversity effects without being affected by propagation path conditions.

Description of the reference numerals

<td> 1</td><td>Wireless transmission device</td>

<td> 2-4</td><td>transmitting antenna</td>

<td> 5, 6</td><td>delay</td>

<td> 7, 8,</td><td>9, 10 wireless receiving device</td>

<td>11a,</td><td>11b, 111a, 111b, 211a, 211b, user dependent signal processor</td>

<td> 12-1</td><td>, 12-2, 12-3, 112-1, a 112-3, 212, -1, a 212-3, 312-1, a 312-3 antenna dependent signal processor</td>

<td> 13</td><td>coding section that fixes the bug</td>

<td> 14</td><td>modulator</td>

15, 215 sub-carrier assignment section

<td> 16</td><td>IFFT section</td>

<td> 17</td><td>parallel-series converter</td>

<td> 18</td><td>GI teaching section</td>

<td> 19-1</td><td>to 19-3 section that imparts delay</td>

119-1 to 119-3 section that imparts circulating delay

<td> 20</td><td>mixer</td>

<td> 21</td><td>filter</td>

<td> 22</td><td>D / A converter</td>

<td> 110</td><td>memory</td>

<td> 219</td><td>phase rotation section</td>

<td> 220</td><td>section imparting delay</td>

<td> 310</td><td>weight calculation section</td>

<td> 319</td><td>weighted multiplication section</td>

<td> 320</td><td>section imparting delay and directivity control</td>