Transmission control method in wireless communication system

FIELD OF THE INVENTION

The present invention generally relates to wireless transmission methods and, in particular, to transmission control methods adapted to a transmission system in which signals are transmitted using antennas using slots assigned to fragments divided in the frequency / time domain due to frequency diversity and multi-user diversity .

This application claims priority for Japanese Patent Application No. 2005-253194, filed in Japan on September 1, 2005, and Japanese Patent Application No. 2005-367860, December 21, 2005, the contents of which are incorporated herein by reference.

State of the art

Recently, methods have been proposed adapted mainly to multi-carrier transmission systems in which a plurality of blocks are allocated along the frequency and time axes and which perform scheduling on signals transmitted to users from wireless transmission devices by units (units) of blocks. In the materials of this application, the areas that are assigned to users for communication and which are determined by the frequency and time axes are indicated as destination slots, and the blocks serving as the basis for determining the destination slots are indicated as fragments.

The above proposes methods in which, in order to transmit broadcast signals, multicast signals, and control signals, blocks whose ranges are extended in the direction of the frequency axis are defined in order to create frequency diversity effects, thereby reducing errors regardless of small reception power. In addition, methods are proposed in which, in order to transmit unicast signals in a one-to-one communication between wireless transmission devices and wireless reception devices, blocks are defined whose ranges are reduced in the direction of the frequency axis in order to create multi-user diversity effects, such thus improving reception power in wireless reception devices.

FIG. 16A and 16B show a relative arrangement with respect to signals transmitted from a wireless transmission device to a wireless reception device in time (horizontal axis) and frequency (vertical axis). In FIG. 16A, the horizontal axis represents time, and the vertical axis represents frequency. Gaps from 1₁ by b, transmission times are given along the time axis. Here, the same time duration is given to intervals from 1₁ by b time, respectively. Frequencies from ί to £₅ gears are set along the frequency axis. Here is the same range of E_from frequencies set for frequencies with ί₁ by ί₅. With reference to gaps from 1₁ by b, transmission time and frequency from ί to ί₅ transmission, given fifteen fragments from Κι to K₁₅as shown in FIG. 16A.

In addition, five fragments from поι to K₅ connected as shown in FIG. 16B, and then equally divided into six time intervals along the time axis, thus defining slots with 8₁ 8 each₆ communication, each of which has a duration of 1₁/ 6 and a frequency range of 5ί1. Slots 8₁ and 8₄ connections are assigned to the first user; slots 8₂ and 8₅ communications are assigned to the second user; and slots 8₃ and 8₆communications assigned to the third user. This makes it possible for the first to third users to receive frequency diversity effects.

Then fragment K₁₀ assigned to fourth user as slot 8₁₁ communication. Fragments K₇, K₈ and K₉ connected to form slots with 8₈ 8 each₁₀ communication, each of which has a temporary duration of 1₂ and frequency range of 3ί₁, and which are assigned to the fifth user. In addition, fragment K6 is assigned to the sixth user as communication slot 87. This enables the fourth to sixth users to receive multi-user diversity effects, and enables the fifth user to receive frequency diversity effect.

In addition, fragment K₁₁ assigned to sixth user as slot 8₁₂ communication. This enables this user to receive multi-user diversity effect. In addition, fragments of K₁₃ and K₁₅ assigned to the eighth user as slots 8₁₉ and 8₂₆ communication. This enables this user to receive multi-user diversity effect.

In addition, two fragments of K₁₂ and K₁₄ equally divided into six slots, thus forming slots with 8₁₃ 8 each₁₈ and from 8₂₀ 8 each₂₅. Slots 8₁₃ , 8₁₆, 8₂₀ and 8₂₃ communications assigned to the ninth user; slots 8₁₄, 8₁₇, 8₂₁ and 8₂₄ communications assigned to the tenth user; and slots 8₁₅, 8₁₈, 8₂₂ and 8₂₅ communications assigned to the eleventh user. This makes it possible for users from the ninth to eleventh to individually obtain frequency diversity effects.

Non-Patent Document 1. Article in 3SRP, K.1-050249, Eo ^ pipk Mi1br1e Asse88 8sheeshe Esokeb ITKA (Downlink multiple access scheme for developed ITKA), [Sampling on August 17, 2005], Internet (ICB: yr: //yr.3drr.ogd/ Т8С_КАЫ / ^ С1_КЕ1 / Т8СК1_40Ы8 / бос8 / К1050249.ζίρ).

Non-Patent Document 2. Article in 3SRP, K1-050590, P11u8yu1 Syapie18 apb MiShr1ekhtd sh Esokeb ITKA Oo \ up1shk (Physical channels and downlink multiplexing developed by ITKA), [Sampling on August 17, 2005], Internet (υК ^: yρ : //yρ.3dρρ.о^д/Т8С_КАN/^С1_К^1/К1_Аб_Ηос8/^ТЕ_АΗ_^й 05 / ^ oc8 / К1-050590.ζ ^ ρ).

- 1 014591

SUMMARY OF THE INVENTION

The tasks solved by the invention

In order to obtain frequency diversity effects in the aforementioned conventionally known methods, it is necessary to increase the expansion coefficients or reduce the coding coefficients in error correction coding in response to changes in the frequencies of transfer functions in the propagation paths.

FIG. 17A and 17B, 18A and 18B are graphs showing delay profiles and transfer functions of signals that propagate through multiple propagation paths having different delay times in order to reach a wireless reception device.

FIG. 17A and 18A show delay profiles showing transmission signals that propagate through multiple propagation paths in order to reach a wireless reception apparatus in time (horizontal axis) and power (vertical axis). FIG. 17B and 18B show transfer functions for performing frequency conversion over delay profiles with respect to frequency (horizontal axis) and power (vertical axis).

FIG. 17A shows the appearance of six delay waveforms ν11 through ν16, and FIG. 18A shows the appearance of three waveforms ν21 through ν23 of delay signals. They differ from each other in maximum times 1₁ and 1₂ delays.

When the maximum delay time 11 is long, as shown in FIG. 17A and 17B, that is, when relatively fast frequency changes occur (fast power changes in the frequency direction) in the transfer function, it is intended to create an adequate frequency diversity effect regardless of the small expansion coefficient and high codingcoefficient in error correction coding. However, when the maximum delay time 12 is small, as shown in FIG. 18A and 18B, that is, when relatively moderate frequency changes occur in the transfer function, it is not intended to create an adequate frequency diversity effect when the expansion coefficient is small and the coding coefficient in error correction coding is high; hence, it is necessary to increase the expansion coefficient and lower the coding coefficient in error correction coding.

Ό1 and Ό2 in FIG. 17B and FIG. 18B show signals, i.e., data. That is, in FIG. 17B, ​​the spreading coefficient of the spread spectrum technology is set to 4 as regards data Ό1 and Ό2, thus assigning four subcarriers with a₁₁ by a₁₄ given Ό1. Similarly, four subcarriers with a₁₅ by a₁₈ assigned to data Ό2. In this case, the transfer function has fast frequency changes; hence the receiving power of the subcarrier a₁₃ with respect to the data, Ό1 decreases markedly, so that the reception power of the subcarrier a₁₆ regarding data Ό2. Therefore, no reception failures occur according to Ό1 and Ό2.

In FIG. 18B, the expansion coefficient is set to 8 in order to designate eight subcarriers with a₂₁ by a₂₈ given Ό1. In this case, the transfer function has slow frequency changes, so that the receiving power of the subcarrier a₂₄ decreases markedly, and the reception power of subcarriers a₂₃ and a₂₅ slightly decreases, while the data expansion coefficient is increased compared with the case of FIG. 17B, ​​so no reception failure occurs according to Ό1. The above values ​​of the expansion coefficients are described for convenience and are not necessarily limited.

The present invention has been made in view of the above circumstances, and it is an object of the invention to provide a wireless transmission apparatus and a wireless transmission method that can produce an adequate frequency diversity effect without controlling the spreading coefficient and coding coefficient in error correction coding on the wireless side transmission.

Means for solving the problem

The present invention is directed to a transmission control method adapted to a transmission system in which slots are assigned to fragments separated in a frequency domain and a time domain. In this case, the transmission signals are delayed before being fed to a plurality of transmission antennas so that the maximum delay time is either set to a first value less than 1 / P_from, or to a second value greater than 1 / P_from (where P_from denotes the bandwidth of each fragment). A determination is made as to whether or not delay control is applied depending on the physical channels.

In the above, delay control is applied to a data channel. In addition, the dedicated pilot channel is controlled with the same maximum delay time as in the data channel corresponding to it.

Result of invention

In the present invention, transmission signals are delayed before being fed to a plurality of transmission antennas, such that the maximum delay time is set either to a first value less than 1 / P_from, or to a second value greater than 1 / P_from (where P_from denotes the bandwidth of each fragment). A determination is made whether or not delay control is applied depending

- 2014591 bridges from physical channels. Additionally, delay control is applied to the data channel. In addition, the dedicated pilot channel is controlled with the same maximum delay time as in the data channel corresponding to it.

Since the time delay is suitably controlled in the data channels depending on the physical channels, it is possible to create frequency diversity effects and multi-user diversity effects without being affected by propagation path conditions.

Brief Description of the Drawings

FIG. 1 is a schematic illustration showing that signals transmitted by a wireless transmission apparatus according to a first embodiment of the present invention are propagated through multiple propagation paths in order to reach a wireless reception apparatus.

FIG. 2A is a graph showing a delay profile applied to signals that propagate through multiple propagation paths having different delay times in order to reach a wireless reception device.

FIG. 2B is a graph showing a transfer function that is created by performing a frequency conversion on the delay profile shown in FIG. 2A.

FIG. ZA is a graph showing another delay profile applied to signals that propagate through multiple propagation paths having different delay times in order to reach a wireless reception device.

FIG. 3B is a graph showing the transfer function of a wireless reception device that is created by performing frequency conversion on the delay profile shown in FIG. PER.

FIG. 3C is a graph showing the transfer function of yet another wireless reception device located at a different location, which is created by performing frequency conversion on the delay profile shown in FIG. PER.

FIG. 4A is a graph showing a maximum delay time (n-1) T in the delay profile.

FIG. 4B is a graph showing the relationship between the maximum delay time (n − 1) T shown in FIG. 4A, and frequency changes.

FIG. 5 A is a graph showing yet another maximum delay time (n-1) T in the delay profile.

FIG. 5B is a graph showing the relationship between the maximum delay time (n − 1) T shown in FIG. 5A, and frequency changes.

FIG. 6A is an illustration showing a wireless transmission / reception system in which the same signal having no delay time is transmitted through multiple antennas of a wireless transmission device.

FIG. 6B is a graph showing an example of a reception signal in the system shown in FIG. 6A.

FIG. 6C is a graph showing another example of a reception signal in the system shown in FIG. 6A.

FIG. 7A is an illustration showing a wireless transmission / reception system in which the same signal is applied with different delay times and then transmitted through multiple transmission antennas of a wireless transmission device.

FIG. 7B is a graph showing an example of a reception signal in the system shown in FIG. 7A.

FIG. 7C is a graph showing another example of a reception signal in the system shown in FIG. 7A.

FIG. 8 is a block diagram showing a physical layer configuration of a wireless transmission apparatus according to a second embodiment of the present invention.

FIG. 9A shows an example of a signal that is created by applying a delay to a transmission signal in accordance with a third embodiment of the present invention.

FIG. 9B shows another example of a signal that is created by applying a delay to a transmission signal in accordance with a third embodiment of the present invention.

FIG. 10 is a block diagram showing a physical layer configuration of a wireless transmission apparatus according to a third embodiment of the present invention.

FIG. 11 is an illustration for explaining the operation of a treatment delay setting section 119-1 in a third embodiment of the present invention.

FIG. 12 is a block diagram showing a physical layer configuration of a wireless transmission apparatus according to a fourth embodiment of the present invention.

FIG. 1H is a block diagram showing a physical layer configuration of a wireless transmission apparatus according to a fifth embodiment of the present invention.

FIG. 14 is a table showing the relationship between the maximum delay time (n − 1) T between transmission antennas and width P_from fragment frequency bands for each physical channel.

FIG. 15 is a table showing another relationship between the maximum delay time (n1) T between transmission antennas and width P_from fragment frequency bands for each physical

- Z 014591 to the channel.

FIG. 16A shows the relative position between signals that are transmitted from the wireless transmission device to the wireless reception device in time (horizontal axis) and frequency (vertical axis).

FIG. 16B is a graph showing communication slots that are assigned to the time-frequency space shown in FIG. 16A.

FIG. 17A is a graph showing a delay profile adapted to signals that propagate through multiple propagation paths having different delay times so as to reach a wireless reception device.

FIG. 17B is a graph showing a transfer function that is created by performing the frequency conversion on the delay profile shown in FIG. 17A.

FIG. 18A is a graph showing a delay profile adapted to signals that propagate through multiple propagation paths having different delay times so as to reach a wireless reception device.

FIG. 18B is a graph showing a transfer function that is created by performing a frequency conversion on the delay profile shown in FIG. 18 A.

Description of reference numbers

- wireless transmission device,

2-4 - transmission antenna,

5, 6 - delay

7, 8, 9, 10 - wireless reception device,

11a, 11b, 111a, 111b, 211a, 211b — a user-dependent signal processor,

12-1, 12-2, 12-3, from 112-1 to 112-3, from 212-1 to 212-3, from 312-1 to 312-3 - an antenna-dependent signal processor,

- error correction coding section,

- modulator

15, 215 - subcarrier assignment section,

- reverse FFT section,

- parallel-serial converter,

- task section 01, from 19-1 to 19-3 - delay task section, from 119-1 to 119-3 - circulation delay task section,

- mixer

- filter

- memory 110 digital-to-analog (E / L) converter,

219 - phase rotation section,

220 - delay setting section,

310 - section for calculating weights,

319 - weighted multiplication section,

320 - delay setting and directional control section.

Best Mode for Carrying Out the Invention

The first embodiment.

FIG. 1 is a schematic illustration showing that signals transmitted by a wireless transmission apparatus 1 are propagated through multiple propagation paths in order to reach a wireless reception apparatus 7. The wireless transmission device 1 contains numerous antennas from 2 to 4 transmission, which are used, respectively, with different times 0, T and 2T delay and from which signals are transmitted. The wireless reception device 7 receives signals transmitted from the wireless transmission device 1. FIG. 1 shows an example in which the wireless transmission device 1 is equipped with three transmission antennas 2 through 4.

Assume that multiple transmission antennas are transmission antennas installed in a wireless transmission device adapted at a base station for cell phones, while three types of transmission antennas are provided with respect to different sectors of the same base station and to different base stations . The following description is given regarding the situation to which they belong, for example, to the same sector, but it is possible to use a different structure. That is, η transmission antennas belong to different sectors, or η transmission antennas belong to different base stations.

In the delay drawing 5 and 6, a delay time T is applied, according to which, as described above, the delay time T is applied to the transmission antenna 3, and the delay time 2T is applied to the transmission antenna 4.

FIG. 2A and 2B show a delay profile and a transfer function for signals that propagate through multiple (three) propagation paths having different delay times in order to reach a wireless reception device. FIG. 2A shows a delay profile showing that transmission signals propagate through multiple propagation paths

- 4 014591, having different delay times, in order to reach the wireless reception device in time (horizontal axis) and power (vertical axis). As shown in FIG. 2A, the delay profile instantly has a maximum delay waveform of 2T + b_tah; hence, compared with the structure in which the same signal is transmitted through each transmission antenna, the maximum delay waveform becomes very large. Here b_tah represents the arrival time difference between the fast propagation path and the slow propagation path when radio waves arrive at the reception antenna from the transmission antenna.

FIG. 2B shows the transfer function that is created by performing the frequency conversion on the delay profile of FIG. 2A with respect to frequency (horizontal axis) and power (vertical axis). In the delay profile, an increase in the maximum time is 2T + b_tah Delay indicates rapid changes in the frequencies of the transfer function. Therefore, as shown in FIG. 2B (similar to FIG. 17B), data Ό1 and Ό2 are spread-spread encoded with a spreading factor of 4 and assigned sub-carriers to them. Preferably, the expansion coefficient or coding coefficient of the error-correcting coding will be adjusted in response to changes in the frequencies of the transfer function in the wireless transmission device 1, wherein the aforementioned method determines that the delay time 2T is recognized in advance by the wireless transmission device 1; from here it is possible to determine the expansion coefficient or coding coefficient of error correction coding, irrespective of changes in the frequencies of propagation paths.

In order to create multi-user diversity effects, it is preferable that the maximum time is 2T + b_tah the delay, which instantly appears in the delay profile, did not increase that much. The effects of multi-user diversity will be described with reference to FIG. 3A-3C.

FIG. 3A-3C show a delay profile and transfer functions for signals that propagate through multiple propagation paths having different delay times in order to reach a wireless reception device. FIG. 3A shows a delay profile adapted to transmission signals that propagate through multiple (three) propagation paths having different delay times so as to reach the wireless reception apparatus in time (horizontal axis) and power (vertical axis).

FIG. 3B shows a transfer function with respect to a wireless reception device used by a user and 1. FIG. 3C shows the transfer function with respect to the wireless reception device used by the user and 2. Since the wireless reception devices of users i1 and i2 differ from each other in location, their instantaneous transfer functions are different from each other.

Assume that the left region is assigned to frequency channel L and the right region is assigned to frequency channel L2 in FIG. 3B and 3C, user u1 enjoys good quality in frequency channel b2, while user u2 uses good quality in frequency channel b1. Therefore, the data from Ό1 to перед4 are transmitted to the user and1 through the frequency channel b2. Data Ό1 through Ό4 are spread. Data b1 to b4 is transmitted to user u2 through frequency channel b1. In this case, the data from Ό1 to Ό4 are subject to the expansion of the spectrum.

As described above, by using the quality difference between the frequency channels at a certain moment, it is possible to create multi-user diversity effects to improve transmission efficiency with respect to different users who communicate using different frequency channels.

However, when the maximum time is 2T + b_tah delay increases so fast frequency changes occur in the transfer function, thereby reducing the quality difference between the frequency channel b1 and the frequency channel b2.

Therefore, in order to create adequate multi-user diversity effects, it is important to reduce the maximum time 2T + b_tah delays as shown in FIG. 3A.

FIG. 4A and 4B, 5A and 5B show the relationship between the maximum delay time (n-1) T and frequency changes. When the divergence of (n-1) T arrival occurs between the arrival waves ν31 and \ ν32, as shown in FIG. 4A, the transfer function of this propagation path is shown in FIG. 4B. That is, the frequency difference between the drops in the power amplitude (vertical axis) is defined as P = 1 / (n-1) T.

When multiple waves ν41 through ν43 appear with a delay, as shown in FIG. 5A, the arrival time difference (p-1) T appears between the first arrival wave ν41 and the last arrival wave ν43, so that the frequency difference between the drops in the power amplitude (vertical axis) is defined as P = 1 / (p-1) T, as shown in FIG. 5B.

In this regard, the effect of frequency diversity is different from the effect of multi-user diversity in terms of changes in the frequencies of their respective transfer functions; hence, in order to create the effect of frequency diversity, the maximum delay time (n − 1) T is set as (n − 1) T> P_fromwhere P_from denotes the bandwidth of the fragment, which is the base area assigned to the user for communication and defined along the frequency axis and the time axis, thus generating a mode that easily creates a frequency diversity effect.

- 5 014591

In contrast, in order to create a multi-user diversity effect, the maximum delay time (n − 1) T is set as (u − 1) T <1 / P_fromwhere P_from denotes the bandwidth of the fragment, thus generating a mode that easily creates the effect of multi-user diversity. In the following description, the inequality (i-1) T <1 / P_from covers (i-1) T = 0. In the following description, the delay times applied to transmission antennas are each represented as a (n − 1) multiple of T, where T is assumed to be constant, while it is possible to vary T for each of the transmission antennas. In order to create the effect of multi-user diversity, it is possible to reduce the maximum delay time by reducing the number of transmission antennas used for transmission, instead of establishing inequality (and-1) T <1 / P_from.

As described above, in response to a determination as to whether the transmission signals are transmitted with frequency diversity transmission or transmission with multi-user diversity (i.e. (u1) T> 1 / P_from or (1) T <1 / P_from), it is possible to create a frequency diversity effect or a multi-user diversity effect without being exposed to propagation path conditions.

As shown in FIG. 16A, with respect to the first user who communicates in the form of a communication slot 51, which is created by connecting multiple consecutive fragments in the frequency direction, and to the user who is assigned discontinuous fragments, such as the ninth user, who is assigned slots 5₁₃, 8₁₆, 5₂₀ and 5₂₃ communication, the width of the BA frequency band (that is, BA = 5P for the first user and BA = 3P for the ninth user) of the communication slot instantly allocated to the user determines the basis for realizing the frequency diversity effect; hence, by setting the maximum delay time as (u-1) T> 1 / VA, it is possible to create a frequency diversity effect.

For example, the delay time T is set so that the maximum delay time (and-1) T between the transmission antennas falls within the range (and-1) T> 1 / VA when the communication signal indicates the effect of frequency diversity, while the delay time T is set so that the maximum delay time (and-1) T between the transmission antennas falls within the range of (and-1) T <1 / Ps.

Although no illustration is provided when a subcarrier, partially included in multiple fragments, is assigned to a specific user, the bandwidth VA of the communication slot assigned to the user represents a frequency difference between subcarriers that deviate from each other no more than within the subcarriers instantly assigned to the user.

The determination as to whether the signals are transmitted with frequency diversity or multi-user diversity transmission can be changed based on the types of transmission signals (e.g. pilot signals, control signals, multicast / broadcast signals, etc.), device speeds wireless reception (where frequency diversity is selected in the case of a high speed of movement, and multi-user diversity is selected in case of low speed of movement), etc.

FIG. 6A-6C are explanatory drawings for a situation in which the same signal having no delay time is transmitted through multiple antennas of the wireless transmission device 8. Assume that, as shown in FIG. 6A, the wireless transmission device 8 is equipped with multiple (three) transmission antennas that are arranged in parallel and that do not have horizontal directionality. Due to the presence of the petals e11 and e12 indicated by the ellipses shown in FIG. 6A, there is a direction arranging a wireless reception device 9 that receives reception signals with a high reception level over all frequency bands (see FIG. 6B), and a direction arranging a wireless reception device 10 that accepts reception signals at a low reception level over all frequency bands (see Fig. 6C).

FIG. 7A-7C are explanatory drawings in which the same signal is applied with correspondingly different delay times, and then transmitted through multiple transmission antennas of the wireless transmission device 8. Assume that the wireless transmission device 8 is equipped with multiple (three) transmission antennas having no directivity that are arranged in parallel. Due to the presence of lobes e21 through e26 in narrow bands, there is a frequency band guaranteeing a high reception level and a frequency band guaranteeing a low reception level within the reception signals, while the average reception level is maintained substantially constant, regardless of direction; hence, it is possible to guarantee substantially the same quality in both of the reception level of the wireless reception device 9 (see FIG. 7B) and the reception level of the wireless reception device 10 (see FIG. 7C). Therefore, a method in which signals are applied with different delay times and then transmitted via transmission antennas of the wireless transmission device 8 compensates for the disadvantages of the method described with reference to FIG. 6A-6C and in which the same signal is transmitted through multiple transmit antennas.

The second embodiment.

A second embodiment of the present invention will be described with reference to the structure of a wireless transmission device. Like the wireless transmission device 1 of the first embodiment (see FIG. 1), the wireless transmission device of the present embodiment

- 6 014591 has numerous transmission antennas.

The wireless transmission device described below is a wireless transmission device in which different delay times are applied to transmission antennas for transmitting signals, wherein delay times are set in the time domain.

The signals used with different delay times in connection with the transmission antennas are described in the present embodiment in such a way that a signal that is delayed by T relative to the transmission signal actually transmitted from the first transmission antenna is transmitted through the second transmission antenna, and, similarly, The η-th transmit antenna transmits a signal delayed by (n-1) T.

FIG. 8 is a block diagram showing a physical layer configuration of a wireless transmission apparatus of the present embodiment. The physical layer is part of the configuration of a wireless transmission device, in particular, which receives transmission signals, which performs signal processing in a form suitable for wireless transmission, and which sends signals to a radio frequency converter to perform frequency to radio frequency conversion.

As shown in FIG. 8, the physical layer includes user-dependent signal processors 11a and 11b and antenna-dependent signal processors 12-1, 12-2, and 12-3. The user-dependent signal processor 11a (similar to the user-dependent signal processor 11b) performs signal processing on the signals to be transmitted to the wireless reception device used by each user. The antenna-dependent signal processor 12-1 (similar to the antenna-dependent signal processors 12-2 and 12-3) performs signal processing on each of the transmission antennas.

The user-dependent signal processor 11a includes an error correction coding section 13, a modulator 14, subcarrier assignment section 15, an inverse FFT (inverse fast Fourier transform) section 16, a parallel-serial conversion section 17, a C1 (guard interval) setting section 18 and delay sections 19-1, 19-2, and 19-3.

The error correction coding section 13 performs error correction coding on the transmission signals. The modulator 14 performs modulation processing, such as OP8K (quadrature phase shift keying) and 160 A M (quadrature amplitude modulation) over the output of the error correction coding section 13.

The subcarrier assignment section 15 assigns the output of the modulator 14 to the appropriate subcarriers based on the subcarrier assignment information indicated by a higher order level. The inverse FFT section 16 performs time-frequency conversion on the output of the subcarrier assignment section 15.

The parallel-serial conversion section 17 performs parallel-serial conversion on the output signal of the inverse FFT section 16. Section 18 of the task 01 sets the guard intervals to the output signal of the section 17 parallel-serial conversion. The delay setting section 19-1 sets different delays to the output of section 18 of the task 01 in connection with the transmission antennas.

The output signals of the sections from 19-1 to 19-3 of the delay job are supplied to the antenna-dependent signal processors 12-1, 12-2 and 12-3, respectively. Sections 19-1 through 19-3 of the delay job provide for different delays (for example, 0, 8, and 28). Here, 8 = T / (sampling time). Sampling time is the minimum time interval between digital signals that are processed in section 18 of task 01, sections 19-1 to 19-3 of the delay task and mixing section 20.

Therefore, setting a delay of 8 samples in sections 19-1 to 19-3 of the delay setting indicates that the time delay T is set at the output contacts of the digital-to-analog (Ό / A) converter 22. A user-dependent signal processor 11 is used in a particular fragment; in other words, it is used either in the area with frequency diversity or in the area with multi-user diversity; from here, it receives a communication signal (frequency diversity / multiuser diversity communication signal) controlling the use of either frequency diversity region or multiuser diversity region from a higher order layer controlling the physical layer. The user-dependent signal processor 11a selectively uses either a frequency division domain or a multi-user diversity region based on a communication signal, acting accordingly to change the delay time T.

The user-dependent signal processor 11b has a structure similar to that of the user-dependent processor 11a, but differs from it in terms of its user.

The antenna-dependent signal processor 12-1 includes a mixing section 20, a filter 21, and a digital-to-analog (digital / analog) converter 22.

Mixing section 20 adds and mixes the signals that are output to the antenna-dependent signal processor 12-1 from the user-dependent signal processors 11a and 11b. Filter 21 extracts signals of only the prescribed band from the output of mixing section 20. The digital-to-analog converter 22 performs the conversion from digital to analog over the output signal of the filter 21.

Both antenna-dependent signal processors 12-2 and 12-3 have a structure similar to that

- 7 014591 for an antenna-dependent signal processor 12-1. The output of the antenna-dependent signal processor 12-1 is sent to a radio frequency converter (not shown) to convert frequencies to radio frequencies, from which it is supplied to multiple (three) transmission antennas, thereby transmitting radio signals.

Third Embodiment

A third embodiment of the present invention will be described with respect to yet another structure of a wireless transmission device. The wireless transmission device of the present embodiment is a wireless transmission device that applies different delay times to transmission antennas in order to transmit signals, wherein delay times are applied with respect to the time domain.

The wireless transmission device processes the signals that are applied at guard intervals for the characters (valid character intervals) of the transmission signals. The signals used with different delay times with respect to the transmission antennas are concentrated on the prescribed areas (intervals of valid characters) of the transmission signals that are actually transmitted through the first antenna, with the exception of guard intervals; hence, only valid symbol intervals are delayed by T and then transmitted through a second transmission antenna; likewise, only valid symbol intervals are delayed by (n − 1) T, and then transmitted through the n-th transmit antenna.

Therefore, transmission antennas transmit signals that are applied at guard intervals in accordance with the intervals of valid characters; hence, unlike the second embodiment, no time deviations occur in the timing of the symbol on the transmission antennas. The method for setting the delay time described above is indicated by reference as setting the delay of the call in the following description. As processing for defining a delay in reversal, providing delay waveforms is preferred over the second embodiment, which describes that delay times are applied to transmission antennas.

FIG. 9A and 9B show examples of signals that are created by defining access delays for transmission signals in the present embodiment. FIG. 9A shows a signal transmitted through a first antenna, and FIG. 9B shows a signal transmitted through a second antenna. FIG. 9A and 9B show that the interval of the actual symbol corresponds to four samples, and the guard interval corresponds to one sample, while with respect to the interval of the actual symbol, one sample is delayed on the second antenna compared to the first antenna. No deviations of the symbol binding time occur at the symbol nodes along the first antenna and the second antenna; hence, even when a call delay is applied to them, it is confirmed that the effect of the guard interval for amplification against interference with adjacent symbols is maintained.

FIG. 10 is a block diagram showing a physical layer configuration of a wireless transmission apparatus according to the present embodiment. As shown in the figure, the physical layer includes user-dependent signal processors 111a and 111b, and antenna-dependent signal processors 112-1, 112-2, and 112-3.

A user-dependent signal processor 111a (similar to a user-dependent signal processor 11b) performs signal processing in connection with a wireless transmission device used by each user. The antenna-dependent signal processor 112-1 (similar to the antenna-dependent signal processors 112 and 112-3) performs signal processing on a prescribed transmission antenna.

The structure of the user-dependent signal processor 111a is substantially identical to the structure of the user-dependent signal processor 11a (Fig. 8) described in the second embodiment, whereas the difference between them is that the task section 18 is not provided, and sections 119-1 to 119-3 are provided instead of sections 19-1 to 19-3.

The user-dependent signal processor 111a shares the same functions as the error correction coding section 13, the modulator 14, the subcarrier assignment section 15, the inverse FFT section 16, and the parallel-serial conversion section 17 included in the second embodiment (see FIG. 8); therefore, they are assigned the same reference numbers, and their description will be omitted.

The access delay setting section 119-1 sets different access delays to the output of the parallel-serial conversion section 18 in connection with the transmission antennas. The output signals of sections 119-1 through 119-3 of the reference delay job are supplied to the antenna-dependent signal processors 112-1, 112-2 and 112-3. In addition, delay setting sections 119-1 through 119-3 provide different delays (e.g., 0, 8, and 28). Here 8 = T / (sampling time).

A user-dependent signal processor 111a is used in a particular fragment. Since it is used in either a frequency diversity area or a multi-user diversity area, it receives a communication signal directing to use either a frequency diversity area or a multi-user diversity area by controlling higher

- 8 014591 th order of the physical level. The user-dependent signal processor 111a selectively uses either a frequency-division domain or a multi-user diversity region based on a communication signal, acting accordingly to change the delay time T.

The user-dependent signal processor 111b has a similar structure as the user-dependent processor 111a, but differs from it in user performance.

FIG. 11 is an illustration for explaining a delay setting section 119-1, which is described as an example of the present embodiment. The access delay setting section 119-1 is equipped with a memory 110. In order to set the delay in accessing the samples, the data Ό11 is sequentially entered in from the address k + 1 to the address η of the memory 110 (that is, 1, 2, 3, ..., (η-k) are entered); then a subsequence of data Ό11 is entered at address 1 (that is, (p-k + 1), (p-k + 2), (η-k + 3), ..., η are entered, thus, entering η data samples Ό11. Then, by sequentially outputting from address 1 of memory 110, it is possible to output data Ό12 that was created by defining a delay in accessing samples η data samples Ό11 (i.e., (p + 1). (P + 2). (Η -k + 3), ..., η, 1, 2, ..., (η-k)).

FIG. 9A shows an example of a signal that is created by defining a zero sample access delay of the data of four samples, and FIG. 9B shows an example of a signal that is created by setting a call delay in one sample.

The structure of the antenna-dependent signal processor 112-1 (FIG. 10) is substantially identical to the structure of the antenna-dependent signal processor 12-1 (FIG. 8) described in the second embodiment, the difference being that section 18 of task C1 is provided for it.

The functions of the mixing section 20, task section 18, filter 21, and digital-to-analog converter 22 included in the antenna-dependent signal processor 112-1 are identical to those included in the second embodiment (FIG. 8); therefore, they are assigned the old reference numbers, and their description will be omitted.

Both antenna-dependent signal processors 112-2 and 112-3 have a structure similar to that of the antenna-dependent signal processor 112-1. The output signals of the antenna-dependent signal processors 112-1, 112-2, and 112-3 are supplied to a radio frequency converter (not shown) to convert frequencies to radio frequencies, from which they are fed to multiple (three) transmission antennas, thereby transmitting radio signals .

Fourth Embodiment

A fourth embodiment of the present invention will be described with reference to the structure of yet another wireless transmission device. The wireless transmission apparatus of the present embodiment is a wireless transmission apparatus in which different delay times are applied to transmission antennas in order to transmit signals, wherein delay times are applied to the frequency domain.

The present embodiment deals with signals that are applied at guard intervals with respect to the symbols (valid symbol intervals) of the transmission signals, and, like the wireless transmission apparatus of the third embodiment (FIG. 10), they are set with access delays.

FIG. 12 is a block diagram showing a physical layer configuration of a wireless transmission apparatus of the present invention. As shown in the figure, the physical layer includes user dependent signal processors 211a and 211b, subcarrier assignment section 215 and antenna dependent signal processors 212-1, 212-2 and 212-3.

The user-dependent signal processor 211a (similar to the user-dependent signal processor 111b) performs signal processing with respect to the wireless transmission device used by each user. The subcarrier assignment section 215 assigns the output of the user dependent signal processor 211a to each subcarrier. The antenna-dependent signal processor 212-1 (similar to the antenna-dependent signal processors 212-2 and 212-3) performs signal processing on the prescribed antenna.

Each of the user-dependent signal processors 211a and 211b includes an error correction coding section 13 and a modulator 14. The functions of the error correction coding section 13 and the modulator 14 are essentially identical to those described in the second embodiment (FIG. 8) ; therefore, they are assigned the same reference numbers, and their description will be omitted.

The output signals of the user-dependent signal processors 211a and 211b are assigned appropriate subcarriers in the subcarrier assignment section 215 based on the subcarrier assignment information indicated by a higher order level; then they are fed into the antenna-dependent signal processors 212-1, 212-2 and 212-3.

The antenna-dependent signal processor 212-1 includes a phase rotation section 219, an inverse FFT section 16, a parallel-serial conversion section 17, a задания reference section 18, a filter 21, and a digital-to-analog converter 22. Functions of the inverse FFT section 16, section 17 parallel-serial conversion, section 18 of the task ΟΙ, the filter 21 and the digital-to-analog Converter 22 are identical to those of the second embodiment (Fig. 8); by

- 9 014591 to this they are assigned the same reference numbers, and their description will be omitted.

The phase rotation section 219 rotates the output of the phase subcarrier assignment section 215 by 0_tas for each subcarrier, and then outputs it to section 16 of the inverse FFT. Both antenna-dependent signal processors 212-2 and 212-3 have a structure similar to that of the antenna-dependent signal processor 212-1.

The output signals of the antenna-dependent signal processors 212-1, 212-2 and 212-3 are supplied to a radio frequency converter (not shown) to convert frequencies to radio frequencies from which they are supplied to multiple transmission antennas, thereby transmitting radio signals.

In the present embodiment, phase 0 rotation_t in phase rotation section 219 is set to 0_t= 2n £_t- (i-1) T. Here £_t denotes the difference in frequency between the 0-th subcarrier and the t-th subcarrier, while it is defined as_t= t / T5. so that (p-1) T represents the delay time of circulation on the p-th antenna in connection with the first antenna. T§ represents the time of a valid symbol for the symbol ΘΡΌΜ (orthogonal frequency division multiplexing).

The delay setting section 220 is constituted by a phase rotation section 219 and a reverse FFT section 16. The phase rotation applied by the phase rotation section 219 undergoes a time-frequency conversion in the inverse FFT section 16, so that it is considered as a time delay in the output of the inverse FFT section 16.

A user-dependent signal processor 211 is used in a particular fragment that is used either in a frequency diversity region or a multi-user diversity region, while it receives a communication signal indicating whether to use a frequency diversity region or a multi-diversity region, with a higher order level governing the physical level. Based on the communication signal, the user-dependent signal processor 211a selectively uses a frequency division region or a multi-user diversity region, acting accordingly to change the delay time T.

Wireless communication devices according to the second to fourth embodiments, each is equipped with a delay setting section for delaying transmission signals supplied to n (n is an integer of two or more) transmission antennas by a maximum delay time (n-1) T in accordance with the delay time T mapped to a communication signal indicating whether transmission signals are transmitted with frequency diversity transmission or transmission with multi-user diversity.

Thus, by properly setting the delay time T based on the determination of whether transmission signals are subjected to frequency division transmission or transmission with multi-user diversity, it is possible to create a frequency diversity effect and a multi-user diversity effect without being affected by propagation path conditions.

Fifth Embodiment

A fifth embodiment of the present invention will be described with respect to the structure of yet another wireless transmission device. The wireless transmission device of the present embodiment is a wireless transmission device that applies different delay times to signals that are then transmitted via transmission antennas in a frequency diversity region, along with applying appropriate weights to the transmission antennas so as to perform directivity control in an area with multi-user diversity, while delay times apply, and directivity control is performed in the frequency domain.

The present embodiment deals with signals that are created by setting guard intervals for transmission signals with respect to symbols (real symbol intervals), and similarly to the third and fourth embodiments, it sets the access delay signals.

FIG. 13 is a block diagram showing a physical layer configuration of a wireless transmission apparatus of the present invention. As shown in the figure, the physical layer includes user dependent signal processors 211a and 211b, subcarrier assignment section 215, weighting coefficient calculation section 310, and antenna dependent signal processors 312-1, 312-2 and 212-3. The structures of the user-dependent processor 211a and subcarrier assignment section 215 are similar to those of the fourth embodiment (FIG. 12); therefore, they are assigned the same reference numbers, and their description will be omitted.

The antenna-dependent signal processor 312-1 (similar to the antenna-dependent signal processors 312-2 and 312-3) performs signal processing on a prescribed transmission antenna.

The antenna-dependent signal processor 312-1 includes a weighted multiplication section 319, an inverse FFT section 16, a parallel-serial conversion section 17, a C1 task section 18, a filter 21 and a digital-to-analog converter 22. Functions of the inverse FFT section 16, section 17 parallel-serial conversion, sections 18 of task 01, filter 21 and digital-to-analog converter 22 are identical to those of the first embodiment (FIG. 8); therefore, they are assigned the same reference numbers, and their description will be omitted.

The weighted multiplication section 319 performs weighted multiplication on the output of the subcarrier assignment section 215 of the subcarriers and outputs the results to the inverse FFT section 16.

- 10 014591

Both antenna-dependent signal processors 312-2 and 312-3 have a structure similar to that of the antenna-dependent signal processor 312-1.

The output signals of the antenna-dependent signal processors 312-1, 312-2 and 312-3 are supplied to a radio frequency converter (not shown) to convert frequencies to radio frequencies, from which the results are fed to transmission antennas, thereby outputting radio signals.

A particular subcarrier is used in a particular fragment. That is, it is used either in a frequency diversity area or a multi-user diversity area. The weighted multiplication section 319 is informed of the determination as to whether to use the frequency diversity area or the multi-user diversity area from a higher order level controlling the physical layer based on which rotation 0_t phase is introduced in order to apply different delay times to the antennas in the area with frequency diversity, while the multiplication is performed using the weight coefficient te_t, in order to perform directional control in multi-user diversity areas.

The delay setting and directional control section 320 is constituted by a weighted multiplication section 319 and an inverse FFT section 16. When the phase rotation is introduced by the weighted multiplication section 319, it is considered as time in the output of the inverse FFT section 16, since the inverse FFT section 16 performs time-frequency conversion. On the other hand, when the weighted multiplication section performs multiplication using weights_t, the inverse FFT section 16 performs time-frequency conversion, so that the output of the inverse FFT section 16 provided from the transmission antenna is subjected to directivity control.

When the weighted multiplication section 319 rotates the phase by 0_t, like the fourth embodiment, it sets 0_t= 2lT_t- (p-1) T. Here £_t denotes the frequency difference between the 0th subcarrier and the tth subcarrier, with_t= w / t₈; and (p-1) T represents the delay time of circulation on the p-th antenna in connection with the first antenna. T₈ represents the time of the valid character for the ΟΡΌΜ character.

In order to perform multiplication using the weight coefficient_t, the next weighting factor is adjusted to perform directional control. Provided that the linear antenna array of n antennas, whose period is half the wavelength of the carrier frequency, the weight coefficient_t calculated in accordance with the following equality (1).

Equality 1

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Weight coefficient_t represents the weighting vector used in the weighted multiplication section 319, wherein in equation (1) the first to last terms describe the weights used in the first to the nth antennas.

In equality (1), which expresses the weight coefficient_t, n denotes the number of antennas, while in the present embodiment, n = 3; 0 indicates the direction in which the main lobe of the antenna pattern is directed; and k denotes the relationship between the frequency used for transmission and the frequency that is measured based on 0.

As for the direction 0 of the main lobe of the antenna pattern, the measured value generated by the wireless transmission device or the terminal of the opposite means of communication is fed to the weighting section 310, in which it is used to calculate the weighting factor_t. Equality (1) provides an example of calculation for the weight coefficient te_t, which can be calculated in the form of another method. Calculation methods regarding 0 and those_t described in Tcc1 Keroy KS82004-229 (Technical Report KS82004-229, published by the Corporate Institute of Electronic Information and Telecommunications in November 2004) and the like.

The delay setting and directivity control section 320 sets a delay of a maximum delay time (n − 1) T of a delay or less between transmission antennas when the communication signal indicates frequency diversity, while it performs multiplication to produce a weight coefficient te_tso as to perform directivity control when the communication signal indicates multi-user diversity.

As described in the first embodiment, the delay setting and directivity control section 320 sets the delay time T, so that the maximum delay time (n − 1) T between the transmission antennas falls within the range (n − 1) T&gt; 1 / P_fromwhen the communication signal indicates frequency diversity.

As described in the first embodiment, the delay setting and directivity control section 320 sets the delay time T so that the maximum delay time (n − 1) T falls within the range of (n − 1) T&gt; 1 / V \ ¥ when the signal communication indicates frequency diversity.

- 11 014591

The above description teaches that the weighted multiplication section 319 of the delay and directivity control section 320 is informed by a higher order level controlling the physical level that either the frequency diversity region or the multi-user diversity region should be used, based on which it applies rotation 0_t phase, in order to set different delay times for the antennas in the area with frequency diversity, along with the fact that it performs multiplication to generate a weight coefficient te_tin order to perform directional management in multi-user diversity areas; however, it is possible to use a different method to use both, turning 0_t phase and weight coefficient those_t, in a multi-user diversity area such that, as described in the fourth embodiment, rotation 0_t the phase is set for both, the frequency diversity area and the multi-user diversity area, before the direction θ of the main lobe of the antenna pattern is generated, and then the directivity control is performed using the weight coefficient te_tafter the direction θ of the main lobe of the antenna pattern is worked out, in the multi-user diversity area. Like the fourth embodiment, the delay time T varies in connection with θ_№ in accordance with the frequency diversity region and the multi-user diversity region. Thus, at the stage before the direction θ of the main lobe of the antenna pattern is developed, it is possible to create the same multi-user diversity effect as the fourth embodiment, while after the direction θ of the main lobe of the antenna pattern is developed, it is proposed to create higher multi-user diversity effect by precise directivity control using the weight coefficient te_t. Moreover, by using the physical layer configuration of the wireless transmission device shown in FIG. 13, more preferably than the fourth embodiment, it is possible to improve performance by controlling directivity by slightly expanding the composition of the circuit.

As described above, the delay setting and directivity control section 320 sets a delay of a maximum time (n − 1) T of a delay or less between transmission antennas when the communication signal indicates frequency diversity, while it sets a maximum time delay (n − 1) T delay or less, or it performs multiplication to produce a weight coefficient of te_tso as to perform directivity control when the communication signal indicates multi-user diversity.

The wireless transmission apparatus performing the above processing has the structure shown in FIG. 13, wherein when the communication signal indicates multi-user diversity, the delay setting and directivity control section sets the delay of the maximum delay time (n-1) T of the delay or less between the transmission antennas, or it performs multiplication to generate a weight coefficient te_tin order to perform directional control.

As described in the first embodiment, the delay setting and directivity control section sets the delay time T, so that the maximum delay time (n-1) T between the transmission antennas falls within the range (n-1) T&gt; 1 / P_fromwhen the communication signal indicates frequency diversity, along with the fact that it sets the delay time T, so that the maximum delay time falls within the range (p-1) T &lt;1 / P_fromwhen the communication signal indicates multi-user diversity, so that a delay is applied between the transmission antennas.

As described in the first embodiment, the delay setting and directivity control section sets the delay time T, so that the maximum delay time (n-1) T between transmission antennas falls within the range (n-1) T&gt; 1 / V \ U . when the communication signal indicates frequency diversity.

The above second to fifth embodiments are described with respect to a case in which the number of users is two and the number of antennas is three, while the number of users and the number of antennas are not necessarily limited to these numbers.

In the aforementioned fourth and fifth embodiments, it is possible to transmit signals that are multiplied using special scrambling codes dependent on antennas, sectors, and base stations to transmission antennas.

The sixth embodiment.

The present embodiment will be described with respect to changes in the maximum time (n − 1) T of a delay dependent on physical channels. The aforementioned first to fifth embodiments are described under the assumption that a one-to-one relationship is made with respect to one particular fragment at a particular moment, with (n-1) T&gt; 1 / P_from set to create the effect of frequency diversity, along with the fact that (n-1) T &lt;1 / P_from set to create a multi-user diversity effect.

Typically, in a communication other than one-to-one communication, a known signal, referred to as a control channel, is transmitted to a wireless transmission device in order to evaluate a propagation path; alternatively, a control channel is used to communicate various types

- 12 014591 parameters before data transfer. The present embodiment will be described with respect to a method for setting a maximum delay time (n − 1) T in these physical channels.

The developed ITRL and ϋΤΚΑΝ (terrestrial radio access and terrestrial radio access network of the universal mobile telecommunications system) systems considered in 3SRP (3rd Generation Partnership Project) provide for common control channels, OSRNS (common control channel for downlink), dedicated control channels, OERSN (dedicated control channel downlink), synchronization channels downlink, 08CH (channel synchronization downlink), common control channels, ESSN (common downlink control channel), shared downlink control signaling channels, E8C8CH (shared downlink control channel), and multicast / broadcast channels (multicast / broadcast channel).

The common control channels, OSRSN, correspond to control channels, SR1CH (common control channel), in ν-СОМА (wideband multiple access with code division multiplexing), which are used to evaluate the conditions of the downlink propagation paths, search for cells, and measure the fading of propagation paths when uplink transmission power control in AMC8 (adaptive modulation and coding scheme).

Dedicated control channels, OORCH, are used to transmit to individual mobile stations via transmission antennas, such as adaptive antenna arrays, whose propagation paths differ from those of the shared hundredth antennas; alternatively, they can be used to enhance shared downlink common control channels, O8PCH, in connection with mobile stations having poor reception quality.

Downlink synchronization channels, O8CH, correspond to synchronization channels, 8CH, in ν-СОМА, and they are used to search for the hundredth mobile stations, radio communication frames ΘΕΌΜ (multiplexing with orthogonal frequency division of channels), time intervals, transmission time intervals, ΤΤΙ (transmission time interval), and synchronization of the timing of characters ΘΕΌΜ.

Common control channels, EESSN, include general control information, such as broadcast information (corresponding to broadcast channels, BCH), corresponding to the main common physical control channels, P-SSRSN, additional common physical control channels, 8-SSRSN, and indicator channel paging call, P1CH, in VCOMA, information of the P1 indicator of the packet search call (corresponding to the channels of the paging indicator, P1CH), specifying the presence of packet calls, information about the packet search call (corresponding to the channels of the search call, RSN) corresponding to the packet calls, and access information on the downlink (corresponding to the access channels on the downlink, EACH).

The shared downlink control signaling channels, O8C8CH, correspond to the shared control channels associated with the H8-E8CH, H8-8CCN, dedicated downlink control channels, ORSSN, reception indicators, A1CH included in high-speed physical shared downlink channels , Н8РО8СН, with N8REA (high speed downlink packet access), however, they are shared by numerous mobile stations and are used to transmit information (modulation methods, spread coding, etc.), which is necessary for the mobile stations to perform demodulation with respect to high-speed shared downlink channels, H8-O8CH, information that is necessary for decoding with error correction and processing NARP (hybrid automatic request for retransmission), and radio resource planning information (frequency, time).

Shared downlink data channels, O8OCH, correspond to high-speed downlink shared channels, H8-O8CH, dedicated downlink data channels, OROSH, included in high-speed physical downlink shared channels, H8-PO8CH, in N8POA, they are used to transmit packet data to mobile stations from higher order levels.

Multicast / broadcast channels are used for broadcast information signals.

The aforementioned physical channels from ν- COMA and Н8ОРА are described in Тас1ика \ уа Кегр, ν-СОМА МоЫ1е Сошшишсабоп MENOB, Ι8ΒΝ4-621-04894-5 (Tachikawa Keyji, Mobile Communication Method VСОМА, Ι8ΒΝ4-621-04894-5). P.

FIG. 14 and 15 are tables describing the interdependencies between the maximum delay time (n-1) T between transmission antennas and width E_from fragment frequency bands in connection with physical channels. As shown in the figures, it is preferable to set (p-1) T &lt;1 / P_from regardless of the area with frequency diversity and the area with multi-user diversity in relation to the overall con

- 13 014591 control channels of control, common control channels and dedicated control channels. It is preferable to set (p-1) T&gt; 1 / P_from regardless of the frequency diversity area and the multi-user diversity area with respect to the downlink synchronization channels.

Regarding the dedicated control channels, it is preferable to set (i-1) T&gt; 1 / E_from in the area with frequency diversity and set (i-1) T &lt;1 / P_from in an area with multi-user explode. Suppose that the selected control signals are transmitted via transmission antennas, while the delay setting section for delaying the transmission signals supplied to η transmission antennas by a maximum delay time (n - 1) T or less sets the delay time T, so that the maximum time (p-1) T delay fell within the range (p-1) T&gt; 1 / P_fromwhen a communication signal that indicates whether fragments including dedicated control channels are completed to frequency diversity transmission or multi-user diversity transmission indicates frequency diversity, while it sets a delay time T in order to perform control directivity using weights derived from the section for calculating weights , or to determine the maximum delay time (n-1) T as (n-1) T &lt;1 / P_fromwhen the communication signal indicates multi-user diversity.

Multicast / broadcast channels are used only in the area with frequency diversity; therefore, it is preferable to set (p-1) T&gt; 1 / P_from.

The reasons why the above settings are made are because the common monitoring channels are not used to notify about the signal levels observed by the terminals, hence it is undesirable that the delay time varies in fragments, while the wireless transmission device needs to know the signal levels from fragments in the case of (n-1) T &lt;1 / E_from in order to perform multi-user diversity, it is therefore preferable to set (n1) T &lt;1 / P_from so that the maximum delay time does not vary across fragments.

Dedicated control channels are used to calculate the estimated values ​​of the propagation paths used to demodulate the data signals. Therefore, it is preferable to perform communication by setting (p-1) T&gt; 1 / E_from in the area with frequency diversity and by setting (n1) T &lt;1 / P_from in an area with multi-user explode.

Downlink synchronization channels are used to synchronize frames, with the estimation of propagation paths not necessary, and it is preferable to guarantee accurate reception in case of low reception power; hence it is preferable to set (p-1) T&gt; 1 / E_fromin order to create a frequency diversity effect. In particular, it is possible that the same signal is transmitted using the same time interval and the same frequency through downlink synchronization channels in the form of multiple sectors and multiple antennas included in a single base station. Therefore, the signals are applied with different delays on the antennas and are transmitted as multiple sectors and multiple antennas included in a single base station, through synchronization channels downlink; thus, it is contemplated to use a high frequency diversity effect, which is higher than that of another physical channel.

It is assumed that the common control channels and dedicated control channels use the estimated values ​​of the propagation paths, which are produced as common control channels; hence, it is preferable that they are set to a maximum delay time, which is identical to that of the common control channels, and transmitted.

However, it is preferable to guarantee accurate reception on the common control channels and dedicated control channels in case of low reception power; hence, it is preferable to create a frequency diversity effect, while taking into account the improvement in the reception characteristics of the control channels at the beginning, when common control channels, dedicated control channels and multicast / broadcast channels are included in the same fragment, it is preferable to transmit through the common control channels by setting (p-1) T&gt; 1 / P_from, thus creating the effect of frequency diversity in the control channels.

When the same fragment is used for multi-user diversity, it is necessary to notify of signal levels in the actual transmission, aligned with multi-user diversity (communication at (n-1) T &lt;1 / E_from); hence, it is preferable to transmit by tuning (p-1) T &lt;1 / P_from.

For this reason, it is possible to establish a relationship between the maximum delay time (n1) T between transmission antennas and width E_from fragment bandwidth, which is identical to the interdependence shown in FIG. 15, on each physical channel.

In order to create the effect of frequency diversity, it is preferable to perform communication by setting (p-1) T&gt; 1 / P_from.

The above embodiment is described such that the maximum delay time falls within the range of (n-1) T &lt;1 / E_from in a multi-user diversity area, while the wireless transmission device described in the fifth embodiment can use the weight coefficient te_t, which is generated by section 310 of the calculation of weights, in the area with

- 14 014591 multi-user diversity.

The above second to fifth embodiments are each described such that a wireless transmission device having η transmission antennas transmits signals used with a prescribed delay time on each of η transmission antennas; but this structure is not limiting. For example, when a wireless transmission device having η transmission antennas chooses to use multi-user diversity, it is possible to transmit signals used with a prescribed delay time T ′ for each of the _) transmission antennas (where _) is an integer, 1 &lt;_) &lt;η) within η transmission antennas.

In the aforementioned structure, compared with a structure in which signals are transmitted using all η transmission antennas, the maximum delay time (| -1) T ′ applied to signals transmitted through _) transmission antennas is reduced so as to further reduce path changes distribution; from here it is possible to create a significant multi-user diversity effect. In the case of _) = 1, in particular, it is possible to reduce the scale of the delay section circuit.

The present embodiment is described under the condition that the maximum delay time is set as (n-1) T&gt; 1 / P_from, in order to create the effect of frequency diversity, whereas, as described in the first embodiment, when the transmission is performed using a physical channel to which a fragment lying in multiple frequency directions is assigned, the frequency bandwidth Βν assigned to the physical channel forms the basis for creating frequency diversity effect, from here it is possible to create a frequency diversity effect by setting the maximum delay time to (η-1) Τ&gt; 1 / Βν.

By using a wireless transmission device according to the above embodiments of the present invention, which selects to use either frequency diversity or multi-user diversity when transmitting signals from η transmission antennas, so as to change the delay times applied to signals transmitted through η transmission antennas to based on the result of the selection; hence, it is possible to create a frequency diversity effect or a multi-user diversity effect without being affected by propagation path conditions.

In the above embodiments, programs that implement the functions of error correction coding section 13, modulator 14, subcarrier assignment sections 15 and 215, inverse FFT sections 16, parallel-serial conversion sections 17, task 01 sections 18, sections 19-1 to 19- 3 delay settings, sections 119-1 to 119-3 of the treatment delay delay, mixing section 20, filter 21, digital-to-analog converter 22, phase rotation section 219, weighting section 310 and weighted multiplying sections 319 shown in FIG. 8, 10, 12, and 13 are stored on computer-readable storage media, so that programs stored on storage media are downloaded to a computer system and then executed in order to control a wireless transmission device. Here, the computer system includes an OS (operating system, 08) and hardware, such as peripherals.

Computer-readable storage media are referred to as floppy disks, magneto-optical disks, ROM (read-only memory, ROM), portable media such as SECOM (ROM on CD-ROM), and storage devices such as hard disks included in a computer system. Moreover, computer-readable storage media includes media for dynamically storing programs within a short period of time, such as communication lines such as the Internet, networks and telephone lines used to transmit programs, and volatile memory to hold programs for a prescribed period of time which are included in a computer system serving as a server and client. The above programs are intended to implement part of the above functions; alternatively, some are designed to implement the above functions in the form of a combination of programs that are previously stored in a computer system.

This invention is described in detail in the form of embodiments with reference to the drawings, while its detailed structure is not necessarily limited to the options for implementation; therefore, it encompasses designs that do not deviate from the essence of this invention.

Industrial applicability

The present invention is applicable to wireless transmission devices and wireless transmission methods that transmit signals to wireless reception devices using multiple transmission antennas, the delay times being set appropriately based on a determination as to whether transmission signals are transmitted in frequency diversity transmission or transmission with multi-user diversity; hence, it is possible to create frequency diversity effects and multi-user diversity effects without being affected by propagation path conditions.