Method of estimating a signal-to-noise ratio in digital video broadcasting network planning

METHOD OF ESTIMATING A SIGNAL-TO-NOISE RATIO IN DIGITAL VIDEO BROADCASTING

NETWORK PLANNING

DESCRIPTION

0004Field of the invention

0005The present invention generally relates to OFDM (Orthogonal Frequency Division Multiplex) telecommunications systems and methods, particularly to DVB (Digital Video Broadcasting) networks, and even more particularly to the planning of DVB-H (DVB-Handheld) networks. Specifically, the invention concerns a method of estimating the signal-to-noise ratio in the planning phase of an OFDM network, and particularly of a DVB-H network.

0006Background of the invention

0007DVB is more than a simple promise: it represents the technological evolution that is going to replace the analog Television (TV) broadcasting systems we have been accustomed to for more than 50 years.

0008In particular, due to the enormous popularity gained by personal mobile communications, a promising evolution of DVB is the DVB-H (DVB-Handheld) system, by means of which TV will be made available to users of mobile communications terminals like mobile phones.

0009As known to those skilled in the art, the DVB-H system is an SFN (Single-Frequency Network) system based on OFDM (Orthogonal Frequency Division Multiplex). In an SFN, all transmitters in the network use the same channel/frequency. The OFDM is modulation system in which the information is carried via a large number of individual (sub-)carriers, in a frequency multiplex scheme; each (sub-)carrier, transports only a relatively small amount of information, and high data capacities are achieved by using a large number of frequency-multiplexed carriers. Each carrier is modulated using QPSK (Quadrature Phase Shift Keying) and QAM (Quadrature Amplitude Modulation) techniques, and has a fixed phase and amplitude for a certain time interval, referred to as the "symbol time", during which a small portion of the information, called "symbol", is carried. After that time period, the modulation is changed and the next symbol carries the next information portion. The symbol time is the inverse of the (sub-)carrier spacing, and this ensures i orthogonality between the carriers,

0010Modulation and demodulation are accomplished using the IFFT (Inverse Fast Fourier Transform) and the FFT, respectively.

0011In order to demodulate the received signal, the generic receiver has to evaluate the symbol 5 during the symbol time. This involves properly positioning an FFT evaluation time window {i.e., the time window for the OFDM demodulation of the received signals).

0012Before the actual deployment of the network in a geographic area of interest, a network planning is performed.

0013Network planning makes use of dedicated software tools, like the one named "DVB-Plan"0 by Wireless Future for the planning of DVB-T networks.

0014In the network planning phase, the geographic area of interest is subdivided into several relatively small elementary area elements, also referred to as pixels, for example squares of 50 m by 50 m. Based on an initial network configuration, with a certain transmission station positioning and radio equipment, the distribution of the electro-magnetic field in every pixel is calculated, by5 means of an electro-magnetic field propagation simulator. The generic pixel is assumed to represent a virtual DVB-H receiver, i.e. it is assumed that, in the generic pixel, at least one DVB-H receiver is located. For each pixel, the signal-to-noise ratio is calculated. In particular, this involves positioning in time the FFT window, so as to determine which of the simulated signals contribute constructively, and which instead contribute interferential^; in particular, the FFT window o positioning method adopted in the cited DVB-Plan tool is the synchronization to the best-server

0015{i.e., strongest) signal.

0016The White Paper of Emmanuel Grenier, ATDI, "DVB-H radio planning aspects in ICS telecom", July 2006, available on the web site www.atdi.com/docs/WP DVBH- planninq ICStelecom.pdf, addresses the problem of efficient planning of DVB-H networks with ICS5 telecom. The document shows that the total power receiver at a receiver can be calculated as the sum of power contributions from received signals, properly weighted depending on the arrival time of the signal with respect to an FFT window.

0017Summary of the invention

0018The Applicant has observed that, due to the fact that the elementary area elements into o which the area of interest is subdivided in the planning phase have finite geometric dimensions, a proper description of the electro-magnetic field in each pixel should take into account statistical variations thereof, This has a reflex on the way the signal-to-noise ratio is calculated.

0019The Applicant has in particular observed that, despite it could be possible to perform the statistic sum of the powers of the n signals received at a considered pixel when the powers are 5 expressed in logarithmic units (dBm), this sum would be meaningless from a physical viewpoint.

0020Thus, the Applicant has tackled the problem of how a correct calculation of the signal-to- noise ratio can be performed in the network planning phase.

0021The Applicant has found that, in order to properly describe, from the statistical viewpoint, the sum of the different signals which, in the simulation, are received at the generic pixel, theo statistical distributions of the corresponding linear variables (expressed in mW) must be considered; in particular, the Applicant has found that the statistic sum must be performed in the linear field, by adding separately average values and variances. In particular, the average value and the variance of the power of the useful signal are calculated as the sum of the average values and variances of constructive contributions; the same is done for the interference /, considering5 interferential contributions. The variables are then retransformed in the logarithmic field, where the signal-to-ratio is computed.

0022Therefore, according to the present invention, first a transformation from a logarithmic unit (dBm) into a linear unit (mW) is carried out, then some processing is performed in the linear field, and then a retransformation from linear unit (mW) into logarithmic unit (dBm) is carried out, where o the signal-to-ratio is computed. Tranformations are carried out passing through neper variables.

0023According to an aspect of the present invention, a method of estimating the signal-to-noise ratio during planning of a digital video broadcasting network in a geographic area of interest is provided, the method comprising simulating reception of radio signals in a plurality of area elements of the area of interest and, for at least one area element of said plurality, performing a decoding of 5 the received radio signals, wherein the power of the received radio signals is expressed in a logarithmic unit, and performing a decoding comprises:

0024- dividing the received radio signals into a useful signal and a noise, the useful signal comprising a group of constructive contributions and the noise comprising a group of interferential contributions, and

0025o - calculating a ratio between the useful signal and the noise; wherein calculating a ratio between the useful signal and the noise comprises:

0026- transforming average values and variances of the power of the received radio signals from the logarithmic unit into a linear unit;

0027- calculating an average value and a variance of the power of the useful signal as a sum of the average value and, respectively, of the variance of the constructive signal contributions, expressed in the linear unit;

0028- calculating an average value and a variance of the power of the noise as a sum of the average value and, respectively, of the variance of the interferential contributions, expressed in the linear unit;

0029- converting the calculated average value and variance of the power of the useful signal from the linear unit into the logarithmic unit;

0030- converting the calculated average value and variance of the power of the noise from the linear unit into the logarithmic unit;

0031- calculating an average value of said ratio between the useful signal and the noise in the logarithmic unit as a difference of the average values of the powers of the useful signal and of the noise in the logarithmic unit; and

0032- calculating a variance of the ratio between the useful signal and the noise in the logarithmic unit as a sum of the variances of the power of the useful signal and of the power of the noise in the logarithmic unit.

0033The step of simulating reception of radio signals in a plurality of area elements of the area of interest may comprise:

0034- providing an initial configuration of the network in the area of interest;

0035- providing a morphological description of the area of interest;

0036- dividing the area of interest into a plurality of area elements; and

0037- simulating a propagation of the radio signals through the area of interest based on said initial configuration of the network.

0038In particular, the logarithmic unit is a base-10 logarithmic unit, and the transforming average values and variances of the power of the received radio signals from the logarithmic unit into a linear unit includes:

0039- transforming the average values and the variances of the power of the received radio signals into a natural logarithmic unit; and

00405 - transforming the average values and the variances of the power of the simulated radio signals from the natural logarithmic unit into the linear unit.

0041The step of converting the calculated average value and variance of the power of the useful signal from the linear unit into the logarithmic unit may comprise:

0042- converting the calculated average value and variance of the power of the useful signal o from the linear unit into the natural logarithmic unit; and

0043- converting the average value and variance of the power of the useful signal from the natural logarithmic unit into the base-10 logarithmic unit.

0044The step of converting the calculated average value and variance of the power of the noise from the linear unit into the logarithmic unit may comprise: 5 - converting the calculated average value and variance of the power of the noise from the linear unit into the natural logarithmic unit; and

0045- converting the average value and variance of the power of the noise from the natural logarithmic unit into the base-10 logarithmic unit.

0046In particular, the base-10 logarithmic unit is absolute decibel, and the natural logarithmic o unit is neper. The linear unit may be Watt or a multiple/submultiple thereof, like milliWatt.

0047The step of performing a decoding of the radio signals may comprise positioning in time a decoding time window.

0048The step of positioning in time may comprise changing the position in time of the decoding time window in order to maximize the calculated signal-to-noise ratio. 5 The step of calculating the signal-to-noise ratio may comprise considering as constructive contributions all the radio signals that, as a result of said simulating, are received at the area element within the decoding window, and considering as interferential contributions all the radio signals that, as a result of said simulating, are received at the area element outside the decoding window.

0049Other aspects of the invention concerns a computer program and a data processing system that, when programmed by the computer program, is adapted to implement the method of the first aspect.

0050In the following, for the sake of simplificity, reference will be made to average values and variances of simulated radio signals, useful signals, and noise, but it is clear that the average values and variances are referred to the power of such variables.

0051Brief description of the drawings

0052The features and advantages of the present invention will result apparent by reading the following detailed description of an embodiment thereof, provided merely by way of non-limitative example, and referring to the annexed drawings, wherein:

0053Figure 1 pictorially shows a portion of a geographic area covered by a DVB-H network, with elevated, wide-range transmission stations and low-height, reduced radio range transmission stations;

0054Figure 2 illustrates the concepts of "guard time interval" and "FFT window positioning";

0055Figure 3 schematically shows a subdivision into elementary area elements, or pixels, of the portion of geographic area of Figure 1 used in a network planning phase, according to an embodiment of the present invention;

0056Figure 4 schematically shows the main functional components of a data processing apparatus that, suitably programmed, is adapted to carry out a DVB-H network planning method according to an embodiment of the invention;

0057Figure 5 schematically shows the main components of a computer program that, when executed on the data processing apparatus of Figure 4, implements a DVB-H network planning method according to an embodiment of the present invention;

0058Figure 6 is a schematic flowchart showing the main steps of a DVB-H network planning method according to an embodiment of the present invention;

0059Figure 7 pictorially shows an FFT window synchronization procedure according to an embodiment of the present invention; and Figure 8 is a schematic flowchart showing the main steps of a preferred procedure for calculating a C// ratio adopted in the network planning method of Figure 6, according to an embodiment of the present invention.

00605 Detailed description of the preferred embodiment of the invention

0061Making reference to Figure 1, there is schematically shown a portion of a geographic area 100 covered by a DVB-H network, for broadcasting TV to DVB-H mobile terminals, like mobile phones 105; the geographic area 100 is assumed to be an area under planning of the DVB-H network. o The scenario depicted in Figure 1, rather typical for DVB-H networks, is characterized by the presence of transmitting stations that are very different in nature: several "low-height" transmission stations, of reduced radio range (of the order of few Kilometers), located for example in correspondence of the transceiver stations (BTSs - Base Transceiver Stations - of a GSM network, Node Bs of a UMTS network) of a mobile telephony network, and few "elevated",5 dominant transmission stations, corresponding to the broadcasting TV antennas, having a much wider radio range (of the order of 100 Km). In particular, looking at Figure 1, just one elevated transmission station 110 is shown, for the sake of simplicity, depicted as located on top of a hill or mountain 115, working in conjunction with four low-height transmission stations 120a, 120b, 120c and 12Od, the first two being distributed in a first urban area 125a (e.g. a town, or a village), the o second two being distributed in a second urban area 125b.

0062Considering a hypothetic DVB-H terminal (a DVB-H receiver) 105 located for example in the first urban area 125a, it will receive the relatively low-strength radio signals irradiated by the low-height transmission stations 120a, 120b distributed across the urban area 125a (particularly, the DVB-H terminal 105 will receive the radio signals irradiated by those, among the transmission 5 stations 120a, 120b, that are located in the neighborhood of the DVB-H terminal 105), and the relatively strong signal irradiated by the elevated site 110, together with the respective echoes.

0063Referring to Figure 2, in order to demodulate the received signals, the DVB-H receiver has to evaluate the symbol during the symbol time. This involves properly positioning an FFT evaluation time window 200, whose duration is as long as the useful symbol time T_u of the signal.

0064O Different time delays are associated with different signals 205a, 205b, and 205c that arrive at the DVB-H receiver following different paths, corresponding for example to the transmission stations 110, 120a, and 120b, and possibly to echoes of a same transmitted signal. Just three signals are shown, however in a real case the number of signals that a generic receiver receives may be higher. In order to allow, as much as possible, a constructive combination of the different signals arriving at the receiver, a guard time interval tg is usually provided for, thereby the useful symbol time T₁₁ of the signal is cyclically extended to obtain an extended symbol time T_s by adding a cyclic extension or a cyclic prefix of every symbol, preceding or following the useful part of each symbol and containing a repetition of the data at the end, or respectively at the beginning of the useful symbol part. In other words, part of the symbol is copied from the beginning of the symbol to the end, or from the end of the symbol to the beginning. Those signals that are received with a delay than cannot be compensated by the guard time cause a worsening of the received signal, and are therefore regarded as interference.

0065With the provision of the guard interval Tg, the DVB-H receiver can position the FFT window in such a way as to reduce ISI.

0066In particular, the DVB-H receiver is synchronized in two phases: in a first phase, an initial synchronization is performed, in which the receiver is temporally aligned to the symbol rate; in a second phase, a secondary synchronization is performed, in which the receiver position the FFT window for demodulating the received signal.

0067The FFT window positioning which is materially performed by the generic receiver is not prescribed in detail in the network system specifications; all manufacturers have their own, proprietary and often undisclosed solutions. For example, the strategies that a receiver can adopt for positioning the FFT window can be classified according to the general overview of the possible strategies for FFT window synchronization in OFDM receivers that is provided in the paper by R.

0068Brugger and D. Hemingway, "OFDM receivers - impact on coverage of inter-symbol interference and FFT window positioning", EBU Technical Review, July 2003. In that paper, five different strategies for the positioning (also referred to as "synchronization") of the FFT window in OFDM receivers are presented: "strongest signal", "first signal above a threshold level", "centre of gravity",

0069"quasi-optimal" and "maximum C//". In brief, in the strongest-signal approach the FFT window is synchronized to the strongest received signal (positioning for example the center of the FFT window at the center of the symbol to which the strongest signal corresponds). In the first signal above a threshold level approach, the first signal above a predetermined threshold signal level serves as a trigger for the FFT window synchronization. In the centre of gravity approach, the receiver looks at the impulse response, calculates the "centre of gravity" of the impulse response spectrum, and centers the FFT window on that point in time. In the quasi-optimal approach, the first signal of the impulse response spectrum above a minimum threshold level is taken as a reference for the FFT window. If the value of the CII (the ratio between the sum C of all the constructive signal 5 contributions received at the receiver, to the sum / of all the remaining, interferential contributions) is good enough to allow demodulation, the FFT window is aligned to the beginning of a symbol carried by such a signal, otherwise the receiver looks for any other signal in the time impulse response that is above the predetermined threshold: if no such signal is found, the FFT window is aligned to the beginning of a symbol of the signal that allows the greatest CII value, otherwise the o FFT window is aligned with the next signal in the impulse response that exceeds the predetermined threshold value. Finally, in the maximum CII approach, the FFT window is positioned so that the effective CII value is maximized.

0070Once the position of the FFT window has been determined, the DVB-H receiver calculates a useful received signal C as the sum of all the received signals C,- that contribute constructively,5 and the interference / is calculated as the sum of the remaining received signals, that contribute interferential^. The DVB-H receiver will consider as constructive contributions the received signals that fall within the FFT window and as interference the received signals that fall outside the FFT window, according to the following formulas: <img file="WO2008064706A1_D0001.tif" />

0071o where the weight coefficient Wi is calculated as follows (the variable t identifying the time at which a generic signal / is received):

0072<img file="WO2008064706A1_D0002.tif" />

0073It has to be noted that in the FFT window has been considered of rectangular shape for the sake of simplicity, but it could have a different shape, such as a trapezoidal shape, thus including 5 different weights.

0074A typical guard time is of 250 μs, corresponding to signal paths differing of about 70 Km. In a scenario like that depicted in Figure 1 , which is rather true-to reality, the elevated transmission stations, like the transmission station 110, having a wide radio range, often happen to be away from, e.g., urban areas like the urban area 125a a distance of the order of a few hundreds of kilometers; thus, while the signals received by the generic DVB-H receiver and coming from the low-height sites like the sites 120a, 120b (either directly or after signal reflections) are generally rather close to each other, in terms of time delay, and thus they fall within the FFT window or within the guard time, the signal(s) coming from the elevated transmission station(s), like the site 110, having to travel for a significantly longer path arrives at the DVB-H receiver with a significant time delay, of more than the typical guard time value of 250 μ.

0075Known DVB-H network planning tools, like the above mentioned "DVB-Plan" commercial software, that operates on the basis of the assumption that DVB-H receivers synchronize the FFT windows on the strongest signals produces an erroneous estimation of the signal interference caused by signals coming from multiple paths, because in a scenario like that depicted in Figure 1 the strongest signal received by a generic DVB-H receiver like the mobile terminal 105 is often the signal irradiated by an elevated transmission station, like the station 110, but this signal is at the same time the more delayed, compared to the signals received from the low-height, closer transmission stations 120a, 120b. As a consequence, these known planning tools provide an erroneous estimation of the service areas, and in particular the indoor service coverage is underestimated.

0076Referring to Figure 3, there is schematically depicted a data processing apparatus 300, which, in one embodiment of the present invention, is used for planning the DVB-H network (for example in respect of the portion of geographic area 100 shown in Figure 1). The data processing apparatus 300 may be a general-purpose computer, like a Personal Computer (PC), a workstation, a minicomputer, a mainframe, and it may as well include two or more PCs or workstations networked together.

0077The general structure of the data processing apparatus 300 is schematically depicted in

0078Figure 4. The data processing apparatus 300 comprises several units that are connected in parallel to a system bus 403. In detail, one (possibly more) data processor (μp) 406 controls the operation of the computer 300; a RAM 409 is directly used as a working memory by the microprocessor 406, and a ROM 411 stores the basic code for a bootstrap of the computer 300. Peripheral units are connected (by means of respective interfaces) to a local bus 413. Particularly, mass storage devices comprise a hard disk 415 and a CD-ROM/DVD-ROM drive 417 for reading CD- ROMs/DVD-ROMs 419. Moreover, the computer 300 typically includes input devices 421, for example a keyboard and a mouse, and output devices 423, such as a display device (monitor) and a printer. A Network Interface Card (NIC) 425 is used to connect the computer 300 to a network 427, e.g. a LAN. A bridge unit 429 interfaces the system bus 403 with the local bus 413. Each microprocessor 406 and the bridge unit 429 can operate as master agents requesting an access to the system bus 403 for transmitting information; an arbiter 431 manages the granting of the access to the system bus 403.

0079With reference again to Figure 3, the planning of the DVB-H network calls for ideally subdividing the geographic area of interest into relatively small, elementary area elements or pixels pxij (where / and / are two indexes which take integer values to span the area of interest), each pixel being an elementary, unit (in the shown example, square) area of predefined width, e.g. a

008050m by 50m square.

0081In the planning of the DVB-H network, the generic pixel px// is assumed to represent a virtual DVB-H receiver, i.e. it is assumed that, in the generic pixel, at least one DVB-H receiver is located.

0082In Figure 5, functional blocks that, in an embodiment of the present invention, may represent components or modules of a computer program adapted to be executed by the data processing apparatus 300 to implement a DVB-H network planning method according to an embodiment of the present invention are schematically shown. In particular, Figure 5 schematically depicts a partial content of the working memory 409 of the data processing apparatus 300. The information (programs and data) is typically stored on the hard disk and loaded (at least partially) into the working memory when the program is executed. The programs may be initially installed onto the hard disk from, e.g., CD-ROMs or DVD-ROMs, or they may be downloaded from, e.g., a distribution server machine through the data communications network 427.

0083An electromagnetic field propagation simulator module 505 simulates the electromagnetic field in the area of interest, given an initial configuration 510 of DVB-H network (number and positions of the transmitting sites, radio equipment and the like) and the characteristics 515 of the territory in the area of interest 100, which are inputs to the program. A further input to the program is a description 520 (including a map) of the area under planning, which is fed to an area subdivider module 525 adapted to subdivide the area under planning into a plurality of elementary area elements or pixels px&lt;/ as illustrated in Figure 3. The subdivision in pixels is provided to the electromagnetic field propagation simulator module 505, so that the electromagnetic field in the different pixels can be simulated. A module 530 is adapted to scan the signals that, based on the electromagnetic field distribution that is simulated by the module 505, are received at each pixel of the area under planning. An FFT window position selector module 535 is adapted to positions the FFT window that is used to simulate a DVB-H receiver demodulation process carried out by a virtual DVB-H receiver corresponding to each pixel. The FFT window position is fed to a C and / calculator module 540, that calculates the value C of the cumulated constructive contributions (the "useful signal") and the value / of the interference (the "noise"), given that FFT window position. The calculated C and / values are fed to a CII evaluator module 545, which is adapted to evaluate the value of the ratio CII for the different possible FFT window positions, based on a calculation procedure that takes into account the statistical nature of the simulated electro-magnetic field in each pixel. A man/machine interface 550 (e.g. a Graphical User Interface - GUI) is provided for the interaction of the network designer with the data processing apparatus 300.

0084The schematic flowchart of Figure 6 schematically shows the main steps of a DVB-H network planning method according to an embodiment of the present invention.

0085Firstly, based on a current DVB-H network topology (number and locations of transmissions sites, radio equipment thereof, etc.) and data related to the nature of the geographic area being planned (describing the morphology of the territory, like orography, the presence of rivers, woods, forests, the density of buildings, efc), a distribution of the electromagnetic field originating from the transmission stations is simulated, for every pixel of the area under planning (block 605).

0086Then, all the pixels of the area under planning are investigated: for each pixel (block 610), the radio signals that, based on the simulation, are received at that pixel are scanned (block 615), and the list of detected signals is stored (block 620).

0087The generic pixel is, as mentioned above, assumed to be a virtual DVB-H receiver; in particular, according to an embodiment of the present invention, every pixel is assumed to be a virtual DVB-H receiver that, in order to position the FFT window for the decoding of the received signals, adopts a criterion based on the maximization of the value of the CII ratio. To this purpose, according to an embodiment of the present invention, an initial position for the FFT window is set (block 625); for example, referring to Figure 7, the FFT window 200 is positioned in such a way that only the first received signal 705a is considered as a constructive contribution (also taking account of the guard time), thus regarding all the remaining signals 705b, 705c, 705d, 705e 705n as interferential contributions. An initial current value for C and /, and then of the C/l ratio, is thus calculated (block 630) and stored as a current CII value, exploiting the procedure described later.

0088The FFT window position is then changed (block 635) so as to embrace also the following received signal 705b. The value of the CII ratio for the current FFT window position is then recalculated (block 640), and the calculated CII value is compared to the current CII value (block 645): if the newly calculated CII value is higher than the current CII value (exit branch Y of block 645), the newly calculated CII value, corresponding to the new position of the FFT window, becomes the new current CII value (block 650), otherwise the current CII value is retained (exit branch N of block 645). These actions are repeated for all the possible FFT window positions (block 655), in particular for all the possible FFT window positions that differ for the signals embraced by the window, and for all the pixels in the area under planning (block 660). It has to be noted that as the window is shifted in one direction (for example from left to right) to embrace progressively new signals, the first embraced signals could exit the window.

0089The DVB-H network planning then proceeds with the estimation of the service area coverage (block 665), determined on the basis on the best CII value calculated for each pixel as just described. If necessary or desired, the network designer may decide to modify the network topology, by adding/removing transmission stations, by increasing/decreasing the respective transmission power so as to reduce the interference, and so on; the above procedure can then be repeated once or more so to estimate the new service coverage.

0090The planning method according to the described embodiment of the present invention provides better results than known planning software tools, and in particular it allows better estimating the service areas, and in particular avoids underestimating the indoor service coverage.

0091Hereinafter, a method for calculating the value of the CII ratio according to an embodiment of the present invention is described.

0092In particular, the method described hereinbelow is based on the observation that since in the planning phase area elements of finite geometric dimensions are considered as the virtual

0093DVB-H receivers, a proper description of the electromagnetic field in each pixel should be statistical in nature, so as to take into account the variations of the field across the pixel area; also, statistical variations in time should preferably be considered, to take into account phenomena like the fading effects. Thus, the strength (power) of the signals that, in the above-described operation flow, are considered as received in the generic pixel (based on the simulation results), are to be treated as stochastic variables. Considering a generic, linear stochastic variable y (like for example a variable representing the power of a radio signal, expressed in watts or milliwatts), it can be said that the linear variable y has a lognormal distribution if the corresponding logarithm x = lny has a normal (i.e., Gaussian) distribution, i.e. if:

0094<img file="WO2008064706A1_D0003.tif" />

0095Let a generic pixel of the area under planning, where the signals coming from n different transmission stations are received. Let P₁[UBm] denote the local average value (expressed in dBm) of the power of the signal received in the considered pixel from the ;-th transmission station; P₁IdBm] is a stochastic variable having a Gaussian distribution with average value μ_p [dBm] l o and standard deviation σ_p [dBm] .

0096Despite it could be possible to perform the statistic sum of the powers of the n signals received at the pixel considered (under the assumption that the received signals are statistically independent, the sum is again a Gaussian variable, with average value equal to the sum of the average values, and variance equal to sum of the variances), this sum would be meaningless from

009715 a physical viewpoint.

0098In order to properly describe, from the statistical viewpoint, the sum of the different signals which, in the simulation, are received at the generic pixel, the statistical distributions of the corresponding linear variables (expressed in mW) are considered, and they are statistically added to each other.

009920 Therefore, according to the present invention, there is a transformation from a logarithmic unit (dBm) into a linear unit (mW), some processing in the linear field, and then a retransformation from linear unit (mW) into logarithmic unit (dBm).

0100In order to pass from the simulated signal powers expressed in dBm to the expression thereof in mW, the dBm variables are firstly transformed into neper variables, exploiting the 25 following equations: Up \neper] = μ_p [dBm] μ^{pX P J} 101og₁₀ e ^μp' ^{V J} σ_p [neper] = — σ_p [dBm]

0101101og₁₀ e

0102Using neper variables, it is possible to express the average μ_p [Hn] and the standard deviation σ_p [liή] of the lognormal distribution of the corresponding linear variables P₁[Un] as:

0103<img file="WO2008064706A1_D0004.tif" />

0104Let it be assumed that the sum of n stochastic variables with lognormal distribution is again a stochastic variable P[Hn] with lognormal distribution, having average value μ_p[Hή] equal to the sum of the averages, and variance σ_p²[liή] equal to the sum of the variances (the contribute of the co-variance is neglected, in the hypothesis that the n signals are statistical independent; in reality, the signals are not really independent, because the effect of shadowing to which they are affected is strongly dependent on the position of the mobile terminal):

0105<img file="WO2008064706A1_D0005.tif" />

0106Since:

0107<img file="WO2008064706A1_D0006.tif" />

0108the average μ_p[dBm] and the variance σ_ρ[dBm] of the Gaussian distribution describing the stochastic variable in logarithmic units P[dBm] can now be derived from:

0109μ_p[dBm] = 10 • log₁₀ e • μ_P[nep] σ_p[dBm] = 10 • log₁₀ e • σ_p[nep]

0110It is remarkable that the average of the neper variables, and thus the average in dBm variables, depend not only on the average of the linear variables, but also on the variance of the linear variables; similarly, the variance of the neper variables, and thus the variance in dBm variables, depend not only on the variance of the linear variables, but also on the average of the linear variables.

0111The above procedure is the proper way to add up different contributions, either constructive or interferential, during the planning phase, taking into account of their statistic nature.

0112Based on the above considerations, the value of the CII ratio can be calculated as illustrated in the flowchart of Figure 8.

0113As a result of the simulation performed by the electromagnetic field propagation simulator 505, n signals are received at the generic pixel, corresponding to the n different transmission stations; the power, in dBm, of each of the n signals is a stochastic variable having normal distribution, with average value μ_p [dBm] and standard deviation σ_p [dBm] .

0114As a first step, the average values μ_p [dBm] and the variances σ_p [dBm] (with i = 1 to n) in dBm are transformed into neper (block 705), using the above equations (eq.1).

0115Then, the average values μ_p [neper] and the variances σ_p [neper] (with i = 1 to n) in neper are transformed into mW (block 710), using the above equations (eq.2).

0116Assuming, by way of approximation, that the virtual DVB-H receiver represented by the generic pixel of the area under planning regards as constructive contributions all the signals that are received within the decoding window, while the remaining signals are regarded as providing an interfering contribution, the statistical distributions of the useful signal C and of the interference / can be calculated in the following way:

0117C = ∑C,(t) i,t_o≤l≤t_o+T_u<img file="WO2008064706A1_D0007.tif" />

0118where d(t) denotes the power of the /-th signal irradiated by the /-th transmission station, in mW, calculated based on the simulation of the propagation of the electromagnetic field, and to is the instant at which the start of the FFT window is from time to time positioned. The average value μ_c[lin] and the variance σ_c[lin\ of the power (in mW) of the useful signal C are calculated as the sum of the average values and variances (in mW) of the constructive contributions (blocks 715); the same is done for the interference /, considering the interferential contributions (block 720).

0119Having the average value and the variance of the statistical distributions of the useful signal

0120C and of the interference /, it is possible to calculate the ratio C/l. In fact, assuming that the two stochastic variables C and / are statistically uncorrelated, by performing the calculations in dBs the average value of the ratio CII is equal to the difference, in dBs, of the average values of C and /, and the variance is equal to the sum of the variances of C and / in dBs. Preferably, the interference / is increased of an amount N being an additional interference contribute that takes into account all the other sources of interference (due to the environment).

0121In greater detail, the average value μrfneper] and μι[neper] and the variance σrfneper] and σi[neper] of C and / are calculated from the average value and variance in mW (blocks 725 and 730), using the formula (eq. 4) given above.

0122The average value and the variance μc[dBm] and μ[dBm] and the variance σc[dBm] and cη[dBm] of C and / are then calculated from the average value and variance in neper (blocks 735 and 740), using the formula (eq. 5) given above.

0123Finally, the average value and the variance of the ratio C//, expressed in dBm, can be calculated as follows (block 745):

0124μ_cι JdBm] - μ_c[dBm] — μ AdBm] a).,, [dBm] = σ_c² [dBm] + σ) [dBm]

0125The present invention has been here described in detail making reference to an exemplary embodiment; however, those skilled in the art will understand that several modifications to the described embodiment, as well as alternative embodiments are conceivable, without departing from the scope of the invention defined in the appended claims.

0126In particular, although described in conjunction with a peculiar FFT positioning method, the present invention is not to be construed as limited to that method, on the contrary it can be exploited in conjunction with any FFT window positioning method.