Dual-loop automatic frequency control for wireless communication

The present application claims priority to provisional U.S. Application Ser. No. 60/657,839, entitled “Method and Apparatus for Dual-Loop Automatic Frequency Control,” filed Mar. 1, 2005, and U.S. application Ser. No. 60/660,914, entitled “Automatic Frequency Controller,” filed Mar. 11, 2005, both assigned to the assignee hereof and incorporated herein by reference.

BACKGROUND

I. Field

The present disclosure relates generally to communication, and more specifically to automatic frequency control (AFC) for wireless communication.

II. Background

In wireless communication, a transmitter modulates data onto a radio frequency (RF) carrier signal to generate an RF modulated signal that is more suitable for transmission. The transmitter then transmits the RF modulated signal via a wireless channel to a receiver. The transmitted signal may reach the receiver via one or more propagation paths, which may include a line-of-sight path and/or reflected paths. The characteristics of the wireless channel may vary over time due to various phenomena such as fading and multipath. Consequently, the transmitted signal may experience different channel conditions and may be received with different amplitudes and/or phases over time.

The receiver receives the transmitted signal, downconverts the received signal with a local oscillator (LO) signal, and processes the downconverted signal to recover the data sent by the transmitter. The receiver typically performs frequency control (e.g., frequency acquisition and tracking) to estimate the frequency error in the LO signal and to correct this frequency error. This frequency error may be due to various factors such as receiver circuit component tolerances, temperature variations, and Doppler effect due to movement by the receiver and/or transmitter. The frequency control may be challenging if the requirements on frequency accuracy are stringent. The frequency control may also be complicated if the receiver intermittently receives data from the transmitter.

There is therefore a need in the art for techniques to expeditiously and reliably perform frequency control for wireless communication.

SUMMARY

Techniques for performing frequency control using dual-loop AFC are described herein. The dual-loop AFC includes an inner loop that corrects short-term frequency variations (e.g., due to Doppler effect) and an outer loop that corrects long-term frequency variations (e.g., due to component tolerances and temperature variations). These techniques may be used for frequency control when receiving one or multiple communication systems, e.g., a broadcast system, a cellular system and/or a satellite positioning system. These techniques may also be used for frequency control when receiving a bursty transmission.

In an aspect, the dual-loop AFC is used for frequency control of multiple systems. In an embodiment, a first inner loop is implemented for frequency control of a first system (e.g., a broadcast system), a second inner loop is implemented for frequency control of a second system (e.g., a cellular system), and at least one outer loop is implemented for adjusting a reference frequency used to receive the first and second systems. The reference frequency may be generated by a reference oscillator (e.g., a TC-VCXO) and may be used for frequency downconversion, sampling and/or other purposes. The first inner loop estimates and corrects the frequency error in a first input signal for the first system. The second inner loop estimates and corrects the frequency error in a second input signal for the second system. The first and second inner loops may be enabled when receiving the first and second systems, respectively. Separate first and second outer loops may be implemented for the first and second systems, respectively, and one outer loop may be selected to update the reference frequency. Alternatively, a single outer loop may be implemented for both systems and may be updated with first and/or second inner loop. Exemplary designs of the inner and outer loops are described below.

In another aspect, the dual-loop AFC is used for frequency control of a bursty transmission in which data is received in bursts. In an embodiment, an AFC inner loop is updated in each inner loop update instant during each burst of data, and an AFC outer loop is updated in each outer loop update instant. The inner loop estimates and corrects the frequency error in the bursts of data. The outer loop estimates and corrects the frequency error in a reference frequency used to receive the bursts of data. The inner loop may be updated, e.g., with each OFDM symbol received during a burst of data. The outer loop may be updated, e.g., at the end of each burst of data.

Various aspects and embodiments of the invention are described in further detail below.

BRIEF DESCRIPTION OF THE DRAWINGS

The features and nature of the present invention will become more apparent from the detailed description set forth below when taken in conjunction with the drawings in which like reference characters identify correspondingly throughout.

<figref idrefs="DRAWINGS">FIG. 1</figref> shows a terminal communicating with multiple systems.

<figref idrefs="DRAWINGS">FIG. 2</figref> shows an exemplary super-frame structure.

<figref idrefs="DRAWINGS">FIG. 3</figref> shows a block diagram of the terminal.

<figref idrefs="DRAWINGS">FIG. 4</figref> shows a block diagram of an AFC unit.

<figref idrefs="DRAWINGS">FIG. 5</figref> shows a block diagram of the dual-loop AFC for one system.

<figref idrefs="DRAWINGS">FIG. 6</figref> shows a block diagram of an initial frequency error estimator.

<figref idrefs="DRAWINGS">FIG. 7</figref> shows a block diagram of a frequency error estimator.

<figref idrefs="DRAWINGS">FIG. 8</figref> shows a model of the dual-loop AFC.

<figref idrefs="DRAWINGS">FIG. 9</figref> shows a process to perform frequency control for multiple systems.

<figref idrefs="DRAWINGS">FIG. 10</figref> shows an apparatus to perform frequency control for multiple systems.

<figref idrefs="DRAWINGS">FIG. 11</figref> shows a process to perform frequency control for one system.

<figref idrefs="DRAWINGS">FIG. 12</figref> shows an apparatus to perform frequency control for one system.

<figref idrefs="DRAWINGS">FIG. 13</figref> shows a process to perform frequency control for bursty data.

<figref idrefs="DRAWINGS">FIG. 14</figref> shows an apparatus to perform frequency control for bursty data.

DETAILED DESCRIPTION

The word “exemplary” is used herein to mean “serving as an example, instance, or illustration.” Any embodiment or design described herein as “exemplary” is not necessarily to be construed as preferred or advantageous over other embodiments or designs.

<figref idrefs="DRAWINGS">FIG. 1</figref> shows a terminal <b>110</b> capable of communicating with multiple communication systems. These systems may include a cellular system <b>120</b>, a broadcast system <b>130</b>, a satellite positioning system <b>140</b>, a wireless local area network (WLAN) system (not shown in <figref idrefs="DRAWINGS">FIG. 1</figref>), other systems, or any combination thereof.

Cellular system <b>120</b> may be a Code Division Multiple Access (CDMA) system, a Time Division Multiple Access (TDMA) system, a Frequency Division Multiple Access (FDMA) system, an Orthogonal Frequency Division Multiple Access (OFDMA) system, a Single-Carrier FDMA (SC-FDMA) system, or some other cellular system. A CDMA system may utilize a radio technology such as cdma2000, Wideband-CDMA (W-CDMA), and so on. cdma2000 covers IS-95, IS-2000 and IS-856 standards. A TDMA system may utilize a radio technology such as Global System for Mobile Communications (GSM), Digital Advanced Mobile Phone System (D-AMPS), and so on. D-AMPS covers IS-136 and IS-54 standards. These various systems, radio technologies, and standards are known in the art. Cellular system <b>120</b> may be a Universal Mobile Telecommunication System (UMTS) that implements W-CDMA, a CDMA2000 1× system that implements IS-2000 and/or IS-95, a CDMA2000 1xEV-DO system that implements IS-856, a GSM system, or some other system.

Broadcast system <b>130</b> may be a MediaFLO system, a Digital Video Broadcasting for Handhelds (DVB-H) system, an Integrated Services Digital Broadcasting for Terrestrial Television Broadcasting (ISDB-T) system, or some other broadcast system. These broadcast systems are known in the art.

Satellite positioning system <b>140</b> may be the United States Global Positioning System (GPS), the Russian Glonass system, the European Galileo system, or some other satellite positioning system. GPS is a constellation of 24 well-spaced satellites plus some spare satellites that orbit the earth. Each GPS satellite transmits an encoded signal that allows receivers on earth to accurately estimate their positions based on measurements for a sufficient number of satellites (typically four) and the known locations of these satellites.

As shown in <figref idrefs="DRAWINGS">FIG. 1</figref>, cellular system <b>120</b> includes a number of base stations <b>122</b> that support communication for the terminals within their coverage. A base station is typically a fixed station used for communicating with the terminals and may also be called a base transceiver subsystem (BTS), a Node B, an access point, and so on. Broadcast system <b>130</b> includes a number of broadcast stations <b>132</b> that broadcast data to the terminals within their coverage. Base stations <b>122</b> and broadcast stations <b>132</b> may be located at different sites (as shown in <figref idrefs="DRAWINGS">FIG. 1</figref>) or co-located at the same site (not shown in <figref idrefs="DRAWINGS">FIG. 1</figref>). Satellite positioning system <b>140</b> includes a number of satellites <b>142</b> that transmit signals used for position determination.

Terminal <b>110</b> may be fixed or mobile and may also be called a mobile station, a user equipment, a mobile equipment, and so on. Terminal <b>110</b> may be a cellular phone, a personal digital assistant (PDA), a wireless modem, a wireless communication device, a handheld device, a subscriber unit, and so on. For clarity, much of the following description is for an embodiment in which terminal <b>110</b> is capable of communicating with a CDMA system (which may be a UMTS system or a CDMA 1× system), the MediaFLO system, and GPS.

<figref idrefs="DRAWINGS">FIG. 2</figref> shows an exemplary super-frame structure <b>200</b> that may be used for broadcast system <b>130</b>. In the embodiment shown in <figref idrefs="DRAWINGS">FIG. 2</figref>, the transmission timeline is partitioned into super-frames, with each super-frame having a particular time duration, e.g., approximately one second. Each super-frame includes a field <b>212</b> for a time division multiplexed (TDM) pilot, a field <b>214</b> for overhead/control information, and a field <b>216</b> with N frames for traffic data, where N≧1. A super-frame may also include different and/or additional fields not shown in <figref idrefs="DRAWINGS">FIG. 2</figref>.

In the embodiment shown in <figref idrefs="DRAWINGS">FIG. 2</figref>, the TDM pilot is composed of S identical pilot sequences, with each pilot sequence containing L time-domain samples, where S&gt;1 and L&gt;1. The TDM pilot may be generated by (1) performing an L-point inverse fast Fourier transform (IFFT) on L modulation symbols to obtain a pilot sequence with L time-domain samples and (2) repeating the pilot sequence S times. The TDM pilot may be used for signal detection, frame synchronization, initial frequency error estimation, coarse time synchronization and/or other purposes.

The overhead information may convey the identity of a broadcast station transmitting the overhead information, where and how data channels are sent in the frames of a super-frame, and/or other information. The data channels are sent in the N frames and at frequency and time locations indicated by the overhead information. Each data channel may carry any type of data such as video, audio, tele-text, data, video/audio clips, and so on. Terminal <b>110</b> may be interested in receiving one or more specific data channels from broadcast system <b>130</b>. Terminal <b>110</b> may ascertain where each desired data channel is sent, e.g., based on the overhead information and/or the data sent on the data channel. Terminal <b>110</b> may go to sleep much of the time to conserve battery power and may wake up periodically to receive the desired data channel(s).

In the embodiment shown in <figref idrefs="DRAWINGS">FIG. 2</figref>, data is transmitted using Orthogonal Frequency Division Multiplexing (OFDM). OFDM partitions the system bandwidth into multiple (K) orthogonal subcarriers, which are also called tones, bins, and so on. Each subcarrier may be modulated with data. Each frame carries multiple (M) OFDM symbols. An OFDM symbol may be generated by (1) performing a K-point IFFT on K modulation symbols to obtain K time-domain samples for a data portion of the OFDM symbol and (2) copying the last C samples of the data portion to form a cyclic prefix for the OFDM symbol. The data portion is also referred to as a useful portion, a transformed symbol, and so on. Windowing/filtering may also be performed on the cyclic prefix and the data portion. An OFDM symbol may contain K+C samples without windowing or possibly more than K+C samples with windowing.

In an embodiment, K=4096, C=512, and each OFDM symbol contains 4608 time-domain samples prior to windowing. In an embodiment, L=128, S=36, and the TDM pilot contains 36 identical pilot sequences of length <b>128</b>. Other values may also be used for K, C, L and S.

<figref idrefs="DRAWINGS">FIG. 2</figref> shows a specific super-frame structure. The frequency control techniques described herein may also be used for other frame and super-frame structures.

<figref idrefs="DRAWINGS">FIG. 3</figref> shows a block diagram of an embodiment of terminal <b>110</b>. In this embodiment, terminal <b>110</b> includes an antenna <b>310</b><i>a </i>and a receiver <b>320</b><i>a </i>to receive signals from the cellular system, an antenna <b>310</b><i>b </i>and a receiver <b>320</b><i>b </i>to receive signals from the broadcast system, and an antenna <b>310</b><i>c </i>and a receiver <b>320</b><i>c </i>to receive signals from GPS satellites. In general, terminal <b>110</b> may include any number of antennas and any number of receivers for any number of systems. Multiple systems may share an antenna if the antenna can provide suitable performance for these systems. Multiple systems may also share a receiver if these systems are not received simultaneously. Multiple antennas and/or multiple receivers may also be used for a given system, e.g., to receive signals in different frequency bands (e.g., cellular and PCS bands).

For the broadcast system, antenna <b>310</b><i>b </i>receives signals transmitted by broadcast stations and provides a received RF signal to receiver <b>320</b><i>b</i>. Within receiver <b>320</b><i>b</i>, a low noise amplifier (LNA) <b>322</b><i>b </i>amplifies the received RF signal and provides an amplified RF signal. A filter <b>322</b><i>b </i>filters the amplified RF signal to pass signal components in the band of interest and to remove out-of-band noise and undesired signals. A downconverter <b>324</b><i>b </i>frequency downconverts the filtered RF signal with an LO signal B_LOfrom an LO generator <b>344</b> and provides a downconverted signal. The frequency of the B_LOsignal is selected such that the signal component in an RF channel of interest is downconverted to baseband or near-baseband. A lowpass filter <b>326</b><i>b </i>filters the downconverted signal to pass the signal components in the RF channel of interest and to remove noise and undesired signals. An amplifier <b>326</b><i>b </i>amplifies the filtered baseband signal and provides an output baseband signal. An analog-to-digital converter (ADC) <b>328</b><i>b </i>digitizes the output baseband signal and provides input samples B_into a data processor <b>330</b>.

Antenna <b>310</b><i>a </i>and receiver <b>320</b><i>a </i>similarly receive and process signals transmitted by base stations in the cellular system and provide input samples C_into data processor <b>330</b>. Antenna <b>310</b><i>c </i>and receiver <b>320</b><i>c </i>receive and process signals transmitted by GPS satellites and provide input samples G_into data processor <b>330</b>. Although not shown in <figref idrefs="DRAWINGS">FIG. 3</figref> for simplicity, the input samples B_in, C_inand G_inmay be complex-valued samples having inphase (I) and quadrature (Q) components.

<figref idrefs="DRAWINGS">FIG. 3</figref> shows a specific design for receivers <b>320</b><i>a</i>, <b>320</b><i>b </i>and <b>320</b><i>c</i>. In general, a receiver may implement a super-heterodyne architecture or a direct-to-baseband architecture. In the super-heterodyne architecture, the received RF signal is downconverted in multiple stages, e.g., from RF to an intermediate frequency (IF) in one stage, and then from IF to baseband in another stage. In the direct-to-baseband architecture, which is shown in <figref idrefs="DRAWINGS">FIG. 3</figref>, the received RF signal is downconverted from RF directly to baseband in one stage. The super-heterodyne and direct-to-baseband architectures may use different circuit blocks and different LO frequencies.

In general, a receiver may perform signal conditioning with one or more stages of amplifier, filter, mixer, and so on. A receiver may include different and/or additional circuit blocks not shown in <figref idrefs="DRAWINGS">FIG. 3</figref>.

Data processor <b>330</b> processes the input samples B_in, C_inand G_inand provides output data for each system. The processing for each system is dependent on the radio technology used by that system and may include demodulation, decoding, and so on. Data processor <b>330</b> is shown as a single processor in <figref idrefs="DRAWINGS">FIG. 3</figref> but may comprise one or more application specific integrated circuits (ASICs), digital signal processors (DSPs), processors, and so on.

An AFC unit <b>340</b> estimates frequency error of a reference oscillator <b>342</b> and generates a frequency control signal F_ctrl, as described below. Reference oscillator <b>342</b> generates a reference signal having a precise frequency f_ref. Reference oscillator <b>342</b> may be a voltage controlled crystal oscillator (VCXO), a temperature compensated crystal oscillator (TCXO), a voltage controlled TCXO (VC-TCXO), a voltage controlled oscillator (VCO), or some other type of oscillator. LO generator <b>344</b> receives the reference signal and generates the LO signals for receivers <b>320</b><i>a</i>, <b>320</b><i>b </i>and <b>320</b><i>c</i>. A clock generator <b>346</b> also receives the reference signal and generates sampling clocks for ADCs <b>328</b><i>a</i>, <b>328</b><i>b </i>and <b>328</b><i>c</i>. LO generator <b>344</b> and clock generator <b>346</b> may each be implemented with VCOs, phase locked loops (PLLs), dividers, and so on, as is known in the art.

A controller/processor <b>350</b> directs the operation of various units at terminal <b>110</b>. Controller/processor <b>350</b> may determine which system(s) to receive and which channel(s) to receive for each system. A memory <b>352</b> stores program codes and data for terminal <b>110</b>.

In the embodiment shown in <figref idrefs="DRAWINGS">FIG. 3</figref>, reference oscillator <b>342</b> provides the reference frequency f_refthat is used to generate the LO signals as well as the sampling clocks for all systems. The use of a single reference oscillator for all systems may reduce cost, power and area and may further simplify operation at terminal <b>110</b>.

Each transmitter in each system (e.g., each base station, each broadcast station, and each satellite) typically transmits at a precise data rate on a precise RF frequency. The reference oscillator at the terminal is relatively accurate but may have frequency error due to component tolerances, temperature variations, and other factors. Furthermore, frequency error may exist between a given transmitter and the terminal due to Doppler effect caused by movement of the terminal and/or transmitter. Frequency error due to component tolerances and temperature variations typically varies at a slow rate and is common for all systems. Frequency error due to Doppler effect may vary at a faster rate and may be different for different transmitters.

In an aspect, dual-loop AFC is used for frequency control at the terminal. The dual-loop AFC includes (1) an inner loop that corrects short-term frequency variations, e.g., due to Doppler effect, and (2) an outer loop that corrects long-term frequency variations, e.g., due to component tolerances and temperature variations. The dual-loop AFC may be controlled such that good performance is achieved for all systems being received, regardless of which systems are being received.

<figref idrefs="DRAWINGS">FIG. 4</figref> shows a block diagram of an embodiment of AFC unit <b>340</b> in <figref idrefs="DRAWINGS">FIG. 3</figref>. In this embodiment, AFC unit <b>340</b> implements an inner loop and an outer loop for the cellular system and an inner loop and an outer loop for the broadcast system. The reference oscillator is driven by either the outer loop for the cellular system or the outer loop for the broadcast system.

Within AFC unit <b>340</b>, an inner loop unit <b>410</b><i>a </i>receives the input samples C_infor the cellular system, estimates the short-term frequency error between a base station and the terminal, corrects this frequency error in the input samples C_inand provides output samples C_outto a cellular demodulator (Demod) <b>450</b><i>a</i>, and further provides a short-term frequency error estimate F_Cinfor the cellular system. Similarly, an inner loop unit <b>410</b><i>b </i>receives the input samples B_infor the broadcast system, estimates the short-term frequency error between a broadcast station and the terminal, corrects this frequency error in the input samples B_inand provides output samples B_outto a broadcast demodulator <b>450</b><i>b</i>, and further provides a short-term frequency error estimate F_Binfor the broadcast system. Units <b>410</b><i>a </i>and <b>410</b><i>b </i>implement the inner loops for the cellular and broadcast systems, respectively.

An outer loop unit <b>420</b><i>a </i>receives the short-term frequency error estimate F_Cinfor the cellular system, estimates the long-term frequency error for the terminal, and provides a long-term frequency error estimate F_Coutto a mode selector <b>430</b>. Similarly, an outer loop unit <b>420</b><i>b </i>receives the short-term frequency error estimate F_Binfor the broadcast system, estimates the long-term frequency error for the terminal, and provides a long-term frequency error estimate F_Boutto mode selector <b>430</b>. Selector <b>430</b> selects either the F_Coutor F_Boutfrequency error estimate based on a Mode_sel control signal and generates the F_ctrlcontrol signal for the reference oscillator. The F_ctrlsignal may be an analog signal or a digital signal. Selector <b>430</b> may perform signal conditioning such as digital-to-analog conversion, level shifting, scaling, and so on. Selector <b>430</b> may also generate a pulse width modulated (PWM) control signal.

<figref idrefs="DRAWINGS">FIG. 4</figref> shows an embodiment in which two outer loops are maintained for two systems, and the reference oscillator is adjusted based on the outer loop for one system. In another embodiment, a single outer loop is maintained for both systems, and the reference oscillator is adjusted based on this single outer loop. This outer loop may receive the F_Binand F_Cinfrequency error estimates from the inner loops for the two systems and may generate a single F_outbased on these frequency error estimates.

Table 1 lists two modes of operation for the terminal. In the cellular and broadcast mode, the terminal concurrently receives the cellular and broadcast systems. In the broadcast-only mode, the terminal receives the broadcast system but not the cellular system. The terminal may also operate in a cellular-only mode (not shown in Table 1) in which the terminal receives the cellular system but not the broadcast system. The terminal may also receive GPS in any operating mode.

Table 1 also lists an embodiment of operating the inner and outer loops for each operating mode. In the cellular and broadcast mode, the inner loops for the cellular and broadcast systems are enabled and track the short-term frequency errors for these systems, and only the outer loop for the cellular system is enabled to control the reference oscillator. In the broadcast-only mode, the inner and outer loops for the cellular system are disabled, the inner and outer loops for the broadcast system are enabled, and the reference oscillator is controlled by the outer loop for the broadcast system.

<tables id="TABLE-US-00001" num="00001"><table frame="none" colsep="0" rowsep="0"><tgroup align="left" colsep="0" rowsep="0" cols="3"><colspec colname="offset" colwidth="112pt" align="left" /><colspec colname="1" colwidth="49pt" align="left" /><colspec colname="2" colwidth="56pt" align="left" /><thead><row><entry /><entry namest="offset" nameend="2" rowsep="1">TABLE 1</entry></row><row><entry /><entry namest="offset" nameend="2" align="center" rowsep="1" /></row><row><entry /><entry>Cellular and</entry><entry /></row><row><entry /><entry>Broadcast</entry><entry>Broadcast-Only</entry></row><row><entry /><entry namest="offset" nameend="2" align="center" rowsep="1" /></row></thead><tbody valign="top"><row><entry /></row></tbody></tgroup><tgroup align="left" colsep="0" rowsep="0" cols="4"><colspec colname="offset" colwidth="14pt" align="left" /><colspec colname="1" colwidth="98pt" align="left" /><colspec colname="2" colwidth="49pt" align="left" /><colspec colname="3" colwidth="56pt" align="left" /><tbody valign="top"><row><entry /><entry>Control of reference oscillator</entry><entry>from cellular</entry><entry>from broadcast</entry></row><row><entry /><entry /><entry>outer loop</entry><entry>outer loop</entry></row><row><entry /><entry>Cellular inner loop</entry><entry>Enabled</entry><entry>Disabled</entry></row><row><entry /><entry>Cellular outer loop</entry><entry>Enabled</entry><entry>Disabled</entry></row><row><entry /><entry>Broadcast inner loop</entry><entry>Enabled</entry><entry>Enabled</entry></row><row><entry /><entry>Broadcast outer loop</entry><entry>Disabled</entry><entry>Enabled</entry></row><row><entry /><entry namest="offset" nameend="3" align="center" rowsep="1" /></row></tbody></tgroup></table></tables>

<figref idrefs="DRAWINGS">FIG. 4</figref> and Table 1 show an embodiment in which the reference oscillator is controlled by either the cellular system or the broadcast system. In other embodiments, the reference oscillator may be controlled by different and/or additional systems. For example, if the terminal receives GPS but not cellular or broadcast, then the reference oscillator may be controlled by an AFC unit that operates based on GPS signals. For clarity, the following description is for the embodiment shown in <figref idrefs="DRAWINGS">FIG. 4</figref> and Table 1.

The inner and outer loops for the cellular and broadcast systems may be implemented in various manners. An exemplary design for the inner and outer loops for the broadcast system is described below.

<figref idrefs="DRAWINGS">FIG. 5</figref> shows a block diagram of an embodiment of inner loop unit <b>410</b><i>b </i>and outer loop unit <b>420</b><i>b </i>for the broadcast system. Within inner loop unit <b>410</b><i>b</i>, the input samples B_inare provided to a phase rotator <b>510</b> and an initial frequency error estimator <b>520</b>. Estimator <b>520</b> derives an initial frequency error estimate Δ{circumflex over (f)}_init(e.g., based on the TDM pilot) whenever directed and provides the initial frequency error estimate to one input of a multiplexer (Mux) <b>546</b>. Phase rotator <b>510</b> rotates each input sample B_inby a phase value θ_kfrom a phase accumulator <b>512</b> and provides a phase-rotated output sample B_out. The output samples have much of the short-term frequency error removed once frequency lock is achieved for the broadcast system. A frequency error estimator <b>530</b> derives frequency error estimates Δ{circumflex over (f)}_m, e.g., based on received OFDM symbols. The frequency error estimates are indicative of residual frequency error in the output samples. A frequency lock detector <b>532</b> determines whether frequency lock is achieved for the broadcast system.

A loop filter <b>540</b> filters the frequency error estimates Δ{circumflex over (f)}_mand provides F_Bin, which is indicative of the short-term frequency error for the broadcast system. Within loop filter <b>540</b>, a multiplier <b>542</b> multiplies the frequency error estimates Δ{circumflex over (f)}_mwith an inner loop gain α. A summer <b>544</b> sums the output of multiplier <b>542</b> with the output of a frequency register <b>548</b>. Multiplexer <b>546</b> receives the output of summer <b>544</b> at another input and provides either the output of summer <b>544</b> or the initial frequency error estimate Δ{circumflex over (f)}_init. Frequency register <b>548</b> stores the output of multiplexer <b>546</b> and provides the short-term frequency error estimate F_Bin. Phase accumulator <b>512</b> accumulates the short-term frequency error estimate in each sample period and provides the phase correction for each input sample.

Within outer loop unit <b>420</b><i>b</i>, a frequency accumulator <b>550</b> accumulates the frequency error estimate F_Binfrom register <b>548</b> and provides an accumulated frequency error. A counter <b>552</b> counts the number of times that F_Binis accumulated in accumulator <b>550</b>. A unit <b>554</b> divides the accumulated frequency error by the number of accumulations and provides an average frequency error estimate Δ{circumflex over (f)}_avg. A loop filter <b>560</b> filters the average frequency error estimate and provides F_Bout, which is indicative of the long-term frequency error in the reference frequency. Within loop filter <b>560</b>, a multiplier <b>562</b> multiplies the average frequency error estimate with an outer loop gain β. A unit <b>564</b> may limit the output of multiplier <b>562</b> to within a particular range to constrain the amount of adjustment to the outer loop in any update period. Unit <b>564</b> may also scale the output of multiplier <b>562</b>. A summer <b>566</b> sums the output of unit <b>564</b> with the output of a frequency register <b>570</b>. Frequency register <b>570</b> stores the output of summer <b>566</b> and provides the long-term frequency error estimate F_Bout.

The inner and outer loops for the broadcast system may operate as follows. When the terminal first wakes up or first tunes to the broadcast system, estimator <b>520</b> derives an initial frequency error estimate Δ{circumflex over (f)}_initthat captures much of the short-term and long-term frequency error at the terminal. Frequency register <b>548</b> stores the initial frequency error estimate. Phase accumulator <b>512</b> computes the phase shift in each sample period due to the frequency error from register <b>548</b>. Phase rotator <b>510</b> rotates each input sample by the phase shift from phase accumulator <b>512</b>. Thereafter, for each received OFDM symbol, estimator <b>530</b> derives a frequency error estimate Δ{circumflex over (f)}_mbased on the output samples for that OFDM symbol. The frequency error estimate Δ{circumflex over (f)}_mis scaled by the inner loop gain α and accumulated by frequency register <b>548</b> via summer <b>544</b> and multiplexer <b>546</b>. Hence, frequency register <b>548</b> is initialized with the initial frequency error estimate and is thereafter updated by the frequency error estimate from each received OFDM symbol.

In an embodiment, outer loop <b>420</b><i>b </i>is updated in each frame. Frequency accumulator <b>550</b>, counter <b>552</b> and frequency register <b>570</b> are reset to zero at the start of each frame. Thereafter, frequency accumulator <b>550</b> accumulates the output of frequency register <b>548</b> in each OFDM symbol period and up to M times in one frame for the super-frame structure shown in <figref idrefs="DRAWINGS">FIG. 2</figref>. Counter <b>552</b> increments by one each time the output of register <b>548</b> is accumulated by accumulator <b>550</b>. At the end of each frame, unit <b>554</b> computes the average frequency error estimate Δ{circumflex over (f)}_avg, which is then scaled by the outer loop gain β, limited and/or scaled by unit <b>564</b>, and accumulated by frequency register <b>570</b> via summer <b>566</b>. Frequency register <b>570</b> is updated by a scaled version of the average frequency error estimate in each frame.

In the embodiment described above, phase rotation is performed on each input sample, the inner loop is updated in each OFDM symbol period, and the outer loop is updated in each frame. The inner and outer loops may also be updated at other rates. In general, the inner loop may be updated whenever a frequency error estimate is available, and the outer loop may be updated whenever an average frequency error estimate is available. For example, the outer loop may be updated after receiving a burst of data. The inner and outer loops may also be operated in different modes, e.g., an acquisition mode and a tracking mode, as described below.

The input samples for the broadcast system may be expressed as: <br /><i>x</i>(<i>k</i>)=<i>s</i>(<i>k</i>)·<i>e</i>^{j2π·Δf·k·T}^{<sub2>s</sub2>}^+φ<i>+n</i>(<i>k</i>),  Eq (1)<br /> where s(k) is a sample transmitted in sample period k, x(k) is an input sample for sample period k, n(k) is the noise for input sample x(k), Δf is a frequency error, φ is an arbitrary phase, and T_sis one sample period.

The TDM pilot contains S identical pilot sequences, as shown in <figref idrefs="DRAWINGS">FIG. 2</figref>. Hence, the transmitted samples are periodic during the TDM pilot, and s(k)=s(k+L). In this case, a correlation on the input samples may be expressed as: <br /><i>x</i>*(<i>k</i>)·<i>x</i>(<i>k+L</i>)=|<i>s</i>(<i>k</i>)|²<i>·e</i>^{j2π·Δf·L·T}^{<sub2>s</sub2>}<i>+ñ</i>(<i>k</i>),  Eq (2)<br /> where ñ(k) is the post-processed noise. Equation (2) indicates that the frequency error Δf may be isolated by correlating input sample x(k) with delayed input sample x(k+L).

A delayed correlation may be performed for each pilot sequence as follows:

<maths id="MATH-US-00001" num="00001"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><msub><mi>C</mi><mi>l</mi></msub><mo>=</mo><mrow><munderover><mo>∑</mo><mrow><mi>i</mi><mo>=</mo><mn>1</mn></mrow><mi>L</mi></munderover><mo>⁢</mo><mrow><mrow><msubsup><mi>x</mi><mi>l</mi><mo>*</mo></msubsup><mo>⁡</mo><mrow><mo>(</mo><mi>i</mi><mo>)</mo></mrow></mrow><mo>·</mo><mrow><msub><mi>x</mi><mi>l</mi></msub><mo>⁡</mo><mrow><mo>(</mo><mrow><mi>i</mi><mo>+</mo><mi>L</mi></mrow><mo>)</mo></mrow></mrow></mrow></mrow></mrow><mo>,</mo></mrow></mtd><mtd><mrow><mi>Eq</mi><mo>⁢</mo><mstyle><mspace width="0.8em" height="0.8ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><mn>3</mn><mo>)</mo></mrow></mrow></mtd></mtr></mtable></math></maths><br /> where x_l(i)=x(i+l·k_s) is the i-th input sample for the l-th pilot sequence, <ul><li id="ul0001-0001" num="0000"><ul><li id="ul0002-0001" num="0070">k_sis the sample index for the start of the first pilot sequence, and</li><li id="ul0002-0002" num="0071">C_lis the correlation result for the l-th pilot sequence.</li></ul></li></ul>

The correlation results for multiple pilot sequences may be accumulated, as follows:

<maths id="MATH-US-00002" num="00002"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><msub><mi>C</mi><mi>init</mi></msub><mo>=</mo><mrow><munderover><mo>∑</mo><mrow><mi>l</mi><mo>=</mo><mn>1</mn></mrow><msup><mi>S</mi><mi>′</mi></msup></munderover><mo>⁢</mo><msub><mi>C</mi><mi>l</mi></msub></mrow></mrow><mo>,</mo></mrow></mtd><mtd><mrow><mi>Eq</mi><mo>⁢</mo><mstyle><mspace width="0.8em" height="0.8ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><mn>4</mn><mo>)</mo></mrow></mrow></mtd></mtr></mtable></math></maths><br /> where S′ is the number of delayed correlations performed, which is S′&lt;S, and <ul><li id="ul0003-0001" num="0000"><ul><li id="ul0004-0001" num="0074">C_initis the accumulated correlation result for all pilot sequences. <br /> Equation (4) performs coherent accumulation on the S′ correlation results and provides C_init, which is a complex value. </li></ul></li></ul>

An initial frequency error estimate may then be derived based on the accumulated correlation result, as follows:

<maths id="MATH-US-00003" num="00003"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><mrow><mi>Δ</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><msub><mover><mi>f</mi><mo>^</mo></mover><mi>init</mi></msub></mrow><mo>=</mo><mrow><mfrac><mn>1</mn><msub><mi>G</mi><mi>L</mi></msub></mfrac><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><mi>arctan</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><msub><mi>C</mi><mi>init</mi></msub><mo>)</mo></mrow></mrow></mrow><mo>,</mo></mrow></mtd><mtd><mrow><mi>Eq</mi><mo>⁢</mo><mstyle><mspace width="0.8em" height="0.8ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><mn>5</mn><mo>)</mo></mrow></mrow></mtd></mtr></mtable></math></maths><br /> where G_Lis a detector gain, which is G_L=2π·L·T_s.

The start of the first pilot sequence may be ascertained by performing a sliding correlation on the input samples and detecting for a peak in the sliding correlation. The input samples may be buffered, and the delayed correlation in equation (3) may be performed for all pilot sequences after the TDM pilot has been detected. Alternatively, the TDM pilot may be detected using some of the pilot sequences, and the initial frequency error estimate may be derived using the remaining pilot sequences.

<figref idrefs="DRAWINGS">FIG. 6</figref> shows a block diagram of an embodiment of initial frequency error estimator <b>520</b> in <figref idrefs="DRAWINGS">FIG. 5</figref>. In this embodiment, a delayed correlator <b>610</b> receives the input samples B_infor the broadcast system and performs the delayed correlation shown in equation (4). Within delayed correlator <b>610</b>, the input samples are provided to an L-sample delay line <b>612</b> and a multiplier <b>616</b>. Delay line <b>612</b> delays each input sample by L sample periods, which is the length of the pilot sequence. A unit <b>614</b> provides the complex conjugate of each delayed sample from delay line <b>612</b>. Multiplier <b>616</b> multiplies each input sample with the corresponding output from unit <b>614</b> and provides the product x*_l(i)·x_l(i+L) in each sample period. A peak detector <b>620</b> detects for the TDM pilot and provides sample index k_sfor the start of the first pilot sequence. An accumulator <b>618</b> accumulates the output of multiplier <b>616</b> over L sample periods for one pilot sequence and provides the correlation result C_lfor each pilot sequence.

An accumulator <b>630</b>, which is formed with a summer <b>632</b> and a register <b>634</b>, accumulates the correlation results from delayed correlator <b>610</b> for S′ pilot sequences and provides the accumulated result C_init. An arctan unit <b>640</b> computes the arctangent of C_init. A scaling unit <b>642</b> scales the output of arctan unit <b>640</b> and provides the initial frequency error estimate Δ{circumflex over (f)}_init.

Each OFDM symbol contains a cyclic prefix that is identical to the last C samples of the data portion, as shown in <figref idrefs="DRAWINGS">FIG. 2</figref>. Hence, the samples during the cyclic prefix are periodic, so that s(k)=s(k+K). A frequency error estimate may be computed for each OFDM symbol based on the cyclic prefix, as follows:

<maths id="MATH-US-00004" num="00004"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><mrow><mi>Δ</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><msub><mover><mi>f</mi><mo>^</mo></mover><mi>m</mi></msub></mrow><mo>=</mo><mrow><mi>Im</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>[</mo><mrow><munderover><mo>∑</mo><mrow><mi>i</mi><mo>=</mo><mn>1</mn></mrow><msup><mi>C</mi><mi>′</mi></msup></munderover><mo>⁢</mo><mrow><mrow><msubsup><mi>y</mi><mi>m</mi><mo>*</mo></msubsup><mo>⁡</mo><mrow><mo>(</mo><mi>i</mi><mo>)</mo></mrow></mrow><mo>·</mo><mrow><msub><mi>y</mi><mi>m</mi></msub><mo>⁡</mo><mrow><mo>(</mo><mrow><mi>i</mi><mo>+</mo><mi>K</mi></mrow><mo>)</mo></mrow></mrow></mrow></mrow><mo>]</mo></mrow></mrow><mo>,</mo></mrow></mtd><mtd><mrow><mi>Eq</mi><mo>⁢</mo><mstyle><mspace width="0.8em" height="0.8ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><mn>6</mn><mo>)</mo></mrow></mrow></mtd></mtr></mtable></math></maths><br /> where y_m(i) is the i-th output sample for the m-th OFDM symbol, <ul><li id="ul0005-0001" num="0000"><ul><li id="ul0006-0001" num="0082">Δ{circumflex over (f)}_mis a frequency error estimate for the m-th OFDM symbol, and</li><li id="ul0006-0002" num="0083">C′ is the number of samples over which correlation is performed, where C′≦C. <br /> The imaginary part Im [ ] in equation (6) is an approximation of the arctangent in equation (5). This approximation is reasonably accurate when the quantity within the square bracket in equation (6) is small, which is typically the case once frequency lock is achieved. </li></ul></li></ul>

The start of each OFDM symbol may be determined by a time tracking loop known in the art and not described herein. The accumulation in equation (6) may be performed over all or a subset of the C samples for the cyclic prefix.

<figref idrefs="DRAWINGS">FIG. 7</figref> shows a block diagram of an embodiment of frequency error estimator <b>530</b> in <figref idrefs="DRAWINGS">FIG. 5</figref>. In this embodiment, a delayed correlator <b>710</b> receives the output samples B_outfor the broadcast system and performs the delayed correlation shown within the square bracket in equation (6). Delayed correlator <b>710</b> includes a delay line <b>712</b>, a complex-conjugate unit <b>714</b>, a multiplier <b>716</b>, and an accumulator <b>718</b> that operate in similar manner as units <b>612</b>, <b>614</b>, <b>616</b> and <b>618</b>, respectively, within delayed correlator <b>610</b> in <figref idrefs="DRAWINGS">FIG. 6</figref>. However, delay line <b>712</b> delays each output sample by K sample periods, which is the length of the data portion. Accumulator <b>718</b> accumulates the output of multiplier <b>716</b> over C′ sample periods for the cyclic prefix and provides a correlation result C_mfor each OFDM symbol. A unit <b>720</b> provides the imaginary part of the correlation result C_mas the frequency error estimate Δ{circumflex over (f)}_m.

<figref idrefs="DRAWINGS">FIGS. 6 and 7</figref> show exemplary embodiments of frequency error estimators <b>520</b> and <b>530</b>, respectively. The embodiment in <figref idrefs="DRAWINGS">FIG. 6</figref> relies on the periodic nature of the TDM pilot to derive the initial frequency error estimate. The embodiment in <figref idrefs="DRAWINGS">FIG. 7</figref> relies on the periodic nature of the cyclic prefix in each OFDM symbol to derive a frequency error estimate. In general, frequency error estimation may be performed in various manners depending on the structure of the transmitted signal, the radio technology used for the transmitted signal, and/or other factors.

Referring back to <figref idrefs="DRAWINGS">FIG. 5</figref>, frequency register <b>548</b> provides the current frequency error estimate F_Bin=Δ{circumflex over (f)} for the broadcast system. Phase accumulator <b>512</b> accumulates this frequency error estimate in each sample period and provides a phase value, which may be given as θ_k=−2π·k·Δ{circumflex over (f)}. Phase rotator <b>510</b> may rotate each input sample as follows: <br /><i>y</i>₁(<i>k</i>)+<i>jy</i>_Q(<i>k</i>)=[<i>x</i>₁(<i>k</i>)+<i>jx</i>_Q(<i>k</i>)]·[cos θ_k<i>+j </i>sin θ_k]  Eq (7)<br /> where x(k)=x₁(k)+jx_Q(k) is a complex-valued input sample for sample period k, and <ul><li id="ul0007-0001" num="0000"><ul><li id="ul0008-0001" num="0088">y(k)=y₁(k)+jy_Q(k) is a complex-valued output sample for sample period k. <br /> The complex multiplication in equation (7) may be performed with four real multiplications and two real additions. </li></ul></li></ul>

Frequency lock detector <b>532</b> may detect for frequency lock in various manners. In an embodiment, detector <b>532</b> initially resets a counter to zero. Thereafter, detector <b>532</b> compares each frequency error estimate Δ{circumflex over (f)}_mfrom estimator <b>530</b> against a threshold Δf_th, increments the counter if the frequency error estimate is less than the threshold, and decrements the counter otherwise. Detector <b>532</b> declares frequency lock if the counter reaches a maximum value and declares loss of lock if the counter reaches zero. The number of bits for the counter and the threshold Δf_thmay be selected to achieve good lock detection performance. Frequency lock may also be detected in other manners.

In an embodiment, the AFC for the broadcast system may be operated in an acquisition mode or a tracking mode. Both loop modes may be applicable when receiving both cellular and broadcast or when receiving only broadcast. For clarity, the following description is for the case when receiving only broadcast.

In an embodiment, the inner and outer loops are both operational in the acquisition and tracking modes, and different parameter values may be used for the inner and/or outer loop in the two modes. For the inner loop, the same inner loop gain a may be used for both modes. Alternatively, a larger inner loop gain may be used for the acquisition mode, and a smaller inner loop gain may be used for the tracking mode. For the outer loop, a larger outer loop gain β and/or a larger limit may be used in the acquisition mode, and frequency register <b>570</b> may be updated by a larger amount in each update interval. In the tracking mode, a smaller outer loop gain β and/or a smaller limit may be used, and frequency register <b>570</b> may be updated by a smaller amount in each update interval.

In another embodiment, the outer loop adjusts the reference oscillator to correct short-term and long-term frequency error in the acquisition mode, and the inner and outer loops are both operational in the tracking mode. In the acquisition mode, the inner loop derives frequency error estimates based on the input samples (and not the output samples) and provides these frequency error estimates to the outer loop. The outer loop drives the reference oscillator to the correct frequency. The outer loop may be operated with a larger outer loop gain β and/or a larger limit in the acquisition mode. In this embodiment, the inner loop is essentially non-operational in the acquisition mode, and the outer loop attempts to quickly move the reference oscillator to the correct frequency. In the tracking mode, the outer loop slowly updates the reference oscillator, and the inner loop corrects for short-term frequency error.

The acquisition and tracking modes may also be implemented in other manners. The terminal may support different and/or additional modes. For example, the terminal may also support a hold mode in which the inner and/or outer loops are maintained fixed, e.g., if the received signal quality is poor or if some other conditions are detected.

The terminal may start in the acquisition mode when powered on, after waking up from an extended sleep, when frequency lock is lost, and/or for other conditions. The terminal may transition from the acquisition mode to the tracking mode upon detecting frequency lock, if the adjustment applied to frequency register <b>570</b> is below a particular value for some number of updates, and/or if some other conditions are satisfied.

The terminal may periodically receive data from the broadcast system. For example, each frame may carry many OFDM symbols (e.g., approximately 300 OFDM symbols), and the terminal may receive only few OFDM symbols (if any) in each frame. In this case, the terminal may sleep for most of the frame, wake up several OFDM symbols prior to the first OFDM symbol of interest, and process each OFDM symbol of interest. The terminal may update the inner loop in each OFDM symbol period while awake and may update the outer loop prior to going to sleep.

<figref idrefs="DRAWINGS">FIG. 8</figref> shows a block diagram of a model <b>800</b> of the dual-loop AFC for the broadcast system. Model <b>800</b> includes a section <b>810</b> for the inner loop and a section <b>820</b> for the outer loop. Model <b>800</b> represents the operation of the inner and outer loops during the tracking mode.

Within outer loop section <b>820</b>, a summer <b>822</b> subtracts the reference frequency f_reffrom a received frequency f_rxand provides an input frequency f_in. The received frequency is the frequency of a signal received from the broadcast system, the reference frequency is the frequency of the reference oscillator, and the input frequency is the frequency error of the input samples B_in. Summer <b>822</b> models the frequency downconversion by downconverter <b>324</b><i>b </i>in <figref idrefs="DRAWINGS">FIG. 3</figref>.

Within inner loop section <b>810</b>, a summer <b>812</b> subtracts a rotator frequency f_rotfrom the input frequency f_inand provides a frequency error f_err. Summer <b>812</b> models the phase rotation by unit <b>510</b> in <figref idrefs="DRAWINGS">FIG. 5</figref>. The rotator frequency f_rotis the frequency provided by register <b>548</b>, and the frequency error f_erris the residual frequency error estimated by frequency error estimator <b>530</b> in <figref idrefs="DRAWINGS">FIG. 5</figref>. The frequency error f_erris scaled with the inner loop gain α by a multiplier <b>816</b> and accumulated by an accumulator <b>814</b>. Multiplier <b>816</b> corresponds to multiplier <b>532</b> in <figref idrefs="DRAWINGS">FIG. 5</figref>, and accumulator <b>814</b> corresponds to summer <b>544</b> and frequency register <b>548</b>. Accumulator <b>814</b> has a transfer function of 1/(z−1) in the z-domain.

In outer loop section <b>820</b>, the rotator frequency f_rotis scaled with the outer loop gain β by a multiplier <b>826</b> and accumulated by an accumulator <b>824</b> to generate the reference frequency. Multiplier <b>826</b> corresponds to multiplier <b>562</b> in <figref idrefs="DRAWINGS">FIG. 5</figref>, and accumulator <b>824</b> corresponds to summer <b>566</b> and frequency register <b>570</b>.

A transfer function H_in(z) for the inner loop may be expressed as:

<maths id="MATH-US-00005" num="00005"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><msub><mi>H</mi><mi>in</mi></msub><mo>⁡</mo><mrow><mo>(</mo><mi>z</mi><mo>)</mo></mrow></mrow><mo>=</mo><mrow><mfrac><msub><mi>f</mi><mi>rot</mi></msub><msub><mi>f</mi><mi>in</mi></msub></mfrac><mo>=</mo><mrow><mfrac><mi>α</mi><mrow><mi>z</mi><mo>-</mo><mn>1</mn><mo>+</mo><mi>α</mi></mrow></mfrac><mo>.</mo></mrow></mrow></mrow></mtd><mtd><mrow><mi>Eq</mi><mo>⁢</mo><mstyle><mspace width="0.8em" height="0.8ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><mn>8</mn><mo>)</mo></mrow></mrow></mtd></mtr></mtable></math></maths>

A transfer function H_out(z) for the outer loop may be expressed as:

<maths id="MATH-US-00006" num="00006"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><msub><mi>H</mi><mi>out</mi></msub><mo>⁡</mo><mrow><mo>(</mo><mi>z</mi><mo>)</mo></mrow></mrow><mo>=</mo><mrow><mfrac><msub><mi>f</mi><mi>ref</mi></msub><msub><mi>f</mi><mi>rx</mi></msub></mfrac><mo>=</mo><mrow><mfrac><mrow><mi>α</mi><mo>·</mo><mi>β</mi></mrow><mrow><msup><mrow><mo>(</mo><mrow><mi>z</mi><mo>-</mo><mn>1</mn></mrow><mo>)</mo></mrow><mn>2</mn></msup><mo>+</mo><mrow><mrow><mo>(</mo><mrow><mi>z</mi><mo>-</mo><mn>1</mn></mrow><mo>)</mo></mrow><mo>·</mo><mi>α</mi></mrow><mo>+</mo><mrow><mi>α</mi><mo>·</mo><mi>β</mi></mrow></mrow></mfrac><mo>.</mo></mrow></mrow></mrow></mtd><mtd><mrow><mi>Eq</mi><mo>⁢</mo><mstyle><mspace width="0.8em" height="0.8ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><mn>9</mn><mo>)</mo></mrow></mrow></mtd></mtr></mtable></math></maths>

Since the sampling rate is typically much higher than the inner and outer loop bandwidths, the z-domain transfer functions in equations (8) and (9) may be converted to s-domain transfer functions using the approximation z−1=jω=s, where ω is normalized frequency. The s-domain transfer functions may be expressed as:

<maths id="MATH-US-00007" num="00007"><math overflow="scroll"><mtable><mtr><mtd><mtable><mtr><mtd><mrow><mrow><msub><mi>H</mi><mi>in</mi></msub><mo>⁡</mo><mrow><mo>(</mo><mi>s</mi><mo>)</mo></mrow></mrow><mo>=</mo><mfrac><mi>α</mi><mrow><mi>s</mi><mo>+</mo><mi>α</mi></mrow></mfrac></mrow></mtd><mtd><mi>and</mi></mtd><mtd><mrow><mrow><msub><mi>H</mi><mi>out</mi></msub><mo>⁡</mo><mrow><mo>(</mo><mi>s</mi><mo>)</mo></mrow></mrow><mo>=</mo><mrow><mfrac><mrow><mi>α</mi><mo>·</mo><mi>β</mi></mrow><mrow><msup><mi>s</mi><mn>2</mn></msup><mo>+</mo><mrow><mi>α</mi><mo>·</mo><mi>s</mi></mrow><mo>+</mo><mrow><mi>α</mi><mo>·</mo><mi>β</mi></mrow></mrow></mfrac><mo>.</mo></mrow></mrow></mtd></mtr></mtable></mtd><mtd><mrow><mi>Eq</mi><mo>⁢</mo><mstyle><mspace width="0.8em" height="0.8ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><mn>10</mn><mo>)</mo></mrow></mrow></mtd></mtr></mtable></math></maths>

The bandwidth of the inner loop may be expressed as:

<maths id="MATH-US-00008" num="00008"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><msub><mi>BW</mi><mi>in</mi></msub><mo>=</mo><mrow><mfrac><mi>α</mi><mn>4</mn></mfrac><mo>=</mo><mfrac><mrow><mi>ξ</mi><mo>·</mo><msub><mi>ω</mi><mi>n</mi></msub></mrow><mn>2</mn></mfrac></mrow></mrow><mo>,</mo></mrow></mtd><mtd><mrow><mi>Eq</mi><mo>⁢</mo><mstyle><mspace width="0.8em" height="0.8ex" /></mstyle><mo>⁢</mo><mrow><mo>(</mo><mn>11</mn><mo>)</mo></mrow></mrow></mtd></mtr></mtable></math></maths><br /> where ω_n=√{square root over (α·β)} is a natural frequency of the loop, and <ul><li id="ul0009-0001" num="0000"><ul><li id="ul0010-0001" num="0108">ξ=0.5√{square root over (α/β)} is a damping factor for the loop.</li></ul></li></ul>

The bandwidth of the outer loop may be expressed as: <br /><i>BW</i>_out=ω_n·[(1−2ξ²)+√{square root over (4ξ⁴−4ξ²+2)}]^1/2.  Eq (12)

The outer loop bandwidth is typically much more narrow than the inner loop bandwidth in the tracking mode. The inner and outer loop bandwidths may be determined as follows. A desired inner loop bandwidth and a desired ratio of BW_into BW_outare initially selected. The damping factor ξ is then determined based on the ratio of BW_into BW_outusing equations (11) and (12). The natural frequency ω_nis next determined based on the damping factor ξ and the inner loop bandwidth BW_inusing equation (11). The inner loop gain α is determined based on the inner loop bandwidth using equation (11). The outer loop gain β is determined based on the inner loop gain α and the natural frequency ω_n. In one exemplary design, BW_in=128 Hertz (Hz), BW_out=12.8 Hz, ξ=3.2, ω_n=0.062, α=0.4 and β=0.01. Other designs may also be used for the inner and outer loops. In general, the inner and outer loops may be designed to achieve the desired frequency acquisition and tracking performance for the specified operating scenarios.

For clarity, the inner and outer loops have been described for a specific broadcast system. Other designs may also be used for the inner and outer loops for the broadcast system. The inner and outer loops for the cellular system and/or other systems may be designed in accordance with the structure of the signals transmitted by these systems and the radio technologies used by these systems. For example, frequency error estimates may be derived based on a pilot transmitted by a system. The pilot may be transmitted continuously or periodically, and the inner loop may be updated whenever the pilot is received.

<figref idrefs="DRAWINGS">FIG. 9</figref> shows an embodiment of a process <b>900</b> for performing frequency control for multiple communication systems. Frequency control for a first communication system is performed with a first inner loop (block <b>912</b>). Frequency control for a second communication system is performed with a second inner loop (block <b>914</b>). A reference frequency used to receive the first and second communication systems is adjusted with an outer loop (block <b>916</b>). The first system may be a broadcast system, and the second system may be a cellular system. The first and second systems may utilize two different radio technologies. For example, the first system may be a broadcast system that utilizes OFDM, and the second system may be a CDMA system. The reference frequency may also be used to receive a satellite positioning system, e.g., GPS. The reference frequency may be used for frequency downconversion, sampling and/or other purposes.

The first inner loop estimates and corrects frequency error in a first input signal for the first system. The second inner loop estimates and corrects frequency error in a second input signal for the second system. The first and second inner loops may be enabled when receiving the first and second systems, respectively.

In an embodiment, first and second outer loops are implemented for the first and second systems, respectively, and are updated with the first and second inner loops, respectively. The first inner loop and the first outer loop may be operational when receiving only the first system. The first and second inner loops and the second outer loop may be operational when receiving the first and second systems. In another embodiment, a single outer loop is implemented for both systems and is updated with the first inner loop or the second inner loop, or both inner loops. In general, the outer loop that is operational estimates the frequency error between the reference frequency and the frequency of the first and/or second system and updates the reference frequency.

<figref idrefs="DRAWINGS">FIG. 10</figref> shows an embodiment of an apparatus <b>1000</b> for performing frequency control for multiple communication systems. Apparatus <b>1000</b> includes means for performing frequency control for a first communication system with a first inner loop (block <b>1012</b>), means for performing frequency control for a second communication system with a second inner loop (block <b>1014</b>), and means adjusting a reference frequency, used to receive the first and second communication systems, with an outer loop for (block <b>916</b>).

<figref idrefs="DRAWINGS">FIG. 11</figref> shows an embodiment of a process <b>1100</b> for performing frequency control for one communication system. Frequency error for a first communication system (e.g., a broadcast system) is estimated and corrected with an inner loop (block <b>1112</b>). Frequency error in a reference frequency used to receive the first system and a second communication system (e.g., a cellular system) is estimated and corrected with an outer loop (block <b>1114</b>). The inner loop is enabled when receiving the first system (block <b>1116</b>). The outer loop is enabled when receiving the first system and if this loop is designated to adjust the reference frequency (block <b>1118</b>).

The inner loop may comprise a phase rotator, first and second frequency error estimators, a loop filter, a frequency lock detector, or a combination thereof. The phase rotator corrects frequency error in input samples for the first system and provides output samples. The first frequency error estimator derives frequency error estimates indicative of the residual frequency error in the output samples. The first frequency error estimator may derive a frequency error estimate for each received OFDM symbol by correlating the cyclic prefix with the data portion. The second frequency error estimator derives an initial frequency error estimate indicative of the frequency error in the input samples. The second frequency error estimator may derive the initial frequency error estimate by correlating periodic sequences in the signal received from the first system. The inner loop filter may be initialized with the initial frequency error estimate and may thereafter filter the frequency error estimates from the first frequency error estimator to generate an output for the inner loop. The frequency lock detector determines whether frequency lock is achieved for the first system.

The outer loop may comprise first and second modules, a loop filter, or a combination thereof. The first module computes an average frequency error from the inner loop. The second module limits the inputs for the outer loop filter. The outer loop filter filters the average frequency error and provides an output for the outer loop. The outer loop may be operable in an acquisition mode or a tracking mode. In the acquisition mode, the second module may limit the inputs for the outer loop filter to within a first range and/or the outer loop filter may use a first gain value. In the tracking mode, the second module may limit the inputs for the outer loop filter to within a second range that is smaller than the first range and/or the outer loop filter may use a second gain value that is smaller than the first gain value.

<figref idrefs="DRAWINGS">FIG. 12</figref> shows an embodiment of an apparatus <b>1200</b> for performing frequency control for one communication system. Apparatus <b>1200</b> includes means for estimating and correcting frequency error for a first communication system with an inner loop (block <b>1212</b>), means for estimating and correcting frequency error in a reference frequency with an outer loop (block <b>1214</b>), means for enabling the inner loop when receiving the first system (block <b>1216</b>), and means for enabling the outer loop when receiving the first system and if this loop is designated to adjust the reference frequency (block <b>1218</b>).

<figref idrefs="DRAWINGS">FIG. 13</figref> shows an embodiment of a process <b>1300</b> for performing frequency control for a bursty transmission. A terminal receives data in bursts, e.g., from a broadcast system, a cellular system, or some other system (block <b>1312</b>). The terminal updates an inner loop for AFC in each inner loop update instant during each burst of data (block <b>1314</b>). The inner loop estimates and corrects the frequency error in the bursts of data. The terminal updates an outer loop for AFC in each outer loop update instant (block <b>1316</b>). The outer loop estimates and corrects the frequency error in a reference frequency used to receive the bursts of data. The terminal may receive at least one OFDM symbol in each burst of data and may update the inner loop with each received OFDM symbol. The terminal may update the outer loop at the end of each burst of data, or more or less often. The terminal may wake up prior to each burst of data and may sleep between bursts of data.

<figref idrefs="DRAWINGS">FIG. 14</figref> shows an embodiment of an apparatus <b>1400</b> for performing frequency control for a bursty transmission. Apparatus <b>1400</b> includes means for receiving data in bursts (block <b>1412</b>), means for updating an inner loop for AFC in each inner loop update instant during each burst of data (block <b>1414</b>), and means for updating an outer loop for AFC in each outer loop update instant (block <b>1416</b>).

The frequency control techniques described herein may be implemented by various means. For example, these techniques may be implemented in hardware, firmware, software, or a combination thereof. For a hardware implementation, the processing units used for frequency control may be implemented within one or more ASICs, DSPs, digital signal processing devices (DSPDs), programmable logic devices (PLDs), field programmable gate arrays (FPGAs), processors, controllers, micro-controllers, microprocessors, electronic devices, other electronic units designed to perform the functions described herein, or a combination thereof.

For a firmware and/or software implementation, the techniques may be implemented with modules (e.g., procedures, functions, and so on) that perform the functions described herein. The firmware and/or software codes may be stored in a memory (e.g., memory <b>352</b> in <figref idrefs="DRAWINGS">FIG. 3</figref>) and executed by a processor (e.g., processor <b>350</b>). The memory may be implemented within the processor or external to the processor.

In an embodiment, the inner loop is implemented in hardware, and the outer loop is implemented in software and/or firmware. In other embodiments, the inner and outer loops may be implemented with other combinations of hardware, software, and/or firmware.

The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.