Code division multiplexer using series sequence expansion spectrum signal processing

[Detailed Description of the Invention]

(Field of the Invention) Generally the present invention relates to code division multiplexing which used in-series sequence extension spectrum signal processing, and relates to signal processing which increases the number of dispatch machines which can be especially multiplexed with predetermined chord length. (Conventional technology) In an extended spectrum system, a transmission signal is extended over a frequency band far larger than the inside of the minimum band required to transmit specific information. With another abnormal-conditions form, such as amplitude abnormal conditions and frequency modulation, while the inside of a transmission band matches the inside of the band of the information itself, in an extended spectrum system, the inside of the information band of 1 kHz is extended to the band of several MHz width by modulating information by the coding signal of an extensive band, for example. That is, there is the important feature which distinguishes an extended spectrum system from another extensive band communications system in signals other than the information sent in extended spectrum signal processing extending a transmission signal. Extension (given by 11 in-series sequence abnormal conditions, (2) frequency hopping, or (3) pulse-ized FM, i.e., the "chirp (chirping)" abnormal conditions.) of the transmission signal in a typical extended spectrum system, A carrier is modulated in in-series sequence abnormal conditions by the digital code sequence with a bit speed far higher than the inside of an information signal. At frequency hopping, carrier frequency is shifted to a discrete increase target by the pattern directed by the code sequence, and a carrier is swept by the extensive band over a predetermined pattern interval in chirp abnormal conditions. Although seldom used, there is also the carrier extending method of time hopping, and now, the transmission time which is short temporal duration is governed by a code sequence and time-several phons cycle Pingu by a usually low duty cycle, and it decides on both code Sequence cover transmission frequency and transmission time. The use of an extended spectrum system is various according to the tapping person who can be [ Decode ] made not to carry out-izing of the communication. There is eye a range method in the resolution according to a voyage, and a specific code speed and use sequence length in another use. It is R, C, the text of Dixon, an "extended spectrum system", John Wiley and 5ons, New York, and 1976, especially refer to Chapter 9 for the details of a use. Although the abnormal conditions of the carrier by any one code sequences of the partly different formant, such as AM or FM, are included in in-series sequence abnormal conditions, the phase shift keying (P S K) of 2 phases is the most common. It controls by 2 phase PSK so that the balanced type mixer a R'F carrier does [ a mixer ] human power to a code sequence is transmitted by the 1st phase shift XO and a carrier is transmitted by 2nd phase shift (180+X)' at the time of code sequence ''0" at the time of code sequence"1''. 2 phase PSK abnormal conditions are advantageous at the point that make it much more difficult that a carrier is controlled at the time of transmission and usual apparatus receives communication compared with other forms, and big power is given a carrier and reversely at information at the time of transmission. The feature of 2 phase PSK is described in the text of above-mentioned Dixon, and Chapter 4. If the secrecy of a meso sage is not required for the kind in particular of code used to extend the inside of the band of transmission, it is preferred, and the maximum code gives the optimal correlation feature. [ of an alignment code ] With the maximum code, it is defined as the longest code which can occur by the predetermined shift register or the delay element of the other place fixed length. In 2 Advance shift register sequence generator, the maximum length (ML) sequence which can occur in the shift register of n stage is 2fi-1 focus. A shift register sequence generator is formed from the shift register which fed back some stages to another stage. An output A bit style has the length according to the number of stages of the used register and feedback before repeating a sequence. For example, five steps of shift registers can generate 2 Advance sequence (that is, 2'-1) of 31 A bit as the maximum length (ML) sequence. Since the shift register ML sequence generator of the stage generates ML Cush -An which is not repeated rarely, a sequence looks random, and has the attribute of a noise and many detection is difficult for it. Therefore, an in-series sequence system is also called a 6 false noise" system. The characteristic of the maximum sequence is summarized by Section 3.1 of above-mentioned Dixon, and 3~100 steps of feedback connection for the maximum code generators are examples in 3.6 tables of the text of Dixon. In the case of 1023 bit codes corresponding to the shift register which has ten steps of the maximum length feedback, 512 1" and 511 "0" exist, and the difference is 1. While the relative position of "1" and "0" changes within the ML code sequence, said [ of "l" in each maximum length sequence and the number of "0" ] is carried out, and they are ML length Cush -About cans regularity. Since the difference of the number of "1'' and 0'' is 1 also about which ML Cush -An, the autocorrelation of the maximum alignment code which compared the sequence with the replica which carried out the phase shift for every bit serves as a value of 1 [ -] except for the focus phase shift region of 0+1, and correlation changes to alignment from -1 to (2''-1). (Therefore, the peak average autocorrelation value [ code / (2'-1) / of 1023 A bit / maximum ], i.e., 30, 1024 .. It has a range of 1db.) It is this feature to make usable in-series sequence extension spectrum communication by code division multiplexing. The receiver by which the cent was carried out to the different Song shift of the common M L code synchronizes only with a dispatch machine with the shift of the common code. Therefore, two or more signals can be simultaneously transmitted clearly on the same frequency. Some dispatch machines and at least one receiver synchronize with this including one Kurofuku with a common autocorrelation form multiplexing system, or the source of timing. A dispatch machine generates the common maximum length sequence, and the at least 1 focus phase shift of the code of each dispatch machine is carried out to other codes. A receiver generates the local replica of the common transmission maximum length who has the code sequence shift corresponding to the shift of the specific dispatch machine which should align. With the correlation detector adjusted so that the level only corresponding to +1 focus synchronization might be recognized, the self-phase mausoleum of the Lou Cal generating sequence is carried out to an input signal, and it shortens and extracts information only from the signal which occurred from the predetermined dispatch machine. the autocorrelation feature of the maximum length code sequence responded to the reciprocal of chord length -- inclining and getting it blocked --;V/(2'-1) However, since the size of the voltage corresponding to "l" and n have the number; of stages of a shift register, duplication produces V between contiguity channels. That is, refusal of the input signal which is not desired is imperfect. Therefore, a clear signal distinction needs the Ghat band between channels, and the possible number of dispatch machines is reduced to predetermined chord length. Although the long maximum length sequence compensates the Ghat band and the possible number of dispatch machines is made to increase, this delays synchronization and produces the power imbalance of a multiplexing dispatch machine. (The object of an invention) Therefore, the main objects of the present invention are to provide improvement autocorrelation type the code division multiplexing method and device which more numbers of dispatch machines can distinguish clearly to predetermined chord length. The another object is to provide carrying out many dispatch machines in distinction from mutual comparatively with the code division multiplexing method and device using the comparatively short ML code. The another object of the present invention is in This - which provides the improvement correlation detector used for signal detection. The another object is to provide the improvement correlation detector used for detection of a signal with a code division multiplexing device. The another object is to provide the improvement correlation detector used for an in-series sequence extension spectrum code division multiplexing device. The further object has required calibration adjustment in providing a minimum correlation detector circuit. The further object has the required calibration adjustment used for a multi-channel detector in providing a minimum improvement correlation detector, in order to search for the correlation grade of the receiver in a code division multi-channel system, and a predetermined dispatch machine. The another object of the present invention is to improve the signal to noise ratio in a code division multiplex receiver. The another object has a plurality of correlation detectors by which time Agreement is carried out in continuous code shift delay of a common pseudo-random code sequence, and there is in improving S/N and the synchronization characteristic in a code division multiplex receiver which is processed so that it may ask for the reception synchronization with optimal output. The another object of the present invention is to improve the synchronization in an in-series sequence extension spectrum receiver. There is the further object in improving the reception synchronization in an in-series sequence extension spectrum receiver which uses a plurality of correlation detectors mutually displaced by a part of equal code chip in order to identify the optimal synchronization delay. The another object is to distinguish an input signal and a noise in an in-series sequence extension spectrum receiver. The further object has data sampling speed in improving reception synchronization with the in-series sequence extension spectrum receiver obtained more highly than the frequency of a timing signal. (Constitution of an invention) The above and other objects are filled by the method and device of the present invention in sync with the source of a timing signal where a plurality of dispatch machines and at least one receiver are common. Each dispatch machine sends the data modulated with the carrier extended by the bipolar pseudo-random code which is the specification shift from which the common bipolar code sequence differed. In order to distinguish from the signal to which the signal sent with the predetermined dispatch machine was sent with other dispatch machines, two local bipolar pseudo-random codes which are the replicas of a common bipolar pseudo-random code in which the receiver was transmitted are generated. ; another side has the code sequence shift specified as neither of the generators with the code sequence shift as the code sequence shift specified as the predetermined generator with same one side of a local generating code. In order to distinguish and extract information from the code transmitted from the predetermined dispatch machine, two local generating codes are processed and 3 Advance code sequence which carried out cross correlation to the input signal is obtained. According to another feature of the present invention, 2 Advance code sequence is the maximum length (ML) sequence with the good autocorrelation characteristic. Information is embedded in 2 Advance code sequence using PSK signal abnormal conditions. According to another feature of the present invention, it is multiplexed by the input data of the bipolar sequence by which the 1st and 2nd standard signal of the form of a bipolar digital sequence was modulated, and the correlation detector of various different modes that those products are subtracted mutually is provided. The difference of subtraction finds the integral, and a random noise is equalized, and also it gets over, and collects 2 Progress information. the transfer function which arises by each channel of a correlation detector -- the bipolar sequence in which r (t) has the code shift corresponding to that of the predetermined generator, the bipolar code sequence which has the code shift as which cr (t) is not specified, and 5 (t) -- an input signal and T -- a bit period. [ however, ] Two standard sequences r to which it corresponds, respectively according to one example of a correlation detector, the multiplication machine, i.e., the subreceiver, of each channel, (t) e The analog multiplexer which has two inputs controlled by (t) is comprised. This multiplexer adds alternatively reversal of human power sequence 5 (t) and an input sequence to a subtraction machine, and it is 5 (t) (r (t) =e (t)). The considerable bottom obtains a sequence, and it integrates with it over a bit period, and produces the degree of correlation. In the 2nd example of a correlation detector, the correlation detector of N channel comprises N 3 human-power analog multiplexers which supply reversal of input signal 5 (t) and input signal 5 (t), or 0 to integration/dumping circuit according to the polarity of two standard sequences and with which it integrates over a continuous bit period. Two standard signal r (t) and e (t) control 3 human-power multiplexer via a digital logic circuit. According to the 3rd example of a correlation detector, all the signal processing is performed in digital ones. Received signal s (t) is digitized and it is arithmetically added over a period equal to a bit period with a Akyu muleta. The difference of beginning [ in a Akyu muleta ] and last 6 value expresses the value of 5 (t) with which it integrated covering the bit period. If the value of two standard signals is equal, the value of a Accum lake will be kept constant. If not equal, the contents of the Akyu muleta are changed according to the value of 5 (t), and it is r. If (t) is "1", the digital value of 5 (t) is added to a Akyu muleta, and it is r. It is subtracted from a Akyu muleta if (t) is "0." According to the example of change of the 3rd example, voltage / frequency converter digitizes a human power signal, and accumulates the sum with a frequency counter. If two standard signals are equal, the clock which drives a counter will be suspended. r If (t) is "1", it will be controlled so that 2 Advance counter accumulates a pulse at the speed proportional to 5 (t) from voltage / frequency converter. If r (t) is "0", accumulation will be subtracted and the count direction will become reverse. According to another feature of the present invention, improving the signal to noise ratio in an in-series sequence extension spectrum system which synchronizes with the source of a timing signal where a plurality of dispatch machines and at least one receiver are common is provided with the To be added method and a device. Each dispatch machine sends the data modulated with the carrier extended by the bipolar pseudo-random code which is the specification shift from which the common bipolar code sequence differed. A receiver is formed with a plurality of correlation detectors, and generates two local bipolar pseudo-random codes which are the replicas of the common bipolar pseudo-random code transmitted, respectively. one side of a local generating code has the same code sequence shift as the code sequence shift specified as the predetermined dispatch machine --; another side -- any dispatch machine -- += -- it has the code sequence shift by which a law is not carried out. Two local generating codes are processed within each correlation detector, 3 Advance code sequence correlated with the input signal is obtained, a correlation signal is generated, the above-mentioned correlation signal is given and receiving timing is adjusted so that each correlation detector may be located in a local correlation peak. According to this invention, synchronization of reception is given, and also the output of a correlation detector receives data, and it is processed so that the signal to noise ratio may be optimized. After checking that it is in agreement with the data numerals which the numerals of each correlation peak are transmitting, if the receiver synchronizes correctly, a correlation output will be processed using the load factor selected according to an existing specific distortion, and the signal to noise ratio will be optimized. According to another feature of the present invention, the method and device which improve synchronization between the dispatch machine and receiver which are used for an in-series sequence extension spectrum system which synchronizes with the source of a timing signal where a plurality of dispatch machines and at least one receiver are common especially are provided. Each dispatch machine sends the data signal extended by the bipolar pseudo-random code which is the specification shift from which the common bipolar code sequence differed. A receiver is formed with a plurality of correlation detectors, and generates two local bipolar pseudo-random codes which are the replicas of the common bipolar pseudo-random code transmitted, respectively. ; another side has the code sequence shift specified as neither of the dispatch machines with the code sequence shift as the code sequence shift specified as the predetermined dispatch machine with same one side of a local generating code. In order to distinguish and extract information from the code transmitted from the predetermined dispatch machine, two local generating codes are processed and 3 Advance code sequence which carried out cross correlation to the input signal is obtained. This cross correlation produces the right-angled phase signal used as the corresponding phase signal and the minimum used as the maximum, when a receiver and a predetermined dispatch machine agree. Synchronization is obtained by adjusting receiving timing so that a right-angled phase cross correlation signal may be made into the minimum. According to one example of this invention, the ratio of a corresponding phase to right-angled phase both signals is measured, and the size of a receiving timing shift is controlled, and it is processed so that perfect synchronization may be obtained, without passing through an interim receiving timing shift. If a ratio is larger than a predetermined number, it will be considered that the receiver synchronizes completely, a dead band will be established, and going too far of synchronization will be decreased. According to another example of this invention, the amplitude ratio of the corresponding phase in one and right-angled phase both the phase opening signal of a correlation detector is measured, and the signal under existence of a noise is identified. If this absolute value is farther [ than 1 ] great, it will be considered that a signal exists and it will be considered that;, otherwise, a receiver received the noise. Only when a measurement ratio is larger than a predetermined value, a receiver is controlled to synchronize with input signal -. According to another feature of the present invention, the method of improving synchronization between the dispatch machine and receiver which are used for an in-series sequence extension spectrum system which synchronizes with the source of a timing signal where a plurality of dispatch machines and at least one receiver are common especially is provided. Each dispatch machine sends the data extended by the bipolar pseudo-random code which is the specification shift from which the common bipolar code sequence differed. The stage which samples a data signal at speed with a receiver equal to the frequency of the source of a timing signal, or its integral multiple, The stage of generating the data sample time corresponding to the specific timing time of the source of a timing signal combining one or more continuous data samples, The stage which locks a receiver at the timing time of the source of a timing signal corresponding to one at the stage [ of detecting which having the maximum while at the data sample time ], and data sample time detected as what has the maximum, It synchronizes with one and the source of a timing signal of a dispatch machine which transmit the data signal extended in pseudo-random code with a predetermined specification code sequence. Synchronization has an advantage of a described method in removing the necessity of performing a redundant data channel sampling on each point which may be ambiguous. A described method enables a data sampling at a speed quicker than the frequency of the source of a timing signal. Whenever it generates a data time combining a continuous data sample, therefore, a data sampling is performed at a speed higher than a net data speed, and the speed is equivalent to the number of a data sample time or bits per per second (generated from the combination of one or more continuous data samples). This composition makes it possible to put a data sample together in digital one (for example, within a microprocessor), and to make timing of actual hardware independent for data speed. The another object and advantage of the present invention will illustrate the desirable example of the invention illustrated only as an optimal mode for inventing, and will become clear from the following detailed statements to explain easily at a person skilled in the art. obvious, a different example of everything but an invention is also possible, and the details do not deviate from an invention, either -- various Ah -- it can change in a clear point. Therefore, a drawing and explanation should be regarded only not as the meaning of restriction but as a meaning of illustration. (EXAMPLE) ■ - vote In extended spectrum communication, the extension in the signal hand beyond under the hand usually required for the data transmitted, It is carried out in modulating in standard pseudo-random code of Length which usually produces at least the signal which carried out the PSK abnormal conditions of the carrier waveform, and then was acquired with the data which should be transmitted first at a speed twice the repetitive speed of data. Since it mentioned above, PSK is preferred, but although a carrier is modulated and a compound signal is extended, abnormal-conditions forms other than PSK can also be used. If the receiving cord by which local generating was carried out with whether hetero gain mixture is carried out in same standard code as having used for a received signal extending compound communication or the code multiplied and transmitted synchronizes in order to restore to signal communication, A carrier's reversal thing which carried out raw in the PSK abnormal conditions of the code with the dispatch machine is removed, and the first base hand abnormal-conditions carrier is reproduced within a receiver. Drawing 1 shows the basic element of a fundamental extended Sky vector receiver including one feature of an invention. Receiver 100 receives the in-series sequence extension spectrum (DS S S) signal transmitted from specific one of the dispatch machines of a plurality of, processes a received signal, and it discriminates from the signal transmitted from the specific dispatch machine out of each signal transmitted from all the dispatch machines. the received signal is modulated twice on substance -- that is, -- a carrier is first modulated by data Next, since it modulates by a pseudo-random code sequence and the compound signal extends a compound signal over the band which matched in the hand of a false random sequence, please care about performing two steps of recoveries of a received signal for receiver 100 to extract transmission data. or [ that heterodyne mixture of the receiving DSSS signal is first carried out in code of the specific dispatch machine with which it is discriminated from the thing and its signal from other dispatch machines ] -- or it is multiplied. Therefore, if the code which occurred in both the dispatch machine and the receiver synchronizes, the reversal thing of carry ° Ya which arose in code PSK abnormal conditions with the dispatch machine will be removed by multiplication machine 102, and the first baseband abnormal-conditions carrier will be reproduced. the reproduction carrier of a Narrow band -- a baseband abnormal-conditions carrier -- Communicate -- the bandpass filter (not shown) designed like is given. Next, baseband data is extracted by heterodyne-mixing or multiplying a reproduction carrier by multiplication machine 104 with a local generating carrier. Usual [, such as accumulation/dumping circuit, ] passes correlation filter 106, and also the output of multiplication machine 104 is given to the sample/hold circuit which produces transmission data and a corresponding signal. Receiver 100 is controlled by standard microprocessor 108 in sync with system clock 110, and each dispatch machine also synchronizes with the clock. Since a noise and undesirable communication are also processed through the same multiplication process by the local generating standard code which compresses a receiving in-series sequence signal into the first carrier band with multiplication machine 102, Any input signal which does not synchronize with a local generating standard code is extended into a hand equal to the sum of an input signal and both the band width of a standard code. Since this asynchronous-inputs signal is Mump(ed) in hand lJ equal during a standard code at least, most portion of undesirable signal power is refusable with a bandpass filter. Although the synchronous input signal in the band which is a point with this important for a D S S'S system and which was got blocked two and modulated in standard code is changed into a baseband abnormal-conditions band, an asynchronous-inputs signal is extended into a code abnormal-conditions hand. In synchronization processing, the characteristic peculiar to the specific code used for the dispatch machine is used. Multiplication with the autocorrelation of the maximum length (ML) sequence, i.e., the time Cyst replica of a sequence, serves as a peak, when the synchronization is attained, as a synchronization is lost (namely, -- as the time lag between a code and its replica approaches more than 1 code chip or it) -P" -- it has an absolute value which falls to /L. However, P is the amplitude of a code sequence and L is chord length. The numerals of an autocorrelation pattern are dependent on the data bit currently used to modulate a dispatch machine. Therefore, if the receiver and the dispatch machine synchronize correctly, transmission data is recoverable with a receiver by monitoring the numerals of an autocorrelation output. If Drawing 2 is referred to, the pseudo-random code sequence with which receiver 100 is aligned will be bipolarity, that is, the polarity of a constant voltage power supply will be switched. In the present invention, since a carrier is controlled by bipolar transmission, in order to improve the transmission efficiency of power, a sequence bipolar [ instead of unipolar ] is used. It helps for bipolar transmission to prevent high concentration of the energy to a certain frequency band, and to avoid the interference during transmission with a different dispatch machine in a system. Each bipolar sequence has amplitude P and chip temporal duration Tc. Those signals depend for the length of ML Cush -An on the different number of dispatch machines by which code division multiplexing should be carried out within a system. The same dispatch code with the predetermined chip from which common ML Cush -An differed is assigned to each dispatch machine. Therefore, the maximum number of the dispatch machine which can be multiplexed within this system is equivalent to the length of ML Cush -An. The number of dispatch machines which can be multiplexed without interfering within this kind of code division multiplex system is theoretically equal to the bit length of a sequence. For example, in the ML code with 63 bit length, the transmission channel can multiplex 63 different dispatch machines theoretically. This is as that by which synchronization is attained between a receiver and a predetermined dispatch machine, when the autocorrelation between the receiving cord from the dispatch machine which all synchronized with the common source of timing, and a local generating code is a peak. however, 1P" [ in / in fact / the autocorrelation of ML Cush -An ] -- since duplication arises between contiguity correlation curves for - reason of a /L paragraph, the number of dispatch machines which can carry out code division multiplexing within a system is farther [ than the theoretical maximum ] low. This point will be more intelligibly understood, if Drawing 3 showing the correlation curve of single transmission and Drawing 4 in which contiguity transmission, i.e., a single code chip, showed a plurality of correlation curves about transmission from which time shifted mutually are referred to. In Drawing 3, when dispatch and a local dispatch code sequence are larger than code chip Tc and time has shifted mutually, a correlation curve has the amplitude of -P"/L. However, P is the absolute amplitude of a sequence and L is sequence length (bit). If whether they are dispatch and local generating both codes are carrying out the A synchronization (i.e., if it is in time gap of 1 code chip mutually), the degree of correlation will reach the peak amplitude of P2 in a full synchronization. Therefore, the synchronization between a receiver and a single generator is detectable by monitoring a correlation output and considering that it synchronizes when a correlation signal is more than the predetermined net price. on the other hand, if Drawing 4 is referred to, it is mutually alike at three dispatch code sequences by which the time shift only of the single code chip was carried out, and it is assumed that they are -1 and a thing which it resembles and in which +1 exists. each -- correlation -- the -- three -- a figure -- the same -- positive -- a peak value -- P -- two -- being negative -- a peak value - P -- " -- /-- L -- having . The correlation curve of a contiguity code sequence overlaps in the field shown with the slash in the 4th figure. In these fields, it is unable for a contiguity code sequence to show common correlation and to distinguish between each dispatch. In order to avoid the interference during each dispatch as a practical question, as shown in Drawing 5, it is necessary to insert the Ghat band between sequences. This is obtained by giving the sequence shift only corresponding to the delay of the code chip in every other one instead of the delay for every code chip to dispatch, as shown in Drawing 4. As a result, compared with the theoretical maximum, only the number of dispatch of a Senior high school student half can be multiplexed. Since the larger Ghat band than obtained when only the code shift delay in every other one is used, in order to avoid the obscurity of a synchronization in fact is required, the number of dispatch machines which can be multiplexed with the code division multiplex system using a bipolar sequence further becomes less than the half of the theoretical maximum. The cross correlation of 3 Advance code which arose by acquiring the difference between the code sequences specified as the code sequence specified as the specific dispatch machine with which a receiver should be aligned, and neither according to one feature of the present invention, and a human power signal is taken, The number of dispatch machines which can be multiplexed increases one from theoretical restriction even to few values. That is, two bipolar code sequences are generated with a receiver. One code is a replica of the common code sequence transmitted from all the dispatch machines, and has the sequence shift corresponding to the sequence shift of one predetermined dispatch machine. The code of another side is a replica of a common bipolar sequence, and consists the code sequence shift specified as neither of the dispatch machines. One side of a local generating code is subtracted from another side, and the result which is 3 Advance code sequence correlates with a human power signal. The sequence shift of 3 Advance code sequence is put in in 1 code chip of the sequence which occurs from the There for static synchronizing methods mentioned below, and a predetermined dispatch machine. the perfect synchronization between a receiver and a predetermined dispatch machine -- general -- the timing of a receiver -- every [ of a code chip / a part ] -- it shifts continuously and is obtained using the dynamic synchronization (in detail after-mentioned) obtained by monitoring the output of a correlation machine. When a correlation output is in a peak, it is considered that the receiver and the predetermined dispatch machine synchronize mutually. (Supposing a jam dispatch machine does not synchronize with one clock pulse but the receiver synchronizes [ To / in sync with the clock pulse to which a receiver and a dispatch machine correspond by This \ / to stop ] with another clock pulse) in order to extract transmission data, the polarity of a correlation output is monitored. 3 Advance pulse sequence by which cross correlation should be carried out to a dispatch sequence -- a generator -- 6th (a)~ (if d1 figure is referred to, understood intelligibly.) Dispatch bipolar sequence 5 (t) which has Tc in the 6th (a) figure amplitude P and during the chip absolutely is an example. This sequence simplifies longer sequences, such as 63 A bit, in fact. Within a receiver, the 1st standard pulse sequence r (t) shown in the 6th (b) figure is generated. Since it is considered that it has the same delay and synchronizes mutually, both the sequences of a dispatch machine and a receiver are sequences r. (t) is equal to sequence S ([) from the predetermined dispatch machine shown in the 6th (a) figure. A receiver generates the 2nd standard pulse sequence e (t) shown in the 6th (c) figure, and this has the same sequence delay as the sequence sent from a predetermined dispatch machine and all the other receivers but specified as no dispatch machine. The difference (r (t) =e (t)) between two local generating standard pulse sequences is acquired, and 3 Advance pulse sequence shown in the 6th (d) figure is given. This 3 * Advance sequence takes a value [+2.0, -2] according to two relative 2 Advance values, standard pulse sequence r (t) and e (t). Although the sequence length in question who showed in Drawing 6 is 7 A bit, since [ which should be carried out code division multiplexing ] many dispatch machines are permitted comparatively, a longer sequence is used in fact. - Reference of Drawing 7 will generate 3 Progressive standard sequence by which cross correlation should be carried out to a human power bipolar pulse sequence for signal multiplexing with receiver 200. Receiver 200 receives dispatch pulse sequence 5 (t), and gives a human power sequence to each input of the 1st correlation multiplication machine 202 and the 2nd correlation multiplication machine 204. The 1st correlation multiplication machine 202 is input sequence s. It multiplies with local generating standard pulse sequence r (t) with the sequence shift which corresponded (t) with the sequence shift of the predetermined dispatch machine. Multiplication machine 204 is human power sequence r. (t) is multiplied with pulse sequence e (t) with a non-specifying pulse sequence shift. The obtained product is given to difference circuit 206, and the difference integrates standard correlation filter 208, and is sampled with it. It is an example that Pleasure multiplication is first carried out with two standard pulse sequence r (t) and e (t), and then input sequence 5 (t) acquires the difference of those products in Drawing 7 in difference circuit 206. This is two standard pulse sequences r. After acquiring the difference of (t) and e (t), it is equal to multiplying the difference with input sequence 5 (t). The cross correlation acquired in this way is shown in Drawing 8. Each correlation curve will serve as value 0, if a predetermined dispatch sequence and local generating standard sequence r(t) =e (t) are displaced mutually as for more than 1 code chip. This point is contrastive with the cross correlation curve of Drawing 3 where negative remains correlation of amplitude P2/L exists. If predetermined dispatch and a local generating standard pulse sequence synchronize, the amplitude of a correlation curve will increase to alignment to peak values P (L+1)/L. the [ which showed correlation of a plurality of contiguity transmissions * according / the advantage of the above-mentioned correlational method / to the present invention ] -- it will be clear ifa [ 9 ] figure is compared with Drawing 4. especially -- the --a [ 9 ] figure shows the code of 2 code chip separation. However, even if "displacement of transmission of the 9th the a figure can be made to do mutually and it makes only the l code shift it like this, while correlation of contiguity transmission does not overlap, in Drawing 4, duplication produces it in a shadow area. Thus, the present invention can make equal to few values the number of dispatch which can be multiplexed one from pulse sequence length (bit), and makes it possible to have been impossible in the conventional system. the -- even if it puts in the Ghat band between dispatch by the method shown ina [ 9 ] figure, the number of dispatch which can be multiplexed so that Cheers is possible is more sharply [ than the number which can be multiplexed using the correlational method shown in Drawing 4 so that reliance is possible ] large. :Y (t) to which it is supposed that code division multiplexing PSK signal Y (t) inputted into a receiver is denoted by a following formula - % PJdJXJ (t) cos (W, t+0)+N (t) As for power;dj in an everybody power bipolar pulse sequence, in code chip cycle;Pj, the polarity of an input each sequence or numerals XNt are [ :O<=t<=T and T ] transmission data about (1), however human power transmission of J: Frequency whose Wc is a carrier (Radians); zero is a carrier's phase; and N. (t) is a noise. As for power;dr of a request input sequence, in :, however Pr to which output v A of the conventional receiver using a single standard code sequence (T) is given with a following formula, data numerals;L of a request input sequence is pulse sequence length (bit); Pj -- power; of each undesirable sequence -- dj -- correspondence data numerals; of an undesirable sequence -- and NA is a noise. Output v m of the receiver which operates according to the principle of the present invention :vi(T) =p to which (r) is given with a following formula, d (1+1/L) +nickel Since the correlational method of (3) present invention includes subtraction of code Seagens with the code sequence shift which is not specified, Output v m While all the non-Obscurity transmission ingredients (a subscript "j" shows) in (T) are refused completely, output Va in the conventional receiver (T) contains the amount contributed of undesirable transmission (subscript "J") and both request transmissions (subscript "r"). Correlation of the three-ingredient signal of a multiplexer includes degradation of 3 dB in SN abnormal conditions of data about the white noise which appears in the input of a receiver compared with the conventional correlation only using a specific dispatch 2 Advance pulse sequence. That is, NA=NB=0 The above-mentioned multiplexing method brings about the capability to refuse undesirable access completely using the arbitrary length ML code with a code division multiplex system. Since the possible number of multiplexers became small far from chord length conventionally, only the sufficiently long ML code was able to be used. The power imbalance of the multiplexing dispatch machine had still arisen. the -- the ideal cross correlation pattern ofa [ 9 ] figure Slip below 1 code chip [ every ] time, respectively, gives the multiplexing design using the code beyond a theoretical limit, and enables more complicated reception composition. for example, between each code sequence which showed the number of dispatch machines which can be multiplexed in Drawing 4 -- further -- 1 code Add -- it was admitted that SN performance of the whole receiver was only spoiled slightly, and it could increase to 2X channel (L-2) by things. the -- as shown inb [ 9 ] figure, an additional code can be inserted between each code shown in Drawing 4. Each code is detected by a plurality of taps provided in the receiver. the -- the output of each receiver tap shown inb [ 9 ] figure -- following passage: -- the 1st table 1, a preliminary code 2, a V2 preliminary code 3 Zero 4, z code 1 5 and code 1+% code 1degree' 1'10% of 6 or 2-piece 1 Do 1+ code code 27, %, :] :channel 1-2x A tap 4 which solves the formula of a Fl'+':1-V2+A code 2' sequence as follows per each channel channel 1' -- a =2X (tap 5-channel 1) channel 2=2X channel (tap 7-channel 1'-tap 4) 2'=2X channel (tap 7-channel 2-Tanopu 5) L'-2x tap (2'L+3) -- actually -- a wall, It is quite difficult to carry out the above-mentioned composition from a noise and synchronous problem. A zero carrier may be made to be generated when correlation envelopment is equal to the 2 [ greatest ] as a method of alternative carrying out. The output type from each tap in such composition is as follows: Yu" L-table 1. Preliminary Code 2 Zero 3 Zero 4 Zero 5, code 1 6 and code 1' 7, code 2 This composition enables perfect data recovery without interference. however -- a little -- the influence of a noise -- Acceptance -- I am easy . the composition which carried out the group division of the two or more code sequences, and was separated in the Ghat band in order to solve the above-mentioned problem -- the -- it shows and comes out toc [ 9 ] figure. Exact separation of the pattern which comprises a group or a group is not related to the above-mentioned composition. This technique makes possible a group division of a dispatch machine with the similar characteristic, and simplifies the problem of a synchronization. The abnormal conditions of the addition by data with a signal and data required for improvement of the communication in a transmitter-receiver part are also included in the above-mentioned method. In this case, required conditions are only not filling the required timing of a pulse sequence of having shifted additional abnormal conditions, but maintaining the multiplexing sensitivity of a receiver. Master's rule 2 River The time synchronization of the predetermined dispatch machine of a receiver must be mutually carried out before extraction of data. If the receiver and the transmitting machine synchronize with the common source of timing (common timing is obtained from a 60-Hz power supply if a commercial electric wire is a transmission medium), synchronization will pose a problem which adapts the timing of reception to delay peculiar to the propagation delay, timing signal, and transmitter-receiver with which dispatch signals differed. Since a part of these delay is constant, it can be compensated using "passive" delay and is mutually synchronized within 1 code chip in a receiver and a predetermined dispatch machine. A chip is a bit period of a Pseudo random code generator in This \. Generally, since the most is constant, static delay can be compensated at the time of initial calibration of a receiver. However, the transmission medium synchronizes with the source of timing where a transmitter-receiver is common with the transmission line, and when communication between both devices is bidirection, difficulty arises. That is, the standard point that must investigate static delay at two standard points, and one of them has a dispatch machine in the source of timing, and others are standard points which have a receiver in the source of timing. When a dispatch machine is located in the source of timing and a receiver is located in others, a timing signal and a dispatch signal are spread from a dispatch machine at A * said-speed to a receiver. Timing change of others between transmitter-receivers is based on the delay which arises in a transmitter-receiver circuit, and can be set up beforehand to synchronize a transmitter-receiver mutually within 1 code chip. Therefore, all the receivers that are distant from the source of timing can take equal static delay. However, when a receiver is located in the source of timing and a dispatch machine is located in others, each receiver needs static delay peculiar to each transmitting machine of the remoteness for a different signal propagation distance. Therefore, in order to make receivable the signal from a plurality of dispatch machines with a receiver, static delay of a receiver must be variable. The static delay value is beforehand set up in a receiver for the subsequent communication with; and the specific dispatch machine with which the static delay between each transmitting machine and a receiver is actually measured by ° at the time of installation of a transmitting machine. Whenever the dispatch from the above-mentioned dispatch machine is received, in order to obtain the synchronization whose dispatch machine corresponded, receiving timing is adjusted automatically and permits the delay corresponding to a specific dispatch machine. In one example of an invention, a plurality of Sending / receiver units are provided with the Lord / what is called "Follow" composition. the station (Follow unit) of others [ which is called the main station in this composition / one / Sending / receiver unit ] -- business -- it functions as a source of a timing signal. In the delaying amount relevant to the timing signal between the main station and each Follow station, The filter delay to the source of a timing signal in the main station, the receive filter delay in the main station, the signal propagation delay between the main unit and a specific Follow unit, joint delay at the main station, and the dispatch filter delay in the main station are included. The quantity of the static delay related by getting to know these various delay between the main station and the specific Follow station estimates. However, a fixed change arises in each delay with change in the To transmit in relevant to a temperature change, transmission frequency, etc. Although the great portion of above-mentioned change in the static delay characteristic between the Lord and a Follow unit can be compensated with dynamic delay adjustment, since it can set to the specific Lord or a Follow unit and Receiver must be able to pursue delay change over the range of a number code chip, the multiplexing capability of a system is reduced a little. This needs the Ghat band of sufficient width to be able to be made to carry out time change of the signal of two contiguity receivers over a correspondence band without interference. However, in order for the quantity of the required Ghat band to measure periodically the static delay relevant to signal transmission between the main station and each Follow station at the main station first and then to return static delay at request within the limits, Being reduced by adjusting the timing of the dispatch signal in a Follow station periodically is accepted. Since required Ghat bands decrease in number sharply to delay change and more code delay can use it for multiplexing by this, dispatch of more Follow stations is attained simultaneously. The change from the synchronization established by static delay is compensated by the dynamic delay mechanism in each receiver. : to which dynamic delay changes from two stages -- fine alignment and rough alignment. While the timing of static delay synchronizes a receiver and a specific dispatch machine mutually within 1 Doitip per piece, fine alignment performs fine tuning in receiving timing using correlation detection not as the function of prediction transmission (static delay) but as a function of reception transmission. After fine-aligning so that receiving timing may serve as a local correlation peak, the local peak by which time Agreement of the receiver was carried out needs to define whether it is the local peak "right" for the optimal correlation. Since a plurality of correlation peaks exist according to the correlation characteristic of a selection code, and other factors, the thing which needs this is because the main local peak has the greatest peak amplitude before long. These two or more peaks arise from the carrier correlation in the code correlation peak of ±ITc. which is right for a synchronization among the timing pulse of the system which exists in each data bit -- it must set a thing. If this decision is not made, while a dispatch machine is locked by one timing pulse, the situation where it is locked by another timing pulse may produce a receiver. This is because two timing pulses exist during the data and the timing which is not right produces a rectangular state between the data periods of a transmitter-receiver. That is, such net energy of a rectangular data period serves as zero. Since data communications cannot be detected and decoded if the transmitter-receiver is not locked by the same timing pulse even if the transmitter-receiver synchronizes mutually correctly, data cannot be extracted from a receiving sequence. Next, fine alignment, rough alignment, and the synchronization to the right timing pulse within each data bit are explained in detail. Drawing 10 shows the correlation pattern which obtained the inputted bipolar pulse sequence by taking the relative correlation with the carrier and a local generating 3 Advance-semi- sequence. A large peak is produced to receiving timing V1, it produces a small correlation peak to receiving timing v2, v3, V6, and v7, and this correlation pattern calls these receiving timing a "channel" below. The correlation peak in the main channel vl is dependent on the correlation characteristic of the code selected as a function of the code chip time delay difference between an input code sequence and a standard code sequence. When a synchronization is attained between transmitter-receivers, the degree of correlation serves as a peak, and the absolute value of the degree of correlation falls to zero as a synchronous difference approaches more than 1 code chip or it. the correlation curve shown in Drawing 10 does not contain a carrier for influence in correlation by the imperfect correlation characteristic and the sign wavelike carrier of a code -- partial -- the [ straight line-like ] -- the ideal correlation curve shown ina [ 9 ] figure, and a ratio -- Vesan -- it is near wavelike. Receiving timing is adjusted until a correlation peak is called for,;, i.e., the fine alignment, this [ whose ] is a reason which needs Ill adjustment, and then, it is 1 rough alignment, It determines whether to be a small correlation peak corresponding to that a correlation peak is a large correlation peak corresponding to channel v1 or channels V2 and V3, ■6 or v7, and others. According to one feature of an invention, it is attained when synchronization of a receiver forms each receiving channel and a plurality of aligned separate subreceivers, i.e., a correlation detector. Supposing each channel V1, ■2, v3, ■6, and ■7 have estranged mutually only for 1 / 3 hours of 1 code chip, by fine alignment, receiving timing will be adjusted so that the whole of each channel may be located in a local peak. Supposing channel Vl synchronizes within 1 code chip, channel ■1 is in less than 1/6 of 1 code chip from a local peak. The output of a correlation detector is given to microprocessor 314 (after-mentioned), the receiving timing signal for a synchronization with a dispatch machine is produced, and outgoing data is extracted. The various examples of a multi-correlation detector are shown in the 11~18th figure. The amount of Dish bowl One example of the multi-channel correlation detector shown in Drawing 11 is generalized about N correlation channels. The multi-channel correlation circuit which showed the whole by 300 is provided with correlation machine 302 which comprises the 1st multiplication machine 304, the 2nd multiplication machine 306, and difference circuit 308, respectively for every channel. The 1st multiplication machine 304 receives 1st local generating standard sequence r (t) with the sequence shift corresponding to 1 human power which receives input sequence 5 (t), and the sequence shift of the predetermined dispatch machine, and also has an input. Multiplication machine 306 is input sequence s. 2nd standard sequence e (t) with the sequence shift which is not specified as 1 human power which receives (t) is received, and also an input is consisted. The output of both multiplication machines 304.306 that express the product of an input sequence and two local generating standard sequences, respectively is given to each input of difference circuit 308. The presenting power is given to integration/dumping type filter 310 which was in agreement with the bit period at chip speed, and produces the following signal ■8 for every channel: However, vN and 5 (t) are an analog signal, and r (tN) and e(ts) The 2 Advance. The output of integration/dumping circuit 310 is given to a sample / hold circuit 312, and the circuit monitors the amplitude of integration machine output VN, and polarity, and it stores it. This value is given to usual microprocessor 314, this extracts 2 Advance data from predetermined transmission according to the output from all the N pieces detector 302, a timing error signal is generated, and a receiver is locked in the synchronous state with a predetermined dispatch machine so that it may explain in full detail later. The analog multi-channel correlation detector shown in Drawing 11 needs very many calibration adjustments in relation to both multiplication machines 304.306, difference circuit 308, integration/dumping circuit 310, and a sample/hold circuit 312. In practice, this kind of eight-channel detector requires calibration adjustment of about 80. If only the polarity of standard sequence r (t) and e (t) is used, large simplification of a system will be obtained only by slight degradation of performance. Since two standard sequences are 2 Communicating (bipolar) signals, as shown in Drawing 12, multiplication can be performed in the correlation machine of N channel by using 2N piece 2 input analog multiplication machine and one inverter. In this execution, it is decided whether which of input signal 5 (t) and reversal input signal ieta is chosen, and 2 Progressive standard signals are added to difference circuit 308. At This \, the request output of each N difference circuit 308 is 5 (tN). It is [r(tN) =e (tN)], Each channel in correlation detector 400 shown in Drawing 12 is provided with 1st 2 human-power multiplexer 402 and 2nd 2 human-power multiplexer 404, and these are controlled by the momentary polarity of 1st and 2nd bipolar standard sequence r (tH) and e (tN), respectively. one person of each multiplexer 402.404 -- power receives input sequence s' (t) -- it is connected to 406 by the 1st line and other inputs are connected to line 408. Line 408 receives input sequence 5 (t) by which polarity was reversed with inverter 410. Both multiplexers 402.404 drive by standard sequence r (tN) and e (tN) via driver 412.414. r (tN) and e If the polarity of (tN) is equal, both multiplexers 402.404 will be connected to line 406. Therefore, human power sequence s (t) is given to positive/negative both the input edges of difference circuit 308, and a zero signal is added to integration/dumping circuit 310 (Drawing 11). If positive and e (ts) have negative r (to), multiplexer 402 will be connected to line 406 and multiplexer 404 will be connected to line 408. Therefore, sequence 5 (t) is given to the right input of difference circuit 308, reversal sequence 5 (t) is given to the negative input of difference circuit 308, and sequence 2s (t) is given to integration/dumping circuit 31o. On the other hand, if the relative polarity of two standard sequences becomes reverse, sequence 5 (t) will be given to the negative input of difference circuit 308, and reversal input sequence ieta will be given to the right input of difference circuit 308. Therefore, NijiN (t) which signal-2s(t) is given to integration/dumping circuit 310, and fills to a following formula =s (tN) Although circuit - of Drawing 11, Worldly, and inverter 410 need two sorts of calibration adjustments (balance and off-cent) in the circuit of [r(tN) =e (tN)] figure 12, Calibration adjustment of an analog multiplication machine is advantageous at the point which is unnecessary in Drawing 12. As a result, the number of adjustments required for an eight-channel detector is reduced from about 80 to 34. When Drawing 13 is referred to, the further simplification of the circuit shown in Drawing 11 is a difference of two signals with which the input to each integration/dumping circuit 310 multiplied and obtained +1 or -1 to input sequence 5 (t), respectively, If both the standard sequence is equal to mutual, it is attained based on an output becoming zero. in Drawing 13, a 2N piece multiplication machine and N subtraction machines exchange and come out by N 3 input analog multiplexers 502 in circuit 500. The 1st human power of each multiplexer 502 is connected to line 504 which receives input sequence 5 (t). Reversal input sequence s by which the 2nd human power of multiplexer 502 was reversed by 508 It is connected to line 506 which receives (t). The 3rd human power of multiplexer 502 is connected to grounded line 510. The 1st standard sequence r (tN) is directly connected to the control input of multiplexer 502 via the inverter / driver 512. In the control input of multiplexer 502, they are two standard sequence r (tN), respectively. It is connected to EX-OR circuit 514 with 2 human power connected to e (LN). When two standard sequences are equal to mutual, the output of EX-OR circuit 514 drives a multiplexer to line 510, and it makes a zero signal produce from the output of multiplexer 502 to integration/dumping circuit 31o (Drawing 11). When 1st standard r (h) is 1, output v (t) of multiplexer 502 is equal to 5 (t). On the other hand, when r (t) is O, multiplexer output v (t) is equal to -5 (t). therefore, a difference circuit -- signal 5 (h) : which produces [r(tl) =e (t, l)] and to which integration/dumping circuit output of each channel is expressed with a following formula if needed -- 3 human-power analog multi of Drawing 13. two kinds of circuits for carrying out plexor 502 -- the -- it is shown inb [ 148.14 ] figure, respectively. the -- the characteristic [ like each following - ina / 14 / figure ] whose two 2 input multiplexers 600.602 are -- To have: It is X=X if it is A= 0. It is x=x if it is A= 1. The 1st standard sequence r (t) is connected to 1 human power of control end A of multiplexer 600, and EX-OR circuit 604. The 2nd standard sequence e (t) is connected to Extraction input of EX-OR circuit 604. The output of EX-OR circuit 604 is connected to control end A of multiplexer 602. Input sequence 5 (t) is connected to Extraction input x0 of the multiplexer via one person power x1 and Ia bar 606 of multiplexer 600. Output X of multiplexer 600 is given to one input X of multiplexer 602, and Extraction input x0 of multiplexer 602 is grounded. the -- output [ of the multiplexer shown ina / 14 / figure ] v (t) -- required formula v (t) -5 (t) It is given by the following truth value table corresponding to [r(L) =e (L) Co. 3rd Table 0 .1 1 -5(t) 1 0 1 5(t) the -- in the example of 3 human-power multiplexer 606 shown inb [ 14 ] figure, it is alternatively connected with the four input xO% XI % XZ(s) and any one output X of X3 according to 2 Advance value of control human power A and B. Input sequence 5 (t) is directly connected to input x2 via input x1 Heyne barter 608. Input X0sX3 is grounded. Two standard sequence e (t) and r (t) are connected to control human power A and B of multiplexer 606, respectively. operation of multiplexer 606 -- the -- the truth value table which related toa [ 14 ] figure and was mentioned above Theory, and desired output v (t) is given. The example of the correlation detector of the 11~14th figure is based on the analog technology which integrates with a continuation signal. The number of required calibration adjustments can further decrease by replacing the analog integration in an integration detector by discrete signal addition. If Drawing 15 is referred to, correlation detector 700 formed in each channel of the receiver will digitize human power sequence 5 (t), and will add a digital signal arithmetically within a Akyu muleta over time equal to a bit period. The difference between the first stage in a Akyu muleta and the last value expresses the value of 5 (t) with which it integrated covering the focus cycle. Accumulation is controlled by standard sequence r (t) and the value of 5 (t). The Accumulation value is eternal if two standard sequences are equal. If r (t) and e (t) are not equal, Accumulation will be fluctuated by the value of 5 (t) according to the value of r (t). It has the analog / digital (A/D) converter 702 which receives correlation detector 700 The and analog sequence 5 (t), and generates the digital signal corresponding according to it in Output end. one person of Addition / fj& Calculation circuit 704 in which the output of A/D converter 702 has an output given to the input of Akyu muleta register 70G -- it is alike to power and is given. The output of Akyu muleta 706 is given to others power B of output register 708, and Addition / subtraction machine 704. Operation of each unit 702~708 and sequencer 710 synchronizes with bit period T. on the other hand -- sequencer 710 -- A/' -- the conversion time of D converter 702, and the Accumulation time of Akyu muleta register 706 -- each -- it controls by-izing Cuffe 12.714. Akyu muleta register 706 is controlled also by two values, standard sequence r (t) and e (t), via Ex-OR gate 716 and AND gate 718. When Addition / subtraction machine 704 produces the output signal which is the sum of the contents of digitization input sequence 5 (t) and Akyu muleta register 706 when standard sequence r ([) is 1 and standard sequence r (t) is zero, It is generating To drink about the difference of the contents of the Akyu muleta register, and the digital value of input sequence 5 (t). The alternative addition and subtraction of two signals added to inputs A and B of Addition / subtraction machine are controlled by the signal which arises from standard sequence r (t) via inverter 720, and is given to input F. r (t) is e. If equal to (t), EX and - OR gate 716 will produce the signal of logic 0 given to 1 human power of AND gate 718. In the others power of AND gate 718, it writes by sequencer 710, and a Accumulation signal arises in it. The "conversion input" signal which sequencer 710 is given to A/D converter 702 and performs the A/D conversion of input sequence 5 (t), The "write-in Accumulation" signal which subtracts and adds the instantaneous value of 5 (t) to a Accumulation value at present is produced by turns, an addition-and-subtraction value is given to output Register 08 and also microphone Lopro sensor 314 (Drawing 11), and this generates 2 advance power and a timing error signal. Therefore, if r (t) is equal to e (t), the contents of Akyu muleta register 706 will not change under control of EX-OR gate 716. If r (t) is logic 1, the contents of Akyu muleta register 706 will be increased only the value of input sequence 5 (t), and if; one side r (t) is logic O, the contents of the Akyu muleta register will decrease only the value of input sequence 5 (t). This is equivalent to hanging and integrating with +1 or -1 to 5 (t). Correlation detector 700 of Drawing 15 can be generalized to correlation detector 800 of N channel shown in Drawing 16. r to which standard sequences r (tll) and e (t, l) are given to 1 to N~1 multiplexer 804.806, respectively It is given to input latch 802 with the output of (tn) and e (t). The output of both multiplexers 804.806 is given to each input of EX-OR gate 80B, and this controls Akyu muleta memory 810 via AND gate 812. Akyu muleta memory 810 of Drawing 16 corresponds to Akyu muleta register 706 of Drawing 15. However, memory 810 includes a plurality of memory fields in which an address is possible by channel sequencer 814 which corresponds to each channel and is controlled by the output of sequencer 816. The output of Akyu muleta memory 810 is given to output register 708 of Drawing 15, and corresponding output memory 81B. However, memory 818 corresponds with a correlation channel, and includes a plurality of memory fields in which an address is possible by the output of sequencer 816. A sample is carried out in a sample / hold circuit 820, and it is added to A/D converter 822, as there described in relation to Drawing 15, input analog sequence 5 (t) is digitized, and input sequence 5 (t) is given to Addition / subtraction machine 824. At the time of operation, a sample / hold circuit 820 carries out the sample of the input analog sequence 5 (t), and it changes into the corresponding digital value synchronizing with focus cycle T which generates the sample from microprocessor 314 (Drawing 11), and is given to sequencer 816. Standard sequence r in the channel to which the contents of Akyu muleta memory 810 in each memory field by which the address was carried out from sequencer 816 corresponded Only the value of 5 (t) at present is fluctuated according to the value of (t). Namely, circuit 800 carries out the sample of the input sequence continuously, squares +1 or -l to the sequence, and integrates the bottom of control of channel sequencer 814, sequencer 816, and microprocessor 314 with it to each channel N of every. Akyu muleta memory 81*0 and output memory 818 monitor N Accumulation channels, and the time synchronization of the signal at the time of channel Sequencing is maintained by a sample / hold circuit 820, and input latch 802. Next, if Drawing 17 is referred to, correlation detector 900 of the single channel which is another digital execution is provided with usual voltage / frequency converter 902 which receives the absolute value of input sequence 5 (t) via absolute-value circuit 914. The thing which needs absolute-value circuit 904 is because voltage / frequency converter 902 usually passes and answers a unipolar input signal. Voltage / frequency converter 902 changes the momentary amplitude of input sequence 5 (t) into one corresponding frequency signal, and this is given to rise/down counter 906 via 1 human power of AND gate 908. Input sequence s (t) is also given to analog comparator 908 and this pursues the polarity of human power sequence 5 (t). That is, the output of analog comparator 908 expresses the numerals of input sequence 5 (t). Standard sequence r (t) and e (L) are given to the others power of AND gate 908 via EX-OR gate 910. Rise/down counter 906 is controlled by another EX-OR gate 912 which inputs the output and the 1st standard sequence r (t) of analog comparator 908. That is, rise/down counter is controlled to carry out amplifier at the time of the thing with both same numerals of input sequence 5 (t) and standard sequence r (t), and if it is except it, it is downed. It is given to latch 914 in sync with Output of counter 906, and bit period T. If clock CLK of amplifier / down counter 906 has two standard sequence r (t) and e (t) equal to mutual, it will become impossible by EX-OR gate 910. Except it, a counter clock is made possible and counter 906 is input sequence s. (L) is pursued. That is, if r (t) is 1, the amplifier of the counter will be carried out by sequence bit 5 of anode nature (t), and it will be downed by sequence bit 5 of cathode nature (t). - Impotence sequence s If (t) is logic zero, Accumulation will turn into that it is subtracted and the direction of a currant will become reverse. Circuit 900 of Drawing 17 is generalized by circuit 100 of Drawing 18 to correlation detection of N channel. In circuit 100, voltage / frequency converter 1002, absolute-value circuit 1004, and analog comparator 1006 are equivalent to the corresponding point of Drawing 17, and common to all the channels. However, rise/down counter 1008, AND gate 1010, and EX-OR gate 1012.1014 are made double for every channel. The output of two Advance each Up / down counter 1008 is given to latch 1016 which synchronized with bit period T in common. While producing 2 Advance which N latch outputs were given to microprocessor (as [ showed / in Drawing 11 ]) 314, and this processed the correlation signal of each channel, and were collected from the predetermined dispatch machine according to it, The timing signal to which receiving timing is shifted so that it may synchronize with a predetermined dispatch machine is produced. Shellfish skin■ As mentioned above, establishing the predetermined delay corresponding to different propagation time relevant to a different dispatch machine in a receiver is included in static synchronization. The static delay set up in the receiver at the time of early installation synchronizes a transmitter-receiver mutually within 1 code chip. Subsequently, perfect correlation is established by the microprocessor according to the correlation signal which arose from the above-mentioned correlation detector. Microprocessor 314 processes a channel correlation signal in more detail, controls receiving timing, is synchronized with a predetermined dispatch machine through two steps, i.e., fine alignment, and rough alignment, and makes synchronous correction to the right pulse of a system clock if needed after that. - If Drawing 10 is referred to again, code correlation will be a function of the code chip time delay difference between a receiving cord and a standard code, It has an absolute value which falls to zero as it becomes a peak and a synchronous difference approaches more than 1 code chip or it, when a synchronization is attained according to the specific correlation characteristic of an applied code. Data is collected from a correlation pattern based on recognition of being dependent on the data bit used for the numerals of a pattern modulating a dispatch machine. That is, when the receiver and the predetermined dispatch machine synchronize mutually correctly, outgoing data is collected by monitoring the numerals of voltage ■1 by a main phase Seki channel. Emergency-plate 1 reading in the Japanese pronunciation When Drawing 19 is referred to, the correlation pattern corresponding to the correlation pattern shown in Drawing 10 is an example in 1100. This is a correlation pattern of a "corresponding phase", and if rough correction channel Vl, 'V2, V3 and v6, and ■7 are used to decide which corresponds to the main channel among mutual peaks and they synchronize, it will serve as the maximum degree of correlation. A pair channel ■4 of an addition and ■5 are fine jam secondary correction channels, and they maintain the synchronization of reception by maximizing the correlation output of the main channel v1. In the account of improvement, all reference to the fraction value of 1 code chip relates to the ratio of carrier frequency to code generating frequency. For example, carrier frequency will make three peaks possible for every 1 code chip in relation to a ratio called 3./2 in the reference to the fraction value of ■ code chip, if 5670 Hz and code generating frequency are 3870 bits per second. Correlation curve 1200 of the addition in Drawing 19 is a correlation curve of the right-angled phase which shifted from the correlation curve of the corresponding phase 90 degrees. When the value of a corresponding phase curve is the maximum, that the value of a right-angled phase curve becomes zero has a meaning which the correlation curve of a right-angled phase has. Detection of a correlation peak is simplified by using correlation of a right-angled phase at the time of the below-mentioned processing so that it may mention below. If main phase Seki channel ■1 synchronizes correctly within 1 code chip since three correlation peaks exist for every code chip, the main channel V1 is located in less than 1/16 of 1 code chip from a "local" peak. Fine alignment adjusts the timing of a receiver so that all of correlation channel Vl and ■2 by which 1 code chip was estranged mutually every [ 3 / 1/], ■3, ■6, and v7 may be located in a local peak under * control of microprocessor 314. One method of adjusting receiving timing W So that five correlation channels may carry out at least each local peak is the 20th (it accomplishes by the sequential retrieval shown in the flow chart of 81 figure.). In this, it is introduction length 2. Use of (pS) is included. However, S is the number of correlation of the minimum resolution required for p to adjust an example by the correlation resolution of a receiver from 1/6 (this example) which broke the code chip cycle, or synchronous zero to a peak in the smooth number of each bit. It is numerical 1 / 6 for every data bit in an introduction by the minimum of the timing l code chip of main phase Seki channel V1 of a receiver. It is adjusted (p) every (Step 1320), and the amplitude of correlation voltage Vl is memorized (1330). The above-mentioned process is repeated until a receiver crosses [ three ] in a maximum of 1/of 1 code chip and changes the timing (1340). Then, the time of the amplitude of main phase Seki V1 serving as the maximum is chosen as a local peak (1350), and the timing of a receiver is adjusted to channel ■1 located at the time (1360). In another fine aligning method braked by microprocessor 314, fine alignment channel V4 and ■5 which were shown in Drawing 19 are used. Time has shifted from main phase Seki channel V1 only the fraction value of the code chip in which the l code chip of fine alignment channels V4 and v5 given with the correlation detector (not shown) of an additional pair is equal to 1/6 or less. An introduction bit is arbitrarily contained in a fine aligning method, the length of the worst case is ps and the minimum receiver correction (resolution) is set to one sixth of 1 code chips. If the 201b1st figure is referred to, correlation voltage ■4 and V5 will be given to correlation voltage [ of the main channel v1 ] ■4, and V5 will be given to microprocessor 314 (Step 1950). A microprocessor determines the direction where receiver timing should be shifted (Step 1980.1990), and makes it the main channel v1 located in a large local correlation peak by comparing the relative amplitude of v4 and ■5 (Step 1960.1970). This kind of system is roughly shown in Drawing 21. It excluded in order to make programming of microprocessor 314 brief, but it is the 20th. It is considered as the easy flow chart of +b1 figure, and the routine performed based on the explanation. In another fine aligning method, the channel by which timing is generated by a right-angled phase carrier is used. if they arise at the peak of corresponding phase correlation pattern 1100, II obtains the zero of right-angled phase correlation pattern 1200, according to the recognition from Drawing 19, error voltage will reveal them to the numerals of the product of corresponding phase and right-angled phase both patterns, and they will occur from microprocessor 314. That is, the numerals of error voltage show the direction where the timing of a receiver must be shifted in order to synchronize the correlation channel of a receiver to a local correlation peak. Although a shift amount required to obtain not only the shift direction of the receiving timing for synchronous achievement but a local peak is decided, the amplitude of corresponding phase and right-angled phase both correlation voltage 1100.1200 can also be used. That is, according to another feature of an invention, it is the 22nd (as summarized to the flow chart of 81 figure, the voltage between both phases of corresponding phase v1 and right-angled phase Vlq is measured (Step 2050).). a corresponding phase and a right-angled phase Vlq car --; from which phase both phase piezo-electricity pressure is calculated (206"0), it is considered that between both phases is the polarity if a ratio is positive (2080), and timing delay of a receiver is increased (2095) -- otherwise It is considered that between both phases is reverse polarity, and timing delay of a receiver decreases (2090). When the receiver synchronizes with the predetermined dispatch machine completely, it prevents the timing of a receiver changing, and the ratio which is substantial function cotangent in order to avoid the complexity that it must act to delay with a receiver as a Yo 1 The student, and To and more than ■ Data throat must make a correction decision using old information -- the absolute value of Vl/Vlq is monitored. the table memorized by the memory attached to microprocessor 314 -- a ratio -- Vl/Vlq is related with 1/48 of 1 code chips for the every number of fine alignment corrections, for example, correction, and the optimal alignment is reached. This table is shown below. The -" (- table) 0 ■ 1 5.022 2.413 1.494 1.005 0.6686 0.41497 0.1999 -- therefore The number of corrections given to the timing of a receiver is called for directly from Vl/Vlq, and if a ratio is larger than 5.02, a correction dead band will exist and it will not search a receiver near [ optimal ] the synchronization. The number of data bits required to move a receiver to a correlation peak from correlation zero is subtracted from 8 (it is this example) by 1 at worst, minimum-izes length required for an introduction, and makes acceleration sequential retrieval possible. furthermore -- ruining the pursuit speed of a receiver -- To -- Into -- continuation data -- since pursuit correction can be forbidden, going too far is avoidable. Residence of Compensation 5" A l Genital wound By obtaining right-angled phase Vlq and the voltage between both phases of the phase ■1, the determination of the signal which exists in a hack grand noise becomes still more possible. if only a noise exists in the input of a receiver as summarized to the program flow chart of 22nd fb1 figure -- Or [ corresponding phase ■1 and both the model pressure of right-angled phase Vlq ] - taking the same value K -- a ratio -- Vl/Vlq approaches one. However, if both a signal and a noise exist, fine alignment will carry out maximum-izing and Vlq for ■1 at worst, and will produce a far larger ratio than 1. therefore, a ratio -- V 1 / V 1 q is used as directions of signal existence. In order that the above-mentioned ratio may be monitored over many data bits and may ensure accuracy in fact, smooth technique or major vote decision (majoritynuoting) is given. The circuit which detects existence of the signal in a bank grand noise is shown in Drawing 21, and microprocessor 314 generates signal v1 and Vlq according to the output of the above-mentioned correlation detector. Size comparison of the absolute value of Vl/Vlq obtained by processing both signal ■1 and Vlq by microprocessor 314, and producing ratios V1/Vlq is carried out with a predetermined black-market price, and it is judged whether they are that an input signal expresses data communications or a mere noise. After aligning a receiver with a local peak using the above-mentioned fine alignment, the local peak needs to judge whether it is that a receiver has the best correlation at the "right" local peak by rough alignment. Rough alignment In rough alignment of a receiver to the predetermined dispatch machine for aligning a receiver certainly to maximum correlation peaks other than secondary according to one example, It fixes to the momentary point as a local peak, a receiver is adjusted by one third of the multiples of 1 code chip, and the sequential retrieval which measures the amplitude of the received signal in each contiguity local peak is included. The amplitude of each peak asks and <= To be and the judgment of being the right peak accomplish. Since it is difficult to distinguish the amplitude of the contiguity peak near the center of a correlation pattern mutually for distortion of a channel filter, It is used for the usual "center-of-gravity (centr -of-mass)" technique of judging based on not selection of a channel but the relative value of all the channels with the greatest correlation amplitude identifying the maximum local peak. [ ] In the sequential retrieval mode of rough alignment, one third of 1 code chip shifts [ microprocessor / 314 ] the timing of the after-discernment receiver of a local peak a multiple every, Measurement memory of the correlation amplitude is carried out, and it is programmed to compare using the center-of-gravity technique or the other techniques, and to identify the right correlation peak. Sequential retrieval requires the transmission introduction bit of length WS. However, it is the number of bits which smooths W by the width (one third of multiples of 1 code chip) of a peak search range, and S smooths by voltage reading. In Drawing 23, the test in Step 1200 which judges whether a receiver is in a local peak using the above-mentioned fine alignment is included in the flow chart which programming of microprocessor 314 which performs rough alignment by sequential retrieval simplified. If there is no receiver in a local peak, it will fine-align until it is judged with a receiver being in a local peak. The receiver located in the local peak is incremented until it is set to +N it to be the timing (Step 1202). However, local timing and N from which K is obtained at the time of fine alignment! One third of predetermined multiples of a code chip. Measurement memory of the correlation value of K+N is carried out (Step 1204), and decree Ment of the 1 code chip is carried out for the timing of a receiver every [ 3 / 1/] after that (Step 1206). Next, measurement memory of the correlation with a receiver and a predetermined dispatch machine is carried out (Step 1208), and it is tested whether it is in the side opposite to local peak Into which the timing of the receiver detected to (K-N, i.e., the beginning) (Step 1210). If there is nothing to the side opposite to, decree Ment of the timing of a receiver will be carried out further, and it will measure and memorize correlation. If it is in the side opposite to, all the memorized correlation will be tested and correlation of To step 1212 and a peak will be identified. According to another example, in order to reduce introduction bit length, a plurality of secondary receiving channels by which only one third of the multiples of 1 code chip were mutually Slip(ed) in the both sides of the main channel v1 produce the primary correlation signal [ secondary ], and these are given to microprocessor 314. Microprocessor 314 is programmed to identify the main channel v1 and the subfollowing channel which have the maximum degree of correlation using center-of-gravity analysis or other analyses. By using the circuit of sequential retrieval, or not programming but a plurality of receiving channels, or a correlation detector, introduction bit length required for rough correction reduces to the number S of smoothing focuses, and it is To be. of course, by This\, it assumes that it is that in which the channel which had common gap of one third of the multiples of 1 code chip on both sides of main phase Seki channel V1 exists, and comes out [ be / it / under / request / of search / receiving ]. It is not necessary to program by using a plurality of receivers to carry out sequential retrieval of micro Process and the 7 To. Instead, microprocessor 314 only measures each output of the total correlation detector aligned with the local peak, and is programmed to identify a peak with maximum amplitude. Timing Trust Positive When the data bit speed of transmission is below half of the pulse repetition speed of the source of timing, it may be locked by different timing pulse even if a dispatch machine and a receiver seem to synchronize mutually completely. For example, it is 30 bits per second in data bit speed, and the source of a timing pulse is 60 Hz, When located between the harmonics whose carrier frequency is 60 Hz, a dispatch machine is the 1st 6 (while it is locked by the timing pulse of Hlz, a receiver may be locked by the Continuing <60Hz timing pulse next.). Therefore, even if between a receiver and a dispatch machine synchronizes completely, since data timing recovery of a receiver is inaccurate, the data communications which carry out a police box are not detected. in order to show this state more intelligibly -- the -- the carrier of 0 dispatch machine with which 24 (a) figure expresses the timing pulse with which a receiver and a predetermined dispatch machine synchronize -- the 24th (it is shown in b1 figure, and the outgoing data showing lo which carries out a police box, and 0 shows and comes out to the 24th (c) figure.) If the receiver and the dispatch machine synchronize with the same timing pulse, integration/dumping circuit 310 of a receiver synchronizes with reversal of outgoing data, and as shown in the 24th idi figure, it dumps by the back end of each data. A "sunspot" shows integration/dumping time among the figure. Therefore, the integration machine output by which the sample was carried out serves as a replica of the data embedded in transmission. However, unless the transmitting machine and the receiver synchronize with the same timing pulse, integration/dumping circuit 310 does not synchronize with outgoing data correctly. This state is the 24th (it is shown in 81 figure, and in This -, integration/dumping time arises between reversal of outgoing data, and the Sample output of an integration machine serves as zero.). That is, if a receiver and a dispatch machine synchronize with the timing pulse which is not the same respectively and gets mixed up, recovery of outgoing data will become impossible. Therefore, it is necessary to test a receiver and a dispatch machine and to confirm synchronizing with the same timing pulse instead of a timing pulse in which both units get mixed up. According to one feature of an invention, subfollowing receiving channel Vl' which consists embedding addition delay of the half of a data bit is attached to the main receiving channel V1, and is provided. Therefore, one side of both channel ■1 and Vl' certainly detects a dispatch signal. the introduction data which was attached to transmission and which carries out a police box -- the Lord -- and -- secondary -- a judgment accomplishes by adding to the following receiving channel. The amplitude of the correlation output of two receiving channels is compared, and the direction of the right (it has large correlation amplitude) channel synchronizes with the same timing pulse as a dispatch machine. It That and data is monitored only by °zeta and this "right" channel. The circuit where the timing of the receiver was simplified for synchronizing so that the same timing pulse might be made to lock a receiver and a dispatch machine is shown in Drawing 25. Microprocessor 314 generates subfollowing channel Vl' from which only the half of the data bit shifted [ channel / Vl / main ]. An input sequence with the introduction bit which carries out a police box is answered, a microprocessor compares both the amplitude of channel ■1 and the data output from channel Vl' which carried out half-A bit delay from it, and while has larger amplitude, and it identifies a channel. That is, this channel is regarded as being locked by the same timing pulse as the dispatch machine being locked, and is again given to a microprocessor for data recovery. In another example of an invention, the necessity for subfollowing receiving channel v1'' is removed. Timing standard frequency is below the sampling speed of data, and if the ratio of the sampling speed of data to timing standard frequency is an integer, a dispatch machine and a receiver can be synchronized by combining many continuous data samples and being generated from one, at the one data time, i.e., a focus. the optimal data sample time is called for by receiving the introduction bit of the numerals which carry out a police box, comparing the amplitude of all the possible addition and choosing inside, the sample which gives the maximum output by combining these data samples. If assigned at the synchronous time with each original sample, synchronization can be attained by locking at time to give the maximum output. For example, if a timing signal has frequency, and 30 samples/second of day Tasan and Bring speed which are 60 Hz, in the case of data speed of 30 bits per second, each data sample is used to be generated at the one data time, i.e., a bit. Although one data bit is produced in the case of 15.7.5 or 3.75 bits per second, 2.4 or eight continuous data samples are used. This method removes the necessity for a redundant data channel, and also removes the necessity of making data sampling speed the same as data speed. Fact 1 A sampling may be performed at a speed higher than data speed. This is Mai about each data sample. It makes it possible to combine in digital one within Cross processor, and can make data speed independent of the timing of actual hardware. i3 Electric dish The data recovery in an extended spectrum system is common knowledge. Please refer to m theory of the text of Dixon taken out before - concerning the Co5tas loop abnormal-conditions machine from 155 pages especially Section 5.3 as the basic background. Since an extended spectrum system which is provided by This \ contains a plurality of correlation channels, according to one feature of an invention, recovery of data is improved by extracting data by each channel only in a single correlation channel. Thereby, the meso sage error ratio of a system is reduced, and the length of an introduction required for synchronization of a receiver can be reduced, or it can also be removed completely. If Drawing 19 is referred to again, it will be admitted that main Agreement of the correlation pattern 1000 is carried out main phase Seki channel ■1. The numerals of main phase Seki channel Vl are dependent on the numerals of transmission data. Therefore, while the right value of ■1 corresponds to transmission logic 1, the negative value of correlation ■1 corresponds to transmission logic 0. ■ Each correlation in 2, V3, v6, and ■7 also has a value according to the numerals of transmission data. That is, the relation of the voltage output in each channel V1, ■2, v3, and v6 and V7 is as follows if a noise and distortion do not exist: V 2 = V 3 = R1-V 1 (?) V6=V7=R2-Vl -- however -- R1=-2/3 R2=]/3 According to this invention, after synchronizing a receiver correctly, the data numerals in the output of each correlation detector are monitored. According to a noise and the distorted characteristic, data is extracted only using the output in channels v1 and V2 and ■3, The length of the relative amplitude in which the noise of vj [ as opposed to the following passage, however Kj=V1 in an effective S/N ratio gain ] is not included, j= 2.3 (Kj-R1 which does not include distortion), and an L-pseudo-random code, uj -V, the load factor of business (j= 1.2.3). A load factor is chosen according to an existing specific distortion. Drawing 26 answers channel VL V2 and ■3, it is the simplified circuit diagram showing microprocessor 314 programmed to extract outgoing data combining all three correlation channels, and a load factor is chosen according to a specific distortion existing on a transmission medium turned out to be. The Vth table shows the improvement of the S/N ratio in the presumed combination of some possible distortion and a load factor. The Vth table Another advantage which collects by all the channels of a receiver can identify and disregard random and the burst error which affect all the channels. Not the right-angled output relevant to a single channel but all the channels are but used for this like the detection of signal existence using a correlation output of the corresponding phase and the right-angled phase which was mentioned above. A synchronization may be able to be monitored during reception of a message as another advantage which performs data recovery from all the correlation channels or at least several correlation channels. Although adjustment of a synchronization cannot be performed during reception of a message, if an additional receiving channel is used, the contents of the message can be collected, without repeating. In the above-mentioned indication, in addition to this, he can use; which illustrated and described only the desirable example of the invention, however the present invention under various kinds of combination and environment, and it should be understood that modification or change is possible within the limits of the inventive concept indicated in the range of a claim.

[Brief Description of the Drawings]

Drawing 1 -- the DSSSS code division multiplex Receiver signal -- easy block diagram; -- Drawing 2 -- Drawing; of a bipolar pseudo-random pulse sequence -- Drawing; showing the autocorrelation pattern for a bipolar pseudo-random pulse sequence as showed Drawing 3 in Drawing 2 Drawing 4 is a superposition figure of the autocorrelation pattern of shoes to correspond to the contiguity dispatch machine in a code division multiplex system; The figure where Drawing 5 is a figure corresponding to Drawing 4, and the signal of the contiguity dispatch machine was separated in the Ghat band; it is Drawing 6 (the wave form chart in which aJ~ (b) shows generating of 3 Advance code; N which shows the receiver with which Drawing 7 operates according to the principle of the present invention single block diagram;). The figure showing the ideal cross correlation pattern between the local generating 3 Advance code sequence based on the present invention in Drawing 8, and an input 2 Advance code sequence; Drawing 9 (a) - (c) is a figure showing the correlation pattern which arose with the multi-channel correlation detector based on the thread type example of the present invention; Drawing 10 is a figure showing the actual correlation pattern obtained with the receiver of the present invention when it operates under existence of various degradation factors; The figure showing the analog example of the multi-correlation detector with which Drawing 11 determines the degree of correlation based on the present invention; the circuit diagram showing simplification of the circuit by the analog example of Drawing 11 where Drawing 12 used 2 Progressive standard signals; Drawing 13 carries out the decrease of the number of analog multiplexers. The figure showing the further simplification of the analog circuitry of Drawing 11 using digital logic; Drawing 14 (al) (bl is a circuit of Drawing 13.) The two methods of performing The shown figure; the figure showing digital execution of one channel of the circuit which showed Drawing 15 in Drawing 11; the figure where Drawing 16 carried out N-To the channel generalization of the circuit execution of Drawing 15; another digital execution of a single channel correlation machine as showed Drawing 17 in Drawing 11 shown Drawing; -- Drawing; which carried out N-To the channel generalization of the circuit which showed Drawing 18 in Drawing 17 -- Drawing; showing a corresponding phase and right-angled phase correlation patterns including the position of the subreceiving channel for correlation detection in Drawing 19 The 20th figure fa reaches (bl is fine alignment of a receiver). The flow chart which shows the two different methods of performing; the figure of the circuit where Drawing 21 was based on the microprocessor which performs fine alignment of signal existence detection and a receiver; flow Char1- which shows how Drawings 22 fa and Tb perform timing correction of a receiver and signal existence detection, respectively; The flow chart which shows one method for Drawing 23 to perform rough alignment of a receiver; Drawing 24 (al-fQ) is Show about the relation of the timing pulse between a receiver and a dispatch machine, To timing diagram; Drawings; and 26 showing a circuit for Drawing 25 to lock a dispatch machine and a receiver in the same timing pulse are circuit diagrams based on the microprocessor for collecting data in a receiver. 100.200 ... Receiver 110 ... Source of a timing signal, 202.304 ... 1st means to obtain a product, 204.306 ... 2nd means to obtain a product, 206.308 ... A means to acquire a difference, and 302.400.700.1000 ... Correlation detector, 310 ... an integrating means and 314 ... a signal processor means and 402 ... the -- 2 input Multiplexer of one, 404 ... the -- 2 human-power multiplexer of two, and 410.508.606.608.720 ... an inverter, 502 ... 3 input Multiplexer and 600.602...1 to 2 input Multiplexer, 606 ... 4 input Multiplexer and 702 ... A/D converter 704.824 ... Addition / subtraction machine, and 706 ... Akyu muleta 708 ... output register, 710.816 ... a sequencer and 716.718.808.812.908.910,912.1010.1012.1014 ... Digital execution. Means and 810 [ ... Bidirectional counter / 908.1006 ... Analog comparator. ] ... A Akyu muleta memory, 902.1002 ... Voltage / frequency converter, 904.1004 ... A means to obtain an absolute value, and 908.1008 The fair copy of a drawing (it is a change-less A hl One to the contents) ig 2 Cross correlation Cross correlation Cross correlation ig9c Fig/theta Written amendment (method) Display of one incident Those who will do patent application No. [ three ] 57688 and amendment in Showa 60 Relation with an incident Applicant 4, representative 5, date of an order for amendment It is an object of 6 and amendment on August 27, Showa 60. The column and complete diagram side of brief explanation of the drawings of a specification 7, the contents of amendment