Fast adaptive power control for a variable multirate communications system

[0001] [Field of Invention] The present invention relates to power control of a wireless communication system, and more particularly to a high-speed adaptive power control system and method for a variable multi-rate communication system. [0002] [Explanation of prior art] Various methods are known as power control methods for wireless communication systems. Figure 1 shows an example of an open-loop power control transmitter system for a single rate data system, that is, a single data rate system. Figure 2 shows an example of the closed-loop power control transmitter system for the single-rate data system. [0003] The purpose of these schemes is in the presence of propagating channels with fading and time-varying interference to minimize transmitter power while allowing data to be received by the other party with acceptable quality. It is to change the power of the transmitter at high speed. In digital devices, it is common to change the transmitter power, for example, by applying variable scale factors to the digital data rather than changing the gain of the RF amplifier. [0004] Third Generation Partnership (3GPP) Project)) In the latest communication methods such as Time Division Duplex (TDD) and Frequency Division Duplex (FDD), multiple channels with variable data rates are combined and transmitted. Figures 3 and 4 show conventional open-loop and closed-loop power control transmission methods, respectively. Background specification data for these methods can be found in 3GPP TS25.223v3.3.0, 3GPP TS25.222v3.2.0, 3GPP TS25.224v3.6 and ARIB 3G Multiple System Version 1.0, Revision 1.0 Wireless Interface Volume 3 Specifications. ing. [0005] The open-loop and closed-loop power control schemes for variable multi-rate wireless communication schemes respond relatively slowly to changes in data speed, resulting in excessive transmitter power and sub-desired quality. The performance remains below the optimum, such as generating the received signal of. For the optimization, it is desired to provide a power control method and method that adapts to changes in data speed at high speed. [0006] [Summary of Invention] The present invention processes user data as a multi-rate signal with a data rate of N (t) and converts the user data signal with a data rate of N (t) into a transmission data signal with a higher data rate of M (t) for transmission. It provides a method of controlling the transmitter power in the wireless communication system as described above. The transmit power is adjusted based on a relatively low data rate criterion based on the quality of the received data at the receiver of the transmitted data. The transmitter power is N (t) / M so that changes in the data rate of the user data signal or changes in the data rate of the transmitted data signal are compensated prior to adjustments based on the data quality associated with that data rate change. Calculated as a function of (t). Preferably, the user data signal at data rate N (t) is further increased in data rate M (t) so that the energy-to-noise spectral density ratio per bit is increased in the transmitted data signal by repeating the selected data bits. Convert to a transmission data signal. [0007] This method can be applied to open-loop or closed-loop power control schemes where the scale factor is applied to control transmitter power. When carrying out the present invention in an open-loop or closed-loop transmitter, preferably N (t) / M (t) is used as the scale factor. [0008] In this method, the transmitter receives reference signal, reference signal power data, interference power data measurements and signal-to-interference ratio (SIR) data, that is, SIR data target values based on received signal quality data collected at a relatively low speed. It can be applied to the open loop power control method. The transmitter measures the reception reference signal, calculates the power thereof, and calculates the communication path loss based on the power data of the received reference signal and the calculated reference signal power. The transmitter then calculates the scale factor based on the path loss calculated value, the received interference power measurement data, the SIR data target value and N (t) / M (t)). [0009] This method also causes the transmitter to utilize the step-up / down data generated by the receiver and calculate the scale factor based on the step-up / down data and (N (t) / M (t)). It can also be applied to the closed loop method. Preferably, the step-up / down data is signal-to-interference ratio (SIR) data that is at least partially based on the interference power data measurements of the signal received by the receiver from the transmitter and the received signal quality data collected at a relatively slow rate. It occurs in combination with the target value. A factor of (N (t) / M) to the nominal SIR data target value based on the received signal quality data collected at a relatively low speed, preferably to adjust the SIR data target value immediately in the event of data rate fluctuations. Multiply (t)) to calculate the SIR data target value. [0010] The invention also processes user data as a multi-rate signal with a data rate of N (t) and converts the user data signal with a data rate of N (t) into a transmit data signal with a higher data rate of M (t) for transmission. Provided is a transmitter in a wireless communication system designed to be used. The transmit power of this transmitter is adjusted on a relatively slow basis by applying a scale factor to the transmitter power based on the quality of the data received at the receiver. The transmitter is a data signal speed converter that raises the user data signal data rate N (t) to a higher data transmission data rate M (t), and transmits based in part on the receiver-generated data related to the quality of the received data. Includes a processor that calculates the power scale factor. In this data signal data speed converter, this processor calculates the transmission power scale coefficient as a function of N (t) / M (t), and the change in the data speed in the user data signal or the data speed of the transmission data signal is the data speed. It is coupled with this processor to be compensated before adjustments based on the quality of received data associated with changes. [0011] Preferably, the data signal data rate converter increases the user data signal at data rate N (t) such that the energy-to-noise spectral density ratio per bit increases in the transmitted data signal due to the repetition of the selected data bits. Converts to a transmitted data signal with a data rate of M (t). [0012] This transmitter is an open loop power control system, that is, a signal based on reference signal power data, interference power measurement data, and received signal quality data collected at a relatively low speed from a receiver that receives transmission data from the transmitter. It can be configured as part of an open loop power control scheme that receives the anti-interference ratio (SIR) data target value. In that case, the transmitter includes a signal measuring device that measures the power of the reception reference signal, and a path loss processing circuit that calculates the communication path loss based on the power data of the reception reference signal and the reception reference signal power measurement value. .. The transmitter processor calculates the scale factor of the transmit power based on the path loss calculated value, the received interference power measurement data, the SIR data target value and N (t) / M (t)). [0013] The transmitter can also be configured as part of a closed-loop power control system, i.e., a closed-loop power control system in which the transmitter receives step-up / down data from a receiver that receives data from the transmitter. In that case, the transmitter processor calculates the scale factor based on the step-up / down data and (N (t) / M (t)). [0014] The invention also processes user data as a multiple data rate (multi-rate) signal with a data rate N (t), which is a function of time, and the user data signal with a data rate N (t) is higher data for transmission. Provided is a closed-loop transmission power control method in which a transmission data signal having a speed of M (t) is converted and the transmission power is adjusted by applying a scale coefficient according to step-up / down data. This scheme includes a receiver that receives a transmit data signal with a data rate of M (t) and generates step-up / down data. Preferably, the receiver reduces the data rate M (t) of the received transmitted data to generate a user data signal with a data rate N (t), and a transmitted data signal data rate converter and data quality of the user data signal. It has a data quality measuring device for measuring and a circuit device for calculating step-up / down data partially based on the data quality measured value of the user data signal. The data signal data speed converter has its circuit calculating step-up / down data as a function of N (t) / M (t), thereby changing the data speed of the user data signal or the data speed of the transmitted data signal. Operates associated with the circuit device to compensate for changes before adjusting the data quality base associated with those changes. [0015] Preferably, this scheme converts a user data signal with a data rate of N (t) into a transmit data signal with a higher data rate of M (t) by repeating the selected data bits, thereby energetically per bit. Includes a transmitter with a data signal data speed converter that increases the to noise spectrum density ratio in the transmitted data signal. [0016] In a preferred embodiment, the receiver has an interference measuring device for measuring the power of an interference signal received together with a transmitted data signal having a data velocity of M (t). The data quality measuring device outputs a nominal SIR data target value based on the received data quality data collected at a relatively low speed. The circuit device of this receiver adjusts the SIR data target value immediately when a change in data velocity occurs, so that the interference power data measurement value of the signal from the signal transmitter and the nominal SIR data target value and the coefficient N The step-up / down data is calculated by combining with the signal-to-interference ratio SIR data target value calculated by multiplying (t) / M (t). [0017] Objectives and advantages other than the above will be apparent to those skilled in the art from the following description of preferred embodiments of the invention. [0018] [Preferable Embodiment] Conventional power control methods of wireless systems such as 3GPP use so-called inner loops and outer loops. The power control method is called an open loop or a closed loop depending on whether the inner loop is an open loop or a closed loop. In both forms, the outer loop is a closed loop. [0019] FIG. 1 shows a related part of an open-loop power control system having a transmitting side transmitting / receiving station 10 and a receiving side transmitting / receiving station 30. Stations 10 and 30 are both transmitters and receivers. Usually one is a base station and the other is a user equipment UE. Only selected components are shown for clarity. [0020] The transmitting station 10 includes a transmitter 11 having a data line 12 for transporting a user data signal for transmission. The user data signal is set to a desired power level by adjusting the transmission power level by applying the transmission power scale coefficient from the output 13 of the processor 15. User data is transmitted from the antenna system 14 of the transmitter 11. [0021] [0021] The radio signal 20 including the transmission data is received by the receiving station 30 via the receiving antenna system 31. The receiving antenna system also receives the interfering radio signal 21 which affects the quality of the received data. The receiving station 30 includes an interference power measuring device 32 that receives a received signal and outputs an interference power data measurement value. Further, the receiving station 30 has a data quality measuring device 34 that receives a received signal and generates a data quality signal. The data quality measuring device 34 is connected to the processing device 36. The processing device 36 receives the signal quality data and calculates the signal-to-interference ratio (SIR) data target value based on the quality reference parameter determined by the user from the input 37. [0022] Further, the receiving station 30 has a transmitter 38 connected to the interference power measuring device 32 and the SIR target value generating processor 38. The transmitter 38 of this receiver transmitter / receiver station has inputs 40, 41 and 42 for user data, a reference signal and transmission power data of the reference signal, respectively. The receiving transmission / reception station 30 transmits the user data, control data, and a reference signal via the associated antenna system 39. [0023] The transmitting station 10 has a receiver 16 and an antenna system 39 connected to the receiver 16. The receiver 16 of this transmitting station receives the radio frequency signal transmitted from the receiving station 30, that is, the radio frequency signal including the user data 44 of the receiving station 30, the control signal generated by the receiving station 30, and the data 45. .. [0024] The transmitter processor 15 works with the transmitter receiver 16 to calculate the scale factor of the transmit power. The transmitter 11 has a device 18 connected to the path loss calculation circuit 19 to measure the reception reference signal power. [0025] In order to calculate this transmit power scale coefficient, the processor 15 is the SIR target value data input 22 for the SIR data target value generated by the SIR target value generation processor 36 of the receiving station, and the interference power measuring device 32 of the receiving station. Data is received from the interference power data input 23 for the generated interference data and the path loss data input 24 which is the output of the path loss calculation circuit 19. The path loss signal is the data from the reference signal transmission power data input 25 for the reference signal transmission power data generated from the receiving station 30, and the reference signal power measurement value input for the output of the reference signal power measuring device 18 of the transmitter 11. The path loss calculation circuit 19 is generated from the data from 26. The reference signal measuring device 18 is connected to the receiver 16 of the transmitting station and measures the power of the reference signal input from the transmitter 38 of the receiving station. Preferably, the path loss calculation circuit 19 calculates the path loss based on the difference between the known reference power signal strength of the input 25 and the received power strength measurement of the input 26. [0026] The interference power data, reference signal power data, and SIR target value values are sent to the transmitting station 10 at a speed sufficiently lower than the time variation of the propagation channel and interference. This "inner" loop is part of this system that depends on interface measurements. This method can be considered as an "open loop". That is, there is no feedback to the algorithm at the same speed as the time variation of this propagation channel, nor is there any feedback to interference that indicates the degree of quality of the estimated minimum transmitted power requirement. If the required transmit power level changes rapidly, this method cannot adjust the scale factor fast enough in response to the change. [0027] For the outer loop of the open-loop power control method shown in FIG. 1, the quality of the received data is evaluated by the measuring device 34 at the receiving station 30. The usual metrics for the quality of digital data are the bit error rate and the block error rate. Calculations of these metrics require data accumulated over a time well longer than the duration of the time variation of propagation channels and interference. For any metric, there is a theoretical relationship between that metric and the SIR received value. Once sufficient data has been accumulated in the receiving station to evaluate the metric, the processor 36 calculates it and compares it to the desired metric (representing the required quality of service) to generate an updated SIR target. To do. The updated SIR target value is a value (theoretical value) that converges the measurement reference measurement value to the required value when applied to the inner loop of the transmitter. Finally, this updated SIR target value is sent to the transmitter 11 via the transmitter 38 on the receiving side and the receiver 16 on the transmitting side, and is used in the loop. The frequency of SIR target updates depends on the time required to accumulate the statistical and practical limits of quality for the frequency of signaling to power controlled transmitters. [0028] FIG. 2 shows a communication method including a transmitting station 50 and a receiving station 70 using a closed-loop power control method. [0029] The transmitting station 50 includes a transmitter 51 having a data line 52 for transporting a user data signal for transmission. The power level of the user data signal is a desired level adjusted by giving a transmit power scale factor from output 53 of processor 55. User data is transmitted from the antenna system 54 of the transmitter 51. [0030] The radio frequency signal 60 including the transmitted data is received by the receiving station 70 via the receiving antenna system 71. The receiving antenna system 71 also receives the interfering radio signal 61, which affects the quality of the received data. The receiving station 70 includes an interference power measuring device 72 that receives a received signal, and the measuring device 72 outputs a SIR data measurement value. The receiving station 70 further includes a data quality measuring device 73 that receives the received signal, and the measuring device 73 generates the data quality signal. The data quality measuring device 73 is connected to a processor 74, which receives the signal quality data and calculates the signal-to-interference ratio (SIR) target value data based on the user-defined quality standard parameter from the input 75. [0031] The synthesizer 76, which preferably consists of a subtractor, compares the SIR data measurement value from the device 72 with the SIR target value data calculation value from the processor 74 by subtraction, and outputs an SIR error signal. The SIR error signal from the synthesizer 76 is sent to the processing circuit 77, and the processing circuit 77 issues a step-up / down command based on the SIR error signal. [0032] The receiving station 70 further has a transmitter 78 connected to this processing circuit 77. The transmitter 78 of the receiving station has an input 80 for user data. The receiving station 70 transmits the user data and the data related to the control from the related antenna system 79. [0033] The transmitting station 50 has a receiver 56 and a receiving antenna system 57. The receiver 56 of the transmitting station receives the radio signal from the receiving station 70 including the user data 84 of the receiving station and the control data 85 generated by the receiving station. [0034] The transmitting station scale factor processor 55 has an input 58 connected to the transmitting station receiver 56. Processor 55 receives an up / down command signal from input 58 and calculates the transmit power scale factor based on it. [0035] For the inner loop of the closed-loop power control method, the transmitter 51 of the transmitting station sets the power based on the high-speed "step-up" and "step-down" commands generated by the receiving station 70. At the receiving station 70, the measuring device 72 measures the SIR of the received data, and the measured value is compared with the SIR target value generated by the processor 74 by the synthesizer 76. The SIR target value is a value (theoretical value) that brings about the desired quality of service when the data is received at that value. If the received SIR measurement is less than the SIR target, the processing circuit 77 sends a "step down" command to the transmitter transmitter 51 via the receiver 78 and the transmitter receiver 56, otherwise. If so, send a "step up" command. This power control scheme can be considered a "closed loop" because of the fast feedback of the "step up" and "step down" commands that respond in real time to the propagation channel and the time variation of interference. If the required transmit power level changes due to time-varying interference and propagation, the scheme responds quickly and adjusts the transmit power accordingly. [0036] Regarding the outer loop of this closed loop power control system, the quality of the received data is evaluated by the measuring device 73 of the receiving station 70. The usual metrics for digital data quality are bit error rate and block error rate. Calculations of these metrics require data accumulated over a time sufficiently longer than the time-varying propagation channels and periods of interference. For any given metric, there is a theoretical relationship between that metric and the received SIR. Once sufficient data has been accumulated in the remote receiver to evaluate the metric, the processor 74 calculates it and compares it to the desired metric (which represents the desired quality of service) and updates the SIR target. Generate a value. The updated SIR target value is a value (theoretical value) that converges the metric to a desired value when applied to the receiving algorithm. The updated SIR target value is used in the inner loop to direct the step-up / down command of the transmitting station to the power scale factor generating processor 55 and control the power of the transmitter 51. [0037] Figures 1 and 2 show a power control scheme for data transmission at a single data rate. However, in digital communication schemes, data can be processed block by block at a given bit rate and given block size, or at a given number of bits per block and given block data rate. In this type of system, for example a 3GPP FDD system or a TDD system, there can be more than one data rate at a given point in time within the communication scheme, and such data rates can fluctuate from moment to moment. .. FIG. 3 shows a modification of the open-loop power control method, and FIG. 4 shows a modification of the closed-loop power control method for a wireless communication system that transmits and receives multiple data channels having variable data rates. [0038] The open-loop power control system of FIG. 1 is equipped with an upconverter 27 at the transmitting station 10 and a downconverter 47 at the receiving station 30 as shown in FIG. 3 so as to be adapted to multi-channel variable data rate data transmission. [0039] Incorporate user data for transmission into a signal with a data rate of N (t). A data upconverter 27 having an output 28 carrying a transmit data signal at speed M (t) converts a data stream with data speed N (t) into a data stream with a higher data speed M (t). [0040] The receiving station 30 receives the user data signal having a data speed M (t) and down-converts it to the original data speed N (t) by the converter 47. The interference power measuring device 32 measures the interference power of the signal received at the data rate M (t). The data quality measuring device 34 is connected to the user data path downstream of the converter 47, down-converts the data to N (t), and then measures the quality of the data. [0041] To accommodate multi-channel variable data rate data transmission, the closed-loop power control scheme of FIG. 2 is modified to include an upconverter 67 at the transmitting station 50 and a downconverter 87 at the receiving station 70, as shown in FIG. To do. Incorporate user data for transmission into a signal with a data rate of N (t). A data upconverter 67 having an output 68 carrying a transmitted data signal at a data rate of M (t) converts a data stream with a data rate of N (t) into a data stream with a higher data rate of M (t). [0042] At the receiving station 70, the user data signal having a data velocity M (t) is down-converted to the original data velocity N (t) by the converter 87. The interference power measuring device 72 measures the interference power of the signal received at the data rate M (t). The data quality measuring device 73 is connected to the user data path downstream of the converter 87, down-converts the data to N (t), and then measures the quality of the data. [0043] In both of these two types of multi-channel variable data rate schemes, the data rate of user data input to transmitters 11,51 for transmission to receivers 30, 70 of remote receivers is N (t). The data speed of the user data output from the receiver is also the same. The data rate N (t) can be a composite of several data rates of different data channels multiplexed for transmission via a common bearer. The fact that this N is a function of (t) indicates that its data velocity can fluctuate, that is, it varies over time or from block to block. This variation is due to the addition and deletion of data channels and the variation of the actual data rate in the current channel, as is usually the case with packet services. [0044] Further, in both of the above equations shown in FIGS. 3 and 4, the data velocity changes from N (t) to M (t) in the transmission data path and returns to N (t) in the receiving station. The data velocity N (t) is the user data velocity, the data velocity M (t) is the data velocity being transmitted, and they are completely independent of each other. [0045] For example, in the 3GPP TDD scheme, M (t) is the number of bits per 10 msec. Frame in a given number of time slots and an orthogonal variable diffusivity code for a given diffusivity. The fact that M is a function of (t) indicates that its data velocity can change over time, and more specifically, it varies from frame to frame. Changing M is equivalent to changing the diffusion rate, the number of physical channels used per frame, etc., and changing N is equivalent to changing the data rate in one or more transport channels. .. The data rate M (t) is equivalent to Ndata, j bits per 10 msec frame, and N (t) is per 10 msec frame during the TFCj valid period t.<img file="JP4684530B2_D0001.tif" />Equivalent to a bit. As defined here in 3GPP Nij is the number of bits of the radio frame before data speed matching between TrCHi and transport format combination j, RMi is a semi-static transmission rate matching attribute for TrCHi signaled from the upper layer, PL has a value that limits the amount of puncture added to minimize the number of physical channels, the puncture limit signaled from the upper layers, Ndataj is the total number of bits available for the coded composite TrCH in the radio frame of the transport format combination j, TFi (j) is TrCHi's transport format for transport format combination j, TB is a transport block of the equivalent term "MACPDU", defined as the basic unit of data exchanged between L1 and MAC. TBS is a set of transport blocks, defined as a set of transport blocks that are exchanged between layers L1 and MAC at the same time using the same transport. TrCH is a transport channel that is provided from the physical layer to layer L2 for data transport between equivalent layers L1 and is marked with entertainment (different types of transport channels are different from each other). , Defined by the method and characteristics of data transfer at the physical layer, for example, whether to use a dedicated physical channel or a common physical channel), TF is a transport format, defined as the format provided from layer L1 to the MAC for the delivery of transport block sets during the transmission time interval on the transport channel (this transport format has two parts). , That is, it consists of a dynamic part and a semi-static part), TFC is a transport format combination, defined as a combination of working transport formats for all transport channels, that is, one transport format from each transport channel. TFCS is a transport format combination set, defined as a set of transport format combinations, MAC is a medium access control, a sublayer of wireless interface layer L2 that provides access to unidentified data transfer services and transport channels on logical channels. A PDU is a protocol data unit, which is a unit of data specified in the (N) -protocol layer and consisting of (N) -protocol control information and (N) -user data. [0046] The conversion from the data velocity N (t) to the data velocity M (t) is performed by the converters 26,67 of the transmitting station 10,50, which is an up-conversion with the coefficients M (t) / N (t). The conversion from the data velocity M (t) to the data velocity N (t) is performed by the converters 47,87 of the receiving stations 30,70, which is the down conversion by the coefficient N (t) / M (t). [0047] In the schemes shown in FIGS. 3 and 4, the data velocity M (t) is assumed to be higher than the data velocity N (t). This is an intentional display. The inconvenient effect of the data speed up-conversion that the present invention seeks to alleviate occurs only in the case of the data speed up-conversion by repetition in the transmitter described later. This effect does not occur when N (t) = M (t), and when N (t)> M (t), the effect is different and is not the subject of the present invention. [0048] Data speed up-conversion is performed by repeating, that is, by repeating the selected bits of the speed N block until the number of bits is the same as that of the speed M block, and down-conversion by repetition is the numerical value of the received repeated "soft" bits. It is performed by target synthesis. An example of iterative up-conversion is shown in Figure 5, where Bi is the i-th "hard" bit in the input sequence for increasing the data rate from 6 bits / block to 8 bits / block, ie ± 1. In this example, two bits, 2 and 5, are repeated to change the block size from 6 to 8. Figure 6 shows b_i+ n_jIs the "soft" bit, i.e. the transmit bit Bi and the noise component n at time j at the receiver in the down-conversion process at the input consisting of eight "soft" bits._jA digital sample of the sum of and is shown. The received "soft" bits 2 and 3 are numerically added to form a scaled version of the original bits 2 and 3, and the similarly received "soft" bits 6 and 7 are also numerically added. Consists of a scaled version of the original bit 5. [0049] The specific repeating bits used in this example represent a uniform distribution of repeating bits, which is a specific scheme used in the 3GPP scheme in relation to the interleaver. However, the selection of bits for repetition is not deeply relevant to the present invention. [0050] The above method of data speed conversion is 3GPP It is an element of so-called "data velocity matching" that uses the repeat function used in the TDD and FDD systems. This can use the energy difference between the original short block and the transmitted long block to improve signal quality compared to the simple method of sending dummy bits (eg 2 bits) to change the data rate. It has the advantage of. That is, in this example, the energy-to-bit noise spectral density ratio (Eb / No) of the received bits 2 and 5 is twice that of the other received bits. Therefore, an overall improvement in the bit error rate and block error rate of the received data can be obtained compared to those having a quality standard of transmitting two dummy bits instead of repeating the bits. Of course, 6 units of energy is enough to use 8 units of energy to transmit data. As a result, there is an effect of transmission energy that is unintended but increased as a result and an effect of improving the quality of received data. The present invention intends to achieve these improving effects. [0051] The open-loop and closed-loop power control schemes shown in FIGS. 3 and 4 for variable multi-data velocity data are substantially the same as those for single-velocity data in FIGS. 1 and 2. Figures 3 and 4 show open-loop and closed-loop power control schemes for 3GPP TDD communication schemes. However, these open-loop and closed-loop power control schemes are not optimal for targeting the effects of data velocity changes on variable multirate data. [0052] In the open-loop scheme of Figure 3, where N (t) is equal to M (t) in a stable state and ignores channel variation or variable interference with fading, the SIR target settles at a quiescent point that provides the desired data quality. .. This state is equivalent to the single data velocity example in Figure 1. However, in the multi-channel variable data rate scheme, t, N or M may change. As mentioned above, in order to obtain an improvement in the quality reference measurements of the data, more energy is transmitted than is actually required. Outer loops operating at relatively low data rates eventually detect improved signal quality, and then are perceived as too high signal quality by lowering the SIR target for the inner loop to lower transmitter power. Compensate. On the other hand, the transmitter 11 uses more energy than is actually required to transmit the data (data to be received with the required quality). When the transmission station of the open-loop power control is a battery-powered mobile device (in the case of the 3GPP method), unnecessary battery power is consumed. [0053] The case where the present invention is applied to open-loop power control for variable multi-data velocity data is shown in FIG. 7, which shows the corresponding components with the same reference numbers as in FIG. As shown in FIG. 7, the transmitter converter 27 has an additional input 29 connected to the scale factor generator 15. This converter supplies a signal equivalent to (N (t) / M (t)) to processor 15 via its input 29 as a factor in the calculation of the transmit power scale factor. Therefore, when applying the corrected scale factor to the transmit data, the transmit power is applied so as to immediately compensate for the N (t) or M (t) data velocity change. N (t) / M (t) Adjust with the coefficient of. [0054] This modified scale factor is applied in the same way as the conventional scale factor for transmission power setting derived from Equation 1. [0055] [Formula 1] P_TS= SIR_TARGET+ I_RS+ α (LL₀) + L₀+ Constant Here, the additive term is a multiplication coefficient expressed in dB. Actually, the additional coefficient used when generating the scale factor is another term in the above equation, and the above equation is as shown in Equation 2. [0056] [Equation 2] P_TS= SIR_TARGET+ I_RS+ α (LL₀) + L₀+ Constant + N (t) / M (t) here, P_TSIs the transmit power level (dB) of the transmitting station SIR_TARGETIs determined by the receiving station, I_RSIs the measured value of the interference power level at the receiving station, L is the estimated path loss (dB) for the most recent time slot where the path loss was estimated. L₀Is the long-term mean value (dB) of the path loss, which is the operating mean value of the estimated path loss value L. The constant is a correction term (this constant corrects the difference between the uplink channel and the downlink channel for the purpose of compensating for the difference between the uplink gain and the downlink gain, etc. Furthermore, this constant is a correction term. If transmission is performed at the transmission power reference level of the receiving station instead of the actual transmission power), it is corrected. α is a weighted value that is a measure of the quality of the estimated route loss value, preferably the number of time slots between the time slot of the last estimated route loss and the first time slot of the communication signal transmitted by the transmitting station. Based on, it has a value between 0 and 1 (generally, if the time difference between time slots is small, the most recent path loss estimate is fairly accurate and α is set to a value close to 1. On the other hand, when the time difference is large, the estimated route loss value is not accurate, and a long-term average route loss measurement is desirable for a better estimated value of the route loss. Therefore, α is set to a value closer to 1. Equations 3 and 4 are equations for determining α. [Equation 3] α = 1- (D-1) / (D_max-1) [Equation 4] α = max {1- (D-1) / (D_max-allowed-1), 0} Here, D is the number of time slots between the time slot of the estimated final path loss value and the first time slot of the transmitted communication signal, and is called a time slot delay. If this delay is for one time slot, then α is 1. D_maxIs the maximum possible delay. The normal value for a frame with 15 time slots is 7. Delay is D_maxIf so, α is 0. D_max-allowedIs the maximum permissible time slot delay for using open-loop power control. Delay is D_max-allowedWhen the value exceeds, the open-loop power control is turned off by setting α = 0). [0057] Since the data velocities N (t) and M (t) fluctuate from moment to moment, the method of the present invention shown in FIG. 7 waits for a modified SIR target value determined by an outer loop to compensate for the change in data velocities. Instead of compensating for changes in required power. In this way, for open-loop power control, the present invention substantially eliminates the time it takes for a transmit signal to be transmitted with excess power due to fluctuations in data rate. [0058] [0058] For the closed-loop scheme of Figure 4, where N (t) is equal to M (t) in the stable state, ignoring channel fluctuations or variable interference with fading, the SIR target is the quiescent point that results in the desired data quality. Placed in. This is equivalent to the single data velocity method in Figure 2. However, in the variable multi-data rate, N and M fluctuate at a certain time t. As mentioned above, this provides an improvement in data quality reference measurements, but requires transmission with more energy than is actually required. However, since the SIR measurements are taken before down-conversion, which increases the extra bit-by-bit Eb / No (or SIR), the SIR measurements do not change with changes in N and M. The outer loop operates at a relatively low speed in the short term, so the power control commands returned to the transmitter are no longer accurate. However, the outer loop detects the improved signal quality and calculates a lower SIR target for the inner loop to compensate for what is perceived as too high signal quality. In that case, this too low SIR target value biases the step-up / down decision downward and reduces the transmitter power. As a result, the signal quality in the receiver is below the required value. Therefore, the outer loop responds with a higher SIR target value due to the degraded signal quality, and in stable conditions this scheme converges to the correct power level. The received signal remains in a degraded state until that state is reached. [0059] FIG. 8, which shows the corresponding components with the same reference numbers as in FIG. 4, shows an example of applying the present invention to a closed-loop power control scheme for variable multirate data. In transmitter 51 of transmitter station 50, converter 67 has an additional input 69 connected to scale factor generator 55. This transducer has (so that the scale factor output from processor 55 via output 53 is a function of N (t) / M (t) as described in relation to the open-loop method in Figure 7. Outputs a signal equivalent to N (t) / M (t)). [0060] In the receiver, the converter 87 outputs a signal equivalent to N (t) / M (t) to the synthesizer 88, which is preferably composed of a multiplier. The output of the SIR target value processor 74 is input to the synthesizer 88. The synthesizer 88 synthesizes the speed change data from the converter 87 and the SIR target value data from the processor 74, and outputs the adjusted SIR target value to the synthesizer 76. [0061] With this configuration, the processor 74 outputs a nominal SIR target value. By applying the coefficient N (t) / M (t) to the nominal SIR target value determined by the signal quality measurement value, a high-speed response for compensating or adjusting the received power fluctuation caused by the data speed fluctuation is performed. [0062] Since the data velocities N (t) and M (t) change from time to time, the method in Figure 8 is at the change in power requirements at the transmitter and at the receiver, rather than waiting for compensation by the outer loop of the change in data velocities. Promptly compensates for changes in the desired signal strength. In this way, in the closed loop power control method of FIG. 8, the time for receiving the received signal with a quality equal to or lower than the allowable received signal quality is shortened due to the change in data speed. [0063] Although various components have been described above as separate components within the transmitting and receiving stations and the receiving and receiving stations, it will be apparent to those skilled in the art that various components can be combined. For example, the synthesizer 88 in the method of FIG. 8 can be embodied as the same processor as the processor 74. Modifications and modifications of the present invention other than the above will be apparent to those skilled in the art. [Simple explanation of drawings] FIG. 1 is a schematic diagram of an open-loop power control method according to a conventional technique for single data speed wireless communication. FIG. 2 is a schematic diagram of a conventional closed-loop power control method for single data rate wireless communication. FIG. 3 is a schematic diagram of an open-loop power control method according to a conventional technique for variable multi-data speed wireless communication. FIG. 4 is a schematic diagram of a conventional closed-loop power control method for variable multi-data speed wireless communication. FIG. 5 is a block diagram of data speed up conversion from 6 bits to 8 bits per block using iteration. FIG. 6 is a block diagram of data speed down conversion from 8 bits to 6 bits per block. FIG. 7 is a schematic diagram of a high-speed adaptive open-loop power control method for variable multi-data speed wireless communication according to the present invention. FIG. 8 is a schematic diagram of a high-speed adaptive closed-loop power control method for variable multi-data speed wireless communication according to the present invention. [Explanation of symbols] 10 Open-loop power control transmitter 50 Closed-loop power control transmitter 30,70 Receiving station 16,56 receiver 38,78 transmitter 14,17,31,39,54,57, 71,79 Antenna system 15,55 Transmission power scale factor calculator 18 Reference signal power measuring device 19 Path loss calculator 27,67 Step-up converter 47,87 Step-down converter 32 Interference power measuring device 34,73 Data quality measuring device 36, 74 SIR target value calculator 40 user data line 74 Nominal SIR target value calculator 76,88 synthesizer