ES2425481T3

Motor control apparatus

Abstract

An engine control apparatus comprising: an inverter circuit (2) that receives a fluctuating voltage, converts said voltage to a desired voltage and sends said desired voltage to a brushless motor (3), said motor control apparatus being configured to apply the voltage to said brushless motor in a maintained phase state, and a control section (4) that receives an input voltage (Vpn) to said inverter circuit, a motor current (lu, lv, lw) flowing to said brushless motor and a motor current order value (ld *, lq *) indicating the value of a current required to flow to said inverter circuit, and generates a voltage order value of application to the motor (Vd, Vq) for said inverter circuit, in which, said control section (4) includes: - a conversion section dq (6) that generates a current detection value of the motor of axis d and of axis q (ld, lq) from said motor current (lu, lv, lw), - an integration controller of proportion (PI) (7, 8) of axis d and axis q receiving an error between said motor current detection value (ld, lq) and said motor current order value (ld *, lq *), and generates a value of 20 order of application voltage to the motor of axis d and axis q (Vd, Vq) based on said error, and - a PWM generation section (9) that receives said order voltage value applied to the motor (Vd, Vq) and said input voltage (Vpn), and sends a PWM signal corresponding to said voltage order value of application to the motor (Vd, Vq) to said inverter circuit (2), and wherein said motor control apparatus is configured to apply the voltage to said brushless motor in a maintained phase state, and characterized in that said section of PWM generation (9) comprises: - a reverse dq conversion section (10) that generates three-phase sinusoidal voltage order values (Vu, Vv, Vw) based on said motor application voltage value (Vd, Vq), - a modulation section line to line (11) that detects a minimum value from said three-phase sinusoidal voltage order values (Vu, Vv and Vw) and sends the results obtained by subtracting said minimum value from said three-phase sinusoidal voltage order values, and - a correction section Vpn (12) that generates a PWM signal from the outputs (Vu ', Vv', Vw ') of said line-to-line modulation section (11) and said input voltage (Vpn), and which detects the maximum value of said outputs (Vu ', Vv', Vw ') of said line-to-line modulation section (11), compares between said maximum value (Vmax) and said input voltage (Vpn) to said circuit inverter, and as a result of the comparison, when said input voltage is greater than said maximum value, generates a PWM signal using a rate of each output of said line-to-line modulation section (11) and said input voltage (Vpn), or when said input voltage is less than or equal to said maximum value, generates a PWM signal using a rate of each output of said line-to-line modulation section (11) and said maximum value (Vmax).

ES2425481T3, drawing sheet 1 — Sheet 1 of 41

Term

Term ended

Projected expiry passed 10 December 2023, 2.8 years ago.

19 claims: 1 independent, 18 dependent

1
ES 2 425 481 T3 REIVINDICACIONES 1. Un aparato de control de motor que comprende:un circuito inversor (2) que recibe un voltaje fluctuante, convierte dicho voltaje en un voltaje deseado y envía dicho voltaje deseado a un motor sin escobillas (3), estando dicho aparato de control de motor configurado para aplicar el voltaje a dicho motor sin escobillas en un estado de fase mantenida, y una sección de control (4) que recibe un voltaje de entrada (Vpn) a dicho circuito inversor, una corriente del motor (lu, lv, lw) que fluye a dicho motor sin escobillas y un valor de orden de corriente del motor (ld*, lq*) que indica el valor de una corriente requerido para fluir a dicho circuito inversor, y genera un valor de orden de voltaje de aplicación al motor (Vd, Vq) para dicho circuito inversor, en el que, dicha sección de control (4) incluye: - una sección de conversión dq (6) que genera un valor de detección de corriente del motor de eje d y de eje q (ld, lq) a partir de dicha corriente del motor (lu, lv, lw), - un controlador de integración de proporción (PI) (7, 8) de eje d y eje q que recibe un error entre dicho valor de detección de corriente del motor (ld, lq) y dicho valor de orden de corriente del motor (ld*, lq*), y genera un valor de orden de voltaje de aplicación al motor de eje d y eje q (Vd, Vq) en base a dicho error, y - una sección de generación PWM (9) que recibe dicho valor de orden de voltaje de aplicación al motor (Vd, Vq) y dicho voltaje de entrada (Vpn), y envía una señal PWM correspondiente a dicho valor de orden de voltaje de aplicación al motor (Vd, Vq) a dicho circuito inversor (2), y en el que dicho aparato de control de motor está configurado para aplicar el voltaje a dicho motor sin escobillas en un estado de fase mantenida, y caracterizado porque dicha sección de generación PWM (9) comprende: - una sección de conversión dq inversa (10) que genera valores de orden de voltaje sinusoidal trifásico (Vu, Vv, Vw) en base a dicho valor de orden de voltaje de aplicación al motor (Vd, Vq), - una sección de modulación línea a línea (11) que detecta un valor mínimo a partir de dichos valores de orden de voltaje sinusoidal trifásico (Vu, Vv y Vw) y envía los resultados obtenidos restando dicho valor mínimo de dichos valores de orden de voltaje sinusoidal trifásico, y - una sección de corrección Vpn (12) que genera una señal PWM a partir de las salidas (Vu',Vv',Vw') de dicha sección de modulación línea a línea (11) y dicho voltaje de entrada (Vpn), y que detecta el valor máximo de dichas salidas (Vu',Vv',Vw') de dicha sección de modulación línea a línea (11), compara entre dicho valor máximo (Vmax) y dicho voltaje de entrada (Vpn) a dicho circuito inversor, y como resultado de la comparación, cuando dicho voltaje de entrada es mayor que dicho valor máximo, genera una señal PWM usando una tasa de cada salida de dicha sección de modulación línea a línea (11) y dicho voltaje de entrada (Vpn), o cuando dicho voltaje de entrada es menor que o igual a dicho valor máximo, genera una señal PWM usando una tasa de cada salida de dicha sección de modulación línea a línea(11) y dicho valor máximo (Vmax).
2
El aparato de control de motor según la reivindicación 1, en el que dicha sección de control estima la fase de rotación de dicho motor sin escobillas en base a dicho valor de detección de corriente del motor (ld, lq) y dicho valor de orden de voltaje de aplicación al motor (Vd, Vq).
3
El aparato de control de motor según la reivindicación 1, en el que dicho controlador de integración de proporción (7, 8) genera dicho valor de orden de voltaje de aplicación al motor (Vd, Vq) realizando una operación de integración de proporción usando el error entre dicho valor de orden de corriente del motor (ld*, lq*) y dicho valor de detección de corriente del motor (ld, lq), y envía dicho valor de orden de voltaje de aplicación al motor (Vd, Vq) a dicha sección de generación PWM (9b), y dicha sección de generación PWM (9b) está configurada de modo que dicho controlador de integración de proporción detiene el funcionamiento integral cuando el voltaje de entrada a aplicar a dicho circuito inversor es menor que o igual a dicho valor máximo.
4
El aparato de control de motor según la reivindicación 1, en el que 34 ES 2 425 481 T3 la sección de conversión dq (6) calcula un valor de detección de corriente de eje d y un valor de detección de corriente de eje q usando la corriente del motor (lu, lv, lw) que fluye hasta dicho motor sin escobillas y la fase de rotación () de un rotor de dicho motor sin escobillas, y en el que el controlador de integración de proporción de eje d (7) recibe el error entre un valor de orden de corriente de eje d (ld*) y dicho valor de detección de corriente de eje d (ld) y envía el valor estándar de una orden de tensión de aplicación a un motor de eje d, y en el que el controlador de integración de proporción de eje q (8) que recibe el error entre un valor de orden de corriente de eje q (lq*) y dicho valor de detección de corriente de eje q (lq) y envía el valor estándar de una orden de tensión de aplicación a un motor de eje q, y en el que la sección de control (4) comprende además:- un multiplicador de eje d (18) que envía el resultado de la multiplicación de dicho valor de detección de corriente de eje q (lq), dichos componentes de eje q (Lq) de una inductancia de dicho motor sin escobillas, y la velocidad de rotación (ω) de dicho motor sin escobillas, - un primer multiplicador de eje q (19) que envía el resultado de la multiplicación de dicho valor de detección de corriente de eje d (ld), componentes de eje d (Ld) de una inductancia de dicho motor sin escobillas, y la velocidad de rotación (ω) de dicho motor sin escobillas, - un segundo multiplicador de eje q (20) que envía el resultado de la multiplicación de la constante de voltaje inducido (Ke) de dicho motor sin escobillas y dicha velocidad de rotación (ω), - un sumador de eje d que añade la salida de dicho multiplicador de eje d (18) a dicho valor estándar de dicha orden de tensión de aplicación a un motor de eje d y envía un valor de orden de voltaje de aplicación al motor de eje d (Vd), - un sumador de eje q que añade las salidas de dicho primer multiplicador de eje q (19) y dicho segundo multiplicador de eje q (20) a dicho valor estándar de la orden de tensión de aplicación a un motor de eje q y envía un valor de orden de voltaje de aplicación al motor de eje q (Vq), - una sección de generación PWM (9) que recibe dicho valor de orden de voltaje de aplicación al motor de eje d (Vd) y dicho valor de orden de voltaje de aplicación al motor de eje q (Vq) y envía una señal de accionamiento de dicho circuito inversor.
5
El aparato de control de motor según la reivindicación 1, en el que dicha sección de control detecta el voltaje de entrada a aplicar a dicho circuito inversor, estima un voltaje a introducir en dicho circuito inversor en el siguiente ciclo de control en base al valor de detección y controla dicho circuito inversor.
6
El aparato de control de motor según la reivindicación 1, que incorpora un condensador en el lado de entrada de dicho circuito inversor, en el que se establece que C 2 x 10' 6 7 8 x P suponiendo que la capacitancia de dicho condensador es C [F] y que la salida máxima de dicho motor es P [W].
7
El aparato de control de motor según la reivindicación 1, que incorpora un inductor en el lado de entrada de dicho circuito inversor, en el que se establece que L 9 x 10' 9 / C suponiendo que la inductancia de dicho inductor es L [H] y que la capacitancia de dicho condensador es C [F].
8
El aparato de control de motor según la reivindicación 1, que comprende además:un circuito elevador que tiene un inductor, diodos, dispositivos de conmutación y un condensador, y una sección de control del circuito elevador para controlar dicho circuito elevador, en el que ES 2 425 481 T3 dicha sección de control del circuito elevador determina el valor de orden para dicho dispositivo de conmutación en base a una señal procedente de dicha sección de control.
9
El aparato de control de motor según la reivindicación 8, en el que dicha sección de control del circuito elevador, que está configurada para recibir la fase de voltaje detectada y corriente CA de una fuente de alimentación CA, comprende:- una sección de orden de corriente CA que envía un valor de orden de corriente CA en base a dicha fase detectada y una señal de control procedente de dicha sección de control, y - una sección de generación de orden PWM que genera valores de orden PWM para accionar dichos dispositivos de conmutación en base a dicho valor de orden de corriente CA y dicha corriente CA detectada de dicha fuente de alimentación CA y envía dichos valores de orden PWM.
10
El aparato de control de motor según la reivindicación 1, que comprende además:- un circuito elevador que tiene un inductor en el que se introduce un voltaje fluctuante, - a partir de diodos que forman un circuito rectificador, dispositivos de conmutación conectados a dicho circuito rectificador y que realizan una operación de encendido/apagado, y un condensador que envía un voltaje elevado, y - una sección de control del circuito elevador para controlar dicho circuito elevador.
11
El aparato de control de motor según la reivindicación 7, en el que un inductor está conectado al lado de entrada del circuito inversor, y se establece L P x 10' 6 suponiendo que la inductancia de dicho inductor es L [H] y que la potencia de salida máxima de dicho es P [W].
12
Un compresor que incorpora dicho aparato de control de motor según una cualquiera de las reivindicaciones 1 a 11.
13
Un climatizador que incorpora dicho aparato de control de motor según una cualquiera de las reivindicaciones 1 a 11.
14
Un frigorífico que incorpora dicho aparato de control de motor según una cualquiera de las reivindicaciones 1 a 11.
15
Una lavadora eléctrica que incorpora dicho aparato de control de motor según una cualquiera de las reivindicaciones 1 a 11.
16
Una secadora eléctrica que incorpora dicho aparato de control de motor según una cualquiera de las reivindicaciones 1 a 11.
17
Un soplador que incorpora dicho aparato de control de motor según una cualquiera de las reivindicaciones 1 a 11.
18
Una aspiradora eléctrica que incorpora dicho aparato de control de motor según una cualquiera de las reivindicaciones 1 a 11.
19
Un calentador de agua de bomba de calor que incorpora dicho aparato de control de motor según una cualquiera de las reivindicaciones 1 a 11.

Independent claims19

328 paragraphs in 19 sections, as filed

ES 2 425 481 T3

DESCRIPTION

Motor control device

BACKGROUND OF THE INVENTION

The present invention relates to a motor control apparatus for controlling brushless motors incorporated in air conditioners, refrigerators, washing machines, blowers, etc., using an inverter circuit.

Fig. 33 is a block diagram showing the configuration of a conventional motor control apparatus for driving a brushless motor. In the following descriptions, the conventional motor control apparatus shown in Fig. 33 is referred to as a conventional first technology. In Figure 33, the number 101 designates an AC power source, the number 102 designates an inductor, the number 103 designates a rectifier diode, the number 104 designates a filter capacitor, the number 106 designates an inverter circuit, the number 107 designates a brushless motor, and the number 108 designates a position sensor. In the case where the AC voltage supplied from the AC power source 101 is converted to a DC voltage using the rectifier diode 103 and the filter capacitor 104 so that a DC power is input to the inverter circuit 106, the current supplied from the AC power source 101 flows only when the voltage of the filter capacitor 104 is lower than the supplied AC voltage. Therefore, the current supplied from the AC power supply 101 has harmonic components. Therefore, in the first conventional technology, the inductor 102 is provided between the AC power supply 101 and the rectifier diode 103 to reduce harmonic components and improve the power factor. As described above, in addition to rectifier diode 103, inductor 102 and filter capacitor 104 are used in first conventional technology rectifier circuit 105. Also, in the case where the brushless motor 107 is driven by the inverter, the information of the rotation angle of the rotor is needed. To this end, in the first conventional technology, the angle of rotation was detected using the position sensor 108. As an example of this first conventional technology, an engine control apparatus disclosed in Japanese Patent Application Laid-Open No. Hei 9-74790 has been proposed.

The inductor 102 and the filter capacitor 104 of the rectifier circuit 105 for use in the first conventional technology are large components having a large inductance and a large capacitance, respectively, in many cases. As a result, the conventional motor control apparatus is often apt to be large in size and high in price. In the field of motor control apparatus, a rectifier circuit that incorporates compact components such as an inductor that has a small inductance and a capacitor that has a small capacitance or a rectifier circuit that does not incorporate these components has been demanded, from the point in view of making the apparatus smaller in size and lower in cost.

In this situation, said motor control apparatus incorporating neither inductor nor filter capacitor as shown in Fig. 34, has been proposed as a second conventional technology. As an example of this second conventional technology, an engine control apparatus described in Japanese Patent Application Laid-Open No. Hei 10-150795 has been proposed. Since no filter capacitor is used in the second conventional technology, the input voltage supplied to the inverter circuit 106 is not a DC voltage, but a pulsed voltage. If this type of pulsed voltage is input to inverter circuit 106, when the input voltage supplied to inverter circuit 106 is low, in some cases inverter circuit 106 cannot generate a desired voltage to apply to brushless motor 107. In the case where the desired voltage cannot be obtained by the second conventional technology, the phase of the voltage to be applied to the brushless motor 107 is advanced. By advancing the phase of the voltage to be applied to the brushless motor 107, the so-called weak field state can be obtained, whereby the required voltage to be applied to the brushless motor 107 can be made lower. Therefore, with the second conventional technology, the brushless motor 107 can be continuously driven even when the input voltage supplied to the inverter circuit 106 is low. However, in the second conventional technology, in the case where the input voltage supplied to the inverter circuit 106 becomes a predetermined value or lower, the switching operation of the inverter circuit 106 stops. This is because the drive of the motor in the weak field state is limited. As described above, the second conventional technology is configured so that no voltage is applied to the brushless motor 107 in the case where the input voltage supplied to the inverter circuit 106 becomes the predetermined value or lower.

In addition, a motor control apparatus that does not use a position sensor is demanded from the point of view of wireless manufacturing and reducing the cost. In this situation, a method of estimating the rotor position of a brushless motor by sensing the motor current is proposed as a third conventional technology. In

ES 2 425 481 T3 the third conventional technology, the rotor position of the motor is estimated using a calculation equation to estimate the derived phase based on a voltage equation of a motor current, a voltage applied to the brushless motor at the timing at which motor current flows, and motor constants, such as resistance, inductance, etc., of the brushless motor. An example of this third conventional technology is described in a thesis “Control of a sensorless salient-pole brushless DC motor on the basis of estimation of speed electromotive force (Back EMF Estimation-Based Sensorless Salient-Pole brushless DC Motor Drives)” by Takeshita , Ichikawa, Lee and Matsui, Thesis Journal, Vol. 117-D, no 1, pages 98 to 104, published by the Institute of Electrical Engineers of Japan in 1997 (T.IEE Japan, Vol. 117-D, no 1, 97).

As described above, in the first conventional technology, the rotor position of a brushless motor is detected using a position sensor, and an inductor and filter capacitor are used to convert the input voltage supplied to a circuit inverter at a DC voltage. Therefore, since the inductor and the filter capacitor are large components having a large inductance and a large capacitance, respectively, it is difficult to make the motor control apparatus incorporating these components smaller.

Furthermore, the second conventional technology is a motor control apparatus, in which the rotor position of a brushless motor is detected using a position sensor, without using large components such as an inductor and a filter capacitor. This technology is thus effective from the point of view of making the apparatus smaller in size and lower in cost. However, since the input voltage supplied to the inverter circuit is pulsed in the second conventional technology, this causes the problem of stopping the application of voltage to the brushless motor when the input voltage is a predetermined value or lower.

A problem described below occurs in the case where an attempt is made to build a lower cost and smaller size sensorless motor control apparatus, combining the second conventional technology configured to use neither inductor nor filter capacitor with the third conventional technology configured to perform sensorless motor drive. In the motor control apparatus having this kind of configuration, the rotor position cannot be estimated in the periods during which the voltage application to the brushless motor is stopped. Therefore, sensorless drive of the brushless motor was impossible. In other words, in the case where the input voltage supplied to the inverter circuit is pulsed, a sensorless motor control apparatus cannot be constructed by simply combining the second conventional technology and the third conventional technology.

P. Foussier in his thesis entitled "Contribution a l'intégration des systémes de commande des machines électriques a courant altematif ', thesis of the National Institute of Applied Sciences of Lyon, January 1, 1998, accessible at http: // docinsa-insa -tyon.fr/these/1998/foussier/these.pdf, discloses a motor control apparatus comprising an inverter circuit that receives a fluctuating voltage, converts said voltage into a desired voltage and sends said desired voltage to a brushless motor , and a control section receiving an input voltage (Vpn) to said inverter circuit, a motor current (lu, lv, lw) flowing to said brushless motor, and a motor current command value (ld *, lq *) that indicates the value of a current required to flow to said inverter circuit, and generates a value of order of voltage applied to the motor (Vd, Vq) for said inverter circuit, in which, said control section includes a dq conversion section that generates a d-axis and q-axis motor current detection value (ld, lq) from said motor current (lu, lv, lw), a ratio integration controller (PI) of d axis and q axis that receives an error between said motor current detection value (ld, lq) and said motor current command value (Id *, lq *), and generates an order value of application voltage to the d-axis and q-axis motor (vd, vq) based on said error, and a PWM generation section that receives said command value of voltage applied to the motor (vd, vq) and said input voltage (Vpn), and sends a PWM signal corresponding to said value of motor application voltage command (Vd, Vq) to said inverter circuit, and said motor control apparatus is configured to apply the voltage to said brushless motor in a phase held state.

GENERAL DESCRIPTION OF THE INVENTION

An object of the present invention is to provide a compact motor control apparatus having a compact rectifier circuit and capable of being configured with and without a position sensor. Furthermore, another object of the present invention is to provide a motor control apparatus capable of carrying out sensorless actuation without stopping the application of voltage to a brushless motor even though the input voltage of the inverter circuit pulses significantly.

In order to achieve said objects, a motor control apparatus according to the present invention is configured to comprise an inverter circuit that receives a fluctuating voltage, converts said voltage to a desired voltage, and

ES 2 425 481 T3 sends said desired voltage to a brushless motor, and a control section that receives the input voltage to said inverter circuit, a motor current flowing to said brushless motor and a current command value of the motor that indicates the value of a current required to flow to said inverter circuit, to control said inverter circuit by maintaining the phase of the voltage applied to said brushless motor when the value of the input voltage to said inverter circuit is smaller than the value of a voltage required to apply it to said brushless motor. The motor control apparatus according to the present invention, configured as described above, can continuously apply a voltage to the brushless motor without stopping the voltage application, even when the DC side voltage of the inverter circuit is low.

In the motor control apparatus according to the present invention, the motor control section may be configured to estimate the rotation phase of the brushless motor based on the motor current. With this configuration, even in the case where sensorless drive is carried out where the phase information of the brushless motor is not obtained from a position sensor, the motor control apparatus can continuously carry out the voltage application without stopping voltage application to the motor. Therefore, the phase of the motor can be estimated, and the motor can be driven without using a position sensor.

In the motor control apparatus according to the present invention, the control section thereof may be configured to stop integral control when the voltage value across said inverter circuit is less than the voltage command value to be applied to said brushless motor. With this configuration, unnecessary errors for a control apparatus for current control are not overlapped, whereby no unnecessary motor current flows, and the accuracy of the sensorless estimation can be improved. Thus, it is possible to provide a motor control apparatus capable of stably carrying out excellent control.

In the motor control apparatus according to the present invention, the motor control section may be configured to calculate said voltage command value using a calculation equation having a non-interacting term. In the motor control apparatus according to the present invention, the feedback control has a non-interaction term as described above. Therefore, the independence of the current control system is improved, the precision of the sensorless estimation is further improved, and a more stable operation is achieved.

In the motor control apparatus according to the present invention, the control section thereof may be configured to detect the voltage of said inverter circuit, estimate a voltage to be applied to said inverter circuit in the next control cycle, and control said inverter circuit. . In the case where the input voltage of the inverter circuit pulses significantly, an error occurs between the detection result and the actual voltage, particularly when the control cycle of the inverter circuit is long. However, using the detected voltage of the inverter circuit, the control section estimates a voltage to be applied to the inverter circuit in the next control cycle and performs control, whereby the control section can accurately estimate the voltage. inverter circuit input. As a result, a more accurate voltage can be applied to the brushless motor. Therefore, the present invention can provide a more excellent motor control apparatus.

The motor control apparatus according to the present invention may be configured to incorporate a capacitor having a small capacitance on the input side of said inverter circuit. In the motor control apparatus according to the present invention, configured as described above, a regenerative current from the motor flows to a capacitor. Therefore, it is possible to avoid abnormal rise of the input side voltage of the inverter main circuit due to regenerative current. Therefore, the apparatus has a function of protecting the circuit against overvoltage, thereby being highly safe.

The motor control apparatus according to the present invention may be configured to incorporate an inductor having a small inductance on the input side of said inverter circuit. The motor control apparatus according to the present invention configured as described above outputs a current having a smooth waveform, thus being capable of eliminating harmonic components. Therefore, the apparatus has a higher power utilization rate.

The motor control apparatus according to the present invention may be configured to further comprise a boost circuit having an inductor, diodes, switching devices and a capacitor, and a boost circuit control section for controlling said boost circuit, wherein said control section of the lift circuit is configured to determine the working value of said

ES 2 425 481 T3 switching device based on a signal from said control section. In the motor control apparatus according to the present invention configured as described above, the boost circuit can raise the input side voltage of the inverter circuit. Therefore, the maximum rotational speed of the brushless motor can be increased, and the brushless motor can operate in a wider range of rotational speeds.

The motor control apparatus according to the present invention, wherein the boost circuit control section, which is configured to receive the sensed voltage phase and AC current from an AC power source, may be configured to comprise a section of AC current command that sends an AC current command value based on said detected phase and a control signal from said control section, and a PWM command generation section that generates PWM command values to actuate said switching devices based on said AC current command value and said detected AC current from said AC power source and outputs said PWM command values. The motor control apparatus according to the present invention configured as described above does not adversely affect the power supply system.

The motor control apparatus according to the present invention may be configured to further comprise a boost circuit having an inductor into which a fluctuating voltage is input, a plurality of diodes forming a rectifier circuit, switching devices connected to said rectifier circuit and that perform the on / off operation, and a capacitor that sends a high voltage, and a boost circuit control section for controlling said boost circuit. The motor control apparatus according to the present invention configured as described above can significantly extend the operating range of a motor, although the configuration of the apparatus is simple.

In the engine control apparatus according to the present invention, it is preferred to set

C <2 x 10 '7 x P assuming that the capacitance of said capacitor is C [F] and that the maximum output of said motor is P [W].

In the motor control apparatus according to the present invention, which incorporates an inductor having a small inductance on the input side of said inverter circuit, it is preferred to set

L <9 x 10 '9 / C assuming that the inductance of said inductor is L [H] and that the capacitance of said capacitor is C [F].

In the engine control apparatus according to the present invention, it is preferred to set

L 6 assuming that the inductance of said inductor is L [H] and that the maximum power output of said motor is P [W].

The motor control apparatus according to the present invention configured as described above can be used for compressors, air conditioners, refrigerators, electric washing machines, electric dryers, blowers, electric vacuum cleaners and heat pump water heaters. The motor control apparatus can continuously apply a desired voltage to a drive source without stopping the voltage application even when the DC side voltage of the inverter circuit is low. Therefore, the motor control apparatus can drive each of said apparatus with high efficiency.

Although the novel features of the invention are set forth particularly in the appended claims, the invention, both in terms of organization and content, will be better understood and appreciated, together with its other objects and features, from the following detailed description taken in conjunction with the drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

ES 2 425 481 T3

Fig. 1 is a block diagram showing a configuration of an example motor control apparatus according to Embodiment 1 of the present invention;

Fig. 2 is a block diagram showing a configuration of a PWM generation section according to Embodiment 1 of the present invention;

Fig. 3 is a flow chart showing an operation of a Vpn correction section according to Embodiment 1 of the present invention;

Fig. 4A is a graph showing a result of a motor current measured in an experiment, etc., under the control of the conventional motor control apparatus;

Fig. 4B is a graph showing a result of a motor current measured in an experiment, etc., under the control of the motor control apparatus according to Embodiment 1;

Fig. 5 is a block diagram of a PWM generation section of a motor control apparatus according to Embodiment 2 of the present invention;

Fig. 6 is a flow chart showing an operation of a ratio correction section according to Embodiment 2 of the present invention;

Fig. 7 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 3 of the present invention;

Fig. 8A is a graph showing a result of a motor current measured in an experiment, etc., by the conventional motor control apparatus;

Fig. 8B is a graph showing a result of a motor current measured in an experiment, etc., by the motor control apparatus according to Embodiment 3;

Fig. 9 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 4 of the present invention;

Fig. 10 is a graph showing a result of a motor current measured in an experiment, etc., by the motor control apparatus according to Embodiment 4 of the present invention;

Fig. 11 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 5 of the present invention;

Fig. 12 is a graph showing a result of a motor current measured in an experiment, etc., by the motor control apparatus according to Embodiment 5 of the present invention;

Fig. 13 is a graph showing a result of an experiment indicating the limit torque of a brushless motor by a motor control apparatus according to the present invention and the conventional motor control apparatus;

Fig. 14 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 7 of the present invention;

Fig. 15 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 8 of the present invention;

Fig. 16A is a block diagram showing a configuration of a motor control apparatus according to Embodiment 9 of the present invention;

Fig. 16B is a circuit diagram showing another configuration of a boost circuit of the motor control apparatus according to Embodiment 9 of the present invention.

Figure 17 is a waveform diagram showing an input waveform to a boost circuit of the

ES 2 425 481 T3 engine control apparatus according to Embodiment 9 of the present invention;

Fig. 18 is a waveform diagram showing an operation of the motor control apparatus according to Embodiment 9 of the present invention;

Fig. 19 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 10 of the present invention;

Fig. 20 is a block diagram showing a configuration of a control section of the boost circuit of the motor control apparatus according to Embodiment 10 of the present invention;

Fig. 21 is a waveform diagram showing an operation of the motor control apparatus according to Embodiment 10 of the present invention;

Fig. 22 is a block diagram showing another configuration of a boost circuit control section of the motor control apparatus according to Embodiment 10 of the present invention;

Fig. 23A is a block diagram showing a configuration of a motor control apparatus according to Embodiment 11 of the present invention;

Fig. 23B is a circuit diagram showing another configuration of a dual voltage rectifier boost circuit of the motor control apparatus according to Embodiment 11 of the present invention;

Fig. 24 is a waveform diagram showing an operation of the motor control apparatus according to Embodiment 11 of the present invention;

Fig. 25 is a block diagram showing the configuration of the compressor according to Embodiment 12 of the present invention;

Fig. 26 is a block diagram showing the configuration of an air conditioner according to Embodiment 13 of the present invention;

Fig. 27 is a block diagram showing the configuration of a refrigerator according to Embodiment 14 of the present invention;

Fig. 28 is a block diagram showing the configuration of an electric washing machine according to the embodiment of the present invention;

Figure 29 is a block diagram showing the configuration of an electric dryer according to the embodiment of the present invention;

Fig. 30 is a block diagram showing the configuration of a blower according to Embodiment 17 of the present invention;

Fig. 31 is a block diagram showing the configuration of an electric vacuum cleaner according to Embodiment 18 of the present invention;

Fig. 32 is a block diagram showing the configuration of a heat pump water heater in accordance with Embodiment 19 of the present invention;

Fig. 33 is the block diagram showing the configuration of the motor control apparatus as the first conventional technology;

Fig. 34 is the block diagram showing the configuration of the motor control apparatus as a second conventional technology;

It will be recognized that some or all of the figures are schematic representations for purposes of illustration and do not necessarily represent the actual relative sizes or positions of the items shown.

ES 2 425 481 T3

DETAILED DESCRIPTION OF THE INVENTION

Engine control apparatuses according to preferred embodiments of the present invention will now be described with reference to the accompanying Figures 1 to 32.

«Realization 1 >>

Fig. 1 is a block diagram showing the configuration of a motor control apparatus according to Embodiment 1 of the present invention. In Figure 1, the AC power output from a single-phase AC power supply 5 is rectified to pulsed DC power by a rectifier circuit 1 and applied to an inverter circuit 2. The inverter circuit 2 converts the rectified power Cc into an AC power and applies a desired voltage to a brushless motor 3. A control section 4 detects the current flowing to the brushless motor 3 and drives and controls the inverter circuit 2. The control section 4 includes a dq conversion section 6, a d-axis PI controller 7, an axis PI controller q 8, a PWM generation section 9, subtraction means, etc.

Next, the operation of the control section 4 according to Embodiment 1 will be described.

The dq 6 conversion section calculates a d-axis current detection value Id and a q-axis current detection value Iq according to the following equation (1) using the current detection values Iu, Iv and Iw flowing at the three-phase windings of the brushless motor 3. In the case where the brushless motor 3 has a position sensor, the position signal from the position sensor is used as a rotation phase θ for this calculation. In the case where the brushless motor 3 has no position sensor, an estimated phase obtained as a result of estimating the rotor position is used as the rotation phase θ.

The error between an axis current command value d Id * calculated based on a rotation command, a torque command, etc., coming from the outside and an axis current detection value d Id output from the section of dq 6 conversion is input to the d-axis PI controller 7. The error is PI controlled by the d-axis PI controller 7 and a d-axis voltage command value is generated Vd. The error between an axis current command value q Iq * calculated on the basis of a rotation command, a torque command, etc., coming from the outside and an axis current detection value q Iq output from the section of Conversion dq 6 is input to the q axis PI controller 8, just as in the case of the d axis PI controller 7. The error is PI controlled by the q axis PI controller 8 and a voltage command value of q axis Vq.

The PWM generation section 9 generates a PWM signal to drive the inverter circuit 2 from the axis voltage command value d Vd, the axis voltage command value q Vq, and an input voltage detection value Vpn obtained. detecting the voltage introduced in the inverter circuit 2, and sends the PWM signal.

FIG. 2 is a block diagram showing the configuration and operation of the PWM generation section 9. As shown in FIG. 2, the PWM generation section 9 has a reverse dq conversion section 10, a line-to-line modulation 11 and a Vpn correction section 12.

The reverse dq conversion section 10 calculates sinusoidal three-phase voltage command values Vu, Vv, and Vw from the d-axis voltage command value Vd and the q-axis voltage command value Vq according to the following equation (2) . In the case where the brushless motor 3 has a position sensor, its position signal is used as a rotation phase θ for this calculation. In the case where the brushless motor 3 has no position sensor, an estimated phase obtained as a result of estimating the rotor position is used as the rotation phase θ.

ES 2 425 481 T3

The line-to-line modulation section 11 detects the minimum value of the entered sinusoidal three-phase voltage command values Vu, Vv and Vw and outputs the results obtained by subtracting the minimum detected value from the sinusoidal three-phase voltage command values as Vu ', Vv 'and Vw'. Therefore, at least the single-phase sinusoidal order value is zero, and the remaining biphasic sinusoidal order values are positive values.

The Vpn correction section 12 receives the outputs Vu ', Vv' and Vw 'from the line-to-line modulation section 11 and also receives the input voltage detection value Vpn, and generates the PWM output work values Du, Dv and Dw. The PWM output work values Du, Dv and Dw are obtained according to equation (3) or (4) described below.

Fig. 3 is a flow chart showing a calculation method performed by the correction section Vpn 12.

The maximum value of the three-phase output values Vu ', Vv' and Vw 'supplied from the line-to-line modulation section 11 is detected, and the value is set as the maximum application voltage value Vmax (in step 31) . Next, the maximum application voltage value Vmax is compared with the input voltage detection value Vpn in magnitude (in step 32). In the case where the input voltage detection value Vpn is greater than the maximum application voltage value Vmax in step 32, an ordinary calculation is carried out and the desired application voltage command values are applied to the brushless motor 3. Therefore, the PWM output working values of phases U, V and W are determined according to the following equation (3) (in step 33).

On the other hand, in the case where the input voltage detection value Vpn is less than the maximum application voltage value Vmax, the desired application voltage order values cannot be applied to the brushless motor 3. The maximum voltage that can be generated at the moment is applied, while the phases of the applied voltages are not changed. For this purpose, the PWM output work values of phases U, V and W are determined according to the following equation (4) (in step 34).

By the calculation according to equation (4) mentioned above, the relations of the phases U, V and W become the same as the relations obtained before the calculation according to equation (4), whereby voltages are applied to the brushless motor 3 while maintaining the phases of the applied voltages.

ES 2 425 481 T3

Fig. 4A is a graph showing a result of an experiment regarding motor current under the control of a conventional motor control apparatus. Fig. 4B is a graph showing a result of an experiment regarding motor current according to Embodiment 1 in the case where equation (4) is used for correction section Vpn 12. In Figures 4A and 4B, the input voltage detection value Vpn, the motor current, the motor current command value and the motor application voltage phase are shown in this sequence from above. In the experiment from which the result shown in Fig. 4A is obtained, a motor control apparatus having the configuration of the above-mentioned first conventional technology was used as a conventional motor control apparatus.

In the conventional motor control apparatus, when the input voltage detection value Vpn serving as the input voltage to the inverter circuit is small, a current significantly deviated from a desired current flows in the brushless motor. This type of current reduces the efficiency of the motor and increases noise. Also, if a large current is flowing, the motor magnets become demagnetized, which can cause problems. Also, the maximum value of the current becomes higher when the load applied to the brushless motor is higher. Therefore, it is necessary to increase the nominal current of the inverter circuit when the brushless motor is driven at a predetermined load. Therefore, it was necessary to use an inverter circuit including expensive components. Furthermore, in the conventional motor control apparatus, when the input voltage detection value Vpn obtained by detecting the voltage input to the inverter circuit 2 is small, the phase of the voltage applied to the motor is disturbed, and the motor current fluctuates. significantly as shown in Figure 4A.

On the other hand, in the case that the motor control apparatus according to Embodiment 1 of the present invention is used, the phase of the voltage applied to the motor is maintained. Therefore, the appropriate phase is applied to the brushless motor 3 even when the input voltage detection value Vpn is small. Furthermore, since the disturbance of the motor current over time is small, the efficiency of the motor is increased and the noise is reduced.

According to the results of the above-mentioned experiments, since the motor current increases more than necessary in the conventional motor control apparatus, this results in the inverter circuit being made larger and more expensive. In the case of the motor control apparatus according to Embodiment 1 of the present invention, the disturbance of the motor current is less, whereby the motor control apparatus can be configured using an inverter circuit having a small capacity of current and the like.

With the motor control apparatus according to Embodiment 1 of the present invention, the rectifier circuit can be made smaller, and the apparatus can be configured with and without a position sensor. In addition, even if the input voltage of the inverter circuit pulses significantly, the motor control apparatus according to Embodiment 1 can carry out the sensorless drive without stopping the application of voltage to the brushless motor.

«Realization 2 >>

Next, a motor control apparatus according to Embodiment 2 of the present invention will be described. Fig. 5 is a block diagram showing the operation of the PWM generation section 90 of the motor control apparatus according to Embodiment 2. The configuration of the motor control apparatus according to Embodiment 2 is substantially identical to the configuration according to Embodiment 1, except for the PWM generation section 9 of the motor control apparatus according to Embodiment 1. Therefore, the PWM generation 90 will be described below.

As shown in Fig. 5, the PWM generation section 90 according to Embodiment 2 has a ratio correction section 13, an inverse dq conversion section 10, a line-to-line modulation section 11, and a power generation section. relationship 14. In Fig. 5, the operations of the reverse dq conversion section 10 and the line-to-line modulation section 11 are similar to those of the above-mentioned embodiment 1.

A calculation method carried out by the ratio correction section 13 is shown in the flow chart of Fig. 6. V1 is calculated from the axis voltage command value d Vd and the voltage command value of q axis Vq according to the following calculation equation (5) (in step 35). V1 is compared in magnitude with the input voltage detection value Vpn (in step 36).

ES 2 425 481 T3 + Yg2) <s>

In the case where the input voltage detection value Vpn is less in step 36, the axis voltage command value d Vd and the axis voltage command value q Vq are changed to Vd 'and Vq ', respectively, according to the following equation (6) and comprising are sent (in step 37). In the case where the input voltage detection value Vpn is larger, the axis voltage command value d Vd and the axis voltage command value q Vq are directly output.

The ratio generation section 14 carries out the calculation according to the above-mentioned equation (3) and generates PWM output work values Du, Dv and Dw.

(¢)

When the axis voltage command value d Vd and the axis voltage command value q Vq are changed to Vd 'and Vq', respectively, by the ratio correction section 13 according to equation (6) as shown described above, the application voltage phase is maintained, even if a desired application voltage is not applied to the brushless motor 3.

The PWM generation section 9 of the motor control apparatus according to the above-mentioned embodiment 1 and the PWM generation section 90 of the motor control apparatus according to the embodiment 2 are different from each other only in the calculation method carried out in the half. Therefore, the PWM output work values Du, Dv and Dw calculated by the PWM generation section 9 are the same as those calculated by the PWM generation section 90, as long as the conditions are the same.

The motor control apparatus according to Embodiment 2 of the present invention can continuously carry out the application of voltage to the brushless motor 3 without stopping the application of voltage, even when the DC side voltage of the inverter circuit is low. Furthermore, in Embodiment 2, even in the case where the sensorless drive is carried out under a circumstance where the phase information of the motor of the brushless motor 3 is not obtained from a position sensor, the application Continuous voltage can be carried out without stopping the application of voltage to the brushless motor 3. Therefore, with the configuration of the motor control apparatus according to Embodiment 2, the phase of the brushless motor 3 can be estimated at all times, whereby the present invention can provide a motor control apparatus capable of driving a motor without using a position sensor.

«Embodiment 3 >>

Next, a motor control apparatus according to Embodiment 3 of the present invention will be described. Fig. 7 is a block diagram showing the configuration of the motor control apparatus according to Embodiment 3. The functions and configurations of the rectifier circuit 1, the inverter circuit 2, the brushless motor 3 and the single-phase AC power supply 5 shown in Fig. 7 are similar to those according to embodiment 1 mentioned above. The control section 4a of the motor control apparatus according to embodiment 3 has a phase estimation section 15. The phase estimation section 15 outputs an estimated phase Θ based on the axis current detection value d Id and the axis current detection value q Iq calculated by the conversion section dq 6 and the axis voltage command value d Vd 'and the axis voltage command value q Vq' sent from a PWM generation section 9a. The method of calculating the estimated phase Θ is detailed in the aforementioned thesis “Control of a sensorless salient-pole brushless DC motor on the basis of estimation of speed electromotive force” by Takeshita, Ichikawa, Lee and Matsui, Thesis Journal, Vol. 117 -D, no 1, pages 98 to 104, published by the Institute of Electrical Engineers of Japan in 1997 (T.IEE Japan, Vol. 117- D, no 1, '97). Therefore, the explanation of the method is omitted here. The estimated phase Θ obtained by the calculation is sent to the dq conversion section 6 and the PWM generation section 9a and used subsequently.

ES 2 425 481 T3

The method of calculating the estimated phase θ described in the aforementioned document "Control of a sensorless salient-pole brushless DC motor on the basis of estimation of speed electromotive force" will be briefly explained herein with reference to figure 7. The Phase estimation section 15 sets an estimated value of the rotor phase of the brushless motor 3 and sets the error between the estimated value and the actual rotor phase of the brushless motor 3. From a general voltage equation of a brushless motor, a voltage equation is established based on the estimated value of the rotor phase using the established error, as described above. The estimated speed of rotation of the brushless motor is calculated according to the equation. Feedback control is carried out so that the calculation result equals the actual rotational speed of the brushless motor. By carrying out feedback control continuously, said error can converge to zero, whereby the estimated phase θ becomes coincident with the actual rotor phase. Motor constants, such as the resistance and inductance values of the windings of the brushless motor 3, are used when establishing such a voltage equation. Furthermore, the voltage applied to the brushless motor 3 and the current flowing at the moment are also used for the voltage equation mentioned above. The phase of the brushless motor 3 can be estimated using the applied voltage, current and constants of the brushless motor 3 as described above. Therefore, sensorless actuation is possible. An estimated rotational speed ω of the brushless motor 3 can also be calculated by differentiating the estimated phase θ.

In the motor control apparatus according to Embodiment 3, the axis voltage command value d Vd 'and the axis voltage command value q Vq' to be input in the phase estimation section 15 are made equal to the value axis voltage command value d Vd and axis voltage command value q Vq to actually be applied to the brushless motor 3 by the PWM generation section 9a, respectively. Therefore, even in the case where the Cc side voltage of the inverter circuit 2 pulses, the phase estimation can be carried out appropriately, whereby sensorless drive is possible. For example, in the case that the PWM generation section 9a according to embodiment 3 is configured based on the aforementioned embodiment 2, the axis voltage command value d Vd 'and the axis voltage command value q Vq 'output from the ratio correction section 13 shown in figure 5 should only be sent to the phase estimation section 15. On the other hand, in the case where the PWM generation section 9a is configured based on embodiment 1 mentioned above, the sinusoidal three-phase voltages Vu, Vv and Vw only have to be calculated again from the working values of PWM output Du, Dv and Dw and the input voltage detection value Vpn supplied from the correction section Vpn 12 shown in figure 2. Next, the d-axis voltage command value and the q-axis voltage command value obtained as a result of dq conversion should only be sent to the phase estimation section 15.

Since the input voltage pulses, the input voltage detection value Vpn applied when determining the working values is different from the input voltage applied when the inverter circuit 2 actually carries out PWM operation. Therefore, without sending the voltage order values Vd 'and Vq' to the phase estimation section 15 at sort time, the d-axis and q-axis voltage order values can be calculated again using the input voltage detection value Vpn obtained when inverter circuit 2 actually carries out PWM operation and subsequently sent to phase estimation section 15. It is not necessary to state that the phase estimation precision is improved by this new calculation.

Fig. 8A is a graph showing the result of an experiment regarding phase estimation by the conventional motor control apparatus. Fig. 8B is a graph showing the result of an experiment regarding phase estimation by the motor control apparatus according to Embodiment 3 of the present invention. In Figures 8A and 8B, the upper waveform shows the input voltage detection value Vpn, and the lower waveform shows the estimated phase waveform. In the experiment shown in Fig. 8A, a motor control apparatus configured by the simple combination of said second and third conventional technologies is used as the conventional motor control apparatus.

As shown in Fig. 8A, in the conventional motor control apparatus, the estimated phase is distorted when the input voltage detection value Vpn of the inverter circuit 2 is small, whereby the estimation result deviates of the real phase. This results in a reduction in motor efficiency and an increase in noise. Also, when the motor load is large, the phase deviation becomes larger. This causes a serious engine stall and loss of timing problem. As an apparatus for solving this kind of problem, the present invention can provide the motor control apparatus according to Embodiment 3. As shown in Fig. 8B, the estimated phase in the motor control apparatus according to Embodiment 3 becomes linear and identical to the real phase. Therefore, the motor control apparatus according to Embodiment 3 can carry out excellent motor control without reducing the efficiency of the motor or increasing the noise, even though the apparatus has a

ES 2 425 481 T3 sensorless configuration.

«Embodiment 4 >>

Next, a motor control apparatus according to Embodiment 4 of the present invention will be described. Fig. 9 is a block diagram showing the configuration of the motor control apparatus according to Embodiment 4. The functions and configurations of the rectifier circuit 1, the inverter circuit 2, the brushless motor 3 and the single-phase AC power supply 5 shown in Figure 9, are similar to those of the aforementioned Embodiment 1. The control section 4b according to embodiment 4 has a d-axis PI controller 7a and a q-axis PI controller 8a, a PWM generation section 9b, a dq conversion section 6, subtraction means, and so on.

The PWM generation section 9b according to embodiment 4 is configured to send an S signal to the d-axis PI controller 7a and the q-axis PI controller 8a when step 34 (the calculation of equation (4)) is carried out depending on the judgment result in step 32 (Fig. 3) in the calculation process of the correction section Vpn (Fig. 2) according to Embodiment 1.

When the PWM generation section 9b carries out step 34, that is, when the axis voltage command value d Vd is generated from the error between the axis current command value d Id * and the value of d-axis current detection Id In step 34, the d-axis PI controller 7a, which has received the S signal from the PWM generation section 9b, performs P (proportional) control, but does not perform the control I (integral). The q-axis PI controller 8a also performs a similar operation as the d-axis PI controller 7a mentioned above.

Fig. 10 is a graph showing a result of an experiment regarding the motor current according to Embodiment 4. In Fig. 10, the input voltage detection value Vpn, the motor current, the order value of Motor current and voltage phase applied to the motor are shown in this sequence from above.

When the result of the experiment shown in Fig. 10 is compared with the result of the experiment shown in Fig. 4B according to the aforementioned Embodiment 1, it is found that the frequency of occurrence at which the current of the particular motor becomes greater than the motor current command value has decreased significantly. It is thus observed that the error has decreased. Furthermore, it has been found that the circled portion of the motor current waveform shown in Figure 10 is closer to the motor current command value than the circled portion of the waveform. of the motor current shown in Figure 4B. As described above, experiments have confirmed that the motor control apparatus according to Embodiment 4 can improve the controllability of the motor current, reduce the occurrence of eddy currents and raise the maximum value of the motor output torque.

«Embodiment 5 >>

Next, a motor control apparatus according to Embodiment 5 of the present invention will be described. Fig. 11 is a block diagram showing the configuration of the motor control apparatus according to Embodiment 5. The functions and configurations of the rectifier circuit 1, the inverter circuit 2, the brushless motor 3 and the single-phase AC power supply 5 shown in Fig. 11 are similar to those according to embodiment 1 mentioned above. The control section 4c according to embodiment 5 has a dq conversion section 6, a d-axis PI controller 7, a q-axis PI controller 8, a PWM generation section 9, a d-axis multiplier 18, a multiplier of q-axis 19 and a q-axis adder 20. The functions of the dq 6 conversion section, the d-axis PI controller 7, the q-axis PI controller 8 and the PWM 9 generation section are similar to those according to the embodiment 1. The d axis multiplier 18 sends the result of the multiplication of the axis current detection value q Iq, the rotational speed ω of the brushless motor 3 and the axis inductance q Iq of the brushless motor 3. The result is sent and then added to the output of the d-axis PI controller 7, and the result of the addition is set as the d-axis voltage command value Vd. The q-axis multiplier 19 sends the result of the multiplication of the d-axis current detection value Id, the rotational speed ω and the d-axis inductance Ld of the brushless motor 3. The q-axis adder 20 outputs the result of the multiplication of the rotational speed ω and the induced voltage Ke of the q-axis brushless motor 3. The result of adding the respective outputs of the q-axis multiplier 19, the q-axis adder 20, and the q-axis PI controller 8 are set as the q-axis voltage command value Vq. These operations are represented by the following calculation equation (7).

ES 2 425 481 T3

- wLqlq (uLdld + ωΚε (7>

In embodiment 5, by adding a non-interacting term, that is, the first term on the right hand side of equation (7), the independence of the d-axis and the q-axis can be improved. Fig. 12 is a graph showing a result of an experiment regarding motor current according to Embodiment 5.

As shown in Fig. 12, the motor current tracking performance of the motor control apparatus according to Embodiment 5 is higher than that of the motor control apparatus according to Embodiment 4 shown in Fig. 10. It is has found that the circled portion of the motor current waveform shown in Figure 12 is closer to the motor current command value than the circled portion shown in Figure 10. Experiments have confirmed that the motor control apparatus according to Embodiment 5 can further reduce the occurrence of eddy currents and raise the maximum value of the motor output torque compared to the motor control apparatus according to Embodiment 4.

Fig. 13 is a graph showing the results of an experiment regarding the relationship between the rotational speed and the limiting torque of a brushless motor in the case where the motor control apparatus according to the present invention is compared with conventional engine control apparatus. The motor control apparatus according to the present invention used for the experiment shown in Fig. 13 is an apparatus configured by combining the configurations of embodiments 1, 3, 4 and 5 mentioned above. Furthermore, the conventional motor control apparatus used as a comparison example is a motor control apparatus configured by the simple combination of the above-mentioned second and third conventional technologies. In this experiment, even when the configuration of the motor control apparatus according to Embodiment 2 was used instead of the configuration of the motor control apparatus according to Embodiment 1, a similar result of the experiment was obtained.

As clearly shown in Fig. 13, the limiting torque in the case of the motor control apparatus according to the present invention is significantly higher than in the case of the conventional motor control apparatus. Therefore, the torque requirements for the compressors of air conditioners, refrigerators, etc., can be sufficiently met by using the motor control apparatus according to the present invention. Furthermore, the specifications of the motor control apparatus for driving motors of electric washing machines, electric dryers, electric vacuum cleaners, blowers, etc., can be met by using the motor control apparatus according to the present invention.

«Embodiment 6 >>

Next, a motor control apparatus according to Embodiment 6 of the present invention will be described. The motor control apparatus according to Embodiment 6 is configured so that the input voltage detection value Vpn input into the inverter circuit is estimated from past data.

Since the input voltage detection value Vpn fluctuates significantly, the value is detected every control cycle in the motor control apparatus according to Embodiment 6. It was assumed herein that the voltage detection value of input detected in the last control cycle is Vpn [n-1] and that the input voltage detection value detected in the penultimate control cycle is Vpn [n-2]. Vpn [n-1] is not used as the input voltage detection value in the present control cycle. Instead, the variation between Vpn [n-1] and Vpn [n-2] is calculated, and the input voltage detection value Vpn [n] is estimated in the present control cycle. The equation for the calculation is represented by the following equation (8).

ES 2 425 481 T3

[rt ~ 1] + -1] - ypn [n - 2]) («)

Equation (8) is established when it is assumed that the variation between the input voltage detection value Vpn [n-1] in the last control cycle and the input voltage detection value Vpn [n-2] in the penultimate control cycle is equal to the variation between the value in the present control cycle and the value in the last control cycle. Using the input voltage detection value Vpn [n] estimated using equation (8), the motor control apparatus according to the present invention can output accurate working values.

The configuration according to embodiment 6 for estimating the input voltage detection value Vpn [n] may be incorporated in the configurations according to embodiments 1 to 5 mentioned above. Therefore, more accurate working values can be sent, and highly efficient control of the motor can be carried out.

«Embodiment 7 >>

Next, a motor control apparatus according to Embodiment 7 of the present invention will be described. When a motor is stopped or the switching operation of an inverter circuit is stopped, the current flowing in the motor is regenerated to the input side of the inverter circuit. In the case where the regenerative current is large, the input side voltage of the inverter circuit increases and it is an overvoltage. This can damage the motor control apparatus that incorporates the inverter circuit. The motor control apparatus according to embodiment 7 has a mechanism to prevent damage due to regenerative current.

Fig. 14 is a circuit diagram showing a rectifier circuit 1, an inverter circuit 2, a brushless motor 3, a single-phase AC power supply 5, etc., other than a control section, in the control apparatus. motor according to embodiment 7 of the present invention. The control section is not displayed. As shown in Fig. 14, a capacitor 16 having a small capacitance is arranged between the rectifier circuit 1 and the inverter circuit 2. Damage to the motor control apparatus due to regenerative current can be avoided by arranging the capacitor 16 between rectifier circuit 1 and inverter circuit 2 as described above. As a result, it is possible to achieve an engine control apparatus having higher safety.

The capacitance of the capacitor 16 is set to a value where the motor control apparatus is not damaged by the regenerative current. For example, in the case where the motor control apparatus is used for the compressor of an air conditioner or a heat pump water heater for domestic use, the capacitance should be about 0.1 to 50 pF. In the case of a refrigerator, an electric washing machine, an electric dryer and an electric vacuum cleaner, the capacitance should be approximately 0.1 to 20 pF since the regenerative current is less than that of the air conditioner.

Although the configuration in which the capacitor 16 is arranged between the rectifier circuit 1 and the inverter circuit 2 has been explained in the descriptions of embodiment 7, the capacitor 16 should only be connected to the input side of the inverter circuit 2.

Regenerative current is a current that flows from the brushless motor 3 to the capacitor 16 when the stored energy determined by the inductance L [H] of the brushless motor windings and the currents flowing through the windings is regenerated as a voltage to capacitor 16 immediately before the brushless motor 3 stop. The maximum output P [W] of the brushless motor 3 depends on the allowable current value and the inductance L of the brushless motor 3. In Embodiment 7, the maximum output P [W] of the brushless motor 3 has a relationship represented by the following equation (9). This relationship is based on the exhaustive consideration of the relationship between said capacitance C [F] and the output of the brushless motor 3, a value at which the motor control apparatus is not damaged, and other factors.

CS 2xl07 XP <9>

The configuration according to Embodiment 7 in which damage of the motor control apparatus due to the

ES 2 425 481 T3 regenerative current, can be incorporated in the configurations according to embodiments 1 to 6 mentioned above. Therefore, it is possible to provide an engine control apparatus having higher reliability.

«Embodiment 8 >>

Next, a motor control apparatus according to Embodiment 8 of the present invention will be described. Fig. 15 is a circuit diagram showing a rectifier circuit 1, an inverter circuit 2, a brushless motor 3, a single-phase AC power supply 5, etc., other than a control section, in the control apparatus. motor according to embodiment 8 of the present invention. The control section is not shown in figure 15.

The input current of the rectifier circuit 1 is affected by the switching operation of the inverter circuit 2. In particular, in the case that the carrier frequency of the switching operation is low, there is a problem of distorting the current waveform. input. In the motor control apparatus according to embodiment 8, an inductor 17 having an inductance L is arranged between the single-phase AC power supply 5 and the rectifier circuit 1 as shown in Fig. 15. By providing the inductor 17 between the single-phase AC power supply 5 and the rectifier circuit 1 of the motor control apparatus according to Embodiment 8, the power factor of the input current can be raised and the waveform of the input current can be improved. current. The inductance L of inductor 17 is set to a value where the current distortion decreases. For example, in the case where the motor control device is used for the compressor of an air conditioner or a heat pump water heater for domestic use, the inductance L should be approximately 0.1 to 2.0 mH. In the case of a refrigerator, an electric washing machine, an electric dryer and an electric vacuum cleaner, the inductance L should be approximately 0.1 to 1.0 mH, since the current is less than that of the air conditioner.

Although the configuration in which the inductor 17 is provided between the single-phase AC power supply 5 and the rectifier circuit 1 has been explained in the descriptions of embodiment 8, the inductor 17 must only be connected to the input side of the inverter circuit 2 .

The inductance L of inductor 17 refers to the magnitude of the input current and the switching frequency of the inverter circuit 2. In the case of the air conditioner, refrigerator, electric washing machine, etc., mentioned above, there is no big difference in frequency. switching. The switching frequency is substantially several kHz to several tens of kHz. Therefore, it is considered that the appropriate inductance L in embodiment 8 is almost determined by the magnitude of the input current. Since the voltage of the single-phase AC power supply 5 is 200 to 230 V according to the universal world standard, there is a correlation between the maximum output P [W] of the brushless motor 3 and the appropriate inductance L. This correlation is plotted substantially by the following equation (10).

L ¿P xl0_yes (10 }

Furthermore, in the case of a motor control apparatus provided with both inductor 17 and capacitor 16, a resonance phenomenon occurs. To prevent the resonance phenomenon from adversely affecting the AC power supply system, the relationship represented by the following equation (11) is established between the inductance L of the inductor 17 and the capacitance C of the capacitor 16.

9xlO '/ C (11)

A capacitor having a capacitance C can also be provided for a motor control apparatus provided with an inductor in order to avoid damage to the motor control apparatus due to regenerative current as explained in the descriptions of the embodiment 7 mentioned above. In this case, however, the inductor is connected in series with the capacitor, whereby a resonance phenomenon can occur. As is generally known, the resonance frequency is 1 / 2pv (LC), a value determined by the values of the inductor and capacitor. Therefore, by setting the inductor and capacitor values so that the resonant frequency is higher than the frequencies speculated in the harmonic standards of the power supply, for example, it is possible to provide a motor control apparatus that

ES 2 425 481 T3 generate less noise.

«Embodiment 9 >>

Next, a motor control apparatus according to Embodiment 9 of the present invention will be described. Fig. 16A is a block diagram showing the configuration of the motor control apparatus according to Embodiment 9 of the present invention. The functions and configurations of the inverter circuit 2, the brushless motor 3, the control section 4 and the single-phase AC power supply 5 shown in Fig. 16A are similar to those of the above-mentioned embodiment 1. In the motor control apparatus according to embodiment 9, a boost circuit 21 is provided on the input side of the inverter circuit 2. The AC voltage (100 V AC, for example) supplied from the single-phase AC power supply 5 is raised (to 200 V AC, for example) by the boost circuit 21 and introduced into the inverter circuit 2.

The boost circuit 21 includes an inductor 200 to which the input voltage V of the single-phase AC power supply 5 is applied, two switching devices 201 and 202 connected in series, two diodes 203 and 204 connected in series, and a capacitor 205. A terminal of the single-phase AC power supply 5 is connected to the connection point of the two switching devices 201 and 202 via the inductor 200. The other terminal of the single-phase AC power supply 5 is connected to the connection point of the two diodes 203 and 204. Furthermore, the series connection of the two switching devices 201 and 202, the series connection of the two diodes 203 and 204 and capacitor 205 are connected in parallel with each other. The output through capacitor 205 is fed into inverter circuit 2.

Furthermore, the engine control apparatus according to Embodiment 9 is provided with a boost circuit control section 22 for controlling the on / off operation of the switching devices 201 and 202 of the boost circuit 21. In the following descriptions, the switching device 201 arranged on the upper side of the motor control apparatus shown in Fig. 16A is called an upper arm switching device 201, and the switching device 202 arranged on the lower side is called a lower arm switching device 202.

Next, an example of the operation of the boost circuit control section 22 of the engine control apparatus according to Embodiment 9 will be described.

The lift circuit control section 22 sends PWM commands to control the upper arm switching device 201 and the lower arm switching device 202 provided in the lift circuit 21. In the PWM command for one of the switching devices, an on / off period in which the switching device repeats the on / off operation at intervals of a predetermined time and an off period in which the switching device maintains its off state are alternately present. Also, in the on / off period in which one of the switching devices repeats the on / off operation at intervals of the predetermined time, the other switching device is in the off period in which the off state is maintained. of the switching device.

In Fig. 17, the signal (a) is a control signal V1 sent from the control section of the lift circuit 22 to the upper arm switching device 201. The signal (b) is a control signal V2 sent from the section from the boost circuit 22 to the lower arm switching device 202. The signal (c) is the output voltage V of the single-phase AC power supply 5. The signals shown in FIG. 17 are examples of these signals. As shown in Fig. 17, for example, it is assumed that, in period A, the upper arm switching device 201 carries out the on / off operation, and the lower arm switching device 202 maintains the turned off. It is also assumed that, in the period B, the lower arm switching device 202 carries out the on / off operation, and the upper arm switching device 201 maintains the off state.

The state in period A is a state in which the output voltage V at the terminal of the single-phase AC power supply 5, not connected to the inductor 200, is higher. Also, the state in period B is a state in which the output voltage V at the terminal of the single-phase AC power supply 5, connected to the inductor 200, is higher. In other words, period A and period B are generated in synchronization with the frequency of the single-phase AC power supply 5. The control section of the lift circuit 22 sends the PWM commands to the lift circuit 21 so that the upper arm switching device 201 and the lower arm switching device 202 provided in the lift circuit 21 carry out the power-on / operation operation. shutdown as described above.

ES 2 425 481 T3

Next, a method of determining the PWM output working values of the PWM command according to Embodiment 9 will be described.

The control section 4 determines whether or not the step 34 shown in figure 3 and explained in the descriptions of the aforementioned embodiment 3 has been carried out at each timing point where the input voltage of the inverter circuit 2 is returns maximum. In other words, the control section 4 determines whether the PWM output working values of the phases U, V and W have been determined according to the equation (4) or not in the case where the voltage detection value of input Vpn is less than the maximum value of application voltage Vmax.

In the case where it is determined that the step 34 has been carried out, the control section 4 sends to the control section of the boost circuit 22 a control signal indicating that the step 34 has been carried out. When the control signal is input from the control section 4, the boost circuit control section 22 increments the PWM output working values of the PWM command that is sent to the boost circuit 21. On the other hand, when the control signal is not input, the boost circuit control section 22 decreases the PWM output working values of the PWM command. As a result, the PWM output work values of the PWM command of the boost circuit control section 22 are changed at each timing point that the input voltage of the inverter circuit 2 becomes the maximum value. This timing point is a timing point at which the output voltage of the single-phase AC power supply 5 becomes the maximum value.

Next, a method of determining whether the operating state is the state in period A or the state in period B will be described.

When the brushless motor 3 is started, the input voltage of the inverter circuit 2 is similar to that obtained when the capacitor 205 is not provided since the capacitance of the capacitor 205 provided in the boost circuit 21 is small (just like the signal input voltage detection signal designated by Vpn in Figures 4A and 4B, for example). At this time, the lower arm switching device 202 is subjected to the on / off operation according to the PWM output working value of the predetermined PWM command, regardless of the control signal of the control section 4. In this case, when the output voltage at the terminal of the single-phase AC power supply 5, connected to the inductor 200, is higher, the voltage of the capacitor 205 is higher than the voltage obtained when the operation is not carried out. on / off. Therefore, the state at this time can be considered to be a state in which the voltage phase of the single-phase AC power supply 5 is the phase in period B. On the other hand, when the output voltage at the terminal of the single-phase AC power supply 5, not connected to the inductor 200, is higher, the voltage of the capacitor 205 does not rise. Therefore, the state at this time can be judged to be a state where the voltage phase of the single-phase AC power supply 5 is the phase in period A.

The voltage phase of the single phase AC power supply 5 can be detected by detecting whether the voltage of the capacitor 205 rises or not, as described above. Therefore, in the motor control apparatus according to Embodiment 9, a judgment can be made on whether the voltage phase is the phase in period A or the phase in period B without using a voltage detection circuit. phase voltage.

Figure 18 shows the waveform of the output voltage V of the single-phase AC power supply 5 and the waveform of a pulse signal changed based on a PWM output working value calculated in the motor control apparatus. according to embodiment 9.

In the above-mentioned embodiment 9, the lower arm switching device 202 is subjected to an on / off operation according to the PWM output work value of the predetermined PWM command. However, the upper arm switching device 201 can be subjected to on / off operation at this time. In this case, it is unnecessary to state that the voltage of capacitor 205 rises in period A and that the voltage does not rise in period B.

Fig. 16B is a circuit diagram showing the configuration of another boost circuit 21a of the motor control apparatus according to Embodiment 9. As shown in Fig. 16B, the boost circuit 21a according to Embodiment 9 may comprise a lifting device. switching, a plurality of diodes and a capacitor. In the case of this configuration, it is not necessary to distinguish between the upper arm switching device and the lower arm switching device. Only one switching device should undergo a switching operation based on a PWM command.

ES 2 425 481 T3

In the motor control apparatus explained in the descriptions of Embodiment 9, in the case where the output voltage of the single-phase AC power supply 5 is so low that the voltage applied to the brushless motor 3 is insufficient, it is It can raise the input voltage of the inverter circuit 2. Therefore, the motor control apparatus according to Embodiment 9 can raise the maximum rotational speed of the brushless motor 3, whereby the operating range of the motor can be significantly expanded. In particular, in the case of an air conditioner, since the maximum rotation speed of its motor can be raised, the range of performance variation for cooling and heating can be extended, thereby further improving comfort. Furthermore, in an apparatus incorporating the motor control apparatus according to Embodiment 9, the maximum performance during the heating operation is especially improved. Thus, it is possible to provide an air conditioner having the highest heating effect.

«Embodiment 10 >>

Next, a motor control apparatus according to Embodiment 10 of the present invention will be described. Fig. 19 is a block diagram showing the configuration of the motor control apparatus according to Embodiment 10 of the present invention. The functions and configurations of the inverter circuit 2, the brushless motor 3, the control section 4 and the single-phase AC power supply 5 of the motor control apparatus according to embodiment 10 shown in Fig. 19 are similar to those according to the embodiment 9 mentioned above.

In the motor control apparatus according to embodiment 10, a boost circuit control section 22a comprises an AC current command generation section 23 and a PWM command generation section 24.

The AC current command generation section 23 of the boost circuit control section 22a detects the voltage phase of the single-phase AC power supply 5 and generates an AC current command value having the same phase as the switching phase. detected voltage. Then, the generation section 23 sends the command value to the PWM command generation section 24. The amplitude value of the AC current command value is generated based on the control signal of the section from control 4.

The control input signal from the control section 4 to the AC current command generation section 23 is the same control signal as explained in the descriptions of the above-mentioned embodiment 9. When the control signal is input from the control section 4, the AC current command generating section 23 increases the amplitude value of the AC current command value. On the other hand, in the case where the control signal is not input from the control section 4, the AC current command generating section 23 decreases the amplitude value of the AC current command value.

The AC current command value from the AC current command generation section 23 and the detected value of the AC current from the single-phase AC power supply 5 are input into the PWM command generation section 24. The PWM command generation 24 performs error amplification so that the output current of the boost circuit 21 is the AC current command value. The PWM command generation section 24 then generates PWM signals to drive the switching devices of the boost circuit 21 and sends the PWM signals to the boost circuit 21. The PWM command generation section 24 according to Embodiment 10 uses PI control as control of feedback for error amplification. Fig. 20 is a circuit diagram showing a specific configuration of the boost circuit control section 22a. However, the present invention is not limited to this type of configuration for PI control. It is possible to use another feedback control that has been used generally.

Figure 21 shows the waveform of the output voltage V of the single-phase AC power supply 5, a calculated PWM output working value, and the waveform of a switched pulse signal based on the PWM output working value. in the engine control apparatus according to embodiment 10.

A judgment as to whether the upper arm switching device or the lower arm switching device of the lift circuit 21 is actuated and controlled is made depending on whether the AC current command value is positive or negative. For example, when the AC current command value is positive, PWM commands are sent so that the lower arm switching device undergoes PWM operation and so that the upper arm switching device remains in the state off. Also, when the AC current command value is negative, PWM commands are sent so that the upper arm switching device undergoes PWM operation and so that the lower arm switching device remains in the same position.

ES 2 425 481 T3 off state. Or, since the voltage phase is detected by the boost circuit control section 22a, the detected voltage phase can be input to the PWM command generation section 24 and then a judgment can be made as to whether the switching device The upper arm switch or the lower arm switching device undergoes PWM operation, based on the detected voltage phase. Fig. 22 is a circuit diagram showing a specific configuration of a boost circuit control section 22b configured as described above.

The boost circuit 21a comprising a switching device and shown in Fig. 16B according to the aforementioned embodiment 9 can be used as the boost circuit 21.

The waveform of the current flowing to the single-phase AC power supply 5 becomes nearly sinusoidal by virtue of the operations of the boost circuit 21 and the boost circuit control sections 22a and 22b mentioned above. Therefore, the power factor of the power supply is almost one, whereby it is possible to provide a motor control apparatus that does not adversely affect the power supply system.

«Embodiment 11 >>

Next, a motor control apparatus according to Embodiment 11 of the present invention will be described. Fig. 23A is a block diagram showing the configuration of the motor control apparatus according to Embodiment 11 of the present invention. The functions and configurations of the inverter circuit 2, the brushless motor 3, the control section 4 and the single-phase AC power supply 5 of the motor control apparatus according to Embodiment 11 shown in Fig. 23A are similar to those of the embodiments. 9 and 10 mentioned above.

The motor control apparatus according to embodiment 11 differs from the motor control apparatus according to embodiment 10 in that a double voltage rectifier boost circuit 25 is provided instead of the boost circuit 21. This double voltage rectifier boost circuit 25 includes an inductor 300, a switching device 301, diodes 302, 303, 304, and 305, a capacitor 306 that has a large capacitance, and a capacitor 307 that has a small capacitance. A step-up circuit control section 22c includes an AC current command generation section 23 and a PWM command generation section 24b. The operation of the AC current command generation section 23 is substantially the same as that explained in the descriptions of embodiments 9 and 10 mentioned above.

The operation of the PWM command generation section 24b and the operation of the dual voltage rectifier boost circuit 25 will be described with reference to Fig. 24.

In a period (hereinafter referred to as period C) in which the output voltage at the terminal of the single-phase AC power supply 5, connected to the inductor 300, is higher than the output voltage at its terminal not connected to inductor 300, a current flows to capacitor 306. On the other hand, in a period (hereinafter referred to as period D) in which the output voltage at the terminal of the single-phase AC power supply 5, not connected to the inductor 300, is higher, a current to capacitor 307.

Therefore, in period C, a current similar to the current introduced in a conventional dual voltage rectifier circuit flows from the 5 single-phase AC power supply. If the inductor 300 becomes smaller in this state, the power factor decreases. In embodiment 11, the PWM command generation section 24b sends a PWM signal to PWM drive the switching device of the double voltage rectifier boost circuit 25 in period C, so that the power factor does not go down.

In period D, the configuration according to Embodiment 11 is similar to the circuit configuration explained in the descriptions of Embodiment 7 mentioned above, whereby the power factor does not go down.

The PWM command generation section 24b according to embodiment 11 differs from the PWM command generation section 24 according to the aforementioned embodiment 10 in that the PWM signal is not sent to the double voltage rectifier boost circuit 25 in period D.

The two capacitors in the conventional dual voltage rectifier circuit have almost the same capacitance and are high capacitance aluminum electrolytic capacitors. However, the capacitance of one of the two

ES 2 425 481 T3 capacitors according to embodiment 11 of the present invention is set to a small value. Since the capacitance of one of the capacitors can be made small, the double voltage rectifier boost circuit 25 of the motor control apparatus according to Embodiment 11 can be made smaller than the conventional double voltage rectifier circuit.

Fig. 23B is a circuit diagram showing the configuration of a dual voltage rectifier boost circuit 25a shown as another configuration of the dual voltage rectifier boost circuit of the motor control apparatus according to the present invention. An effect similar to that of the above-mentioned embodiment 11 is also obtained even though the dual voltage rectifier boost circuit 25a shown in Fig. 23B is used instead of the dual voltage rectifier boost circuit 25 shown in Fig. 23A.

«Embodiment 12 >>

Next, a compressor incorporating one of the motor control apparatus according to Embodiments 1 to 11 will be described with reference to Fig. 25. Fig. 25 is a block diagram showing the configuration of the compressor according to Embodiment 12 of the present invention.

In Figure 25, a compressor 41 connected to a single-phase AC power supply 5 has a motor control apparatus 40 and a compression mechanism 42 driven by a brushless motor 3. The functions and settings of the brushless motor 3 and the Single-phase AC power supply 5 according to embodiment 12 are similar to those according to embodiment 1 mentioned above. Furthermore, one of the motor control apparatus according to the above-mentioned embodiments 1 to 11 is applied to the motor control apparatus 40. The output of the motor control apparatus 40 is connected to the brushless motor 3 arranged inside the compression mechanism 42, whereby the brushless motor 3 is rotated and driven by the motor control apparatus 40. By rotating the brushless motor 3, the compression mechanism 42 sucks and compresses refrigerant gas and discharges high pressure gas.

As described above, the engine control apparatus 40, one of the engine control apparatus according to the above-mentioned embodiments 1 to 11 of the present invention, is made smaller and lighter than the engine control apparatus. conventional. Therefore, the present invention can provide the compressor 41 which is made compact by integrating the compression mechanism 42 with the engine control apparatus 40 as explained in the descriptions of Embodiment 12.

«Embodiment 13 >>

Fig. 26 is a block diagram showing the configuration of an air conditioner according to Embodiment 13 of the present invention.

The air conditioner 43 according to embodiment 13 has an indoor unit 44 and an outdoor unit 45 and is used to cool or heat a room. The compression mechanism 42 of the air conditioner 43 circulates a refrigerant between the indoor unit 44 and the outdoor unit 45. The motor control apparatus 40 connected to the single-phase AC power source 5 drives and controls a brushless motor arranged within the mechanism. compression 42. The functions and configurations of the brushless motor and the single-phase AC power supply 5 according to embodiment 13 are similar to those according to the aforementioned embodiment 1. Furthermore, one of the engine control apparatus according to the above-mentioned embodiments 1 to 11 is applied to the engine control apparatus 40.

In the air conditioner 43 according to embodiment 13, the indoor unit 44 has an indoor-side heat exchanger 48, and the outdoor unit 45 has a four-way valve 46, a throttle device 47, and an outdoor-side heat exchanger 49, thereby forming a refrigerant circulation passage.

The indoor side heat exchanger 48 has a blower 48a to raise the heat exchange efficiency and a temperature sensor 48b to measure the temperature of the indoor side heat exchanger 48 or the temperature around it. The outdoor side heat exchanger 49 has a blower 49a to raise the heat exchange efficiency and a temperature sensor 49b to measure the temperature of the outdoor side heat exchanger 49 or the temperature around it.

In the air conditioner 43 according to embodiment 13, the compression mechanism 42 and the four-way valve 46 are arranged in the refrigerant circulation passage between the indoor side heat exchanger 48 and the

ES 2 425 481 T3 outdoor side heat exchanger 49. In the air conditioner 43 according to embodiment 13, the direction of the refrigerant flowing through the refrigerant circulation passage is changed by the selection operation of the four-way valve 46 For example, in the refrigerant circulation passage of the air conditioner 43, the refrigerant flows in the direction indicated by the arrow A. The refrigerant that has passed through the outer side heat exchanger 49 is drawn into the compression mechanism 42 by the four-way valve 46. The refrigerant discharged from the compression mechanism 42 is supplied to the inner side heat exchanger 48. By On the other hand, when the selection operation of the four-way valve 46 is performed, the refrigerant flows in the direction indicated by the arrow B. The refrigerant that has passed through the indoor-side heat exchanger 48 is drawn into the compression mechanism 42 by the four-way valve 46. The refrigerant discharged from the compression mechanism 42 is supplied to the outdoor-side heat exchanger 49. Such As described above, the flow direction of the refrigerant is changed by the selection operation of the four-way valve 46.

The throttle device 47 arranged in the refrigerant circulation passage between the indoor side heat exchanger 48 and the outdoor side heat exchanger 49 has a function of throttling the flow rate of the circulating refrigerant and also has a function of automatically adjusting the flow rate. of the refrigerant. While the refrigerant circulates through the refrigerant circulation passage, the throttle device 47 throttles the flow rate of the refrigerant liquid sent from a condenser to an evaporator so that the refrigerant liquid can expand immediately after throttling and supply the exact amount of the refrigerant that requires the evaporator.

In the air conditioner 43, the indoor side heat exchanger 48 functions as a condenser during heating and functions as an evaporator during cooling. Furthermore, the outer side heat exchanger 49 functions as an evaporator during heating and functions as a condenser during cooling. In the condenser, the heat of the refrigerant gas flowing through and having high temperature and pressure is removed by the supplied air, whereby the refrigerant gas gradually liquefies. Near the outlet of the condenser, the refrigerant is in a liquid state or a state of mixture of liquid and gas under high pressure. This is equivalent to a phenomenon where the refrigerant radiates heat into the atmosphere and liquefies. In addition, the refrigerant converted into a liquid state or a low temperature and pressure liquid-gas mixture state by the throttle device 47 flows to the evaporator. When room air is supplied to the evaporator in this state, the refrigerant removes a large amount of heat from the air and evaporates, thereby being a refrigerant having a larger amount of gas. Air from which a large amount of heat has been removed by the evaporator is discharged as a cold jet from the air outlet of the air conditioner 43.

In the air conditioner 43, the commanded rotation speed of the brushless motor is adjusted based on the operating state, that is, a target temperature set for the air conditioner 43, the actual room temperature, and the outside air temperature. Analogously to the motor control apparatus according to the aforementioned Embodiment 1, the motor control apparatus 40 controls the rotational speed of the brushless motor of the compression mechanism 42 based on the preset commanded rotational speed.

Next, a method of controlling the rotational speed of the brushless motor at the preset commanded rotational speed will be described.

The ordered rotational speed is assumed to be ω * and the actual rotational speed of the brushless motor is ω. In the case of a brushless motor that has a position sensor, ω can be obtained by differentiating the signal from the position sensor. In the case of a brushless motor that does not have a position sensor, ω must be the estimated speed of rotation ω obtained by differentiating the estimated phase Θ, as explained in the descriptions of embodiment 3. The error between the ordered rotational speed ω * and the actual rotational speed ω is calculated. A value obtained by subjecting the error to PI control is sent as a general current command value I *. Using the current phase command value B * stored within control section 4, the axis current command value d Id * and the axis current command value q Iq * are calculated according to the following equations ( 12) and (13).

ES 2 425 481 T3

β * is a value to determine the running state of the brushless motor 3. This value can be a default value or it can be changed depending on the running state of the brushless motor. By adding said function to the control section 4, in the case where the actual rotational speed is less than the commanded rotational speed, the d-axis current command value and the axis current command value q are incremented by the PI control. Therefore, the output torque of the brushless motor 3 increases and the brushless motor accelerates. By this operation of the control section 4, the motor control apparatus operates so that the preset commanded rotational speed is obtained, whereby the brushless motor rotates at the commanded rotational speed.

Next, the operation of the air conditioner 43 according to Embodiment 13 will be described.

In the air conditioner 43 according to embodiment 13, when a driving voltage is applied from the engine control apparatus 40 to the compression mechanism 42, the refrigerant circulates through the refrigerant circulation passage. During this circulation, heat exchange takes place in the heat exchanger 48 of the indoor unit 44 and the heat exchanger 49 of the outdoor unit 45. In other words, in the air conditioner 43, the refrigerant sealed in the closed refrigerant circulation passage is circulated through the compression mechanism 42, whereby a known heat pump cycle is formed in the closed refrigerant circulation passage. . This heats or cools the room.

For example, in the case where the air conditioner 43 carries out a heating operation, the user sets the four-way valve 46 so that the refrigerant flows in the direction indicated by the arrow A. In this case, the exchanger Heat exchanger 48 functions as a condenser and discharges heat by virtue of the circulation of the refrigerant through the refrigerant circulation passage. This heats up the room.

On the other hand, in the case where the air conditioner 43 performs a cooling operation, the user sets the four-way valve 46 so that the refrigerant flows in the direction indicated by the arrow B. In this case, the Heat exchanger 48 functions as an evaporator and absorbs heat from the ambient air by virtue of the circulation of the refrigerant through the refrigerant circulation passage. This cools the room.

In the air conditioner 43 according to embodiment 13, the commanded rotation speed is determined based on a target temperature set for the air conditioner 43, the actual room temperature, and the outside air temperature. Analogously to the motor control apparatus according to the aforementioned embodiment 1, the motor control apparatus 40 controls the rotational speed of the brushless motor of the compression mechanism 42 based on the determined commanded rotational speed. As a result, the air conditioner 43 according to embodiment 13 can carry out comfortable cooling and heating.

Since the motor control apparatus 40 of the air conditioner 43 according to embodiment 13 is smaller and lighter than the conventional motor control apparatus, the motor control apparatus 40 has a greater degree of freedom of arrangement within the unit. exterior 45. This further facilitates production design. Furthermore, by making the motor control apparatus smaller, it is possible to provide an outdoor unit 45 which is smaller and lighter, whereby the outdoor unit can be installed more easily by consumers. These excellent effects can be achieved.

In the case where brushless motors are used to drive the blower 48a of the indoor side heat exchanger 48 and the blower 49a of the outdoor side heat exchanger 49 of the air conditioner 43 according to Embodiment 13, the motor control apparatus To drive and control each of these brushless motors it can be any of the motor control apparatuses explained in the descriptions of embodiments 1 to 11.

ES 2 425 481 T3

In the descriptions of Embodiment 13, the air conditioner capable of cooling and heating is explained. In the case of a cooling-only air conditioner, the four-way valve 46 must be removed so that the refrigerant flows in the direction indicated by arrow B.

«Embodiment 14 >>

Fig. 27 is a block diagram showing the configuration of a refrigerator according to Embodiment 14 of the present invention.

The refrigerator 51 according to embodiment 14 has a motor control apparatus 40, a compression mechanism 42, a condenser 52, a refrigeration chamber evaporator 53 and a throttle device 54.

In the refrigerator 51 according to embodiment 14, the compression mechanism 42, the condenser 52, the throttle device 54 and the evaporator of the refrigeration chamber 53 are arranged within the refrigerant circulation passage. The motor control apparatus 40 is connected to a single-phase AC power source 5 that serves as an input power source and drives and controls a brushless motor that serves as a drive source for the compression mechanism 42.

The functions and configurations of the brushless motor arranged within the compression mechanism 42 and the single-phase AC power supply 5 serving as the input power source of the motor control apparatus 40 according to embodiment 14 are similar to those according to embodiment 1 mentioned above. Furthermore, one of the engine control apparatus according to the above-mentioned embodiments 1 to 11 is applied to the engine control apparatus 40.

Analogously to the throttle device 47 of the air conditioner 43 according to embodiment 13 mentioned above, the throttle device 54 of the refrigerator 51 according to embodiment 14 throttles the flow of the refrigerant sent from the condenser 52 so that the refrigerant can expand and supply the exact amount of the refrigerant required for the evaporator 53 while the refrigerant circulates through the refrigerant circulation passage.

The condenser 52 condenses the refrigerant gas flowing through it having a high temperature and pressure and discharges the heat of the refrigerant to the outside. The heat from the refrigerant gas sent to the condenser 52 is removed by the outside air, and the refrigerant gas gradually liquefies. In the vicinity of the outlet of the condenser 52, the refrigerant becomes a liquid state or a state of mixture of liquid and gas under high pressure.

The evaporator of the refrigeration chamber 53 evaporates the refrigerant having a low temperature, thereby cooling the interior of the refrigerator. The evaporator of the refrigeration chamber 53 has a blower 53a to raise the heat exchange efficiency and a temperature sensor 53b to detect the temperature inside the refrigerator.

Next, the operation of the refrigerator 51 according to Embodiment 14 will be described.

In the refrigerator 51 according to embodiment 14, when an excitation voltage is applied from the motor control apparatus 40 to the brushless motor of the compression mechanism 42, the compression mechanism 42 is actuated and the refrigerant circulates through the passage of refrigerant circulation in the direction indicated by arrows C. During this circulation, heat exchange takes place in the condenser 52 and the evaporator of the refrigeration chamber 53, thereby cooling the interior of the refrigerator.

In other words, the flow rate of the condensed refrigerant in the condenser 52 is throttled by the throttle device 54, whereby the refrigerant expands and becomes a refrigerant having a low temperature. When the low temperature refrigerant is sent to the evaporator of the refrigeration chamber 53, the refrigerant having a low temperature in the evaporator of the refrigeration chamber 53 evaporates, thereby cooling the inside of the refrigerator. During this cooling, the air within the refrigerator is forcibly sent to the evaporator of the refrigeration chamber 53 by the blower 53a, whereby the evaporator of the refrigeration chamber 53 efficiently carries out heat exchange.

Furthermore, in the refrigerator 51 according to embodiment 14, the commanded rotation speed is adjusted depending on a target temperature set for the refrigerator 51 and the temperature inside the refrigerator. Analogously to the motor control apparatus according to embodiment 13, the motor control apparatus 40 controls the rotational speed of the brushless motor of the compression mechanism 42 based on the value of the rotational speed.

ES 2 425 481 T3 ordered preset. As a result, the temperature inside the refrigerator 51 is kept at the target temperature.

Since the motor control apparatus 40 of the refrigerator 51 according to Embodiment 14 is smaller and lighter than the conventional motor control apparatus as described above, the motor control apparatus 40 has a higher degree of freedom. arrangement inside the refrigerator than conventional motor control apparatus. Furthermore, the greater degree of freedom of arrangement of the motor control apparatus has the effect of increasing the capacity within the refrigerator 51. In addition, since a motor control apparatus that is light in weight can be provided, the weight of the refrigerator 51 can be reduced.

In the case where the brushless motor 3 is used to drive the blower 53a of the refrigerator 51 according to Embodiment 14, the motor control apparatus 40 for driving and controlling the brushless motor may be any of the motor explained in the descriptions of embodiments 1 to 11 mentioned above.

«Embodiment 15 >>

Fig. 28 is a block diagram showing the configuration of an electric washing machine according to Embodiment 15 of the present invention.

The electric washing machine 55 according to embodiment 15 has an outer frame 56. A tub 57 is suspended within the outer frame 56 by suspension rods 58. Within the tub 57 is a washing and wringing drum 59 so that it can rotate. At the bottom of the washing and draining drum 59 an agitator 60 is arranged so that it can rotate.

A brushless motor 3 for rotating the washing and draining drum 59 and the agitator 60 is arranged in the space under the tub 57 within the outer frame 56. In addition, a motor control apparatus 40, connected to the source of Single-phase AC power 5 to drive and control the brushless motor 3 is installed in the outer frame 56.

The functions and configurations of the brushless motor arranged within the outer frame 56 and the single-phase AC power supply 5 serving as the input power source of the motor control apparatus 40 according to embodiment 15 are similar to those according to the aforementioned embodiment 1 previously. Furthermore, one of the engine control apparatus according to the above-mentioned embodiments 1 to 11 is applied to the engine control apparatus 40.

In the electric washing machine 55 according to embodiment 15, a command signal indicating the commanded rotation speed depending on the operation of the user is input from a microcomputer (not shown) to control the operation of the electric washing machine 55 to the control apparatus. motor 40.

Next, the operation of the electric washing machine 55 according to Embodiment 15 will be described.

In the electric washing machine 55 according to embodiment 15, when a user performs a predetermined operation, the command signal is input from the microcomputer into the motor control apparatus 40, whereby a driving voltage is applied to the motor without brushes 3. Therefore, the brushless motor 3 is driven, and the agitator 60 or the washing and drying drum 59 rotates, whereby the laundry and the like inside the washing and drying drum 59 are washed or drained. During this operation, in the electric washing machine 55 according to embodiment 15, the rotational speed of the brushless motor 3 is controlled by the motor control apparatus 40 based on the commanded rotational speed indicated by the command signal sent from the microcomputer, just as in the case of embodiment 13 mentioned above. As a result, in the electric washing machine 55, the appropriate operation is carried out depending on the amount and dirt of the clothes and the like to be washed.

Since the motor control apparatus 40 which is compact in size is used for the electric washing machine 55 according to embodiment 15 as described above, the present invention has the effect of increasing the capacity of the washing and wringing drum even when The external dimensions of the electric washing machine are the same as those of a conventional electric washing machine. Furthermore, since the light weight motor control apparatus 40 is used for the electric washing machine 55 according to the present invention, the present invention has an excellent effect of reducing the weight of the whole washing machine.

ES 2 425 481 T3

In the electric washing machine 55 according to embodiment 15 of the present invention, the motor control apparatus 40 for driving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of embodiments 1 to 11 mentioned above.

«Embodiment 16 >>

FIG. 29 is a block diagram showing the configuration of an electric dryer according to Embodiment 16 of the present invention.

The electric dryer 61 according to embodiment 16 has an outer frame 62. Within the outer frame 62, a drum 63 is arranged so that it can rotate. A brushless motor 3 is connected to drum 63 so that brushless motor 3 rotates drum 63.

The functions and configurations of the brushless motor 3 and the motor control apparatus 40 arranged within the outer frame 62 and the single-phase AC power supply 5 according to embodiment 16 are similar to those according to embodiment 1 mentioned above. Furthermore, one of the engine control apparatus according to the above-mentioned embodiments 1 to 11 is applied to the engine control apparatus 40.

In the electric dryer 61 according to embodiment 16, a command signal indicating the ordered rotation speed depending on the user's operation is input from a microcomputer (not shown) to control the operation of the electric dryer 61 to the control apparatus. motor 40.

Next, the operation of the electric dryer 61 according to Embodiment 16 will be described.

In the electric dryer 61 according to embodiment 16, when a user performs a predetermined operation, the command signal is input from the microcomputer into the motor control apparatus 40. Therefore, a driving voltage is applied to the motor. brushless 3. As a result, the brushless motor 3 is driven, and the drum 63 rotates, whereby the laundry and the like inside the drum 63 are dried.

During this operation, in the electric dryer 61 according to embodiment 16, the rotational speed of the brushless motor 3 is controlled by the motor control apparatus 40 based on the commanded rotational speed indicated by the command signal sent from the microcomputer, just as in the case of embodiment 13 mentioned above. As a result, in the electric dryer 61 according to embodiment 16, an appropriate operation is carried out depending on the amount and dirt of the clothes and the like to be dried.

Since the motor control apparatus 40 which is compact in size is used for the electric dryer 61 according to Embodiment 16 as described above, the present invention has the effect of increasing the capacity of the drum even when the outer dimensions of the electric dryer are the same as those of a conventional electric dryer. Furthermore, since the motor control apparatus 40 which is light in weight is used for the electric dryer according to the present invention, the present invention has the effect of reducing the weight of the entire dryer.

In the electric dryer 61 according to embodiment 16 of the present invention, the motor control apparatus 40 for moving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of embodiments 1 to 11 mentioned above.

«Embodiment 17 >>

Fig. 30 is a block diagram showing the configuration of a blower according to Embodiment 17 of the present invention.

The blower 64 according to embodiment 17 has a fan 65, a brushless motor 3 for rotating and driving the fan 65 and a motor control apparatus 40 for driving and controlling the brushless motor 3. The motor control apparatus 40 It is connected to a single phase AC power source 5 so that a single phase AC voltage is applied.

The functions and configurations of the brushless motor 3 and the motor control apparatus 40 arranged within the blower 64 and the single-phase AC power supply 5 according to embodiment 17 are similar to those according to embodiment 1 mentioned above. Furthermore, one of the motor control apparatus according to Embodiments 1

ES 2 425 481 T3 to 11 mentioned above applies to motor control apparatus 40.

In the blower 64 according to embodiment 17, a command signal indicating the commanded rotational speed depending on the operation of the user is input from a microcomputer (not shown) to control the operation of the blower 64 in the motor control apparatus 40 .

Next, the operation of the blower 64 according to Embodiment 17 will be described.

In the blower 64 according to embodiment 17, when a user performs a predetermined operation, the command signal is input from the microcomputer into the motor control apparatus 40. When the command signal is input into the engine control apparatus motor 40, a driving voltage is applied from the motor control apparatus 40 to the brushless motor 3. As a result, the brushless motor 3 is driven, and the fan 65 rotates, whereby air blowing is carried out. During this operation, in the blower 64 according to embodiment 17, the output of the brushless motor 3 is controlled by the motor control apparatus 40 based on the command signal from the microcomputer, just as in the case of the aforementioned embodiment 13. previously. As a result, at the blower 64, the flow rate and intensity of the blowing are adjusted.

Since the motor control apparatus 40 which is compact in size and light weight is used for the blower 64 according to embodiment 17 as described above, the blower itself can be made smaller and lighter than a conventional blower. . Therefore, the present invention can provide a blower having excellent portability.

In the blower 64 according to embodiment 17 of the present invention, the motor control apparatus 40 for moving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of the aforementioned embodiments 1 to 11 previously.

«Embodiment 18 >>

Fig. 31 is a block diagram showing the configuration of an electric vacuum cleaner according to Embodiment 18 of the present invention.

The electric vacuum cleaner 66 according to embodiment 18 comprises a cleaning body 69, a floor suction tool 67 having a suction hole formed on the underside, and a dust suction hose 68, one end of which is connected to the floor suction tool 67 and the other end of which is connected to the cleaning body 69.

The cleaning body 69 according to embodiment 18 includes a dust chamber 71 to which the end of the dust suction hose 68 is connected on the side of the cleaning body, and an electric blower 70 arranged on the outlet side of the chamber. dust 71. The electric blower 70 comprises a fan 72 arranged so as to be opposite the outlet side of the dust chamber 71, a brushless motor 3 for rotating the fan 72, and a motor control apparatus 40 for driving and controlling the brushless motor 3. The motor control apparatus 40 is connected to a single-phase AC power source 5 so that a single-phase AC voltage is applied. By rotating the fan 72 air is drawn in through the suction hole formed in the underside of the floor suction tool 67 by the dust suction hose 68 and the dust chamber 71.

The functions and configurations of the brushless motor 3, the motor control apparatus 40 and the single-phase AC power supply 5 according to embodiment 18 are similar to those according to embodiment 1 mentioned above. Furthermore, one of the engine control apparatus according to the above-mentioned embodiments 1 to 11 is applied to the engine control apparatus 40.

In the electric vacuum cleaner 66 according to embodiment 18, a command signal indicating the commanded rotation speed depending on the user's operation is input from a microcomputer (not shown) to control the operation of the fan 72 in the motor control apparatus. 40.

Next, the operation of the electric vacuum cleaner 66 according to Embodiment 18 will be described.

In the electric vacuum cleaner 66 according to embodiment 18, when a user performs a predetermined operation, the command signal is input from the microcomputer into the motor control apparatus 40. When the command signal

The command is input to the motor control apparatus 40, a driving voltage is applied from the motor control apparatus 40 to the brushless motor 3, and the brushless motor 3 is driven. As a result, the fan 72 rotates, thereby generating a suction force within the cleaning body 69. By the suction force generated inside the cleaning body 69, air is sucked through the suction hole formed on the underside of the floor suction tool 67 which is connected to the cleaning body 69 by the dust suction hose 68. Thereby Therefore, dust is sucked from the floor to be cleaned together with air through the suction port of the floor suction tool 67 and collected in the dust chamber 71 of the cleaning body 69. During this operation, in the electric vacuum cleaner 66 according to embodiment 18, the rotational speed of the brushless motor 3 is controlled by the motor control apparatus 40 based on the command signal from the microcomputer, just as in the case of the embodiment 13 mentioned above. As a result, in the electric vacuum cleaner 66 according to embodiment 18, the rotational speed of the brushless motor 3 is controlled, whereby the intensity of the suction force is regulated.

Since the motor control apparatus 40 which is compact in size and light weight is used for the electric vacuum cleaner 66 according to embodiment 18 as described above, the cleaner body 69 can be made smaller and lighter than that of a conventional electric vacuum cleaner. Therefore, the present invention can provide an electric vacuum cleaner having excellent portability and ease of handling by the user.

In the electric vacuum cleaner 66 according to embodiment 18 of the present invention, the motor control apparatus 40 for driving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of embodiments 1 to 11 mentioned above.

«Embodiment 19 >>

Fig. 32 is a block diagram showing the configuration of a heat pump water heater according to Embodiment 19 of the present invention.

The heat pump water heater 72 according to embodiment 19 includes a refrigeration cycle unit 73 for heating supplied water and discharging hot water, a hot water storage unit 74 for storing hot water discharged from the heating cycle unit. cooling 73, and water lines 74a, 74b, 75a and 75b to connect these components.

The refrigeration cycle unit 73 includes a compression mechanism 42, an air heat exchanger 76, a throttle device 77, and a water heat exchanger 78, thereby forming a refrigerant circulation passage. Furthermore, the refrigeration cycle unit 73 is provided with a motor control apparatus 40 connected to a single-phase AC power source 5 so that a single-phase AC voltage is supplied.

The functions and configurations of the brushless motor 3, the motor control apparatus 40 and the single-phase AC power supply 5 according to embodiment 19 are similar to those according to the aforementioned embodiment 1. Furthermore, one of the engine control apparatus according to the above-mentioned embodiments 1 to 11 is applied to the engine control apparatus 40.

Analogously to the throttle device 47 of the air conditioner 43 according to the aforementioned embodiment 13 shown in figure 26, the throttle device 77 throttles the flow rate of the cooling liquid sent from the water heat exchanger 78 to the air heat exchanger 76 so that the coolant can expand immediately after throttling.

The water heat exchanger 78 is a condenser for heating the water supplied to the refrigeration cycle unit 73 and has a temperature sensor 78a for detecting the temperature of the heated water. The air heat exchanger 76 is an evaporator for absorbing heat from the ambient atmosphere and has a blower 76a to raise the heat exchange efficiency and a temperature sensor 76b to detect the ambient atmosphere.

A refrigerant pipe 79 is used to connect the compression mechanism 42, the water heat exchanger 78, the throttle device 77, and the air heat exchanger 76, thereby forming a refrigerant circulation passage. A refrigerant circulates along the refrigerant circulation passage formed by compression mechanism 42, water heat exchanger 78, throttle device 77, and air heat exchanger 76. The refrigerant pipe 79 is further connected to a bypass pipe

ES 2 425 481 T3 defrost 80 so that the refrigerant discharged from the compression mechanism 42 is supplied to the air heat exchanger 76 without passing through the water heat exchanger 78 and the throttle device 77. A bypass valve of Defrost 81 is arranged in a part of defrost bypass pipe 80.

The hot water storage unit 74 has a hot water storage tank 82 for storing hot water or water. A water supply pipe 83 for supplying water from the outside into the hot water storage tank 82 is connected to the water receiving port 82c of the hot water storage tank 82. Furthermore, a hot water supply pipe for use in a bathtub 84 for supplying hot water from the hot water storage tank 82 to a bathtub is connected to the hot water outlet port 82d of the hot water storage tank 82. Furthermore, a hot water supply pipe 85 for supplying the hot water stored in the tank 82 to the outside is connected to the water inlet-outlet port 82a of the hot water storage tank 82.

The water heat exchanger 78 of the refrigeration cycle unit 73 is connected to the hot water storage tank 82 by the water pipes 74a, 74b, 75a and 75b. Therefore, a water circulation passage is formed between the hot water storage tank 82 and the water heat exchanger 78.

The water pipe 74b is a pipe arranged on the side of the hot water storage tank and is used to supply water from the hot water storage tank 82 to the water heat exchanger 78. One end of the water pipe 74b is connected to the water outlet port 82b of the hot water storage tank 82, and the other end is connected to the water pipe 75b on the water supply side of the heat exchanger of the water 78 through a gasket 87b. Furthermore, a water discharge valve 86 for discharging water or hot water from the hot water storage tank 82 is installed at one end of the water pipe 74b.

The water pipe 74a is a pipe arranged on the side of the hot water storage tank and is used for the return of water from the water heat exchanger 78 to the hot water storage tank 82. One end of the water pipe 74a is connected to the water inlet-outlet port 82a of the hot water storage tank 82, and the other end is connected to the water pipe 75a on the discharge side of the heat exchanger. heat from the water 78 by means of a gasket 87a.

A pump 88 for circulating water through the water circulation passage is arranged in the middle of the water pipe 75b on the water supply side. Water pipe 75b is used to connect water heat exchanger 78 to joint 87b.

In the heat pump water heater 72 according to embodiment 19, the commanded rotational speed of the brushless motor 3 is determined based on the operating state of the heat pump water heater 72, that is, a target temperature of the hot water set on heat pump water heater 72, the temperature of the water supplied from the hot water storage unit 74 to the water heat exchanger 78 of the refrigeration cycle unit 73 and the temperature of the outside air. Then, the motor control apparatus 40 determines the necessary motor output for the brushless motor 3 of the compression mechanism 42 based on the commanded rotational speed.

Next, the operation of the heat pump water heater 72 according to Embodiment 19 will be described.

In the heat pump water heater 72 according to embodiment 19, when a driving voltage Cd is applied from the motor control apparatus 40 to the brushless motor of the compression mechanism 42, the compression mechanism 42 is driven. A high temperature refrigerant obtained by compression in compression mechanism 42 circulates in the direction indicated by arrows D. Therefore, the high temperature refrigerant is supplied from the comparison mechanism 42 to the water heat exchanger 78 through the refrigerant pipe 79. In addition, when the pump 88 is driven in the water circulation passage, water is supplied. from the hot water storage tank 82 to the water heat exchanger 78.

At this time, heat exchange takes place between the high-temperature refrigerant and the supplied water from the hot water storage tank 82, thereby transferring heat from the

ES 2 425 481 T3 water-based coolant. Therefore, the water supplied to the water heat exchanger 78 is heated, and the heated water is supplied to the hot water storage tank 82. At this time, the temperature of the heated water is monitored by the condensing temperature sensor. 78a.

Furthermore, the refrigerant in the water heat exchanger 78 is condensed by heat exchange and liquefied. The flow of the refrigerant liquid obtained by the condensation is throttled by the throttle device 77, whereby the refrigerant expands and is supplied to the air heat exchanger 76.

In the heat pump water heater 72 according to embodiment 19, the air heat exchanger 76 functions as an evaporator. The air heat exchanger 76 absorbs heat from the outside air sent by the blower 76a and evaporates the low temperature refrigerant. At this time, the ambient atmosphere temperature of the air heat exchanger 76 is monitored by the temperature sensor 76b.

Furthermore, in the refrigeration cycle unit 73, when the air heat exchanger 76 freezes, the defrost bypass valve 81 opens, the high temperature refrigerant is supplied to the air heat exchanger 76 through the exhaust pipe. defrost bypass 80. Therefore, the air heat exchanger 76 is defrosted.

On the other hand, hot water is supplied from the water heat exchanger 78 of the refrigeration cycle unit 73 to the hot water storage unit 74 via the water pipes 74a and 75a. The hot water supplied to the hot water storage unit 74 is stored in the hot water storage tank 82. The hot water stored in the hot water storage tank 82 is supplied outside through the hot water supply line 85 as needed. In particular, in the case where hot water is supplied to the bathtub, the hot water stored in the hot water storage tank 82 is supplied to the bathtub through the hot water supply pipe for bathtub use. 84.

Furthermore, in the case where the amount of the water or hot water stored in the hot water storage tank 82 is a constant value or less, water is filled from outside through the water supply pipe 83.

In the heat pump water heater 72 according to embodiment 19, the commanded rotational speed of the brushless motor 3 is determined by the motor control apparatus 40 based on a target hot water temperature set in the water heater. of heat pump 72, the temperature of the water supplied to the water heat exchanger 78 and the temperature of the outside air. In the heat pump water heater 72 according to embodiment 19, the rotational speed of the brushless motor 3 of the compression mechanism 42 is controlled by the motor control apparatus 40 based on the commanded rotational speed, just as in the case of embodiment 13 mentioned above. As a result, in the heat pump water heater 72 according to embodiment 19, hot water having the target temperature can be safely supplied.

Since the engine control apparatus 40 which is compact in size and light weight is used for the heat pump water heater 72 according to Embodiment 19 as described above, the heat pump water heater 72 is It can make it smaller and lighter than a conventional heat pump water heater. Therefore, in the heat pump water heater according to the present invention, the ease of installation is improved due to the reduction in size and is also improved due to the reduction in weight. Furthermore, the cost of the heat pump water heater according to the present invention can be significantly reduced relative to that of the conventional heat pump water heater, whereby the heat pump water heater has more benefits. for the user.

In the heat pump water heater 72 according to embodiment 19 of the present invention, the motor control apparatus 40 for driving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of embodiments 1 to 11 mentioned above.

The present invention explained in the descriptions of embodiments 1 to 19 is applicable not only to the motor control apparatus to be installed in the apparatuses mentioned in the descriptions of the above-mentioned embodiments, but also in other motor control apparatuses for driving motors. brushless using inverter circuits. By making the motor control apparatus smaller and lighter, the design degrees of freedom of any corresponding apparatus can be improved, and the apparatus can be supplied at a lower cost, whereby the effect of the present invention is highly significant.

ES 2 425 481 T3

The significance of the effect will be described with respect to an air conditioner and a compressor built into the air conditioner.

Most of the home use air conditioners sold in Japan are inverter controlled and save a lot of energy compared to air conditioners that are not inverter controlled. Therefore, the energy consumption of an air conditioner sold in Japan is about half the energy consumption of an air conditioner produced ten years earlier. Inverter-controlled air conditioners have become widely used in Japan. However, from a global point of view, the vast majority of air conditioners are not inverter controlled. Therefore, it is desired that the air conditioners available in the world be inverter controlled, from the point of view of promoting energy saving and conservation of the global environment.

Commercial products in the form of air conditioners that incorporate compressors predominate in Japan. However, in countries other than Japan, commercial products are often supplied as discrete compressors. In the markets for such discrete compressors, there is a demand for compressors of equal or smaller size than conventional compressors. Therefore, if a compressor is larger than the conventional compressor by adding an inverter circuit, the compressor cannot gain market acceptance. Thus, it is difficult to make inverter controlled compressors in the world and promote energy saving. Therefore, it is necessary to provide a compressor incorporating an inverter, which is equal to a conventional compressor in performance and which is equal in size to or smaller than the conventional compressor.

As described above, the present invention can provide a motor control apparatus configured without using an inductor to improve power factor and a filter capacitor having a large capacitance, that is, large components incorporated in a power factor apparatus. conventional motor control. Therefore, the present invention can provide a compressor incorporating a compact motor control apparatus, which is equal in size to or smaller than the conventional compressor. The present invention can thus promote energy saving worldwide and can be significantly beneficial to the conservation of the global environment.

In the descriptions of each of the aforementioned embodiments, a configuration in which a supplied AC voltage is rectified and fed into an inverter circuit has been taken as an example. However, the present invention is not limited to this type of configuration. In the present invention, even if a fluctuating voltage is introduced into the inverter circuit, the voltage is converted to a desired voltage by the inverter circuit and sent to a brushless motor. For example, in the case where a plurality of loads are connected to a DC power source, just as in the case of vehicle-mounted brushless motors, the output voltage of the DC power source fluctuates depending on the conditions. operation of the loads. Although this fluctuating DC power source is connected to the motor control apparatus according to the present invention, the voltage is converted to a desired voltage by the inverter circuit. Therefore, the motor control apparatus can precisely drive the corresponding brushless motor.

The engine control apparatus according to the present invention can also be applied to a vehicle-mounted air conditioner driven by a brushless motor. The engine control apparatus according to the present invention is beneficial for a vehicle whose engine stops during vehicle stop and starts when the vehicle is started, for example, a vehicle stopped in idle or the like in which idling engine stops during vehicle stop. When the engine is started, the power supply voltage drops instantly. However, in the case where the engine control apparatus according to the present invention is mounted on the compressor of a vehicle-mounted air conditioner, the voltage applied to its brushless motor can be adjusted even when the source voltage power drops instantly when engine is started. Therefore, the brushless motor does not stop temporarily, so the vehicle-mounted air conditioner can operate continuously. As described above, the engine control apparatus according to the present invention is especially beneficial for a vehicle or the like whose engine stops during vehicle stoppage and starts when the vehicle is started, for example a stop-motion vehicle. in vacuum or the like in particular.

Furthermore, the phase detection method using the current supplied to a brushless motor without using a position sensor in each of the aforementioned embodiments has been explained using said method described in the thesis “Control of a sensorless salient-pole brushless DC motor on the basis of estimation of speed electromotive force ”by Takeshita, Ichikawa, Lee and Matsui, Thesis Journal, Vol. 117-D, No. 1, pages 98-104, published by the Japan Institute of Electrical Engineers in 1997. However, the present invention is not limited to

ES 2 425 481 T3 to this method. Any method in which the phase is detected using current supplied to a brushless motor can be applied to the present invention.

As detailed descriptions of the above-mentioned embodiments have made clear, the present invention has the following effects.

The present invention can provide a compact motor control apparatus whose rectifier circuit can be made smaller and which can have a configuration with a position sensor and a configuration without a position sensor.

Furthermore, the present invention can provide a motor control apparatus capable of carrying out sensorless driving of a brushless motor without stopping the application of voltage to the brushless motor even though the input voltage to the inverter circuit is pulsing significantly.

Furthermore, the present invention can provide a motor control apparatus capable of continuously carrying out voltage application without stopping voltage application to the motor even when the DC side voltage of the inverter circuit is low.

Furthermore, according to the present invention, even in the case where sensorless drive is carried out where the phase information of the motor of a brushless motor is not obtained from a position sensor, the voltage application can be carried out performed continuously without stopping the application of voltage to the motor. Therefore, the phase of the motor can be estimated, whereby the present invention can provide a motor control apparatus capable of driving a brushless motor without using a position sensor.

In addition, according to the present invention, unnecessary errors for a current control apparatus do not overlap, thus no unnecessary current flows from the motor, and the precision of the sensorless estimation can be improved. Thus, it is possible to provide a motor control apparatus having high precision and stability.

Furthermore, the present invention can provide a motor control apparatus capable of significantly improving the output torque of a motor without using a filter capacitor having a large capacitance in the rectifier circuit of the motor control apparatus. In the motor control apparatus according to the present invention, even when the input voltage of the inverter circuit pulses and a desired voltage cannot be applied to the motor, the phase of the voltage applied to the motor can be maintained. Therefore, it is possible to reduce wasted motor current and decrease motor stall due to overcurrent.

Furthermore, the motor control apparatus according to the present invention can carry out an accurate phase estimation. Therefore, the motor control apparatus can carry out sensorless motor driving and can be applied to compressors for air conditioners, refrigerators, etc.

Furthermore, according to the present invention, the current tracking operation of the motor can be improved. Therefore, the present invention can provide a motor control apparatus that has high efficiency, generates low noise, and improves the output torque of a motor.

Furthermore, the present invention can provide a motor control apparatus capable of being configured without using an inductor to improve the power factor and a filter capacitor having a large capacitance, that is, large components incorporated in a power control apparatus. conventional motor. Therefore, the present invention can provide a compressor incorporating a motor control apparatus, equal in size to or smaller than a conventional compressor. The present invention can thus promote energy saving worldwide and can be significantly beneficial to the conservation of the global environment.

Furthermore, in the motor control apparatus according to the present invention, in the case where the output voltage of the single-phase AC power source is low to the point that the voltage applied to a brushless motor is insufficient, it is It can raise the input voltage of the inverter circuit. Therefore, the present invention can provide a motor control apparatus capable of raising the maximum rotational speed of the brushless motor and significantly expanding the operating range of the motor.

Furthermore, according to the present invention, the waveform of the current flowing to the single-phase AC power source is nearly sinusoidal driving the boost circuit and the control section of the boost circuit. Therefore, the power factor of the power supply becomes almost one. The present invention can

ES 2 425 481 T3 so as to provide a motor control apparatus that does not adversely affect the power supply system.

Furthermore, in the motor control apparatus according to the present invention, the capacitance of one of the two capacitors of the double voltage rectifier boost circuit thereof can be made lower, whereby the double voltage rectifier boost circuit can be made smaller than a conventional dual voltage rectifier circuit.

21 members in 8 offices

This recordMember, by publication datePriority claim

Priority claims10

Priority claims
Document	Office	Kind	Date
2002361156	Japan	A	2002-12-12
2002361156	Japan	A	2002-12-12
2002361156	Japan	–	2002-12-12
2003154938	Japan	A	2003-05-30
2003154938	Japan	A	2003-05-30
2003154938	Japan	–	2003-05-30
2002361156	–	–	–
2003154938	–	–	–
JP20020361156	–	–	–
JP20030154938	–	–	–

Members21

Family members, oldest first
Document	Office	Kind
EP1429450A1	European Patent Office (EPO)	A1	2004-06-16
KR20040051554A	Republic of Korea	A	2004-06-18
CN1507145A	China	A	2004-06-23
US2004124807A1	United States of America	A1	2004-07-01
JP2005020986A	Japan	A	2005-01-20
US6984948B2	United States of America	B2	2006-01-10
EP1843463A2	European Patent Office (EPO)	A2	2007-10-10
CN100359794C	China	C	2008-01-02
EP1429450B1	European Patent Office (EPO)	B1	2008-02-13
AT386362T	Austria	T	2008-03-15
ATE386362T1	Austria	T1	2008-03-15
DE60319053D1	Germany	D1	2008-03-27
ES2300538T3	Spain	T3	2008-06-16
JP4416486B2	Japan	B2	2010-02-17
KR101006589B1	Republic of Korea	B1	2011-01-07
EP1843463A3	European Patent Office (EPO)	A3	2011-09-14
EP2573935A2	European Patent Office (EPO)	A2	2013-03-27
EP2573935A3	European Patent Office (EPO)	A3	2013-04-03
EP1843463B1	European Patent Office (EPO)	B1	2013-07-03
ES2425481T3This record	Spain	T3	2013-10-15
EP2573935B1	European Patent Office (EPO)	B1	2019-01-16

Motor control apparatus

Abstract

Term

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DESCRIPTION

BACKGROUND OF THE INVENTION

GENERAL DESCRIPTION OF THE INVENTION

BRIEF DESCRIPTION OF THE DRAWINGS

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DETAILED DESCRIPTION OF THE INVENTION

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Priority claims10

Members21

Numbers

Titles2

Classification