ES2300538T3

Motor control apparatus

Abstract

A motor control apparatus including: an inverter circuit (2) that receives a fluctuating input voltage (Vpn), converts said voltage to a desired voltage and sends said desired voltage as an application voltage to a brushless motor (3), and a control section (4 ) which receives the input voltage (Vpn) to said inverter circuit, a motor current flowing to said brushless motor (3) and a motor current order value (Id *, Iq *) indicating the value of a current that has to circulate to said brushless motor (3) and sends order voltage values from motor application to said inverter circuit, characterized in that the control section - determines an axis coordinate d (Vd) and an axis coordinate q (Vq) of a voltage order vector based on said motor current order value (Id *, Iq *) , - calculates a value (V1) based on the norm of said voltage order vector (Vd, Vq) - compares said value (V1) with said input voltage (Vpn) to said inverter so that when said value (V1 ) is higher than said input voltage value (Vpn), said d-axis coordinate (Vd) and said q-axis coordinate (Vq) are corrected by a factor KK = Vpn / V1 - calculates said motor application voltage order values based on said corrected d-axis coordinate (Vd ) and said corrected axis coordinate (Vq).

ES2300538T3, drawing sheet 1 — Sheet 1 of 43

Term

Term ended

Projected expiry passed 10 December 2023, 2.8 years ago.

1 claim: 1 independent, 0 dependent

1
ES 2 300 538 T3 REIVINDICACIONES 1. Un aparato de control de motor incluyendo:un circuito inversor (2) que recibe un voltaje de entrada fluctuante (Vpn), convierte dicho voltaje a un voltaje deseado y envía dicho voltaje deseado como un voltaje de aplicación a un motor sin escobillas (3), y una sección de control (4) que recibe el voltaje de entrada (Vpn) a dicho circuito inversor, una corriente de motor que fluye a dicho motor sin escobillas (3) y un valor de orden de corriente de motor (Id*,Iq*) que indica el valor de una corriente que tiene que circular a dicho motor sin escobillas (3) y envía valores de orden de voltaje de aplicación a motor a dicho circuito inversor, caracterizado porque la sección de control - determina una coordenada de eje d (Vd) y una coordenada de eje q (Vq) de un vector de orden de voltaje en base a dicho valor de orden de corriente de motor (Id*, Iq*), - calcula un valor (V1) basado en la norma de dicho vector de orden de voltaje (Vd, Vq) - compara dicho valor (V1) con dicho voltaje de entrada (Vpn) a dicho inversor de modo que cuando dicho valor (V1) sea más alto que dicho valor de voltaje de entrada (Vpn), dicha coordenada de eje d (Vd) y dicha coordenada de eje q (Vq) sean corregidas por un factor K K=Vpn/V1 - calcula dichos valores de orden de voltaje de aplicación a motor en base a dicha coordenada de eje d corregida (Vd) y dicha coordenada de eje q corregida (Vq).

326 paragraphs in 21 sections, as filed

ES 2 300 538 T3

DESCRIPTION

Engine control device.

Background of the invention

The present invention relates to a motor control apparatus for controlling brushless motors incorporated in air conditioners, refrigerators, washing machines, fans, etc., using an inverter circuit.

Fig. 33 is a block diagram showing the configuration of a conventional motor control apparatus for driving a brushless motor. In the following descriptions, the conventional motor control apparatus shown in Fig. 33 is referred to as a first conventional technology. In Figure 33, the number 101 designates an AC power source, the number 102 designates an inductor, the number 103 designates a rectifier diode, the number 104 designates a filtering capacitor, the number 106 designates an inverter circuit, the number 107 designates a brushless motor, and the number 108 designates a position sensor. In the case where the AC voltage supplied from the AC power source 101 is converted to a DC voltage using the rectifier diode 103 and the filtering capacitor 104 so that a DC power enters the inverter circuit 106, the current supplied from the AC power source 101 flows only when the voltage of the filter capacitor 104 is lower than the supplied AC voltage. Therefore, the current supplied from the AC power source 101 has harmonic components. Therefore, in the first conventional technology, the inductor 102 is arranged between the AC power source 101 and the rectifier diode 103 to reduce harmonic components and improve the power factor. As described above, in addition to rectifier diode 103, inductor 102 and filter capacitor 104 are used in first conventional technology rectifier circuit 105. Also, in the case where the brushless motor 107 is driven by the inverter, the information of the rotation angle of the rotor is needed. For this, in the first conventional technology, the angle of rotation was detected using the position sensor 108. As an example of this first conventional technology, an engine control apparatus described in published Japanese Patent Application No. Hei 9-74790 has been proposed.

The inductor 102 and the filtering capacitor 104 of the rectifier circuit 105 for use in the first conventional technology are large components having a large inductance and a large capacitance, respectively, in many cases. As a result, the conventional motor control apparatus often has to be large in size and high in price. In the field of motor control apparatus, a rectifier circuit that incorporates compact components such as an inductor that has a small inductance and a capacitor that has a small capacitance or a rectifier circuit that does not incorporate these components is in demand, from the point of view of view of making the apparatus smaller in size and lower in cost.

In this situation, such a motor control apparatus incorporating no inductor or filtering capacitor as shown in Fig. 34 has been proposed as a second conventional technology. As an example of this second conventional technology, an engine control apparatus described in published Japanese Patent Application No. Hei 10-150795 has been proposed. Since no filtering capacitor is used in the second conventional technology, the input voltage supplied to the inverter circuit 106 is not a DC voltage, but a pulsating voltage. If this type of pulsing voltage is input to inverter circuit 106, when the input voltage supplied to inverter circuit 106 is low, inverter circuit 106 cannot generate a desired voltage to apply to brushless motor 107 in some cases. In the case where the desired voltage cannot be obtained by the second conventional technology, the phase of the voltage to be applied to the brushless motor 107 is advanced. By advancing the phase of the voltage to be applied to the brushless motor 107, the so-called weak field state can be obtained, whereby the required voltage to be applied to the brushless motor 107 can be lower. Therefore, with the second conventional technology, the brushless motor 107 can be continuously driven even when the input voltage supplied to the inverter circuit 106 is low. However, in the second conventional technology, in the case where the input voltage supplied to the inverter circuit 106 is a predetermined value or less, the switching operation of the inverter circuit 106 is stopped. This is because the drive of the motor in the weak field state is limited. As described above, the second conventional technology is configured so that no voltage is applied to the brushless motor 107 in the case where the input voltage supplied to the inverter circuit 106 is the predetermined value or less.

In addition, a motor control apparatus that does not use a position sensor is demanded from the point of view of wireless manufacturing and reducing the cost. In this situation, a method of estimating the rotor position of a brushless motor by sensing the motor current is proposed as a third conventional technology. In the third conventional technology, the rotor position of the motor is estimated using a calculation equation to estimate the derived phase based on a voltage equation of a motor current, a voltage applied to the brushless motor at the same time as the current of motor flows, and motor constants, such as resistance, inductance, etc., of the brushless motor. An example of this third conventional technology is described in a thesis “Control of a sensorless salient-pole brushless DC motor on the basis of estimation of speed electromotive force (Back EMF Estimation-Based Sensorless Salient-Pole brushless DC Motor Drives)” by Takeshita , Ichikawa, Lee and Matsui, Thesis Journal, Vol. 117D, No. 1, pages 98-104, published by the Institute of Electrical Engineers of Japan in 1997 (T.IEE Japan, Vol. 117D, No. 1, 97) .

ES 2 300 538 T3

As described above, in the first conventional technology, the rotor position of a brushless motor is detected using a position sensor, and an inductor and a filtering capacitor are used to convert the input voltage supplied to an inverter circuit. at a DC voltage. Therefore, since the inductor and the filtering capacitor are large components having a large inductance and a large capacitance, respectively, it is difficult to make the motor control apparatus incorporating these components smaller.

Furthermore, the second conventional technology is a motor control apparatus in which the rotor position of a brushless motor is detected using a position sensor, without using large components such as an inductor and a filtering capacitor. This technology is thus effective from the point of view of making the apparatus smaller and cheaper. However, since the input voltage supplied to the inverter circuit pulses in the second conventional technology, this causes the problem of stopping the application of voltage to the brushless motor when the input voltage is a predetermined value or less.

A problem described below occurs in the case where an attempt is made to build a lower cost and smaller size sensorless motor control apparatus by combining the second conventional technology configured to use no inductor and no filtering capacitor with the third conventional technology. configured to implement sensorless motor drive. In the motor control apparatus having this kind of configuration, the rotor position cannot be estimated in the periods when the voltage application to the brushless motor is stopped. Therefore, sensorless drive of the brushless motor was impossible. In other words, in the case where the input voltage supplied to the inverter circuit pulses, a sensorless motor control apparatus cannot be constructed by the simple combination of the second conventional technology and the third conventional technology.

The PhD thesis “Contribution to the integration des systemes de commande des machines electriques a courant alternatif” by P. Foussier, 1998, INSA of Lyon, describes a motor control device in which an inverter circuit receives a voltage Vbat, converts said voltage to a desired voltage and sends that desired voltage to a brushless motor. A control section maintains the phase of the voltage vector in the dp coordinate system using a PWM control method: a voltage vector application time (Ti, Ti+i) defines the required voltage value to apply to the brushless motor. If time (Ti + Ti + i) is higher than a switching time Tcom which corresponds to the maximum applicable voltage value Vbat, then the voltage vector is limited by the relation Tcom/ (Ti+ Ti + i) thus maintaining the phase of the voltage vector.

General description of the invention

An object of the present invention is to provide a compact motor control apparatus having a compact rectifier circuit and capable of being configured with and without a position sensor. Furthermore, another object of the present invention is to provide a motor control apparatus capable of performing sensorless driving without stopping the application of voltage to a brushless motor even though the input voltage of the inverter circuit is pulsing significantly.

In order to achieve said objects, a motor control apparatus according to the present invention is set forth in claim 1.

The motor control apparatus according to the present invention configured as described above can continuously apply a voltage to the brushless motor without stopping the voltage application, even when the DC side voltage of the inverter circuit is low.

In the motor control apparatus according to the present invention, its control section may be configured to estimate the rotation phase of the brushless motor based on the motor current. With this configuration, even in the case where sensorless drive is carried out where the phase information of the brushless motor is not obtained from a position sensor, the motor control apparatus can continuously implement the voltage application without stopping the application of voltage to the motor. Therefore, the phase of the motor can be estimated, and the motor can be moved without using a position sensor.

In the motor control apparatus according to the present invention, its control section may be configured to stop integral control when the voltage value across said inverter circuit is less than the voltage command value to be applied to said motor without brushes. With this configuration, unnecessary errors for a control apparatus for current control are not overlapped, whereby no unnecessary current flows from the motor and the accuracy of the sensorless estimation can be improved. Thus, it is possible to provide a motor control apparatus capable of stably performing excellent control.

In the motor control apparatus according to the present invention, its control section may be configured to calculate said voltage command value using a calculation equation having a non-interacting term. In the motor control apparatus according to the present invention, the feedback control has a non-interacting term as described above. Therefore, the independence of the current control system is improved, the accuracy of the sensorless estimation is further improved, and a more stable operation is achieved.

ES 2 300 538 T3

In the motor control apparatus according to the present invention, its control section may be configured to detect the voltage of said inverter circuit, estimate a voltage to be applied to said inverter circuit in the next control cycle, and control said inverter circuit. In the case where the input voltage of the inverter circuit pulses significantly, an error occurs between the detection result and the actual voltage, particularly when the control cycle of the inverter circuit is long. However, using the detected voltage of the inverter circuit, the control section estimates a voltage to be applied to the inverter circuit in the next control cycle and carries out the control, whereby the control section can accurately estimate the input voltage. inverter circuit. As a result, a more accurate voltage can be applied to the brushless motor. Therefore, the present invention can provide a more excellent motor control apparatus.

The motor control apparatus according to the present invention may be configured to incorporate a capacitor having a small capacitance on the input side of said inverter circuit. In the motor control apparatus according to the present invention configured as described above, a regenerative current from the motor flows to a capacitor. Therefore, it is possible to avoid abnormal rise of the input side voltage of the inverter main circuit due to regenerative current. Therefore, the apparatus has a function of protecting the circuit against overvoltage, thereby being highly safe.

The motor control apparatus according to the present invention may be configured to incorporate an inductor having a small inductance on the input side of said inverter circuit. The motor control apparatus according to the present invention configured as described above outputs a current having a smooth waveform, thereby being capable of eliminating harmonic components. Therefore, the apparatus has a higher power utilization rate.

The motor control apparatus according to the present invention may be configured to further include a boost circuit having an inductor, diodes, switching devices and a capacitor, and a control circuit boost section for controlling said boost circuit, where said control circuit boost section is configured to determine the working value of said switching device based on a signal from said control section. In the motor control apparatus according to the present invention configured as described above, the boost circuit can raise the input side voltage of the inverter circuit. Therefore, the maximum rotational speed of the brushless motor can be increased, and the brushless motor can operate in a wider range of rotational speeds.

In the motor control apparatus according to the present invention the control circuit boost section, which is configured to receive the sensed voltage phase and AC current from an AC power source, may be configured to include a command section of AC current that sends an AC current command value based on said detected phase and a control signal from said control section, and a PWM command generation section that generates PWM command values to move said switching devices based on said AC current command value and said detected AC current from said AC power source and outputs said PWM command values. The engine control apparatus according to the present invention configured as described above does not adversely affect the power source system.

The motor control apparatus according to the present invention may be configured to further include a boost circuit having an inductor into which a fluctuating voltage is input, a plurality of diodes forming a rectifier circuit, switching devices connected to said circuit rectifier and that perform the on / off operation, and a capacitor that sends a high voltage, and

A control circuit lift section for controlling said lift circuit. The motor control apparatus according to the present invention configured as described above can significantly expand the operating range of a motor, although the configuration of the apparatus is simple.

In the engine control apparatus according to the present invention, it is preferred to set

C% 2 x 10 'x P assuming that the capacitance of said capacitor is C [F] and that the maximum output of said motor is P [W].

In the motor control apparatus according to the present invention, which incorporates an inductor having a small inductance on the input side of said inverter circuit, it is preferred to set

L% 9 x 10-9 / C assuming that the inductance of said inductor is L [H] and that the capacitance of said capacitor is C [F].

ES 2 300 538 T3

In the engine control apparatus according to the present invention, it is preferred to set

L% P x 10-6 assuming that the inductance of said inductor is L [H] and that the maximum power output of said motor is P [W].

The motor control apparatus according to the present invention configured as described above can be used for compressors, air conditioners, refrigerators, electric washing machines, electric dryers, fans, electric vacuum cleaners and heat pump water heaters. The motor control apparatus can continuously apply a desired voltage to a drive source without stopping the application of voltage even when the DC side voltage of the inverter circuit is low. Therefore, the motor control apparatus can drive each of said apparatus with high efficiency.

Although the novel features of the invention are set forth in particular in the appended claims, the invention, both in terms of organization and content, will be better understood and appreciated, together with its other objects and features, by the following detailed description taken in conjunction with the drawings.

Brief description of the drawings

Fig. 1 is a block diagram showing a configuration of an example motor control apparatus.

FIG. 2 is a block diagram showing a configuration of an example PWM generation section.

Fig. 3 is a flow chart showing an operation of an example correction section Vpn.

Fig. 4A is a graph representing a result of an experimentally measured motor current, etc., under the control of the conventional motor control apparatus.

Fig. 4B is a graph showing a result of an experimentally measured motor current, etc., under the control of the motor control apparatus according to Embodiment 1.

Fig. 5 is a block diagram of a PWM generation section of a motor control apparatus according to Embodiment 2 of the present invention.

Fig. 6 is a flow chart showing an operation of a ratio correction section according to Embodiment 2 of the present invention.

Fig. 7 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 3 of the present invention.

Fig. 8A is a graph showing a result of an experimentally measured motor current, etc., by the conventional motor control apparatus.

Fig. 8B is a graph showing a result of an experimentally measured motor current, etc., by the motor control apparatus according to Embodiment 3.

Fig. 9 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 4 of the present invention.

Fig. 10 is a graph showing a result of an experimentally measured motor current, etc., by the motor control apparatus according to Embodiment 4 of the present invention.

Fig. 11 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 5 of the present invention.

Fig. 12 is a graph showing a result of an experimentally measured motor current, etc., by the motor control apparatus according to Embodiment 5 of the present invention.

Fig. 13 is a graph representing a result of an experiment indicating the limit torque of a brushless motor by a motor control apparatus according to the present invention and the conventional motor control apparatus.

Fig. 14 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 7 of the present invention.

ES 2 300 538 T3

Fig. 15 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 8 of the present invention.

Fig. 16A is a block diagram showing a configuration of a motor control apparatus according to Embodiment 9 of the present invention.

Fig. 16B is a circuit diagram showing another configuration of a boost circuit of the motor control apparatus according to Embodiment 9 of the present invention.

Fig. 17 is a waveform diagram showing an input waveform to a boost circuit of the motor control apparatus according to Embodiment 9 of the present invention.

Fig. 18 is a waveform diagram showing an operation of the motor control apparatus according to Embodiment 9 of the present invention.

Fig. 19 is a block diagram showing a configuration of a motor control apparatus according to Embodiment 10 of the present invention.

Fig. 20 is a block diagram showing a configuration of a control circuit boost section of the motor control apparatus according to Embodiment 10 of the present invention.

Fig. 21 is a waveform diagram showing an operation of the motor control apparatus according to Embodiment 10 of the present invention.

Fig. 22 is a block diagram showing another configuration of a control circuit boost section of the motor control apparatus according to Embodiment 10 of the present invention.

Fig. 23A is a block diagram showing a configuration of a motor control apparatus according to Embodiment 11 of the present invention.

Fig. 23B is a circuit diagram showing another configuration of a dual voltage rectifier boost circuit of the motor control apparatus according to Embodiment 11 of the present invention.

Fig. 24 is a waveform diagram showing an operation of the motor control apparatus according to Embodiment 11 of the present invention.

Fig. 25 is a block diagram showing the configuration of the compressor according to Embodiment 12 of the present invention.

Fig. 26 is a block diagram showing the configuration of an air conditioner according to Embodiment 13 of the present invention.

Fig. 27 is a block diagram showing the configuration of a refrigerator according to Embodiment 14 of the present invention.

Fig. 28 is a block diagram showing the configuration of an electric washing machine according to Embodiment 15 of the present invention.

Figure 29 is a block diagram showing the configuration of an electric dryer according to Embodiment 16 of the present invention.

Fig. 30 is a block diagram showing the configuration of a fan according to Embodiment 17 of the present invention.

Fig. 31 is a block diagram showing the configuration of an electric vacuum cleaner according to Embodiment 18 of the present invention.

Fig. 32 is a block diagram showing the configuration of a heat pump water heater according to Embodiment 19 of the present invention.

Fig. 33 is the block diagram showing the configuration of the motor control apparatus as the first conventional technology.

Fig. 34 is the block diagram showing the configuration of the motor control apparatus as the second conventional technology.

It will be recognized that some or all of the figures are schematic representations for purposes of illustration and do not necessarily illustrate the actual relative sizes or positions of the items depicted.

ES 2 300 538 T3

Detailed description of the invention

Engine control apparatus according to preferred embodiments of the present invention will now be described with reference to accompanying figures 1 to 32.

Example of a motor control device

Fig. 1 is a block diagram showing the configuration of an example of a motor control apparatus. In Figure 1, the AC power output from a single-phase AC power source 5 is rectified to pulsed DC power by a rectifier circuit 1 and applied to an inverter circuit 2. The inverter circuit 2 converts the rectified DC power to an AC power and applies a desired voltage to a brushless motor 3. A control section 4 detects the current flowing to the brushless motor 3 and drives and controls the inverter circuit 2 the control section 4 includes a dq conversion section 6, a d-axis PI controller 7, a q-axis PI controller 8, a PWM generation section 9, subtractor means, etc.

Next, the operation of the control section 4 of the example will be described.

The dq 6 conversion section calculates a d-axis current detection value Id and a q-axis current detection value Iq according to the following equation (1) using the current detection values Iu, Iv and Iw flowing at the three-phase windings of the brushless motor 3. In the case that the brushless motor 3 has a position sensor, the position signal from the position sensor is used as a rotation phase θ for this calculation. In the case that the brushless motor 3 does not have a position sensor, an estimated phase obtained as a result of estimating the rotor position is used as the rotation phase θ.

The error between an axis current command value d Id * calculated on the basis of a rotation command, a torque command, etc., coming from outside and an axis current detection value d Id output from the conversion section dq 6 is input to the d-axis PI controller 7. The error is PI controlled by the d-axis PI controller 7 and a d-axis voltage command value is generated Vd. The error between an axis current command value q Iq * calculated on the basis of a rotation command, a torque command, etc., coming from outside and an axis current detection value q Iq output from the conversion section dq 6 is input to the q 8 axis PI controller, just as in the case of the d 7 axis PI controller. The error is PI controlled by the q 8 axis PI controller and an axis voltage command value is generated q Vq.

The PWM generation section 9 generates a PWM signal to drive the inverter circuit 2 from the axis voltage command value d Vd, the axis voltage command value q Vq, and an input voltage detection value Vpn obtained. detecting the voltage introduced in the inverter circuit 2, and sends the PWM signal.

Figure 2 is a block diagram representing the configuration and operation of the PWM generation section 9. As shown in Figure 2, the PWM generation section 9 has a reverse dq conversion section 10, a line modulation section to line 11 and a correction section Vpn 12.

The reverse dq conversion section 10 calculates sinusoidal three-phase voltage command values Vu, Vv, and Vw from the d-axis voltage command value Vd and the q-axis voltage command value Vq according to the following equation (2) . In the case where the brushless motor 3 has a position sensor, its position signal is used as a rotation phase θ for this calculation. In the case where the brushless motor 3 has no position sensor, an estimated phase obtained as a result of estimating the rotor position is used as the rotation phase fase.

ES 2 300 538 T3

The line-to-line modulation section 11 detects the minimum value of the entered sinusoidal three-phase voltage command values Vu, Vv and Vw and outputs the results obtained by subtracting the minimum detected value from the sinusoidal three-phase voltage command values as Vu ', Vv 'and Vw'. Therefore, at least the sinusoidal order value of a phase is zero, and the remaining biphasic sinusoidal order values are positive values.

The correction section Vpn 12 receives the outputs Vu ', Vv' and Vw 'from the line-to-line modulation section 11 and also receives the input voltage detection value Vpn, and generates PWM output work values Du, Dv and Dw. The PWM output work values Du, Dv and Dw are obtained according to equation (3) or (4) described below.

Fig. 3 is a flow chart showing a calculation method performed by the correction section Vpn 12.

The maximum value of the three-phase output values Vu ', Vv' and Vw 'supplied from the line-to-line modulation section 11 is detected, and the value is set as the maximum application voltage value Vmax (in step 31) . Next, the maximum application voltage value Vmax is compared with the input voltage detection value Vpn in magnitude (in step 32). In the case where the input voltage detection value Vpn is greater than the maximum application voltage value Vmax in step 32, an ordinary calculation is carried out and the desired application voltage command values are applied to the motor. brushless 3. Therefore, the PWM output working values of phases U, V and W are determined according to the following equation (3) (in step 33).

On the other hand, in the case where the input voltage detection value Vpn is less than the maximum application voltage value Vmax, the desired application voltage order values cannot be applied to the brushless motor 3. It is applies the maximum voltage that can then be generated, while the phases of the applied voltages are not changed. For this purpose, the PWM output work values of phases U, V and W are determined according to the following equation (4) (in step 34).

------------ (4) V max

By the calculation according to said equation (4), the relations of the phases U, V and W are the same as the relations obtained before the calculation according to equation (4), so voltages are applied to the brushless motor 3 while they maintain the phases of the applied voltages.

Fig. 4A is a graph representing a result of an experiment regarding motor current under the control of a conventional motor control apparatus. Fig. 4B is a graph representing a result of an experiment regarding the motor current of the example in the case where equation (4) is used for the correction section Vpn 12. In Figures 4A and 4B, the input voltage detection value Vpn, the motor current, the motor current command value and the motor application voltage phase are represented in this sequence from above. In the experiment from which the result shown in Fig. 4A is obtained, a motor control apparatus having the configuration of said first conventional technology was used as the conventional motor control apparatus.

In the conventional motor control apparatus, when the input voltage detection value Vpn serving as the input voltage to the inverter circuit is small, a current significantly deviated from a desired current flows in the brushless motor. This type of current reduces the efficiency of the motor and increases noise. Also, if a large current flows, the motor magnets become demagnetized, which can cause problems. Also, the maximum value of the current is higher when the load applied to the brushless motor is higher. Therefore, the rated current of the inverter circuit must be increased when the brushless motor is driven at a predetermined load. Therefore, you have to use an inverter circuit including expensive components. Furthermore, in the conventional motor control apparatus, when the input voltage detection value Vpn obtained by detecting the voltage input to the inverter circuit 2 is small, the phase of the voltage applied to the motor is disturbed, and the motor current fluctuates. significantly as depicted in Figure 4A.

On the other hand, in the case of using the motor control apparatus according to the example, the phase of the voltage applied to the motor is maintained. Therefore, the appropriate phase is applied to the brushless motor 3 even when the input voltage detection value Vpn is small. Furthermore, since the disturbance of the motor current over time is small, the efficiency of the motor is raised and the noise is reduced.

ES 2 300 538 T3

According to said results of experiments, since the motor current increases more than necessary in the conventional motor control apparatus, this results in the inverter circuit being larger and more expensive. In the case of the motor control apparatus of Example 1, the disturbance of the motor current is less, so that the motor control apparatus can be configured using a low current capacity inverter circuit and the like.

With the motor control apparatus according to the example, the rectifier circuit can be made smaller, and the apparatus can be configured with and without a position sensor. In addition, even if the input voltage of the inverter circuit pulses significantly, the motor control apparatus according to Embodiment 1 can implement sensorless drive without stopping the application of voltage to the brushless motor.

Embodiment 2

Next, a motor control apparatus according to Embodiment 2 of the present invention will be described. Fig. 5 is a block diagram showing the operation of the PWM generation section 90 of the motor control apparatus according to Embodiment 2. The configuration of the motor control apparatus according to Embodiment 2 is substantially identical to the configuration according to Embodiment 1, except for the PWM generation section 9 of the motor control apparatus according to Embodiment 1. Therefore, the PWM generation 90 will be described below.

As shown in Fig. 5, the PWM generation section 90 according to Embodiment 2 has a ratio correction section 13, an inverse dq conversion section 10, a line-to-line modulation section 11, and a ratio generation section 14. In Fig. 5, the operations of the reverse dq conversion section 10 and the line-to-line modulation section 11 are similar to those of said embodiment 1.

A calculation method performed by the ratio correction section 13 is depicted in the flow chart of Fig. 6. V1 is calculated from the d-axis voltage command value Vd and the q-axis voltage command value. Vq according to the following calculation equation (5) (in step 35). V1 is compared in magnitude with the input voltage detection value Vpn (in step 36).

In the case where the input voltage detection value Vpn is less in step 36, the axis voltage command value d Vd and the axis voltage command value q Vq are changed to Vd 'and Vq' , respectively, according to the following equation (6) and subsequently send (in step 37). In the case where the input voltage detection value Vpn is higher, the axis voltage command value d Vd and the axis voltage command value q Vq are sent directly.

The ratio generation section 14 performs the calculation according to said equation (3) and generates PWM output work values Du, Dv and Dw.

When the axis voltage command value d Vd and the axis voltage command value q Vq are changed to Vd 'and Vq', respectively, by the ratio correction section 13 according to equation (6) as has described above, the phase of the application voltage is maintained, even if a desired application voltage is not applied to the brushless motor 3.

The PWM generation section 9 of the motor control apparatus according to said embodiment 1 and the PWM generation section 90 of the motor control apparatus according to embodiment 2 differ from each other only in the calculation method performed in the middle. Therefore, the PWM output work values Du, Dv and Dw calculated by the PWM generation section 9 are the same as those calculated by the PWM generation section 90, provided that the conditions are the same.

The motor control apparatus according to Embodiment 2 of the present invention can continuously carry out the application of voltage to the brushless motor 3 without stopping the application of voltage, even when the DC side voltage of the inverter circuit is low. Furthermore, in Embodiment 2, even in the case where the sensorless drive is carried out under a circumstance where the phase information of the motor of the brushless motor 3 is not obtained from a position sensor, the continuous application of voltage Can be carried out non-stop applying voltage to brushless motor 3. Therefore, with the configuration of the motor control apparatus according to Embodiment 2, the phase of the brushless motor 3 can be estimated at all times, whereby the present invention can provide a motor control apparatus capable of moving a motor without using a position sensor.

ES 2 300 538 T3

Embodiment 3

Next, a motor control apparatus according to Embodiment 3 of the present invention will be described. Fig. 7 is a block diagram showing the configuration of the motor control apparatus according to Embodiment 3. The functions and configurations of the rectifier circuit 1, the inverter circuit 2, the brushless motor 3 and the single-phase AC power source 5 represented in figure 7 are similar to those of said embodiment 1. The control section 4a of the motor control apparatus according to embodiment 3 has a phase estimating section 15. The phase estimating section 15 outputs an estimated phase θ based on the axis current detection value d Id and the axis current detection value q Iq calculated by the conversion section dq 6 and the axis voltage command value d Vd 'and the axis voltage command value q Vq' sent from a PWM generation section 9a. The method of calculating the estimated phase θ is detailed in said thesis "Control of a sensorless salient-pole brushless DC motor on the basis of estimation of speed electromotive force" by Takeshita, Ichikawa, Lee and Matsui, Thesis Journal, Vol. 117- D, No. 1, pages 98-104, published by the Institute of Electrical Engineers of Japan in 1997 (T.IEE Japan, Vol. 117- D, No. 1, '97). Therefore, the explanation of the method is omitted here. The estimated phase θ obtained by the calculation is sent to the dq conversion section 6 and the PWM generation section 9a and used later.

The method of calculating the estimated phase θ described in said document "Control of a sensorless salient-pole brushless DC motor on the basis of estimation of speed electromotive force" will be explained here briefly with reference to figure 7. The section of estimation of phase 15 sets an estimated value of the rotor phase of brushless motor 3 and sets the error between the estimated value and the actual rotor phase of brushless motor 3. From a general voltage equation of a brushless motor, a voltage equation is established based on the estimated value of the rotor phase using the established error, as described above. The estimated speed of rotation of the brushless motor is calculated according to the equation. Feedback control is carried out so that the calculation result equals the actual rotational speed of the brushless motor. By performing feedback control continuously, said error can converge to zero, whereby the estimated phase θ becomes coincident with the actual rotor phase. Motor constants, such as the resistance and inductance values of the windings of the brushless motor 3, are used when establishing such a voltage equation. Furthermore, the voltage applied to the brushless motor 3 and the current flowing in time are also used for said voltage equation. The phase of the brushless motor 3 can be estimated using the applied voltage, current and constants of the brushless motor 3 as described above. Therefore, sensorless actuation is possible. An estimated rotational speed ω of the brushless motor 3 can also be calculated by differentiating the estimated phase θ.

In the motor control apparatus according to Embodiment 3, the axis voltage command value d Vd 'and the axis voltage command value q Vq' to be input in the phase estimation section 15 are made equal to the value axis voltage command value d Vd and axis voltage command value q Vq to actually be applied to the brushless motor 3 by the PWM generation section 9a, respectively. Therefore, even in the case where the DC side voltage of the inverter circuit 2 pulses, the phase estimation can be carried out properly, whereby the sensorless drive is possible. For example, in the case that the PWM generation section 9a according to embodiment 3 is configured based on said embodiment 2, the axis voltage command value d Vd 'and the axis voltage command value q Vq' output from the ratio correction section 13 represented in figure 5 should be sent only to the phase estimation section 15. On the other hand, in the case that the PWM generation section 9a is configured based on said embodiment 1, the sinusoidal three-phase voltages Vu, Vv and Vw only have to be calculated again from the PWM output work values Du , Dv and Dw and the input voltage detection value Vpn supplied from the correction section Vpn 12 shown in Fig. 2. Then, the d-axis voltage order value and the q-axis voltage order value obtained as the dq conversion result should only be sent to the phase estimation section 15.

Since the input voltage pulses, the input voltage detection value Vpn applied when determining the working values is different from the input voltage applied when the inverter circuit 2 actually carries out PWM operation. Therefore, without sending the voltage order values Vd 'and Vq' to the phase estimation section 15 at the ordering time, the d-axis and q-axis voltage order values can be calculated again using the input voltage detection value Vpn obtained when inverter circuit 2 actually carries out PWM operation and subsequently sent to phase estimation section 15. It goes without saying that the phase estimation accuracy is improved by this recalculation.

Fig. 8A is a graph representing the result of an experiment regarding phase estimation by the conventional motor control apparatus. Fig. 8B is a graph showing the result of an experiment regarding phase estimation by the motor control apparatus according to Embodiment 3 of the present invention. In Figures 8A and 8B, the upper waveform represents the input voltage detection value Vpn, and the lower waveform represents the estimated phase waveform. In the experiment depicted in Fig. 8A, a motor control apparatus configured by the simple combination of said second and third conventional technologies is used as the conventional motor control apparatus.

As shown in Fig. 8A, in the conventional motor control apparatus, the estimated phase is distorted when the input voltage detection value Vpn of the inverter circuit 2 is small, whereby the estimation result deviates from the actual phase. This results in a reduction in motor efficiency and an increase in noise. Also, when the motor load is large, the phase deviation is greater. This constitutes a serious problem of loss of synchronism and engine stall. As an apparatus for solving this kind of problem, the

ES 2 300 538 T3 present invention can provide the motor control apparatus according to Embodiment 3. As shown in Fig. 8B, the estimated phase in the motor control apparatus according to Embodiment 3 is linear and identical to the actual phase . Therefore, the motor control apparatus according to Embodiment 3 can implement excellent motor control without reducing the efficiency of the motor or increasing the noise, even though the apparatus has a sensorless configuration.

Embodiment 4

Next, a motor control apparatus according to Embodiment 4 of the present invention will be described.

Fig. 9 is a block diagram showing the configuration of the motor control apparatus according to Embodiment 4. The functions and configurations of the rectifier circuit 1, the inverter circuit 2, the brushless motor 3 and the single-phase AC power source 5 represented in Figure 9, are similar to those of Embodiment 1. The control section 4b according to embodiment 4 has a d-axis PI controller 7a and a q-axis PI controller 8a, a PWM generation section 9b, a dq conversion section 6, subtractor means, and so on.

The PWM generation section 9b according to embodiment 4 is configured to send an S signal to the d-axis PI controller 7a and the q-axis PI controller 8a when step 34 (the calculation of equation (4)) is carried out depending on the judgment result in step 32 (Fig. 3) in the calculation process of the correction section Vpn (Fig. 2) according to Embodiment 1.

When the PWM generation section 9b carries out step 34, that is, when the axis voltage command value d Vd is generated from the error between the axis current command value d Id * and the value of d-axis current detection Id In step 34, the d-axis PI controller 7a, which has received the S signal from the PWM generation section 9b, performs P (proportional) control, but does not perform control I (integral). The q-axis PI controller 8a also performs a similar operation as said d-axis PI controller 7a.

Fig. 10 is a graph showing a result of an experiment regarding the motor current according to Embodiment 4. In Fig. 10, the input voltage detection value Vpn, the motor current, the order value of Motor current and motor application voltage phase are represented in this sequence from above.

When the result of the experiment represented in Figure 10 is compared with the result of the experiment represented in Figure 4B according to said embodiment 1, it is seen that the frequency of occurrence where the motor current is especially greater than the current order value of engine has slowed down significantly. It is thus observed that the error has decreased. Furthermore, it is seen that the circled portion of the motor current waveform depicted in Fig. 10 is closer to the motor current command value than the circled portion of the current waveform. engine depicted in FIG. 4B. As described above, experiments have confirmed that the motor control apparatus according to Embodiment 4 can improve the controllability of the motor current, reduce the occurrence of transient currents and raise the maximum value of the motor output torque.

Embodiment 5

Next, a motor control apparatus according to Embodiment 5 of the present invention will be described. Fig. 11 is a block diagram showing the configuration of the motor control apparatus according to Embodiment 5. The functions and configurations of the rectifier circuit 1, the inverter circuit 2, the brushless motor 3 and the single-phase AC power source 5 represented in figure 11 are similar to those of said embodiment 1. The control section 4c according to embodiment 5 has a dq conversion section 6, a d-axis PI controller 7, a q-axis PI controller 8, a PWM generation section 9, a d-axis multiplier 18, a multiplier of q-axis 19 and a q-axis adder 20. The functions of the dq 6 conversion section, the d-axis PI controller 7, the q-axis PI controller 8, and the PWM 9 generation section are similar to the realization 1. The d axis multiplier 18 sends the result of the multiplication of the axis current detection value q Iq, the rotational speed ω of the brushless motor 3 and the axis inductance q Iq of the brushless motor 3. The result is sent and subsequently added to the output of the d-axis PI controller 7, and the result of the addition is set as the d-axis voltage command value Vd. The q-axis multiplier 19 sends the result of the multiplication of the d-axis current detection value Id, the rotation speed ω and the d-axis inductance Ld of the brushless motor 3. The q-axis adder 20 sends the result of the multiplication of the rotational speed ω and the induced voltage Ke of the q-axis brushless motor 3. The result of adding the respective outputs of the q-axis multiplier 19, the q-axis adder 20, and the q-axis PI controller 8 are set as the q-axis voltage command value Vq. These operations are represented by the following calculation equation (7).

ES 2 300 538 T3 (7) 'id * -Id' *

[Iq -Iq) (Vd \ (- CúLqlq \] + PI coLdld + a) Ke)

I______________________________________________________________________________I

Term without interaction

In Embodiment 5, by adding a non-interacting term, that is, the first term on the right hand side of equation (7), the independence of the d-axis and the q-axis can be improved. Fig. 12 is a graph representing a result of an experiment regarding motor current according to Embodiment 5.

As shown in Fig. 12, the motor current tracking performance of the motor control apparatus according to Embodiment 5 is higher than that of the motor control apparatus according to Embodiment 4 shown in Fig. 10. It has been found that the circled portion of the motor current waveform depicted in FIG. 12 is closer to the motor current command value than the circled portion depicted in FIG. 10. Experiments have confirmed that the motor control apparatus according to embodiment 5 can further reduce the occurrence of transient currents and raise the maximum value of the motor output torque compared to the motor control apparatus according to embodiment 4.

Fig. 13 is a graph representing the results of an experiment regarding the relationship between the rotational speed and the limiting torque of a brushless motor in the case where the motor control apparatus according to the present invention is compared with conventional engine control apparatus. The motor control apparatus according to the present invention used for the experiment represented in figure 13 is an apparatus configured by the combination of the configurations of said embodiments 1, 3, 4 and 5. Furthermore, the conventional motor control apparatus used as the comparison example is a motor control apparatus configured by the simple combination of said second and third conventional technologies. In this experiment, even when the configuration of the motor control apparatus according to Embodiment 2 was used instead of the configuration of the motor control apparatus according to Embodiment 1, a similar result of the experiment was obtained.

As clearly shown in Fig. 13, the limiting torque in the case of the motor control apparatus according to the present invention is significantly higher than in the case of the conventional motor control apparatus. Therefore, the torque requirements for the compressors of air conditioners, refrigerators, etc., can be sufficiently met by using the engine control apparatus according to the present invention. Furthermore, the specifications of the motor control apparatus for driving motors of electric washing machines, electric dryers, electric vacuum cleaners, fans, etc., can be met by using the motor control apparatus according to the present invention.

Embodiment 6

Next, a motor control apparatus according to Embodiment 6 of the present invention will be described. The motor control apparatus according to Embodiment 6 is configured so that the input voltage detection value Vpn input into the inverter circuit is estimated from past data.

Since the input voltage detection value Vpn fluctuates significantly, the value is detected every control cycle in the motor control apparatus according to Embodiment 6. It is here assumed that the input voltage detection value detected in the last control cycle is Vpn [n-1] and that the input voltage detection value detected in the penultimate control cycle is Vpn [n-2]. Vpn [n-1] is not used as the input voltage detection value in the present control loop. Instead, the variation between Vpn [n-1] and Vpn [n-2] is calculated, and the input voltage detection value Vpn [n] is estimated in the present control cycle. The equation for the calculation is represented by the following equation (8).

Vpn [n] = 1 / pn [nl] + (Fpn [n -1] - Vpn \ n - 2]) (8)

Equation (8) is established when it is assumed that the variation between the input voltage detection value Vpn [n-1] in the last control cycle and the input voltage detection value Vpn [n-2] in the penultimate control cycle is equal to the variation between the value in the present control cycle and the value in the last control cycle. Using the input voltage detection value Vpn [n] estimated using equation (8), the motor control apparatus according to the present invention can give exact working values.

The configuration according to embodiment 6 for estimating the input voltage detection value Vpn [n] can be incorporated in the configurations according to said embodiments 1 to 5. Therefore, more accurate working values can be sent, and it can be carried perform highly efficient engine control.

ES 2 300 538 T3

Embodiment 7

Next, a motor control apparatus according to Embodiment 7 of the present invention will be described. When a motor is stopped or the switching operation of an inverter circuit is stopped, the current flowing in the motor is regenerated to the input side of the inverter circuit. In the case where the regenerative current is large, the input side voltage of the inverter circuit increases and it is an overvoltage. This can damage the motor control apparatus that incorporates the inverter circuit. The motor control apparatus according to embodiment 7 has a mechanism to prevent damage due to regenerative current.

Fig. 14 is a circuit diagram showing a rectifier circuit 1, an inverter circuit 2, a brushless motor 3, a single-phase AC power source 5, etc., other than a control section, in the motor control apparatus. according to embodiment 7 of the present invention. The control section is not rendered. As shown in Fig. 14, a capacitor 16 having a small capacitance is arranged between the rectifier circuit 1 and the inverter circuit 2. Damage to the motor control apparatus due to regenerative current can be avoided by arranging the capacitor 16 between rectifier circuit 1 and inverter circuit 2 as previously described . As a result, it is possible to achieve a motor control apparatus having higher safety.

The capacitance of the capacitor 16 is set to a value where the motor control apparatus is not damaged by the regenerative current. For example, in the case where the motor control device is used for the compressor of an air conditioner or a heat pump water heater for domestic use, the capacitance should be about 0.1 to 50 μΕ In the In the case of a refrigerator, an electric washing machine, an electric dryer and an electric vacuum cleaner, the capacitance should be approximately 0.1 to 20 μΡ since the regenerative current is less than that of the air conditioner.

Although the configuration where the capacitor 16 is arranged between the rectifier circuit 1 and the inverter circuit 2 has been explained in the descriptions of embodiment 7, the capacitor 16 should only be connected to the input side of the inverter circuit 2.

Regenerative current is a current that flows from the brushless motor 3 to the capacitor 16 when the stored energy determined by the inductance L [H] of the brushless motor windings and the currents flowing through the windings is regenerated as a voltage to capacitor 16 immediately before the brushless motor stop 3. The maximum output P [W] of the brushless motor 3 depends on the current allowable value and the inductance L of the brushless motor 3. In Embodiment 7, the maximum output P [W] of the brushless motor 3 has a relationship represented by the following equation (9). This relationship is based on the general consideration of the relationship between said capacitance C [F] and the output of the brushless motor 3, a value at which the motor control apparatus is not damaged, and other factors.

C 2 X ΙΟ-7 XP (9)

The configuration according to embodiment 7 where damage of the motor control apparatus due to regenerative current is prevented, can be incorporated in the configurations according to said embodiments 1 to 6. Therefore, it is possible to provide a motor control apparatus which has higher reliability.

Embodiment 8

Next, a motor control apparatus according to Embodiment 8 of the present invention will be described. Fig. 15 is a circuit diagram showing a rectifier circuit 1, an inverter circuit 2, a brushless motor 3, a single-phase AC power source 5, etc., other than a control section, in the motor control apparatus. according to embodiment 8 of the present invention. The control section is not shown in figure 15.

The input current of the rectifier circuit 1 is affected by the switching operation of the inverter circuit 2. In particular, in the case that the carrier frequency of the switching operation is low, there is a problem of distorting the waveform of the Input current. In the motor control apparatus according to embodiment 8, an inductor 17 having an inductance L is arranged between the single-phase AC power source 5 and the rectifier circuit 1 as shown in FIG. 15. Arranging the inductor 17 between the Single-phase AC power source 5 and the rectifier circuit 1 of the motor control apparatus according to Embodiment 8, the power factor of the input current can be raised and the waveform of the current can be improved. The inductance L of inductor 17 is set to a value where the current distortion decreases. For example, in the case where the engine control apparatus is used for the compressor of an air conditioner or a heat pump water heater for domestic use, the inductance L should be about 0.1 to 2.0 mH. In the case of a refrigerator, an electric washing machine, an electric dryer and an electric vacuum cleaner, the inductance L should be approximately 0.1 to 1.0 mH since the current is less than that of the air conditioner.

Although the configuration where the inductor 17 is arranged between the single-phase AC power source 5 and the rectifier circuit 1 has been explained in the descriptions of embodiment 8, the inductor 17 should only be connected to the input side of the inverter circuit 2.

ES 2 300 538 T3

The inductance L of inductor 17 refers to the magnitude of the input current and the switching frequency of the inverter circuit 2. In the case of such an air conditioner, refrigerator, electric washing machine, etc., there is no great difference in the frequency of commutation. The switching frequency is substantially from several kHz to several tens of kHz. Therefore, it is considered that the appropriate inductance L in embodiment 8 is almost determined by the magnitude of the input current. Since the voltage of the single-phase AC power source 5 is 200 to 230 V according to the universal world standard, there is a correlation between the maximum output P [W] of the brushless motor 3 and the appropriate inductance L. This correlation is substantially represented by the following equation (10).

(10)

Furthermore, in the case of a motor control apparatus provided with the inductor 17 and the capacitor 16, a resonance phenomenon occurs. To prevent the resonance phenomenon from adversely affecting the AC power source system, the relationship represented by the following equation (11) is established between the inductance L of the inductor 17 and the capacitance C of the capacitor 16.

L 9x109/ C (11)

A capacitor having a capacitance C can also be provided for a motor control apparatus provided with an inductor in order to avoid damage to the motor control apparatus due to regenerative current as explained in the descriptions of said embodiment. 7. In this case, however, the inductor is connected in series with the capacitor, so a resonance phenomenon may occur. As is generally known, the resonance frequency is 1 / 2pv (LC), a value determined by the values of the inductor and capacitor. Therefore, by setting the inductor and capacitor values so that the resonant frequency is higher than the frequencies speculated in the harmonic standards of the power source, for example, it is possible to provide a motor control apparatus that generates less noise.

Embodiment 9

Next, a motor control apparatus according to Embodiment 9 of the present invention will be described. Fig. 16A is a block diagram showing the configuration of the motor control apparatus according to Embodiment 9 of the present invention. The functions and configurations of the inverter circuit 2, the brushless motor 3, the control section 4 and the single-phase AC power source 5 shown in Fig. 16A are similar to those of said embodiment 1. In the motor control apparatus according to embodiment 9, a boost circuit 21 is arranged on the input side of the inverter circuit 2. The AC voltage (100 V AC, for example) supplied from the single-phase AC power source 5 is high. (at 200 V AC, for example) by the boost circuit 21, and introduced into the inverter circuit 2.

The boost circuit 21 includes an inductor 200 to which the input voltage V of the single-phase AC power source 5 is applied, two switching devices 201 and 202 connected in series, two diodes 203 and 204 connected in series, and a capacitor 205. A terminal of the single-phase AC power source 5 is connected to the connection point of the two switching devices 201 and 202 via the inductor 200. The other terminal of the single-phase AC power source 5 is connected to the connection point of the two diodes 203 and 204. Furthermore, the series connection of the two switching devices 201 and 202, the series connection of the two diodes 203 and 204 and capacitor 205 are connected in parallel with each other. The output through capacitor 205 is fed into inverter circuit 2.

Furthermore, the engine control apparatus according to embodiment 9 is provided with a control circuit boost section 22 for controlling the on / off operation of the switching devices 201 and 202 of the boost circuit 21. In the following descriptions, the switching device 201 arranged on the upper side of the motor control apparatus shown in Fig. 16A is called an upper arm switching device 201, and the switching device 202 arranged on the lower side is called a lower arm switching device 202.

Next, an example of the operation of the control circuit booster section 22 of the engine control apparatus according to Embodiment 9 will be described.

The control circuit lift section 22 sends PWM commands to control the upper arm switching device 201 and the lower arm switching device 202 arranged in the lift circuit 21. In the PWM command for one of the switching devices, an on / off period in which the switching device repeats the on / off operation at intervals of a predetermined time and an off period in which the switching device maintains its off state are alternately present. Also, in the on / off period in which one of the switching devices repeats the on / off operation at intervals of the predetermined time, the other switching device is in the off period in which the off state is maintained. of the switching device.

ES 2 300 538 T3

In Fig. 17, signal (a) is a control signal V1 sent from control circuit lift section 22 to upper arm switching device 201. Signal (b) is a control signal V2 sent from section control circuit boost 22 to the lower arm switching device 202. Signal (c) is the output voltage V of single-phase AC power source 5. The signals shown in FIG. 17 are examples of these signals. As shown in Fig. 17, for example, it is assumed that, in period A, the upper arm switching device 201 carries out the on / off operation, and the lower arm switching device 202 maintains the state switched off. It is also assumed that, in the period B, the lower arm switching device 202 carries out the on / off operation, and the upper arm switching device 201 maintains the off state.

The state in period A is a state where the output voltage V at the terminal of the single-phase AC power source 5, not connected to the inductor 200, is higher. Also, the state in period B is a state where the output voltage V at the terminal of the single-phase AC power source 5, connected to the inductor 200, is higher. In other words, period A and period B are generated in synchronism with the frequency of the single-phase AC power source 5. The control circuit booster section 22 sends the PWM commands to the booster circuit 21 so that the upper arm switching device 201 and the lower arm switching device 202 arranged in the booster circuit 21 carry out the power-on operation. / shutdown as described above.

Next, a method of determining the PWM output working values of the PWM command according to Embodiment 9 will be described.

The control section 4 determines whether the step 34 represented in figure 3 and explained in the descriptions of said embodiment 3 has been carried out or not at each point of time in which the input voltage of the inverter circuit 2 is maximum. In other words, the control section 4 determines whether the PWM output working values of the phases U, V and W have been determined according to the equation (4) or not in the case where the input voltage detection value Vpn is less than the maximum value of the application voltage Vmax.

In the case where it is determined that step 34 has been performed, the control section 4 sends to the control circuit booster section 22 a control signal indicating that step 34 has been performed. When the control signal is input from the control section 4, the control circuit boost section 22 increments the PWM output working values of the PWM command that is sent to the boost circuit 21. On the other hand, when the control signal is not input, the control circuit boost section 22 decreases the PWM output working values of the PWM command. As a result, the PWM output work values of the PWM command of the boost section of the control circuit 22 are changed at each time point when the input voltage of the inverter circuit 2 is the maximum value. This time point is a time point where the output voltage of the single phase AC power source 5 is the maximum value.

Next, a method of determining whether the operating status is the status in period A or the status in period B.

When the brushless motor 3 is started, the input voltage of the inverter circuit 2 is similar to that obtained when the capacitor 205 is not arranged since the capacitance of the capacitor 205 arranged in the boost circuit 21 is small (just like the signal input voltage detection signal designated by Vpn in Figures 4A and 4B, for example). Then, the lower arm switching device 202 is subjected to the on / off operation according to the PWM output working value of the predetermined PWM command, regardless of the control signal of the control section 4. In this case, when the output voltage at the terminal of the single-phase AC power source 5, connected to the inductor 200, is higher, the voltage of the capacitor 205 is higher than the voltage obtained when the operation is not carried out. on / off. Therefore, the state at this time can be judged to be a state where the voltage phase of the single-phase AC power source 5 is the phase in period B. On the other hand, when the output voltage at the terminal of the single-phase AC power source 5, not connected to the inductor 200, is higher, the voltage of the capacitor 205 does not rise. Therefore, the state at this time can be judged to be a state where the voltage phase of the single-phase AC power source 5 is the phase in period A.

The voltage phase of the single phase AC power source 5 can be detected by detecting whether the voltage of the capacitor 205 rises or not, as described above. Therefore, in the motor control apparatus according to Embodiment 9, a judgment can be made on whether the voltage phase is the phase in period A or the phase in period B without using a voltage detection circuit. phase voltage.

Figure 18 represents the waveform of the output voltage V of the single-phase AC power source 5 and the waveform of a switched pulse signal based on a PWM output work value calculated in the motor control apparatus. according to embodiment 9.

In said embodiment 9, the lower arm switching device 202 is subjected to an on / off operation according to the PWM output working value of the predetermined PWM command. However, the upper arm switching device 201 can be subjected to on / off operation at this time. In this case, it is unnecessary to state that the voltage of capacitor 205 rises in period A and that the voltage does not rise in period B.

ES 2 300 538 T3

Figure 16B is a circuit diagram showing the configuration of another boost circuit 21a of the motor control apparatus according to Embodiment 9. As shown in Figure 16B, the boost circuit 21a according to Embodiment 9 may include a switching device , a plurality of diodes and a capacitor. In the case of this configuration, it is not necessary to distinguish between the upper arm switching device and the lower arm switching device. Only one switching device shall undergo a switching operation based on a PWM command.

In the motor control apparatus explained in the descriptions of Embodiment 9, in the case where the output voltage of the single-phase AC power source 5 is so low that the voltage applied to the brushless motor 3 is insufficient, it can be raise the input voltage of the inverter circuit 2. Therefore, the motor control apparatus according to Embodiment 9 can raise the maximum rotational speed of the brushless motor 3, whereby the operating range of the motor can be significantly expanded. In particular, in the case of an air conditioner, since the maximum rotation speed of its motor can be raised, the range of performance variation for cooling and heating can be extended, so that comfort is further improved. Furthermore, in an apparatus incorporating the motor control apparatus according to Embodiment 9, the maximum performance during the heating operation is especially improved. Thus, it is possible to provide an air conditioner having the highest heating effect.

Embodiment 10

Next, a motor control apparatus according to Embodiment 10 of the present invention will be described. Fig. 19 is a block diagram showing the configuration of the motor control apparatus according to Embodiment 10 of the present invention. The functions and configurations of the inverter circuit 2, the brushless motor 3, the control section 4 and the single-phase AC power source 5 of the motor control apparatus according to embodiment 10 shown in Fig. 19 are similar to those of said embodiment. 9.

In the motor control apparatus according to embodiment 10, a control circuit boost section 22a includes an AC current command generating section 23 and a PWM command generating section 24.

The AC current command generation section 23 of the control circuit boost section 22a detects the voltage phase of the single-phase AC power source 5 and generates an AC current command value that has the same phase as the voltage phase. detected voltage. Then, the generation section 23 sends the command value to the PWM command generation section 24. The amplitude value of the AC current command value is generated based on the control signal of the control section 4.

The control input signal from the control section 4 to the AC current command generation section 23 is the same control signal as explained in the descriptions of said embodiment 9. When the control signal is input from the section of control 4, the AC current command generating section 23 increases the amplitude value of the AC current command value. On the other hand, in the case where the control signal is not input from the control section 4, the AC current command generating section 23 decreases the amplitude value of the AC current command value.

The AC current command value of the AC current command generation section 23 and the detected value of the AC current of the single-phase AC power source 5 are input to the PWM command generation section 24. The generation section PWM command 24 performs error amplification so that the output current of the boost circuit 21 is the AC current command value. The PWM command generation section 24 then generates PWM signals to drive the switching devices of the boost circuit 21 and sends the PWM signals to the boost circuit 21. The PWM command generation section 24 according to Embodiment 10 uses PI control as control of feedback for error amplification. Fig. 20 is a circuit diagram showing a specific configuration of the control circuit lift section 22a. However, the present invention is not limited to this type of configuration for PI control. It is possible to use another feedback control that has been used generally.

Figure 21 represents the waveform of the output voltage V of the single-phase AC power source 5, a calculated PWM output working value, and the waveform of a changed pulse signal based on the PWM output working value. in the engine control apparatus according to embodiment 10.

A judgment on whether the upper arm switching device or the lower arm switching device of the lift circuit 21 is moved and controlled is made depending on whether the AC current command value is positive or negative. For example, when the AC current command value is positive, PWM commands are sent so that the lower arm switching device undergoes PWM operation and so that the upper arm switching device remains in the off state. . In addition, when the AC current command value is negative, PWM commands are sent so that the upper arm switching device is subjected to PWM operation and so that the lower arm switching device is kept in the off state. Or, since the voltage phase is detected by the control circuit boost section 22a, the detected voltage phase can be input to the PWM command generation section 24 and then a judgment can be made as to whether the switching device The upper arm switch or the lower arm switching device undergoes PWM operation, based on the detected voltage phase. Fig. 22 is a circuit diagram depicting a specific configuration of a control circuit boost section 22b configured as described above.

ES 2 300 538 T3

The boost circuit 21a including a switching device and shown in Fig. 16B according to said embodiment 9 can be used as the boost circuit 21.

The waveform of the current flowing to the single-phase AC power source 5 is nearly sinusoidal by virtue of such operations of the boost circuit 21 and the boost circuit control sections 22a and 22b. Therefore, the power factor of the power source is almost one, whereby it is possible to provide a motor control apparatus that does not adversely affect the power source system.

Embodiment 11

Next, a motor control apparatus according to Embodiment 11 of the present invention will be described. Fig. 23A is a block diagram showing the configuration of the motor control apparatus according to Embodiment 11 of the present invention. The functions and configurations of the inverter circuit 2, the brushless motor 3, the control section 4 and the single-phase AC power source 5 of the motor control apparatus according to embodiment 11 shown in Fig. 23A are similar to those of said embodiments. 9 and 10.

The motor control apparatus according to embodiment 11 differs from the motor control apparatus according to embodiment 10 in that a double voltage rectifier boost circuit 25 is provided instead of the boost circuit 21. This double voltage rectifier boost circuit 25 includes an inductor 300, a switching device 301, diodes 302, 303, 304, and 305, a capacitor 306 that has a large capacitance, and a capacitor 307 that has a small capacitance. A step-up circuit control section 22c includes an AC current command generation section 23 and a PWM command generation section 24b. The operation of the AC current command generation section 23 is substantially the same as that explained in the descriptions of said embodiments 9 and 10.

The operation of the PWM command generation section 24b and the operation of the dual voltage rectifier boost circuit 25 will be described with reference to Fig. 24.

In a period (hereinafter referred to as period C) in which the output voltage at the terminal of the single-phase AC power source 5, connected to the inductor 300, is higher than the output voltage at its terminal not connected to the inductor 300 , a current flows to capacitor 306. On the other hand, in a period (hereinafter referred to as period D) in which the output voltage at the terminal of the single-phase AC power source 5, not connected to the inductor 300, is higher, a current flows to the capacitor 307.

Therefore, in period C, a current similar to the current introduced in a conventional dual voltage rectifier circuit flows from the single-phase AC power source 5. If the inductor 300 becomes smaller in this state, the power factor decreases. In embodiment 11, the PWM command generation section 24b sends a PWM signal to PWM drive the switching device of the double voltage rectifier boost circuit 25 in period C so that the power factor does not go down.

In period D, the configuration according to embodiment 11 is similar to the circuit configuration explained in the descriptions of said embodiment 7, whereby the power factor does not drop.

The PWM command generation section 24b according to embodiment 11 differs from the PWM command generation section 24 according to said embodiment 10 in that the PWM signal is not sent to the double voltage rectifier boost circuit 25 in period D.

The two capacitors in the conventional dual voltage rectifier circuit have almost the same capacitance and are high capacitance aluminum electrolytic capacitors. However, the capacitance of one of the two capacitors according to embodiment 11 of the present invention is set to a small value. Since the capacitance of one of the capacitors can be made small, the double voltage rectifier boost circuit 25 of the motor control apparatus according to Embodiment 11 can be made smaller than the conventional double voltage rectifier circuit.

Fig. 23B is a circuit diagram showing the configuration of a dual voltage rectifier boost circuit 25a shown as another configuration of the dual voltage rectifier boost circuit of the motor control apparatus according to the present invention. An effect similar to that of said embodiment 11 is also obtained even if the double voltage rectifier boost circuit 25a shown in FIG. 23B is used instead of the double voltage rectifier boost circuit 25 shown in FIG. 23A.

Embodiment 12

Next, a compressor incorporating one of the motor control apparatus according to embodiments 1 to 11 will be described with reference to Fig. 25. Fig. 25 is a block diagram showing the configuration of the compressor according to Embodiment 12 of the present invention.

In Fig. 25, a compressor 41 connected to a single-phase AC power source 5 has a motor control apparatus 40 and a compression mechanism 42 driven by a brushless motor 3. The functions and settings of the brushless motor 3 and the single-phase AC power source 5 according to embodiment 12 are similar to those of said

ES 2 300 538 T3 embodiment 1. Furthermore, one of the motor control apparatus according to said embodiments 1 to 11 is applied to the motor control apparatus 40. The output of the motor control apparatus 40 is connected to the brushless motor 3 disposed within the compression mechanism 42, whereby the brushless motor 3 is rotated and driven by the motor control apparatus 40. By the rotation of the brushless motor 3, the compression mechanism 42 sucks and compresses refrigerant gas and discharges high pressure gas.

As described above, the motor control apparatus 40, one of the motor control apparatus according to said embodiments 1 to 11 of the present invention, is made smaller and lighter than conventional motor control apparatus. Therefore, the present invention can provide the compressor 41 which is made compact by integrating the compression mechanism 42 with the engine control apparatus 40 as explained in the descriptions of Embodiment 12.

Embodiment 13

Fig. 26 is a block diagram showing the configuration of an air conditioner according to Embodiment 13 of the present invention.

The air conditioner 43 according to embodiment 13 has an indoor unit 44 and an outdoor unit 45 and is used for cooling or heating a room. The compression mechanism 42 of the air conditioner 43 circulates a refrigerant between the indoor unit 44 and the outdoor unit 45. The motor control apparatus 40 connected to the single-phase AC power source 5 drives and controls a brushless motor arranged within the compression mechanism 42. The functions and configurations of the brushless motor and the single-phase AC power source 5 according to embodiment 13 are similar to those of said embodiment 1. In addition, one of the motor control apparatus according to said embodiments 1 to 11 is applied to the apparatus of motor control 40.

In the air conditioner 43 according to embodiment 13, the indoor unit 44 has an indoor-side heat exchanger 48, and the outdoor unit 45 has a four-way valve 46, a throttle device 47, and an outdoor-side heat exchanger. 49, thereby forming a coolant circulation passage.

The indoor side heat exchanger 48 has a fan 48a to raise the heat exchange performance and a temperature sensor 48b to measure the temperature of the indoor side heat exchanger 48 or the temperature around it. The outdoor side heat exchanger 49 has a fan 49a to raise the heat exchange performance and a temperature sensor 49b to measure the temperature of the outdoor side heat exchanger 49 or the temperature around it.

In the air conditioner 43 according to embodiment 13, the compression mechanism 42 and the four-way valve 46 are arranged in the refrigerant circulation passage between the indoor-side heat exchanger 48 and the outdoor-side heat exchanger 49 In the air conditioner 43 according to embodiment 13, the direction of the refrigerant flowing through the refrigerant circulation passage is changed by the selection operation of the four-way valve 46. For example, in the refrigerant circulation passage of the air conditioner 43, the refrigerant flows in the direction indicated by the arrow A. The refrigerant that has passed through the outdoor side heat exchanger 49 is sucked into the compression mechanism 42 via the four-way valve 46. The refrigerant discharged from the compression mechanism 42 is supplied to the indoor-side heat exchanger 48. On the other hand, when the selection operation of the four-way valve 46 is performed, the refrigerant flows in the direction indicated by the arrow B. The refrigerant that has passed through the indoor-side heat exchanger 48 is sucked into the mechanism. compressor 42 via the four-way valve 46. The refrigerant discharged from the compression mechanism 42 is supplied to the outdoor side heat exchanger 49. As described above, the flow direction of the refrigerant is changed by the selection operation of the four-way valve 46.

The throttle device 47 arranged in the refrigerant circulation passage between the indoor side heat exchanger 48 and the outdoor side heat exchanger 49 has a function of throttling the flow rate of the circulating refrigerant and also has a function of automatically adjusting the flow rate. of the refrigerant. As the refrigerant circulates through the refrigerant circulation passage, the throttle device 47 throttles the flow rate of the refrigerant liquid sent from a condenser to an evaporator so that the refrigerant liquid can expand immediately after throttling and supply the exact amount of refrigerant that requires evaporator.

In the air conditioner 43, the indoor side heat exchanger 48 operates as a condenser during heating and operates as an evaporator during cooling. Furthermore, the outdoor side heat exchanger 49 operates as an evaporator during heating and operates as a condenser during cooling. In the condenser, the heat of the refrigerant gas flowing through it and having high temperature and pressure is removed by the supplied air, whereby the refrigerant gas gradually liquefies. Near the outlet of the condenser, the refrigerant is in a liquid state or a state of high pressure liquid and gas mixture. This is equivalent to a phenomenon where the refrigerant radiates heat into the atmosphere and liquefies. Furthermore, the refrigerant converted to a liquid state or a low temperature and pressure liquid-gas mixture state by the throttle device 47 flows to the evaporator. When room air is supplied to the evaporator in this state, the refrigerant removes a large amount of

ES 2 300 538 T3 amount of heat from the air and evaporates, thus being a refrigerant that has a greater amount of gas. Air from which a large amount of heat has been removed by the evaporator is discharged as a cold jet from the air outlet of the air conditioner 43.

In the air conditioner 43, the commanded rotation speed of the brushless motor is set based on the operating state, that is, a desired temperature set for the air conditioner 43, the actual room temperature, and the outside air temperature. Analogously to the motor control apparatus according to said embodiment 1, the motor control apparatus 40 controls the rotational speed of the brushless motor of the compression mechanism 42 based on the preset commanded rotational speed.

Next, a method of controlling the rotational speed of the brushless motor at the preset commanded rotational speed will be described.

The ordered rotational speed is assumed to be ω * and the actual rotational speed of the brushless motor is ω. In the case of a brushless motor that has a position sensor, ω can be obtained by differentiating the signal from the position sensor. In the case of a brushless motor that does not have a position sensor, ω should be the estimated speed of rotation ω obtained by differentiating the estimated phase θ, as explained in the descriptions of embodiment 3. The error between the ordered rotational speed ω * and the actual rotational speed ω is calculated. A value obtained by subjecting the error to PI control is sent as a general current command value I *. Using the current phase command value B * stored within control section 4, the axis current command value d Id * and the axis current command value q Iq * are calculated according to the following equations ( 12) and (13).

β * is a value to determine the operating state of the brushless motor 3. This value can be a default value or it can be changed depending on the operating state of the brushless motor. By adding said function to the control section 4, in the case where the actual rotational speed is less than the commanded rotational speed, the d-axis current command value and the q-axis current command value are incremented by the PI control. Therefore, the output torque of the brushless motor 3 increases and the brushless motor accelerates. By this operation of the control section 4, the motor control apparatus operates so that the preset commanded rotational speed is obtained, whereby the brushless motor rotates at the commanded rotational speed.

Next, the operation of the air conditioner 43 according to Embodiment 13 will be described.

In the air conditioner 43 according to embodiment 13, when a driving voltage is applied from the engine control apparatus 40 to the compression mechanism 42, the refrigerant circulates through the refrigerant circulation passage. During this circulation, heat exchange takes place in the heat exchanger 48 of the indoor unit 44 and the heat exchanger 49 of the outdoor unit 45. In other words, in the air conditioner 43, the refrigerant sealed in the closed refrigerant circulation passage is circulated through the compression mechanism 42, whereby a known heat pump cycle is formed in the closed circulation passage. of refrigerant. This heats or cools the room.

For example, in the case where the air conditioner 43 carries out a heating operation, the user sets the four-way valve 46 so that the refrigerant flows in the direction indicated by the arrow A. In this case, the Heat exchanger 48 operates as a condenser and discharges heat by virtue of the circulation of the refrigerant through the refrigerant circulation passage. This is how the room is heated.

On the other hand, in the case where the air conditioner 43 carries out a cooling operation, the user sets the four-way valve 46 so that the refrigerant flows in the direction indicated by the arrow B. In this case, the heat exchanger 48 operates as an evaporator and absorbs heat from the ambient air by virtue of the circulation of the refrigerant through the refrigerant circulation passage. This cools the room.

In the air conditioner 43 according to embodiment 13, the commanded rotation speed is determined based on a desired temperature set for the air conditioner 43, the actual room temperature and the outside air temperature. Analogously to the motor control apparatus according to said embodiment 1, the motor control apparatus 40 controls the rotational speed of the brushless motor of the compression mechanism 42 based on the determined commanded rotational speed. As a result, the air conditioner 43 according to Embodiment 13 can implement comfortable cooling and heating.

ES 2 300 538 T3

Since the engine control apparatus 40 of the air conditioner 43 according to embodiment 13 is smaller and lighter than the conventional engine control apparatus, the engine control apparatus 40 has a greater degree of freedom of arrangement within the outdoor unit 45. This further facilitates the production design. Furthermore, by making the motor control apparatus smaller, it is possible to provide an outdoor unit 45 that is smaller and lighter, whereby the outdoor unit can be installed more easily by consumers. These excellent effects can be achieved.

In the case where brushless motors are used to drive the fan 48a of the indoor-side heat exchanger 48 and the fan 49a of the outdoor-side heat exchanger 49 of the air conditioner 43 according to Embodiment 13, the air conditioner control apparatus motor for moving and controlling each of these brushless motors can be any of the motor control apparatus explained in the descriptions of embodiments 1 to 11.

In the descriptions of Embodiment 13, the air conditioner capable of cooling and heating has been explained. In the case of a cooling-only air conditioner, the four-way valve 46 should be removed so that the refrigerant flows in the direction indicated by arrow B.

Embodiment 14

Fig. 27 is a block diagram showing the configuration of a refrigerator according to Embodiment 14 of the present invention.

The refrigerator 51 according to embodiment 14 has a motor control apparatus 40, a compression mechanism 42, a condenser 52, a refrigeration chamber evaporator 53 and a throttle device 54.

In the refrigerator 51 according to embodiment 14, the compression mechanism 42, the condenser 52, the throttle device 54 and the refrigeration chamber evaporator 53 are arranged within the refrigerant circulation passage. The motor control apparatus 40 is connected to a single phase AC power source 5 that serves as an input power source and drives and controls a brushless motor that serves as the drive source of the compression mechanism 42.

The functions and configurations of the brushless motor arranged within the compression mechanism 42 and the single-phase AC power source 5 serving as the input power source of the motor control apparatus 40 according to embodiment 14 are similar to those of said embodiment. Furthermore, one of the engine control apparatus according to said embodiments 1 to 11 is applied to the engine control apparatus 40.

Analogously to the throttle device 47 of the air conditioner 43 according to said embodiment 13, the throttle device 54 of the refrigerator 51 according to embodiment 14 throttles the flow of the refrigerant sent from the condenser 52 so that the refrigerant can expand and supply the exact amount of the refrigerant required for the evaporator 53 while the refrigerant circulates through the refrigerant circulation passage.

The condenser 52 condenses the refrigerant gas flowing through it having a high temperature and pressure and discharges the heat of the refrigerant to the outside. The heat from the refrigerant gas sent to the condenser 52 is removed by the outside air, and the refrigerant gas gradually liquefies. Near the outlet of the condenser 52, the refrigerant is a liquid state or a high pressure liquid-gas mixture state.

The refrigeration chamber evaporator 53 evaporates the refrigerant having a low temperature, thereby cooling the inside of the refrigerator. The cooling chamber evaporator 53 has a fan 53a to raise the heat exchange efficiency and a temperature sensor 53b to detect the temperature inside the refrigerator.

Next, the operation of the refrigerator 51 according to Embodiment 14 will be described.

In the refrigerator 51 according to embodiment 14, when a driving voltage is applied from the motor control apparatus 40 to the brushless motor of the compression mechanism 42, the compression mechanism 42 is moved and the refrigerant circulates through the passage of refrigerant circulation in the direction indicated by arrows C. During this circulation, heat exchange takes place in the condenser 52 and the refrigeration chamber evaporator 53, thereby cooling the interior of the refrigerator.

In other words, the flow rate of the condensed refrigerant in the condenser 52 is throttled by the throttle device 54, whereby the refrigerant expands and is a refrigerant having a low temperature. When the low-temperature refrigerant is sent to the refrigeration chamber evaporator 53, the refrigerant having a low temperature in the refrigeration chamber evaporator 53 evaporates, thereby cooling the inside of the refrigerator. During this cooling, the air inside the refrigerator is forcibly sent to the cooling chamber evaporator 53 by the fan 53a, whereby the cooling chamber evaporator 53 efficiently carries out heat exchange.

Furthermore, in the refrigerator 51 according to embodiment 14, the commanded rotation speed is set depending on a desired temperature set for the refrigerator 51 and the temperature inside the refrigerator. Analogously to the engine control apparatus according to embodiment 13, the engine control apparatus 40 controls the speed

ES 2 300 538 T3 of rotation of the brushless motor of the compression mechanism 42 based on the value of the preset commanded rotational speed. As a result, the temperature within the refrigerator 51 is kept at the desired temperature.

Since the motor control apparatus 40 of the refrigerator 51 according to Embodiment 14 is smaller and lighter than the conventional motor control apparatus as described above, the motor control apparatus 40 has a higher degree of freedom of arrangement within the refrigerator than conventional motor control apparatus. Furthermore, the greater degree of freedom of arrangement of the engine control apparatus has the effect of increasing the capacity within the refrigerator 51. Furthermore, since the light weight engine control apparatus can be provided, the weight of the refrigerator 51 is can reduce.

In the case where the brushless motor 3 is used to drive the fan 53a of the refrigerator 51 according to Embodiment 14, the motor control apparatus 40 for moving and controlling the brushless motor may be any of the motor control apparatus. explained in the descriptions of said embodiments 1 to 11.

Embodiment 15

Fig. 28 is a block diagram showing the configuration of an electric washing machine according to Embodiment 15 of the present invention.

The electric washing machine 55 according to embodiment 15 has an outer frame 56. A tub 57 is suspended within the outer frame 56 by suspension rods 58. Within the tub 57 is a wash and drain drum 59 so that it can rotate. At the bottom of the wash and drain drum 59, an agitator 60 is arranged so that it can rotate.

A brushless motor 3 for rotating the wash and drip drum 59 and the agitator 60 is arranged in the space under the tub 57 within the outer frame 56. In addition, a motor control apparatus 40, connected to the power source Single phase AC 5 to drive and control brushless motor 3 is installed in outer frame 56.

The functions and configurations of the brushless motor arranged within the outer frame 56 and the single-phase AC power source 5 serving as the input power source of the motor control apparatus 40 according to embodiment 15 are similar to those of said embodiment 1 Furthermore, one of the engine control apparatus according to said embodiments 1 to 11 is applied to the engine control apparatus 40.

In the electric washing machine 55 according to embodiment 15, a command signal indicating the commanded rotation speed depending on the operation of the user is input from a microcomputer (not shown) to control the operation of the electric washing machine 55 to the control apparatus. motor 40.

Next, the operation of the electric washing machine 55 according to Embodiment 15 will be described.

In the electric washing machine 55 according to embodiment 15, when a user performs a predetermined operation, the command signal is input from the microcomputer into the motor control apparatus 40, whereby a driving voltage is applied to the motor without brushes 3. Therefore, the brushless motor 3 moves, and the agitator 60 or the wash and drain drum 59 rotates, whereby the clothes and the like inside the wash and drain drum 59 are washed or drained. During this operation, in the electric washing machine 55 according to embodiment 15, the rotational speed of the brushless motor 3 is controlled by the motor control apparatus 40 based on the commanded rotational speed indicated by the command signal sent from the microcomputer, just as in the case of said embodiment 13. As a result, in the electric washing machine 55, the appropriate operation is carried out depending on the amount and dirt of the clothes and the like to be washed.

Since the compact size motor control apparatus 40 is used for the electric washing machine 55 according to embodiment 15 as described above, the present invention has the effect of increasing the capacity of the wash and drip drum even when the outer dimensions of the electric washing machine are the same as a conventional electric washing machine. Furthermore, since the light weight motor control apparatus 40 is used for the electric washing machine 55 according to the present invention, the present invention has an excellent effect of reducing the weight of the whole washing machine.

In the electric washing machine 55 according to embodiment 15 of the present invention, the motor control apparatus 40 for moving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of said embodiments 1 to 11 .

Embodiment 16

Figure 29 is a block diagram showing the configuration of an electric dryer according to Embodiment 16 of the present invention.

ES 2 300 538 T3

The electric dryer 61 according to embodiment 16 has an outer frame 62. Within the outer frame 62, a drum 63 is arranged so that it can rotate. A brushless motor 3 is connected to the drum 63 so that the brushless motor 3 rotates the drum 63.

The functions and configurations of the brushless motor 3 and the motor control apparatus 40 arranged within the outer frame 62 and the single-phase AC power source 5 according to embodiment 16 are similar to those of said embodiment 1. Furthermore, one of the apparatus The engine control device according to said embodiments 1 to 11 is applied to the engine control apparatus 40.

In the electric dryer 61 according to embodiment 16, a command signal indicating the ordered rotation speed depending on the operation of the user is input from a microcomputer (not shown) to control the operation of the electric dryer 61 to the control apparatus. motor 40.

Next, the operation of the electric dryer 61 according to Embodiment 16 will be described.

In the electric dryer 61 according to embodiment 16, when a user performs a predetermined operation, the command signal is input from the microcomputer into the motor control apparatus 40. Therefore, a driving voltage is applied to the motor. brushless 3. As a result, the brushless motor 3 moves, and the drum 63 rotates, so the laundry and the like inside the drum 63 run off.

During this operation, in the electric dryer 61 according to embodiment 16, the rotational speed of the brushless motor 3 is controlled by the motor control apparatus 40 based on the commanded rotational speed indicated by the command signal sent from the microcomputer, just as in the case of said embodiment 13. As a result, in the electric dryer 61 according to embodiment 16, an appropriate operation is carried out depending on the amount and dirt of the clothes and the like to be dried.

Since the compact size motor control apparatus 40 is used for the electric dryer 61 according to embodiment 16 as described above, the present invention has the effect of increasing the capacity of the drum even when the outer dimensions of the electric dryer they are the same as those of a conventional electric dryer. Furthermore, since the light weight motor control apparatus 40 is used for the electric dryer according to the present invention, the present invention has the effect of reducing the weight of the entire dryer.

In the electric dryer 61 according to embodiment 16 of the present invention, the motor control apparatus 40 for moving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of said embodiments 1 to 11 .

Embodiment 17

Fig. 30 is a block diagram showing the configuration of a fan according to Embodiment 17 of the present invention.

The fan 64 according to embodiment 17 has a fan 65, a brushless motor 3 for rotating and moving the fan 65, and a motor control apparatus 40 for moving and controlling the brushless motor 3. The motor control apparatus 40 is connected to a single phase AC power source 5 so that a single phase AC voltage is applied.

The functions and configurations of the brushless motor 3 and the motor control apparatus 40 arranged inside the fan 64 and the single-phase AC power source 5 according to embodiment 17 are similar to those of said embodiment 1. Furthermore, one of the Motor control according to said embodiments 1 to 11 is applied to the motor control apparatus 40.

In the fan 64 according to embodiment 17, a command signal indicating the commanded rotation speed depending on the operation of the user is input from a microcomputer (not shown) to control the operation of the fan 64 in the motor control apparatus 40 .

Next, the operation of the fan 64 according to Embodiment 17 will be described.

In the fan 64 according to embodiment 17, when a user performs a predetermined operation, the command signal is input from the microcomputer into the motor control apparatus 40. When the command signal is input into the engine control apparatus motor 40, a driving voltage is applied from the motor control apparatus 40 to the brushless motor 3. As a result, the brushless motor 3 moves, and the fan 65 rotates, whereby air blowing is carried out. During this operation, in the fan 64 according to embodiment 17, the output of the brushless motor 3 is controlled by the motor control apparatus 40 based on the command signal from the microcomputer, just as in the case of said embodiment 13. As a result, in fan 64, the flow rate and intensity of the blowing are regulated.

ES 2 300 538 T3

Since the compact size and light weight motor control apparatus 40 is used for the fan 64 according to embodiment 17 as described above, the fan itself can be made smaller and lighter than a conventional fan. Therefore, the present invention can provide a fan having excellent portability.

In the fan 64 according to embodiment 17 of the present invention, the motor control apparatus 40 for moving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of said embodiments 1 to 11.

Embodiment 18

Fig. 31 is a block diagram showing the configuration of an electric vacuum cleaner according to Embodiment 18 of the present invention.

The electric vacuum cleaner 66 according to embodiment 18 includes a cleaning body 69, a floor suction tool 67 having a suction hole formed on the underside, and a dust suction hose 68, one end of which is connected to the floor suction tool 67 and the other end of which is connected to the cleaning body 69.

The cleaning body 69 according to embodiment 18 includes a dust chamber 71 to which the end of the dust suction hose 68 is connected on the side of the cleaning body, and an electric fan 70 arranged on the outlet side of the chamber. dust 71. The electric fan 70 includes a fan 72 arranged to face the outlet side of the dust chamber 71, a brushless motor 3 for rotating the fan 72, and a motor control apparatus 40 for moving and controlling the motor. brushless 3. The motor control apparatus 40 is connected to a single-phase AC power source 5 so that a single-phase AC voltage is applied. By rotating the fan 72 air is drawn in through the suction hole formed in the underside of the floor suction tool 67 by the dust suction hose 68 and the dust chamber 71.

The functions and configurations of the brushless motor 3, the motor control apparatus 40 and the single-phase AC power source 5 according to embodiment 18 are similar to those of said embodiment 1. Furthermore, one of the motor control apparatus according to said Embodiments 1 to 11 apply to motor control apparatus 40.

In the electric vacuum cleaner 66 according to embodiment 18, a command signal indicating the commanded rotation speed depending on the user's operation is input from a microcomputer (not shown) to control the operation of the fan 72 in the motor control apparatus. 40.

Next, the operation of the electric vacuum cleaner 66 according to Embodiment 18 will be described.

In the electric vacuum cleaner 66 according to embodiment 18, when a user performs a predetermined operation, the command signal is input from the microcomputer into the motor control apparatus 40. When the command signal is input into the control apparatus of motor 40, a driving voltage is applied from the motor control apparatus 40 to the brushless motor 3, and the brushless motor 3 is moved. As a result, the fan 72 rotates, whereby a suction force is generated inside the cleaning body 69. By the suction force generated inside the cleaning body 69, air is sucked in through the suction hole formed on the underside of the tool. floor suction hose 67 which is connected to the cleaning body 69 by the dust suction hose 68. Therefore, dust is sucked from the floor to be cleaned together with air through the suction hole of the floor suction tool 67 and collected in the dust chamber 71 of the cleaning body 69. During this operation, in the electric vacuum cleaner 66 according to embodiment 18, the rotational speed of the brushless motor 3 is controlled by the motor control apparatus 40 based on the command signal from the microcomputer, just as in the case of said embodiment 13. As a result, in the electric vacuum cleaner 66 according to embodiment 18, the rotational speed of the brushless motor 3 is controlled, whereby the intensity of the suction force is regulated.

Since the compact size and light weight motor control apparatus 40 is used for the electric vacuum cleaner 66 according to embodiment 18 as described above, the cleaner body 69 can be made smaller and lighter than that of an electric vacuum cleaner. conventional. Therefore, the present invention can provide an electric vacuum cleaner having excellent portability and ease of handling by the user.

In the electric vacuum cleaner 66 according to embodiment 18 of the present invention, the motor control apparatus 40 for moving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of said embodiments 1 to 11 .

Embodiment 19

Fig. 32 is a block diagram showing the configuration of a heat pump water heater according to Embodiment 19 of the present invention.

ES 2 300 538 T3

The heat pump water heater 72 according to embodiment 19 includes a refrigeration cycle unit 73 for heating supplied water and discharging hot water, a hot water storage unit 74 for storing hot water discharged from the heating cycle unit. cooling 73, and water lines 74a, 74b, 75a and 75b to connect these components.

The refrigeration cycle unit 73 includes a compression mechanism 42, an air heat exchanger 76, a throttle device 77, and a water heat exchanger 78, thereby forming a refrigerant circulation passage. Furthermore, the refrigeration cycle unit 73 is provided with a motor control apparatus 40 connected to a single-phase AC power source 5 so that a single-phase AC voltage is supplied.

The functions and configurations of the brushless motor 3, the motor control apparatus 40 and the single-phase AC power source 5 according to embodiment 19 are similar to those of said embodiment 1. Furthermore, one of the motor control apparatus according to said Embodiments 1 to 11 apply to motor control apparatus 40.

Analogously to the throttle device 47 of the air conditioner 43 according to said embodiment 13 shown in figure 26, the throttle device 77 throttles the flow rate of the cooling liquid sent from the water heat exchanger 78 to the air heat exchanger 76 so that the coolant can expand immediately after throttling.

The water heat exchanger 78 is a condenser for heating the water supplied to the refrigeration cycle unit 73 and has a temperature sensor 78a for detecting the temperature of the heated water. The air heat exchanger 76 is an evaporator for absorbing heat from the ambient atmosphere and has a fan 76a to raise the heat exchange efficiency and a temperature sensor 76b to detect the ambient atmosphere.

A refrigerant tube 79 is used to connect the compression mechanism 42, the water heat exchanger 78, the throttle device 77, and the air heat exchanger 76, thereby forming a refrigerant circulation passage. A refrigerant circulates along the refrigerant circulation passage formed by the compression mechanism 42, the water heat exchanger 78, the throttle device 77, and the air heat exchanger 76. Refrigerant tube 79 is further connected to defrost bypass tube 80 so that refrigerant discharged from compression mechanism 42 is supplied to air heat exchanger 76 without passing through water heat exchanger 78 and device choke 77. A defrost bypass valve 81 is provided in a portion of the defrost bypass tube 80.

The hot water storage unit 74 has a hot water storage tank 82 for storing hot water or water. A supply water pipe 83 for supplying water from the outside into the hot water storage tank 82 is connected to the water receiving port 82c of the hot water storage tank 82. Furthermore, a hot water supply tube for use in a bathtub 84 for supplying hot water from the hot water storage tank 82 to a bathtub is connected to the hot water outlet port 82d of the hot water storage tank 82. Furthermore, a hot water supply pipe 85 for supplying the hot water stored in the tank 82 to the outside is connected to the water inlet-outlet port 82a of the hot water storage tank 82.

The water heat exchanger 78 of the refrigeration cycle unit 73 is connected to the hot water storage tank 82 by the water pipes 74a, 74b, 75a and 75b. Therefore, a water circulation passage is formed between the hot water storage tank 82 and the water heat exchanger 78.

The water pipe 74b is a pipe arranged on the side of the hot water storage tank and is used to supply water from the hot water storage tank 82 to the water heat exchanger 78. One end of the water tube 74b is connected to the water outlet port 82b of the hot water storage tank 82, and the other end is connected to the water tube 75b on the water supply side of the water heat exchanger 78 by means of a joint 87b. Furthermore, a water discharge valve 86 for discharging water or hot water from the hot water storage tank 82 is installed at one end of the water pipe 74b.

The water pipe 74a is a pipe arranged on the side of the hot water storage tank and is used for the return of water from the water heat exchanger 78 to the hot water storage tank 82. One end of the water tube 74a is connected to the water inlet-outlet port 82a of the hot water storage tank 82, and the other end is connected to the water tube 75a on the water discharge side of the heat exchanger of the water 78 by means of a joint 87a.

A pump 88 for circulating water through the water circulation passage is arranged in the middle of the water pipe 75b on the water supply side. Water tube 75b is used to connect water heat exchanger 78 to joint 87b.

In the heat pump water heater 72 according to embodiment 19, the commanded rotation speed of the brushless motor 3 is determined based on the operating state of the heat pump water heater 72, that is, a desired temperature of the hot water set on the heat pump water heater 72, the water temperature

ES 2 300 538 T3 supplied from the hot water storage unit 74 to the water heat exchanger 78 of the refrigeration cycle unit 73 and the outside air temperature. Then, the motor control apparatus 40 determines the necessary motor output for the brushless motor 3 of the compression mechanism 42 based on the commanded rotational speed.

Next, the operation of the heat pump water heater 72 according to Embodiment 19 will be described.

In the heat pump water heater 72 according to embodiment 19, when a driving voltage Cd is applied from the motor control apparatus 40 to the brushless motor of the compression mechanism 42, the compression mechanism 42 moves. A high temperature refrigerant obtained by compression in compression mechanism 42 circulates in the direction indicated by arrows D. Therefore, the high-temperature refrigerant is supplied from the comparison mechanism 42 to the water heat exchanger 78 through the refrigerant pipe 79. In addition, when the pump 88 is moved in the water circulation passage, water is supplied. from the hot water storage tank 82 to the water heat exchanger 78.

Then, heat exchange is carried out between the high temperature coolant and the supplied water from the hot water storage tank 82, whereby heat is transferred from the coolant to the water. Therefore, the water supplied to the water heat exchanger 78 is heated, and the heated water is supplied to the hot water storage tank 82. Then, the temperature of the heated water is monitored by the condensing temperature sensor 78a.

In addition, the refrigerant in the water heat exchanger 78 is heat-exchanged and liquefied. The flow rate of the refrigerant liquid obtained by the condensation is throttled by the throttle device 77, whereby the refrigerant expands and is supplied to the air heat exchanger 76.

In the heat pump water heater 72 according to embodiment 19, the air heat exchanger 76 operates as an evaporator. The air heat exchanger 76 absorbs heat from the outside air sent by the fan 76a and evaporates the refrigerant at low temperature. Then, the ambient atmosphere temperature of the air heat exchanger 76 is monitored by the temperature sensor 76b.

Furthermore, in the refrigeration cycle unit 73, when the air heat exchanger 76 freezes, the defrost bypass valve 81 opens, the high temperature refrigerant is supplied to the air heat exchanger 76 through the exhaust pipe. defrost bypass 80. Therefore, the air heat exchanger 76 is defrosted.

On the other hand, hot water is supplied from the water heat exchanger 78 of the refrigeration cycle unit 73 to the hot water storage unit 74 by the water pipes 74a and 75a. The hot water supplied to the hot water storage unit 74 is stored in the hot water storage tank 82. The hot water stored in the hot water storage tank 82 is supplied outside through the hot water supply pipe 85 as needed. In particular, in the case where hot water is supplied to the bathtub, the hot water stored in the hot water storage tank 82 is supplied to the bathtub through the hot water supply pipe for use in the bathtub 84.

In addition, in the case where the amount of the water or hot water stored in the hot water storage tank 82 is a constant value or less, water is filled from outside through the supply water pipe 83.

In the heat pump water heater 72 according to embodiment 19, the commanded rotational speed of the brushless motor 3 is determined by the motor control apparatus 40 based on a desired hot water temperature set in the water heater. of heat pump 72, the temperature of the water supplied to the water heat exchanger 78 and the temperature of the outside air. In the heat pump water heater 72 according to embodiment 19, the rotational speed of the brushless motor 3 of the compression mechanism 42 is controlled by the motor control apparatus 40 based on the commanded rotational speed, just as in the case of said embodiment 13. As a result, in the heat pump water heater 72 according to embodiment 19, hot water having the desired temperature can be safely supplied.

Since the compact size and light weight motor control apparatus 40 is used for the heat pump water heater 72 according to embodiment 19 as described above, the heat pump water heater 72 can be made more small and lighter than a conventional heat pump water heater. Therefore, in the heat pump water heater according to the present invention, the ease of installation is improved due to the reduction in size and is also improved due to the reduction in weight. In addition, the cost of the heat pump water heater according to the present invention can be significantly reduced relative to that of the conventional heat pump water heater, whereby the heat pump water heater is more beneficial for the user.

In the heat pump water heater 72 according to embodiment 19 of the present invention, the motor control apparatus 40 for moving and controlling the brushless motor 3 may be any of the motor control apparatus explained in the descriptions of said embodiments 1 to 11.

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The present invention explained in the descriptions of embodiments 1 to 19 is applicable not only to the motor control apparatus to be installed in the apparatuses mentioned in the descriptions of said embodiments, but also to other motor control apparatus for moving brushless motors. using inverter circuits. By making the motor control apparatus smaller and lighter, the design degrees of freedom of any corresponding apparatus can be improved, and the apparatus can be supplied at a lower cost, so that the effect of the present invention is highly significant.

The significance of the effect will be described with respect to an air conditioner and a compressor built into the air conditioner.

Most of the domestic air conditioners sold in Japan are inverter controlled and save a lot of energy compared to air conditioners that are not inverter controlled. Therefore, the power consumption of an air conditioner sold in Japan is about half the power consumption of an air conditioner produced ten years earlier. Inverter controlled air conditioners have become widely used in Japan. However, from a global point of view, the vast majority of air conditioners are not inverter controlled. Therefore, it is desired that the air conditioners available in the world be inverter controlled, from the point of view of promoting energy saving and conservation of the global environment.

Commercial products in the form of air conditioners that incorporate compressors predominate in Japan. However, in countries other than Japan, commercial products are often supplied as discrete compressors. In the markets for such discrete compressors, there is a demand for compressors of equal or smaller size than conventional compressors. Therefore, if a compressor is larger than the conventional compressor by adding an inverter circuit, the compressor cannot gain market acceptance. Thus, it is difficult to make inverter controlled compressors in the world and promote energy saving. Therefore, it is necessary to provide a compressor that incorporates an inverter, that is equal to a conventional compressor in performance and that is equal in size or smaller than the conventional compressor.

As described above, the present invention can provide a motor control apparatus configured without using an inductor to improve the power factor and a filtering capacitor having a large capacitance, that is, large components incorporated in a control apparatus. conventional motor. Therefore, the present invention can provide a compressor incorporating a compact motor control apparatus, which is equal in size to or smaller than the conventional compressor. The present invention can thus promote energy saving worldwide and can be significantly beneficial for the conservation of the global environment.

In the descriptions of each of said embodiments, a configuration in which a supplied AC voltage is rectified and fed into an inverter circuit has been taken as an example. However, the present invention is not limited to this type of configuration. In the present invention, even if a fluctuating voltage is introduced into the inverter circuit, the voltage is converted to a desired voltage by the inverter circuit and sent to a brushless motor. For example, in the case where a plurality of loads are connected to a DC power source, just as in the case of vehicle-mounted brushless motors, the output voltage of the DC power source fluctuates depending on the operating conditions. of the loads. Although this fluctuating DC power source is connected to the motor control apparatus according to the present invention, the voltage is converted to a desired voltage by the inverter circuit. Therefore, the motor control apparatus can exactly drive the corresponding brushless motor.

The engine control apparatus according to the present invention can also be applied to a vehicle-mounted air conditioner driven by a brushless motor. The engine control apparatus according to the present invention is beneficial for a vehicle whose engine stops during vehicle stop and starts when the vehicle is started, for example, a vehicle idling or the like in which idling engine stops during vehicle stop. When the engine is started, the voltage of the power source drops instantly. However, in the case where the engine control apparatus according to the present invention is mounted on the compressor of a vehicle-mounted air conditioner, the voltage applied to its brushless motor can be adjusted even when the source voltage Power drops instantly when the engine is started. Therefore, the brushless motor does not stop temporarily, so the vehicle-mounted air conditioner can operate continuously. As described above, the engine control apparatus according to the present invention is especially beneficial for a vehicle or the like whose engine stops during vehicle stoppage and starts when the vehicle is started, for example, a vehicle from running stop in vacuum or the like in particular.

Furthermore, the method of detecting the phase using the current supplied to a brushless motor without using a position sensor in each of said embodiments has been explained using said method described in the thesis “Control of a sensorless salient-pole brushless DC motor on the basis of estimation of speed electromotive force ”by Takeshita, Ichikawa, Lee and Matsui, Thesis Journal, Vol. 117-D, n ° 1, pages 98 to 104, published by the Institute of Electrical Engineers of Japan in 1997 . However, the present invention is not limited to this method. Any method where phase is detected using current supplied to a brushless motor can be applied to the present invention.

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As detailed descriptions of such embodiments have made clear, the present invention has the following effects.

The present invention can provide a compact motor control apparatus whose rectifier circuit can be made smaller and which can have a configuration with a position sensor and a configuration without a position sensor.

Furthermore, the present invention can provide a motor control apparatus capable of performing sensorless driving of a brushless motor without stopping the application of voltage to the brushless motor even though the input voltage to the inverter circuit pulses significantly.

Furthermore, the present invention can provide a motor control apparatus capable of continuously performing voltage application without stopping voltage application to the motor even when the DC side voltage of the inverter circuit is low.

Furthermore, according to the present invention, even in the case where sensorless drive is carried out where the phase information of the motor of a brushless motor is not obtained from a position sensor, the voltage application can be carried out continuously without stopping the application of voltage to the motor. Therefore, the phase of the motor can be estimated, whereby the present invention can provide a motor control apparatus capable of moving a brushless motor without using a position sensor.

Furthermore, according to the present invention, unnecessary errors for a current control apparatus do not overlap, whereby no unnecessary current flows from the motor, and the accuracy of the sensorless estimation can be improved. Thus, it is possible to provide an engine control apparatus having high accuracy and stability.

Furthermore, the present invention can provide a motor control apparatus capable of significantly improving the output torque of a motor without using a filter capacitor having a large capacitance in the rectifier circuit of the motor control apparatus. In the motor control apparatus according to the present invention, even when the input voltage of the inverter circuit pulses and a desired voltage cannot be applied to the motor, the phase of the voltage applied to the motor can be maintained. Therefore, it is possible to reduce wasted motor current and decrease motor stall due to overcurrent.

Furthermore, the engine control apparatus according to the present invention can implement an accurate phase estimation. Therefore, the engine control apparatus can realize sensorless engine driving and can be applied to compressors for air conditioners, refrigerators, etc.

Furthermore, according to the present invention, the current tracking operation of the motor can be improved. Therefore, the present invention can provide a motor control apparatus that has high efficiency, generates low noise, and improves the output torque of a motor.

In addition, the present invention can provide a motor control apparatus capable of being configured without using an inductor to improve the power factor and a filtering capacitor having a large capacitance, that is, large components incorporated in a motor control apparatus. conventional motor. Therefore, the present invention can provide a compressor incorporating a motor control apparatus, equal in size to or smaller than a conventional compressor. The present invention can thus promote energy saving worldwide and can be significantly beneficial to the conservation of the global environment.

Furthermore, in the motor control apparatus according to the present invention, in the case that the output voltage of the single-phase AC power source is low to the point that the voltage applied to a brushless motor is insufficient, it can be raise the input voltage of the inverter circuit. Therefore, the present invention can provide a motor control apparatus capable of raising the maximum rotational speed of the brushless motor and significantly expanding the operating range of the motor.

Furthermore, according to the present invention, the waveform of the current flowing to the single-phase AC power source is nearly sinusoidal operating the boost circuit and the boost section of the control circuit. Therefore, the power factor of the power source is almost one. The present invention can thus provide an engine control apparatus that does not adversely affect the power source system.

Furthermore, in the motor control apparatus according to the present invention, the capacitance of one of the two capacitors of its double voltage rectifier boost circuit can be made smaller, whereby the double voltage rectifier boost circuit can be made smaller. than a conventional dual voltage rectifier circuit.

21 members in 8 offices

This recordMember, by publication datePriority claim

Priority claims4

Priority claims
Document	Office	Kind	Date
20020361156	Japan	–	2002-12-12
2002361156	Japan	A	2002-12-12
20030154938	Japan	–	2003-05-30
2003154938	Japan	A	2003-05-30

Members21

Family members, oldest first
Document	Office	Kind
EP1429450A1	European Patent Office (EPO)	A1	2004-06-16
KR20040051554A	Republic of Korea	A	2004-06-18
CN1507145A	China	A	2004-06-23
US2004124807A1	United States of America	A1	2004-07-01
JP2005020986A	Japan	A	2005-01-20
US6984948B2	United States of America	B2	2006-01-10
EP1843463A2	European Patent Office (EPO)	A2	2007-10-10
CN100359794C	China	C	2008-01-02
EP1429450B1	European Patent Office (EPO)	B1	2008-02-13
AT386362T	Austria	T	2008-03-15
ATE386362T1	Austria	T1	2008-03-15
DE60319053D1	Germany	D1	2008-03-27
ES2300538T3This record	Spain	T3	2008-06-16
JP4416486B2	Japan	B2	2010-02-17
KR101006589B1	Republic of Korea	B1	2011-01-07
EP1843463A3	European Patent Office (EPO)	A3	2011-09-14
EP2573935A2	European Patent Office (EPO)	A2	2013-03-27
EP2573935A3	European Patent Office (EPO)	A3	2013-04-03
EP1843463B1	European Patent Office (EPO)	B1	2013-07-03
ES2425481T3	Spain	T3	2013-10-15
EP2573935B1	European Patent Office (EPO)	B1	2019-01-16

Motor control apparatus

Abstract

Term

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DESCRIPTION

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Priority claims4

Members21

Numbers

Titles2

Classification