ES2347129T3

Emitter with pilot signal synchronisation

Abstract

A method of communication between a base station and a mobile station by means of a communication channel, the method including the step of: transmitting control signals and data signals through the communication channel, said control signals having a first synchronization sequence of bit frame that has a bit number L and a second bit frame synchronization sequence that has a bit number L; where the first and second sequence of frame synchronization of L-bit numbers are selected such that the result of adding autocorrelation values of an autocorrelation of the first frame synchronization sequence to respective autocorrelation values of an autocorrelation of the autocorrelation of second frame synchronization sequence includes maximum peaks at zero and medium time shifts, which are equal to each other and of opposite polarity, and zero values in the other time shifts.

ES2347129T3, drawing sheet 1 — Sheet 1 of 54

Term

Term ended

Projected expiry passed 15 March 2020, 6.5 years ago.

7 claims: 1 independent, 6 dependent

1
ES 2 347 129 T3 ES 2 347 129 T3 CLAIMS REIVINDICACIONES 1. A method of communication between a base station and a mobile station via a communication channel, the method including the step of:1. Un método de comunicación entre una estación base y una estación móvil mediante un canal de comunicación, incluyendo el método el paso de: transmitir señales de control y señales de datos por el canal de comunicación, teniendo dichas señales de control una primera secuencia de sincronización de trama de bits que tiene un número L de bits y una segunda secuencia de sincronización de trama de bits que tiene un número L de bits;transmitting control signals and data signals over the communication channel, said control signals having a first bit frame synchronization sequence having an L number of bits and a second bit frame synchronization sequence having an L number of bits;donde la primera y la segunda secuencia de sincronización de tramas de número L de bits se seleccionan de tal manera que el resultado de añadir valores de autocorrelación de una autocorrelación de la primera secuencia de sincronización de trama a respectivos valores de autocorrelación de una autocorrelación de la segunda secuencia de sincronización de trama incluya picos máximos a desplazamientos de tiempo cero y medio, que son iguales entre sí y de polaridad opuesta, y valores cero en los otros desplazamientos de tiempo. where the first and second frame synchronization sequences of number L bits are selected in such a way that the result of adding autocorrelation values of an autocorrelation of the first frame synchronization sequence to respective autocorrelation values of an autocorrelation of the second frame synchronization sequence includes peak peaks at zero and half time offsets, which are equal to each other and of opposite polarity, and zero values in the other time offsets.

268 paragraphs in 13 sections, as filed

ES 2 347 129 T3

DESCRIPTION

Pilot symbols for channel synchronization and / or estimation.

Background of the invention

1. Field of the invention

The present invention relates to communication systems, and more specifically, to cellular communication systems.

2. Background of Related Art

The use of code division multiple access (CDMA) modulation techniques is one of several techniques to facilitate communications in large numbers of systems. Figure 1 generally illustrates a system 10, using CDMA communication techniques in communication between user equipment (UE) 12a and 12b, each UE including a cellular telephone, and base stations (BTS) 14a and 14b. A base station controller (BSC) 16 typically includes an interface and processing circuitry to provide system control to the BTSs 14a, 14b. The BSC 16 controls the routing of telephone calls from the public switched telephone network (PSTN) to the appropriate BTS for transmission to the appropriate UE. The BSC 16 also controls the routing of calls from the UEs, via at least one BTS to the PSTN. The BSC 16 may direct calls between UEs via the appropriate BTS since the UEs typically do not communicate directly with each other. The BSC 16 can be coupled to the BTSs 14a and 14b by various means including dedicated telephone lines, fiber optic links, or microwave communication links.

Arrows 13a-13d define the possible communication links between the BTS 14a and the UEs 12a and 12b. Arrows 15a-15d define the possible communication links between the BTS 14ba and the UEs 12a and 12b. On the reverse channel or uplink (i.e. UE to BTS), the UE signals are received by BTS 14a and / or BTS 14b, which, after demodulation and combining, pass the signal forward to the combining point , typically BSC 16. On the forward channel or downlink (ie from BTS to UE), the BTS signals are received by UE 12a and / or UE 12b. The above system is described in US Patent Nos. 5,101,501; 5,103,459; 5,109,390 and 5,416,797, the full description of which is incorporated herein by reference.

A radio channel is a generally hostile medium by nature. It is quite difficult to predict their behavior. Traditionally, radio channels are statistically modeled using actual propagation measurement data. In general, signal fading in a radio environment can be decomposed into a large-scale path loss component in conjunction with a medium-scale slow variable component that has a logarithmic normal distribution, and a small-scale slow variable component with a Rician or Rayleigh distribution, depending on the presence or absence of the line-of-sight (LOS) situation between the transmitter and the receiver.

Figure 2 illustrates these three different propagation phenomena. Extreme variation in transmission path between transmitter and receiver can be found, which is in the range of direct LOS to severely obstructed paths due to buildings, mountains, or foliage. The phenomenon of decrease in received power with distance due to reflection, diffraction around structures and refraction is known as path loss.

As depicted, the transmitted signal is reflected by many obstacles between a transmitter and a receiver, thus creating a multipath channel. Due to interference between many multipaths with different time delays, the received signal experiences frequency selective multipath fading. For example, when using the 2 GHz carrier frequency band and a car having a UE is traveling at a speed of 100 km / h, the maximum Doppler frequency of fading is 185 Hz. Although coherent detection can be used to increase link capacity, in such fast fading, coherent detection channel estimation is generally very difficult to achieve. Because of the fading channels, it is difficult to obtain a phase reference for coherent detection of the modulated data signal. Therefore, it is beneficial to have a separate pilot channel.

Typically, a channel estimate for coherent detection is obtained from a common pilot channel. However, a common pilot channel transmitted with an omni-directional antenna experiences a different radio channel than a traffic channel signal transmitted through a narrow beam. Common control channels have been found to be often problematic on the downlink when adaptive antennas are used. The problem can be solved with dedicated user pilot symbols, which are used as a reference signal for channel estimation. Dedicated pilot symbols can be time or code multiplexed.

Figure 3 illustrates a block diagram of a time multiplexed pilot symbol transmitter and receiver for an improved channel estimation method that operates successfully in slow to fast fading environments. Known pilot symbols are periodically multiplexed with the sequence of transmitted data. The pilot symbols and the data symbols that follow the pilot symbols constitute an interval, as shown in Figure 3.

ES 2 347 129 T3

Furthermore, in a DS-CDMA transmitter, the information signal is modulated by a spreading code, and in the receiver, it is correlated with a replica of the same code. Thus, in cross-correlation between wanted and interfering users it is important to suppress multiple access interference. Good autocorrelation properties are required for reliable initial synchronization, since large side lobes of the autocorrelation function can lead to erroneous code synchronization decisions. Furthermore, good autocorrelation properties are important to reliably separate multipath components.

Since the autocorrelation function of a spreading code should as closely as possible resemble the autocorrelation function of white Gaussian noise, DS code sequences are also called pseudo-noise (PN) sequences. The autocorrelation and cross-correlation functions are connected in such a way that it is not possible to achieve good values of autocorrelation and correlation simultaneously. This can be explained intuitively by noting that it has good autocorrelation properties that are also an indication of good randomness of a sequence. Random codes exhibit worse cross-correlation properties than deterministic codes.

Such a mobile communication system has gone through different stages of evolution, and various countries used different standards. First-generation mobile systems in the 1980s used analog transmission for voice services. Advanced Mobile Telephone Service (AMPS) in the United States, Total Access Communications System (TACS) in the United Kingdom, Nordic Mobile Telephone (NMT) in Scandinavia, Japan Telephones and Telegraphs (NTT) in Japan, etc. , they belonged to the first generation.

Second-generation systems using digital transmission were introduced in the late 1980s. They offer higher spectrum efficiency, better data services, and more advanced roaming than first-generation systems. The Global System for Mobile Communications (GSM) in Europe, Personal Digital Cellular (PDC) in Japan, and IS-95 in the United States belonged to the second generation.

Recently, third generation mobile radio networks have been the subject of intense research and explanation and will emerge around the year 2000. In the International Telecommunications Union (ITU), third generation networks are called International Mobile Telecommunications - 2000 (IMT-2000 ) and in Europe Universal Mobile Telecommunications System (UNITS). IMT-2000 will provide a multitude of services, including multimedia and high bit rate packet data.

Broadband CDMA has emerged as the leading air interface solution for third-generation networks. Broadband CDMA systems are currently being standardized by the European Telecommunications Standards Institute (ETSI) in Europe, the Association of Broadcasting and Radio Companies (ARIB) in Japan, the TIA TR45 and TR46 Technical Committees and the T1 Committee. T1P1 in the United States, and the Telecommunications Technology Association TTAI and TTA II (renamed CDMA Global I and II, respectively) in Korea. The above description and background for various systems can be viewed in WIDEBAND CDMA FOR THIRD GENERATION MOBILE COMMUNICATIONS by T. Ojanpera et al., Published 1998, by Artech House Publishers, the full description of which is incorporated herein by reference.

Recently, ARIB in Japan, ETSI in Europe, T1 in the United States of America, and TTA in Korea have designed a third generation mobile communications system based on a core network technique and radio access of a Global System for Mobile Communications. (GSM) existing to provide various services including multimedia, such as audio, video and data. They have agreed on a joint study for the submission of a technical specification on the evolved next generation mobile communication system and have named a project for the joint study as a third generation joint project (3GPP).

The 3GPP is classified in three partial technical studies. The first part is a structure and serviceability of the 3GPP system based on the 3GPP specification. The second part is a study of a Universal Terrestrial Radio Access Network (UTRAN), which is a radio access network (RAN) that applies the broadband CDMA technique based on a duplex frequency division (FDD) mode. , and a TD-CDMA technique based on a duplex time division (TDD) mode. The third part is a study of a core network evolved from a second generation GSM, which has third generation network capabilities, such as mobility management and global roaming.

Among the 3GPP technical studies, the UTRAN study defines and specifies the transport and physical channels. This technical specification, TS S1.11 v1.1.0, was released in March 1999, the full description of which is incorporated herein by reference. The physical channel includes the dedicated physical channels (DPCHs) used in the uplink and downlink. Each DPCH is generally provided with three layers, eg super frames, radio frames and time slots. As specified in the 3Gpp radio access network (RAN) standard, a super frame has a maximum frame unit of period of 720 ms. In view of the number of frames in the system, a super frame is made up of seventy-two radio frames. Each radio frame has a period of 10 ms, and a radio frame includes sixteen time slots, each of which includes fields with corresponding information bits based on the DPCH.

Figure 4 illustrates a frame structure of an uplink DPCH based on the RAN 3GPP standard. The uplink DPCH is provided with two types of channels, for example a dedicated physical data channel

ES 2 347 129 T3 (DPDCH) and a dedicated physical control channel (DPCCH). The uplink DPDCH is adapted to carry the dedicated data and the uplink DPCCH is adapted to carry the control information.

The uplink DPCCH for the transport of control information includes several fields such as a pilot field 21 of N ^ bits, a transmission power-control field (TPC) 22 of NTPC bits, a feedback information field (FBI) 23 of NFBi bits and an optional 24 N Combination Transport-Indicator (TFCI) fieldtFci bits. Pilot field 21 includes pilot bits Npuot to support channel estimation for coherent detection. The TFCI field 4 supports the simultaneous provision of a plurality of services by the system. The absence of the TFCI 4 field in the uplink DPCCH means that the associated service is a fixed rate service. The parameter k determines the number of bits per uplink DPDCH / DPCCH slot. It is related to the spreading factor SF of the physical channel as SF = 256/2k. The spreading factor SF can thus be in the range 256 to 4.

Fig. 5 is a table showing various information of the uplink DPCCH, where the bit rates and channel symbols are the pre-spreading. (At the time of this technical specification the exact number of bits of the different uplink DPCCH fields of Figure 4 (Npuot, NTPC, NFbi, Y NTFCI)).

Figure 6 is a table illustrating uplink DPCCH pilot bit patterns, and more specifically, 6-bit and 8-bit pilot bit patterns for each slot. In Figure 6, the unshaded sequence is used for channel estimation, and the shaded sequence can be used as words or frame synchronization sequences. The pilot bits other than the frame sync word, for example the channel estimate word, have a value of 1.

For example, in the case where each slot includes six pilot bits Npuot = 6, the sequences formed by slot # 1 through slot # 16 in bit # 1, bit # 2, bit # 4 and bit # 5 are used as the frame sync words. In the case where each slot consists of eight pilot bits (Npuot = 8), the sequences in bit # 1, bit # 3, bit # 5 and bit # 7 are used as the frame sync words. In the case where the pilot bits of each sequence interval are 6 or 8 in number, a total of four is used as the frame sync word. As a result, since a radio frame is provided with sixteen time slots, the number of pilot bits used as the frame sync word is 64 bits per frame.

Figure 7 depicts a spreading / coding arrangement for the uplink DPCH based on the RAN 3GPP standard. The arrangement of Figure 7 is provided for executing a Quadrature Phase Shift Keying (QPSK) operation where the DPDCH and the uplink DPCCH are mapped to I and Q channel branches, respectively.

Spreading is an operation to switch all symbols through respective channel branches to a plurality of chips. The I and Q channel branches are respectively spread at chip rates based on two different orthogonal variable spreading factors (OVSFs), or C channelization codes.D and Cc. The OVSF represents the number of chips per symbol on each channel branch. The spreading of two channel branches is summed and then complex encoded by a specific complex encoding code Cscramb. The complete encoding result is separated into real and imaginary and subsequently transmitted after being placed on respective carriers.

Figure 8 illustrates a frame structure of a downlink DPCH based on the RAN 3GPP standard. The number of pilot bits (or symbols) on the uplink DPCH is 6 or 8 because the uplink DPCH is activated at a fixed rate of 16 Kbps. However, since the downlink DPCH is activated at a fixed rate variable, has the pilot symbol configurations illustrated in Figure 9.

Referring to Fig. 8, similar to the uplink DPCH, the downlink DPCH is provided with two types of channels, for example, a dedicated physical data channel (DPDCH) and a dedicated physical control channel (DPCCH). In the downlink DPCH, the downlink DPDCH is adapted to carry the dedicated data and the downlink DPCCH is adapted to carry the control information. The downlink DPCCH for carrying the control information is composed of several fields such as a pilot field 27, TPC field 26, and TFCI field 25. Pilot field 27 includes pilot symbols to support channel estimation for coherent detection.

Figure 9 is a table illustrating pilot symbol configurations contained in the downlink DPCCH, which are classified according to different downlink DPCCH symbol rates. For example, in the case where the symbol rate is 16, 32, 64, or 128Kbps, each slot includes four pilot symbols for an I-channel branch and four pilot symbols for a Q-channel branch, totaling eight pilot symbols.

In Figure 9, the unshaded sequence is used for channel estimation and the shaded sequences can be used as frame sync words. The remaining pilot symbols other than the frame sync word (eg, channel estimate) have a value of 11. For example, in the case where the symbol rate is 16, 32, 64, or 128 Kbps, the sequences, formed by pilot symbols from interval # 1 to interval # 16,

ES 2 347 129 T3 in symbol # 1 and in symbol # 3 are used as the frame sync words. Accordingly, since the number of pilot symbols used as the frame sync words is 4 per slot, 64 pilot symbols are used in each radio frame.

Figure 10 illustrates a spreading / coding arrangement for the downlink DPCH based on the RAN 3GPP standard. The arrangement of Figure 10 is provided for downlink DPCH spreading and encoding and a common physical control channel (CCPCH) operation is performed. A QPSK operation is performed on a pair of symbols from the two channels so that they are converted serial to parallel and subsequently mapped to I and Q channel branches, respectively.

Channel branches I and Q are respectively spread at chip rates based on two equal channelization codes Cch. The spread of the two channel branches is summed and then complex encoded by a complex specific encoding code Cscramb. The complex encoding result is separated into real and imaginary and subsequently transmitted, after being placed on respective carriers. It is noteworthy that the same coding code is used for all physical channels in a cell, while different channelization codes are used for different physical channels. Data and various control information are transported to a receiver via the uplink and downlink DPCHs undergoing such spreading and coding.

The TS S1.11 v1.1.0 specification also specified a primary common control physical channel (PCCPCH), which is a fixed rate downlink physical channel used to carry the broadcast channel (BCH), and a physical control channel secondary common (SCCPCH) used to bring the direct access channel (FACH) and the search channel (PCH) at a constant rate. Figures 11A and 11B illustrate the frame structure of PCCPCH and SCCPCH, each having a pilot field. The TSS1.11v1.1.0 specification recommended pilot configurations for the PCCPCH and SCCPCH. In addition, the TS S1.11 v1.1.0 specification recommended the pilot configuration of the DPCH channel for the diversity antenna using open-loop antenna diversity based on space-time block coding (STTD) -based transmission diversity and antenna pilot configurations. diversity for PCCPCH and SCCPCH. The settings can be seen in the TS S1.11 v1.1.0 specification, and the detailed description is omitted.

For frame synchronization, an autocorrelation function must be performed based on the pilot configuration sequence. In the pilot sequence design, finding an autocorrelation of a sequence with the lowest lag coefficient is important to decrease the probability of false alarm regarding timing. A false alarm is determined when a peak is detected when there should be no peak detection.

Optimally, the autocorrelation result for a frame with a sequence in a preset pilot bit should have the same maximum values at zero and a half time offsets of a correlation period, which are of different polarity, and the remaining side lobes at time offsets other than zero and a half they should have a value of zero. However, the various pilot configurations recommended in TS S1.11 v1.1.0 do not meet this requirement, both on the uplink and on the downlink.

In an article entitled "Synchronization Sequence Design with Double Thresholds for Digital Cellular Telephone" by Young Joon Song et al. (August 18-20, 1998), of which the present inventor is a co-author, the article describes a correlator circuit for codes GSM where the phase shift coefficients are all zero except for one exception at the zero and a half offset which has a first peak and a second peak, where the first and second peaks are of opposite polarity, but the peaks are not equal to each other. Also, the article describes lower lag coefficients of +4 and -4. However, the article does not indicate how such sequences and autocorrelation can be used to achieve the optimal results described above, and the article does not sufficiently describe that the sequences achieve or can achieve the lowest autocorrelation side lobes.

As described above, pilot patterns used as frame sync words or sequences do not achieve optimal results. Also, the above pilot configurations do not quickly and accurately perform frame synchronization. Furthermore, the above pilot configurations and frame sync sequences do not provide optimal cross-correlation and autocorrelation. Additionally, neither the TS specification nor the article provides a solution to the use of the pilot configurations for interval-to-interval double check frame synchronization scheme, nor does it describe the use of the frame synchronization sequence for channel estimation.

US3461451 describes pulse signaling systems that use autocorrelation techniques using code words so that the sum of the autocorrelation functions is equal to zero for all non-zero offsets.

Summary of the invention

An object of the present invention is to obviate at least the problems and disadvantages of the related art.

An object of the present invention is to provide frame sync words that result in optimal autocorrelation results.

Another object of the present invention is to eliminate or avoid side lobes.

ES 2 347 129 T3

Another object of the present invention is to provide maximum values at the zero and a half time offsets.

Another object of the present invention is to provide a sync word for at least one of the fast and accurate frame sync.

Another object of the present invention is to provide an interval-to-interval double check frame synchronization scheme.

Another object of the present invention is to provide a frame sync word that can be used for channel estimation.

Another object of the present invention is to provide good cross correlation and autocorrelation simultaneously.

According to a first aspect of the invention, a method according to claim 1 is provided.

Embodiments of the present invention can be achieved in whole or in part by a method of synchronizing a frame using an optimal pilot symbol, including the steps of: (1) receiving a pilot symbol from each slot in the frame through respective physical channels on a communication link; (2) correlating a received position of each of the pilot symbols to a corresponding pilot sequence; (3) combine and sum more than one result of the correlations, and derive a final result from the correlations in which the side lobes of the results of the correlations are off; and (4) synchronizing the frame using the final result.

In such embodiments, the pilot symbols are combined in each of the pilot sequences in such a way that the final result of the correlations represents side lobes with "0" values excluding particular positions of correlation periods. The particular positions are initial points (x = 0) of the correlation periods (x) and points of x / an integer. The pilot symbol is a combination of pilot symbols in the form of (a, / a). The pilot sequence provides fewer correlation results in positions excluding the initial points and half of the initial points in the correlation periods. The pilot symbols excluding the pilot symbols used in the correlation are used in a channel estimate for coherent detection. The pilot symbol of each slot in the frame is transmitted, with the pilot symbol contained in a pilot field of an exclusive physical control channel between respective exclusive channels on the communication link. Pilot sequences different from each other in an uplink communication link are used in correlation according to bit values included in a pilot field of an exclusive physical control channel. Pilot sequences different from each other in a downlink communication link are used in correlation according to a symbol rate of an exclusive physical control channel.

Embodiments of the present invention may also be achieved in whole or in part by a method of synchronizing a frame using an optimal pilot symbol, including the steps of: (1) receiving a pilot symbol from each interval in the frame through respective channels physical on a communication link; (2) correlating a received position of each of the pilot symbols to a corresponding pilot sequence; (3) combine and sum more than one result of the correlations, and derive a final result of the correlations in which the side lobes of the results of the correlations have minimum values and the results of the correlations at initial points and midpoints of correlation periods have maximum values with different polarity; and (4) synchronizing the frame using the final result.

Embodiments of the present invention can be achieved in whole or in part by a method of eliminating side lobes in a communication channel between a base station and a mobile station, including the steps of: generating control signals and data signals within the channel communication, the control signals having a first sequence of L bits and a second sequence of L bits; generating a first set of presets based on the first sequence, which has a first preset relationship to the first set of presets; generating a second set of presets based on the second sequence, which has a second preset relationship to the second set of presets; and combining the first and second sets of preset values.

Embodiments of the present invention may be achieved in whole or in part by a method of establishing a communication channel, the method including the steps of: generating a plurality of frames; generating a number L of intervals for each frame, each interval having a pilot signal of N-bits and a corresponding bit in each interval forming a word of sequence L of pilot bits such that there is a number N of words, where the number of two pilot bit bit values that are the same between two adjacent words from 1 to L intervals minus the number of two pilot bit values that are different between the two adjacent words from 1 to L is zero or a preset number close to zero.

Embodiments of the present invention may be achieved in whole or in part by a method of establishing a communication channel having at least one of frame synchronization and channel estimation, the method including the steps of: generating a plurality of frames; generate a number L of intervals for each frame, each interval having a pilot signal of N bits and a corresponding bit in each interval forming a word of sequence L of pilot bits such that there is a number N of words, where the words have at least one of the following characteristics: the cross-correlation between two adjacent sequences used for frame synchronization

ES 2 347 129 T3 is zero at zero time offset, or the cross correlation between a word used for frame synchronization and a word used for channel estimation is zero at all time offsets.

Embodiments of the present invention may be achieved in whole or in part by a method of reducing side lobes for frame synchronization, including the steps of: generating a plurality of frame synchronization words, each frame synchronization word having a plurality of bits; performing autocorrelation functions on a pair of frame sync words to generate a pair of preset value sets; and combining the pair of preset value sets such that two peak values of equal magnitude and opposite polarity are achieved at zero and a half time offsets.

Embodiments of the present invention may be achieved in whole or in part by a method of generating pilot signals of a preset configuration within a frame having a number L of slots, including the steps of: generating the number N of pilot bits for each interval; and forming a number N of L bit words based on the previous step, where a preset number of words is used for frame sync words and each frame sync word has a first preset number b0 of bit values of "0" and a second preset number bi of bit values of "I", such that bi-b0 is equal to zero or a number close to zero.

Embodiments of the present invention can be achieved in whole or in part by a communication link between a user equipment and a base station including a plurality of layers, where one of the layers is a physical layer for establishing communication between the user equipment. and the base station and the physical layer have at least one of data and control information, one of the control information being a pilot field of N bits transmitted for the number L of intervals in such a way that the number N of L-bit words is formed, where the cross-correlation between two adjacent terms used for frame synchronization is zero at zero time offset or the cross correlation between a word used for frame synchronization and a word used for channel estimation is zero at all time offsets.

Embodiments of the present invention may be achieved in whole or in part by a correlator circuit for at least one of a user equipment and a base station, including: a plurality of latches, each latch circuit holding a word formed by a pilot bit of a plurality of slots; a plurality of correlators, each correlator coupled to a corresponding latch and correlating the word to a set of preset values; and a combiner that combines the set of each correlator in such a way that maximum peak values of equal magnitude and opposite polarity are formed at zero and a half time offsets.

Embodiments of the present invention may be achieved in whole or in part by a communications device including: means for transmitting at least one of data and control information; means for receiving at least one of control data and information, wherein the receiving means includes: a plurality of latches, each latch holding a word formed by a pilot bit of a plurality of slots; a plurality of correlators, each correlator coupled to a corresponding latch and correlating the word to a set of preset values; a plurality of buffers, each buffer coupled to a corresponding correlator for storing the set of preset values; and a combiner that combines the set of each buffer in such a way that maximum peaks of equal magnitude and opposite polarity are formed at zero and a half time offsets.

Additional advantages, objects, and features of the invention are set forth in part in the description that follows and in part will be apparent to those skilled in the art upon examination of the following or may be known from practice of the invention. The objects and advantages of the invention can be realized and achieved as pointed out in particular in the appended claims.

Brief description of the drawings

The invention will be described in detail with reference to the following drawings in which like reference numerals refer to like elements where:

Figure 1 generally illustrates a system, using CDMA modulation techniques in communication between user and base stations.

Figure 2 illustrates these three different propagation phenomena.

Figure 3 illustrates a block diagram of a transmitter and a receiver for time multiplexed pilot symbols.

Figure 4 illustrates a frame structure of an uplink DPCH based on the RAN 3GPP standard.

Fig. 5 is a table showing various information of the uplink DPCCH.

Figure 6 is a table illustrating uplink DPCCH pilot bit configurations.

ES 2 347 129 T3

Figure 7 depicts a spreading / coding arrangement for the uplink DPCH based on the RAN 3GPP standard.

Figure 8 illustrates a frame structure of a downlink DPCH based on the RAN 3GPP standard.

Figure 9 is a table illustrating pilot symbol configurations contained in the downlink DPCCH.

Figure 10 illustrates a spreading / coding arrangement for the downlink DPCH based on the RAN 3GPP standard.

Figures 11A and 11B illustrate the frame structure of PCCPCH and SCCPCH, respectively.

Fig. 12A is a table illustrating frame sync words Ci to C, lh according to a preferred embodiment of the present invention.

Fig. 12B is a table illustrating the autocorrelation function of the pilot bit sequences.

Figure 13A illustrates the addition of two autocorrelation functions.

Figure 13B illustrates the addition of the four autocorrelation functions.

Figures 14A and 14B are tables illustrating pilot configurations in accordance with a preferred embodiment of the present invention for uplink DPCCHs.

Figure 14C is a table illustrating the mapping relationship between the 8 sync words C1 -C8 of Figure 12A and the shaded pilot bit patterns of Figures 14A and 14B.

Figure 14D illustrates a correlation circuit for frame synchronization based on pilot bits of the uplink DPCCH according to a preferred embodiment of the present invention.

Figure 14E is a table illustrating the correlation results at points A1-A4, and the sum of the correlation results at point B of Figure 14D.

FIG. 14F is a table illustrating various results of adding correlation results based on the uplink pilot configurations of the frame sync words in accordance with the preferred embodiment of the present invention.

Figure 14G illustrates a correlator circuit for frame synchronization based on pilot bit sequences of an uplink DPCCH according to an alternative embodiment.

Figure 14H illustrates the receiver circuitry of a base station or user equipment for recovering the received spread signal by including the frame sync words in the pilot field.

Figure 14I illustrates the results of the correlation circuit using the pilot configuration of the technical specification.

Figure 14J illustrates a time shift graph of the sum of results of Figure 14I.

Figure 15A illustrates the pilot symbol configurations for downlink DPCH.

Figure 15B illustrates the mapping relationship between the 8 frame sync words of Figure 12A, and the shaded pilot symbol pattern of Figure 15A.

FIG. 15C illustrates a correlation circuit for frame synchronization for downlink DPCCH in accordance with the preferred embodiment.

Figure 16A illustrates the PCCPCH pilot symbol configuration.

Figure 16B illustrates the mapping relationship between the sync words C1 -C8 of Figure 12A, and the pilot symbol shaded patterns of Figure 16A.

Figure 16C illustrates the SCCHPCH pilot symbol configuration.

Figure 16D illustrates the mapping relationship between the sync words C1-C8 of Figure 12A, and the pilot symbol shaded patterns of Figure 16C.

ES 2 347 129 T3

Figures 17A-17C illustrate the addition of frame sync word autocorrelation functions of the preferred embodiment and current pilot configurations (described in TS specification S1.11 v1.1.0) for DPCHs and PCCPCHs.

Figure 18A illustrates the parameters used to obtain PD, PFA and PS in uplink DPCCH and downlink DPCH over Additive White Gaussian Noise (AWGN).

Figure 18B illustrates the detection probability PD on downlink DPCCH per AWGN channel.

Figure 18C illustrates the false alarm probability PFA on downlink DPCCH per AWGN channel.

Figure 18D illustrates the probability of a PS frame sync confirmation success on downlink DPCCH per AWGN channel.

Figure 19A illustrates downlink DPCH pilot symbol configurations for the diversity antenna using a transmit diversity based on block space time (STTD) coding.

Figure 19B illustrates the mapping relationship between the 8 Ci-C words8 of Figure 12A and shaded patterns of pilot symbols of Figure 19A.

Figure 19C illustrates the diversity antenna pilot symbol configuration for PCCPCH.

Figure 19D illustrates the mapping relationship between the C words1 -C8 of Figure 12A and shaded patterns of pilot symbols of Figure 19C.

Figure 19E illustrates the pilot symbol configuration for the diversity antenna when STTD coding is used on the SCCPCH.

Figure 19F illustrates the mapping relationship between the C words1 -C8 of Figure 12A and the pilot symbol shaded patterns of Figure 19E.

Figure 20A is a table illustrating frame C sync words1 -C18 (i = 16) and the autocorrelated function according to another preferred embodiment of the present invention.

FIG. 20B is a table illustrating the autocorrelation function of the pilot bits of each classified frame sync word in the PCSP.

Figure 20C illustrates the uplink DPCCH pilot bit pattern.

Figure 20D illustrates a mapping relationship between frame sync alternative words C1-C16 of FIG. 20A and the shaded frame sync words of FIG. 20C.

Figures 20E and 20F illustrate the downlink DPCH pilot symbol pattern.

Figure 20G illustrates a mapping relationship between frame sync alternative words C1-C16 of FIG. 20A and the shaded frame sync words of FIGS. 20E and 20F.

Figure 20H illustrates the downlink PCCPCH pilot symbol configuration.

Figure 20I illustrates a mapping relationship between frame sync alternative words C1-C16 of FIG. 20A and the shaded frame sync words of FIG. 20H.

Figure 21 illustrates a preferred embodiment for the new frame sync words C1-Ci_th.

Figure 22A illustrates the addition of two autocorrelation functions.

Figure 22B illustrates the addition of two cross-correlation functions between the two frame sync words within the same class.

Figure 22C illustrates the addition of four autocorrelation functions.

Figure 22D illustrates the addition of four cross-correlation functions between the four frame sync words of two classes.

Figure 23A illustrates the pilot bit patterns on uplink DPCCH with = 2, 3 and 4.

Figure 23C illustrates the pilot bit configurations in uplink DPCCH with N ^ = 2, 3 and 4 according to an alternative embodiment compared to Figure 23A.

ES 2 347 129 T3

Figures 23E and 23F illustrate the pilot bit configurations in uplink DPCCH with N ^ = 5, 6, and 8.

Figures 23B and 23D illustrate the mapping relationship between the frame sync words of Figure 21 and the shaded frame sync words of Figures 23A and 23D, respectively.

Figure 23G illustrates the mapping relationship between the frame sync words of Figure 21 and the shaded frame sync words of Figures 23E and 23F.

Figure 23H illustrates the random access channel structure.

Figure 23I illustrates the random access message control fields.

Figure 23J illustrates the RACH pilot bit pattern.

Figure 24A illustrates pilot symbol configurations on downlink DPCH when Npilot = 2, 4, and 16.

Figure 24B illustrates the mapping relationship between the Ci-C frame sync words8 of Figure 21 and shaded patterns of pilot symbols of Figure 24A.

Figure 24C illustrates the downlink DPCH pilot symbol configurations for the diversity antenna using STTD.

Figure 24D illustrates the mapping relationship between frame sync words C1-C8 of Figure 21 and shaded patterns of pilot symbols of Figure 24C.

Figure 25A illustrates the pilot symbol configurations for downlink SCCPCH for Npilot = 8 and 16.

Figure 25B illustrates the mapping relationship of frame sync words C1-C8 of Figure 21 and shaded patterns of pilot symbols of Figure 25A.

Figure 25C illustrates the downlink SCCPCH pilot symbol configurations for Npilot = 8 and 16 for the diversity antenna using STTD.

Figure 25D illustrates the mapping relationship between frame sync words C1-C8 of Figure 21 and shaded patterns of pilot symbols of Figure 25C.

Figure 26A illustrates the parameters used to evaluate the performance of the pilot bit pattern on uplink DPCCH over AWGN.

Figure 26B illustrates the PS frame synchronization confirmation success probability on uplink DPCCH with Npilot = 6 per AWGN channel.

Figure 26C illustrates the probability of a false alarm PFA on uplink DPCCH with Npilot = 6 per AWGN channel.

and Fig. 27 is a comparison graph between the embodiments for 15 time slots and 16 slots.

Detailed description of preferred embodiments

The new frame sync words according to the preferred embodiment have the lowest offset values of the autocorrelation function with two peak values of equal magnitude and opposite polarity at zero and a half offsets. Frame sync words are suitable for frame sync confirmation since, by simply adding autocorrelation functions of such words, one can achieve double maximum correlation values of equal magnitude and opposite polarity at zero and a half offsets. This property can be used to double check the frame sync time and reduce the sync search time.

The UE establishes downlink chip synchronization and frame synchronization based on the primary CCPCH synchronization time and frame deviation group, interval deviation group reported from the network. Frame synchronization can be confirmed using the frame synchronization word. The network establishes uplink channel chip synchronization and frame synchronization based on the frame deviation group and the slot deviation group. Frame synchronization can also be confirmed using the frame synchronization word.

ES 2 347 129 T3

When using a long coding code on uplink channels or downlink channels, failure to confirm frame sync using frame sync words always means missing frame and chip syncs since the coding code phase long repeats each frame. Whereas in the case of a short scrambling code on uplink DPCCH, failure to confirm frame synchronization does not always imply loss of chip synchronization since the short scrambling code length is 256 and corresponds to a period of uplink DPCCH symbol with SF = 256. Thus, the frame sync word of the pilot configuration can detect sync status and this information can be used in Layer 2 RRC connection establishment and release procedures.

Fig. 12A is a table illustrating frame sync words Ci to C, th according to a preferred embodiment of the present invention, wherein each word includes a pilot bit sequence number L (L> 1) from a preset bit position of Npilot bits (Npiiot> 0) of each interval of number L of intervals. In the first preferred embodiment described below, the number of sync words i is equal to 8, the number of slots L = 16 and the number of pilot bits Npilot in each interval is between 4 and 16, but the present invention is applicable to different variations of i, L, and Npilot.

Sync words C1 -C8 of the preferred embodiment can be divided into 4 classes (EH, called Preferred Correlation Sequence Pair (PCSP)) according to the autocorrelation function of the synchronization words, as follows:

E ^ C ^ Cg}

F = {C2, C6} G = {C3, C7} H = {C4, C8}

Figure 12B is a table illustrating the autocorrelation function of pilot bit sequences 1 to 16 of each frame sync word classified into classes E, F, G, and H within a correlation period of one time offset. 0 to 15. As depicted in Figures 12A and 12B, each class contains 2 sequences, and the sequences of the same class have the same autocorrelation function. In FIG. 12B, the sync words have the lowest phase shift values of the autocorrelation function with two peak values of equal magnitude and opposite polarity at zero and one-half offsets. Furthermore, the results R1 and R2 of the autocorrelation function are complements of each other. The following relationships between the autocorrelation functions are expressed in equations (1) - (4):

From equations (1), (2), and (3) the following equation is obtained.

The addition of two autocorrelation functions Rand(t) and RF(t), or Rg(t) and Rh(t) is the function with two peak values of equal magnitude and opposite polarity to zero and a half offsets, and all zero values except for the zero and a half offsets, which are illustrated in Figure 13A, where the peak values are equal to 2 * L or -2 * L. In the

ES 2 347 129 T3 preferred embodiment, the peak values of figure 13A are 32 and -32, given that L = 16. The other combinations such as (Rand(τ) + Rg(t), (Rand(t) + Rh(t)), (RF(t) + Rg(τ)), and (RF(t) + Rh(t)) do not have the same value as in Figure 13A. Using the properties derived from the frame sync words, the following property is achieved.

2nd

ΣΛ,(τ) = α (/?£(τ) + Λ£(τ)), 1 <α <4 (6) i = l where R, (t) is the sequence autocorrelation function Ci, 1 <i <8.

The addition of the four autocorrelation functions is illustrated in Figure 13B, which is the same as Figure 13B except that the maximum value is doubled to 4 * L or -4 * L (the maximum values being 64 and -64 for the preferred embodiment) since (Rand(t) + RF(t) + Rg(t) + Rh(t)) = 2 (Rand(t) + RF(t)) by equations (5) and (6). This property allows double checking of the frame synchronization time and the reduction of the synchronization search time.

First embodiment for uplink DPCCH

Figures 14A and 14B are tables illustrating pilot configurations in accordance with a preferred embodiment of the present invention for uplink DPCCH with Npilot = 5, 6, 7 and 8. The shaded configuration of Figures 14A and 14B is used for frame synchronization (which can also be used for channel estimation), and the pilot bit other than the frame synchronization words (for example, channel estimate) has a value of 1. Figure 14C is a table illustrating the mapping relationship between the 8 Ci-C sync words8 of Figure 12A and the shaded pilot bit patterns of Figures 14A and 14B, where the frame sync words C1, C2, C3 and C4 are the elements of the set {E, F, G, and H}, respectively. The results of Figures 13A and 13B are obtained by α = 1 and 2 in equation (6), respectively, which allows a double check of the frame synchronization time and a reduction of the synchronization time in uplink DPCCH with Npiiot = 5, 6, 7 and 8.

For example, the frame sync words in bit # 1 (C1), in bit # 2 (C2), in bit # 4 (C3) and bit # 5 (C4) are used in the autocorrelation process for frame synchronization when Npilot = 6. For Npilot = 8, the frame sync words in bit # 1 (C1), in bit # 3 (C2), in bit # 5 (C3) and bit # 7 (C4) are used in the autocorrelation process for frame synchronization. For Npilot = 5, 6, 7 and 8 in each slot, a total of four frame sync words are used. As a result, since a radio frame has sixteen time slots, the number of pilot bits used for frame synchronization is only 64 per frame in the preferred embodiment. As can be seen, the number of terms used for frame synchronization can vary depending on the variations of Npilot. For example, when Npilot = 1, one of frame sync words C1-C8 it can be used for frame synchronization and channel estimation due to the new feature of the preferred embodiment.

Figure 14D illustrates a correlation circuit for frame synchronization based on pilot bits of the uplink DPCCH according to a preferred embodiment of the present invention when using frame synchronization words C1-C4. Frame sync words C1 -C4 they are held in latches 31-34, respectively. The correlators 41-44 perform the correlation function R (x), where x = 0 to L-1, of the frame synchronization words C1-C4, respectively, to generate the correlation results A1-TO4, which are stored in buffers 51-53.

Figure 14E is a table illustrating the correlation results at points A1-TO4, and the sum of the correlation results at point B. As shown, the result has maximum values of opposite polarity at zero and one-half time shifts R (0) and R (8). Also, the remaining side lobes at non-zero and a half time offsets have zero values after the addition at point B. The side lobes are removed or minimized, and the results at point B correspond to the optimal results in the figure. 13B.

Figure 14F is a table illustrating various results of adding correlation results at points A1TO4 based on the uplink pilot configurations of the C-frame sync words1-C4 according to the preferred embodiment of the present invention. The respective addition of the autocorrelation results of the points (A1+ A2), (TO3+ A4), (TO1 + A4) already2+ A3) exhibits the same characteristics of the optimal results illustrated in Figure 13A.

Figure 14G illustrates a correlator circuit for frame synchronization based on pilot bit sequences of an uplink DPCCH according to an alternative embodiment. The elements are the same as the correlator circuit of Figure 14D. The frame sync words of (C1 and C2), (C2 and C3), (C3 and C4), or (C4 and C1) are correlated and summed to provide the results at point D. The sum result at point D of Figure 14G is similar to the correlator circuit of Figure 14D except that the maximum values of opposite polarity are 2 * L (32) and -2 * L (-32), rather than 4 * L (64) and -4 * L (-64), respectively, corresponding to the results of Figure 14F and the optimal results of Figure 13A .

ES 2 347 129 T3

Figure 14H illustrates the receiver circuit 60 of a base station or user equipment for recovering the received spread signal by including the frame sync words in the pilot field. After de-spreading the spread signal received by the de-spreading circuit 61, the channel estimator and frame synchronizer 62 performs the channel estimation and frame synchronization based on the pilot field. The Rake combiner 63 uses the results of the channel estimator and frame synchronizer, and after the Rake combination, the data is de-interleaved by the de-interleaving circuit 64 in the reverse order from the transmitter side. The data is then retrieved after decoding by a decoder 65.

The advantages of the present invention can be easily known based on the comparison of the frame synchronization words previously recommended in the TS S1.11 v1.1.0 specification and the frame synchronization words, for example, for Npuot = 6. Applying the same principle of equations (1) - (6) and the correlator circuit of figure 14D, the results are obtained in figure 14i for the pilot configuration indicated in the technical specification. When the sum result at point B is mapped onto a time shift graph, the side lobe problem is readily apparent, as depicted in Figure 14J. In other words, there are no maximum peak values of opposite polarity at zero and one-half time offsets, and there are sidelobes at non-zero and one-half time offsets.

As described in the background of the invention, obtaining a good cross correlation and simultaneous autocorrelation is difficult to achieve, where cross correlation refers to different words at different time shifts and autocorrelation refers to the same sequences that are the time-shifted version. The good cross correlation and autocorrelation of the present invention are based on unique properties of the frame sync words.

The unique characteristics of the frame sync words according to the preferred embodiment can be readily understood in light of Figures 12, 14A and 14B. As represented in the Ci-C frame sync words8 In Figure 12, each word has substantially the same number of 1 and 0. In other words, the number (b1) of pilot bits of a frame sync word having a value of 1 minus the number (bo) of frame sync pilot bits having a value of 0 is equal to or close to zero. In the preferred embodiment, when there are an even number of slot numbers, there is the same number of pilot bits having a value of 1 and 0 in a single frame sync word such that b1 -b0 is zero. As can be seen, when there is an odd number of pilot bits in a single frame sync word, the result of b1 -b0 is plus or minus one, for example, close to zero.

The second characteristic of frame sync words can be learned from an examination between a pair of adjacent frame sync words (shaded patterns of Figures 14A and 14B for Npilot = 5, 6, and 7), or between an adjacent frame sync word and channel estimate word pair (shaded and unshaded configurations of Figures 14A and 14B for Npilot = 5, 6, 7 and 8). Generally, the number (b3) of bit values that are the same (0, 0 and 1, 1) between a pair of adjacent words (that is, between two adjacent frame sync words, or between a frame sync word and an estimate word channels, which are adjacent) minus the number (b4) of bit values that are different (1.0 or 0.1) between adjacent words (that is, between two adjacent frame sync words, or between a frame sync word and a channel estimate word, which are adjacent) is equal to zero or a preset number close to zero.

In the preferred embodiment, the number (b3) of pilot bit values that is the same between two adjacent words equals the number (b4) of the pilot bit value that is different between the two adjacent words, that is, b3 -b4 = 0. In the preferred embodiment, when the Npilot = 5, between two sync words of C1 at bit # 0 and C2 In bit # 1, there are the same number of pilot bit values that are the same (0.0 and 1.1) and the pilot bit values that are different (1.0 and 0.1) from interval # 1 to interval # 16, as depicted in FIG. 14A. Likewise, between a C2 sync word in bit # 1 and a channel estimate word in bit # 2, there are the same number of pilot bit values that are the same (0.0 and 1.1) and values pilot bits that are different (1.0 and 0.1) from slot # 1 to slot # 16. The same applies between two adjacent words at bit # 2 and bit # 3, and between two adjacent words at bit # 3 and bit # 4. The above also applies to adjacent words of Npilot = 6, 7 and 8. As you can see, when an odd number of intervals is used, the result of b3-b4 is equal to plus or minus one, for example, close to zero.

As a result of this characteristic, the cross-correlation between two adjacent words used for frame synchronization is zero (orthogonal) at zero time offset. Furthermore, the cross-correlation between a word used for frame synchronization and the sequence used for channel estimation is zero (orthogonal) at all time shifts. In other words, within the number Npilot of L-bit words, there are an even number of terms used for frame synchronization, but all words perform channel estimation, where between the adjacent terms used for frame synchronization, there is substantially zero cross-correlation. Furthermore, the terms used for frame synchronization have substantially zero cross-correlation with words not used for frame synchronization, ie, channel estimation, at any time offset.

Also, each N wordpilot corresponds to a number pre-established by an autocorrelation function in such a way that when a pair of a set of autocorrelated results corresponding to terms used for frame synchronization is combined, two peak values of equal magnitude and opposite polarity are achieved.

ES 2 347 129 T3 zero and a half time offsets while the side lobes are substantially eliminated at non-zero and a half time offsets. Autocorrelation according to the present invention can be broadly defined as a correlation between a word and its time-shifted replica (including time-shifted replication), where the correlation is the number of bit values that are the same between two words minus the number of bit values that are different between the same two words. Furthermore, as depicted in Figure 12B, R1 and R2 they are complements of each other.

First embodiment for downlink DPCH

Figure 15A illustrates the pilot symbol configurations for downlink DPCHs for = 4, 8, and 16, where two pilot bits form one symbol since the right bit is used for the I-anal branch and the left bit is used for the Q channel branch. In the preferred embodiment, Npuot = 4 can be used for 8 ksps (kilo symbols per second); Np^ot = 8 can be used for 16, 32, 64 and 128 ksps; and Npilot = 16 can be used for 256, 512 and 1024ksps. The shaded symbols in Figure 15A can be used for frame sync, and the pilot symbol value other than for frame sync word, eg, channel estimate (channel estimate word), is 11. The results of Figure 15A are obtained by allowing α = 1 for = 4, α = 2 for = 8, and α = 4 for Npuot = 16 in equation (6) for downlink DPCH.

Figure 15B illustrates the mapping relationship between the 8 frame sync words of Figure 12A, and shaded pilot symbol pattern of Figure 15A. For example, in the preferred embodiment of Npuot = 4, symbol # 1 includes two frame sync words from C1 (for the I-CH channel branch, that is, left sequence of bits from slot # 1 to slot # 16) and C2 (for the I-CH branch). Q channel Q-CH, that is, right sequence of bits from slot # 1 to slot # 16). For Npuot = 8 and Npuot = 16, the correspondence of words to channels for corresponding symbols is evident in Figure 15B. Similar to uplink DPCCH, frame sync time slot-by-slot double check and frame sync search time reduction can be achieved by using the autocorrelation property of the pilot symbol pattern based on equation (6 ).

Since the frame sync words of the downlink DPCH are based on the frame sync words of Figure 12A, the characteristics described for uplink DPCCH are applicable to downlink DPCH. For example, the number (b3) of bit values that are the same (0.0 and 1.1) between adjacent words (that is, between the I-channel branch sync word and the Q-channel branch sync word of a sync symbol or between a channel estimate word of the Q-channel branch and a frame sync word of the I-channel branch, which are adjacent, or between a frame sync word of the Q-channel branch and a channel estimate word of the I-channel branch, which are adjacent) minus the number (b4) of bit values that are different (1.0 and 0.1) between adjacent words (that is, between the I-channel branch sync word and the Q-channel branch sync word of a Q-channel sync symbol). frame, or between a channel estimate word of the Q-channel branch and a frame sync word of the I-channel branch, which are adjacent, or between a frame sync word of the Q-channel branch and a channel estimate word of the I-channel branch, which are adjacent) is equal to zero or a preset number close to zero.

For example, for Npuot = 8, between symbols # 0 and # 1, the number of a pair of adjacent bits, that is, one bit of the Q-channel branch of symbol # 0 and one bit of the I-channel branch of symbol # 1, that have bit values of 1.1 and 0.0 is the same as the number of adjacent bits that have bit values of 1.0 and 0.1. In other words, b3 -b4 = 0. As can be seen, if the number of intervals L is an odd number, the result of b3 -b4 is plus or minus one, for example, a preset number close to zero.

Figure 15C illustrates a correlation circuit for frame synchronization for downlink DPCCH of Npuot = 8 according to the preferred embodiment. The operation and components are the same as in the Figure 14D correlation circuit for uplink DPCCH, except receiving I-channel branch and Q-channel branch sync words. The results of points A1 -TO4 and point B are the same as in Figure 14E. Likewise, side lobes are eliminated or minimized, and the results correspond to the optimal results in Figure 13B. Since the number of pilot symbols (or pilot bits) used for frame synchronization is 2 symbols per slot (or 4 bits per slot), 32 pilot symbols (or 64 pilot bits) are used in each radio frame for radio synchronization. plot.

For Npuot = 4 in the downlink DPCCH the correlator circuit of Fig. 14G can be used. In such a case, the I and Q channel frame sync words are input to the correlator circuit. The summation result would be the same as in Figure 14F, which corresponds to the optimal results in Figure 13A. In this case, the number of pilot symbols (or pilot bits) used for frame synchronization is 1 symbol per slot (or 2 bits per slot), and 16 symbols (or 32 pilot bits) are used in each radio frame for frame synchronization.

As with respect to Npuot = 16 on the downlink DPCCH, the correlation circuit of Figure 15C can be expanded to accommodate the additional frame sync words of the I and Q channel branches of pilot symbol # 5 and symbol # 7. The summation result would be similar to the optimal results in Figure 13B, but the maximum peak values of opposite polarity would be 128 (8 * L) and -128 (-8 * L). Also, the number

ES 2 347 129 T3 of pilot symbols (or pilot bits) used for frame synchronization is 4 symbols per slot (or 8 bits per slot), and 64 pilot symbols (or 128 pilot bits) are used in each radio frame for frame synchronization.

Downlink PCCPCH and SCCPCH First Realization

Figure 16A illustrates the PCCPCH pilot symbol configuration. The shaded symbols can be used for frame synchronization, and the pilot symbol value other than for frame synchronization is 11. Figure 16B illustrates the mapping relationship between the synchronization words C1-C8 of Figure 12A, and the pilot symbol shaded patterns of Figure 16A. Synchronization time double check frame and synchronization search time reduction can be achieved with α = 1 or 2 in equation (6).

Figure 16C illustrates the SCCPCH pilot symbol configuration. The shaded symbols can be used for frame synchronization, and the pilot symbol value other than for frame synchronization is 11. Figure 16D illustrates the mapping relationship between the synchronization words C1-C8 of Figure 12A, and the pilot symbol shaded patterns of Figure 16C.

As shown above, the PCCPCH and SCCPCH frame sync words are based on the C frame sync words.1 -C8, and the description for the uplink DPCCH and the downlink DPCH can be applied. Therefore, a detailed description of the various features including cross correlation and autocorrelation, operations and implements is omitted since the present invention can be readily appreciated by those skilled in the art based on the uplink DPCCH and downlink DPCH.

As described above, the unshaded symbols that are the pilot symbols not used for frame synchronization include 11 symbols, and the shaded symbols are used for frame synchronization. The frame sync words of the pilot configuration are used for frame sync confirmation, and the sum of autocorrelated values is required for each frame sync word. The sum property of autocorrelated values of frame sync words is very important.

The addition of frame sync word autocorrelation functions of the preferred embodiment and current pilot configurations (described in the TS S1.11 v1.1.0 specification) for DPCHs and PCCPCHs are illustrated in Figures 17A (Np¡lot = 4), Figure 17B (Np¡lot = 8) and figure 17C (Np¡lot = 16). As depicted, current pilot configurations have non-zero offset autocorrelation function with maximum value at zero offset, while frame sync words of the preferred embodiment have zero offset autocorrelation function with two peak values of equal magnitude and of opposite polarity to zero and a half time offsets (lags).

Correlation to a preset frame sync word is an optimal method for frame sync. Since the pilot configuration frame sync word is used for frame sync confirmation, the following events and parameters are used to evaluate the frame sync confirmation performance using the frame sync words of the preferred embodiment and the common pilot configurations:

H1: the event that the correlator output exceeds the predetermined threshold when the code offset between the received shaded column frame sync word and its corresponding receiver's stored frame sync word is zero.

H2: The event that the correlator output exceeds the predetermined threshold when the code offset between the received shaded column frame sync word and its corresponding receiver's stored frame sync word is not zero.

H3: an event of H1 and no H2 events for a frame.

H4: the event that the correlator output exceeds the predetermined threshold or is less than -1 x (default threshold) when the code offset between the received shaded column frame sync word and its stored frame sync word from the corresponding receiver is 0 or 8, respectively.

H5: the event that the correlator output exceeds the predetermined threshold or is less than -1 x (default threshold) when the code offset between the received shaded column frame sync word and its stored frame sync word from the corresponding receiver is not 0 and 8.

H6: an event of H4 and no event of H5 for a plot.

PD: probability of a detection.

PFA: probability of a false alarm.

PS: probability of a frame synchronization confirm success for a frame.

ES 2 347 129 T3

By the above definitions, when the current pilot configuration is used for frame synchronization confirmation, the probability of a detection and a false alarm can be expressed as:

Pd = Prob (Hi). (7)

Pfa = Prob (H2)(8)

The probability of a frame synchronization confirmation success for a frame is PS = Prob (H3) and can be expressed as

Ps = Pd (I-Pfa)15(9)

Whereas in the case of the frame sync words of the preferred embodiment, as noted, double thresholds are needed for double check frame sync, and the probability of a detection and a false alarm can be expressed as:

Pd = Prob (H4)(10)

PFA = Prob (H5)(11)

Similarly, in the case of frame sync words of the preferred embodiment, the probability of a frame confirm success for a frame is PS = Prob (H6) and is given by

Ps = Pd (I-Pfa)14(12)

According to equations (9) and (12), the probability of a frame synchronization confirmation is largely affected by the probability of a false alarm since PS is proportional to PD and (1-PFA)14 or (1-PFA)15. For example, assuming that PFA = 10 ', then (1-PFA)14 = 0.2288 and (1-PFA)15 = 0.2059. Suppose now that PFA = 10_3, then (1-PFA)14 0.9861 and (1-PFA)15 = 0.9851. The frame synchronization performance can be sufficiently evaluated by selecting the threshold so that the PFA is much less than (1-PD).

The parameters of Figure 18A are used to obtain PD, PFA, and PS in uplink DPCCH and downlink DPCH over additive white Gaussian noise (AWGN). Figure 18B illustrates the detection probability PD on downlink DPCCH with N ^ = 4 per AWGN channel, Figure 18C illustrates the false alarm probability PFA on downlink DPCCH with Npiiot= 4 per AWGN channel, and Figure 18D illustrates the probability of a PS frame sync confirmation success on downlink DPCCH with Npilot = 4 per AWGN between the pilot configuration of the preferred embodiment and the current pilot configuration, where PD, PFA, and PS are given as a function of the relationship Eb/ N0 (ANDb = energy per bit, N0 = noise power spectral density).

PD and PS of the pilot configurations of the preferred embodiment are larger than those of the current pilot configuration. Furthermore, PFA of the pilot configurations according to the preferred embodiment are also smaller than that of the current pilot configurations. Theoretical equations (9) and (12) are identical to the simulation results of Figure 18D. Therefore, there is a significant difference between the frame synchronization performance of the pilot configurations of the preferred embodiment and that of the current pilot configuration. For example, in Figure 18D, there is 3dB gain at PS = 0.93 using the pilot settings of the preferred embodiment.

The frame sync words of the preferred embodiment are especially suitable for frame sync confirmation. By adding the autocorrelation functions of shaded frame sync words, we obtain double maximum values of equal magnitude and opposite polarity at zero and a half offsets. This property can be used for double checking and interval by interval of the frame synchronization time and to reduce the synchronization search time. The frame synchronization confirmation performance by AWGN using pilot configuration illustrates the significant differences between the frame synchronization performance of the pilot configuration of the preferred embodiment and the current pilot configuration.

ES 2 347 129 T3

First realization of downlink DPCH, PCCPCH and SCCPH for STTD diversity

Figure 19A illustrates new downlink DPCH pilot symbol configurations for the diversity antenna using a transmit diversity based on block space time (STTD) coding. For diversity pilot symbol configuration on downlink DPCH, STTD is applied to shaded pilot symbols # 1 and # 3 for Npilot = 8, and the shaded pilot symbols # 1, # 3, # 5, and # 7 for Npilot = 16. The unshaded pilot symbols # 0 and # 2 for Npilot = 8, and the unshaded pilot symbols # 0, # 2, # 4, and # 6 for Npilot = 16 are encoded so that they are orthogonal to the pilot symbol of Figure 15A. However, the diversity pilot configuration for downlink DPCH with Npilot = 4 is STTD encoded since STTD encoding requires two symbols. Figure 19B illustrates the mapping relationship between the 8 C words1-C8 of Figure 12A and the pilot symbol shaded patterns of Figure 19A.

Figure 19C illustrates the new diversity antenna pilot symbol configuration for PCCPCH. The pilot symbols of Figure 19C are coded to be orthogonal to the pilot symbols of Figure 16A. Figure 19D illustrates the mapping relationship between the C words1-C8 of Figure 12A and the pilot symbol shaded patterns of Figure 19C.

Figure 19E illustrates the new pilot symbol configuration for the diversity antenna when STTD coding is used on the SCCPCH. For diversity pilot symbol configuration in SCCPCH, STTD is applied to shaded pilot symbols # 1, and # 3 of Npilot = 8, and the shaded pilot symbols # 1, # 3, # 5, and # 7 of Npilot = 16 in Figure 19e, while the unshaded pilot symbols # 0 and # 2 of Npilot = 8, and unshaded # 0, # 2, # 4, # 6 of Npilot = 16 are encoded so that they are orthogonal to those in Figure 16C. Figure 19F illustrates the mapping relationship between the C words1 -C8 of Figure 12A and the pilot symbol shaded patterns of Figure 19E.

Since the above is based on C words1 -C8, the previous explanation regarding uplink DPCCH and downlink DPCH, PCCPCH and SCCPH, is easily applicable. Those skilled in the art can easily appreciate the characteristics for downlink using diversity antenna based on the above description, and a detailed description is omitted.

Alternative embodiments for uplink DPCCH and downlink DPCH and PCCPCH

Figure 20A is a table illustrating frame C sync words1-C16 (i = 16) and the autocorrelated function according to another preferred embodiment of the present invention. Frame sync words C1-C16 can be classified in the PCSP of the first embodiment, as follows:

E = {C ,, C3, C9, C ,,} F - {C2, C4, C10, C12] G = {C5, C7, C13, C15} H = {^ 6, C8, C14, C1S}

The classification of the alternative C-frame sync words1-C16 they are also applicable to equations (1) - (6) and have the same properties and characteristics of the first embodiment. Fig. 20B is a table illustrating the autocorrelation function of the pilot bits of each classified frame sync word in the PCSP. In this particular case, each class contains four sequences and the sequences of the same class have the same autocorrelation function.

Figure 20C illustrates the uplink DPCCH pilot bit pattern with Npilot = 6 and 8 and Figure 20D illustrates a mapping relationship between the alternate frame sync words C1-C16 of FIG. 20A and the shaded frame sync words of FIG. 20C. Figures 20E and 20F illustrate the downlink DPCH pilot symbol configuration with 8, 16, 32, 64, 128, 256, 512, 1024, 2048 and 4096 ksps, and Figure 20G illustrates a mapping relationship between the words C frame synchronization alternatives1 -C16 of FIG. 20A and the shaded frame sync words of FIGS. 20E and 20F. Figure 20H illustrates the downlink PCCPCH pilot symbol configuration and Figure 20I illustrates a mapping relationship between alternate C frame sync words1 -C16 of FIG. 20A and the shaded frame sync words of FIG. 20H.

Since the above is based on alternative words C1-C16, which have the same characteristics as C words1 -C8 of the first embodiment, the above explanation regarding the uplink DPCCH and downlink DPCH, PCCPCH and SCCPH of the first embodiment is easily applicable. Those skilled in the art can easily appreciate the features of this embodiment based on the above description, and a detailed description is omitted.

The frame sync words of the preferred embodiment are especially suitable for frame sync confirmation. Adding the frame sync word autocorrelation functions

ES 2 347 129 T3 shaded, double maximum values of equal magnitude and opposite polarity are obtained at zero and a half displacements. This property can be used for double and interval-by-interval checking of the frame synchronization time and to reduce the synchronization search time. Furthermore, the present invention allows for a simpler construction of the correlator circuit for a receiver, thereby reducing the complexity of the receiver. Due to various advantages of the present invention, the first preferred embodiment has been accepted by 3GPP, as shown in TS 25.211 v2.0.1, issued June 1999, the full description of which is incorporated herein by reference.

Preferred embodiment for L = 15

The above pilot configurations according to preferred embodiments of the present invention have several advantages including confirmation of frame synchronization. However, alternative pilot configurations are needed for 15 slots (L = 15) due to OHG harmonization. Figure 21 illustrates a preferred embodiment for the new frame sync words C1 -Ci-th, which has the lowest lag coefficient autocorrelation function and the lowest magnitude of the cross-correlation function with a minus maximum value at mean offset, where i = 8. The frame sync words are used to design the configurations regular pilots and the uplink DPCH, and downlink DPCH and SCCPCH diversity antenna pilot configurations of the preferred embodiment. Using the two correlation functions, it is possible to perform a double frame synchronization check at zero and a half offsets. When performing AWGN environment single check and double check frame synchronization confirmation performance evaluation, the C words1-C8 of Figure 21 are suitable for frame synchronization confirmation.

Frame sync words C1 -C8 have the following two-value autocorrelation function:

where Rj (t) is the frame sync word autocorrelation function C,. Similar to L = 16, the words in figure 21 can be divided into 4 classes, as follows:

F = {C3, C4} θ = {C5, c6}

H = {C7, C8}

The two words within the same class are PCSP. The cross-correlation spectrum for the preferred pair {C1, C2}, {C3, 04}, {C5, C6}, or {C7, C8} is

where R, j (t) is a cross-correlation function between two preferred pair words of E, F, G, H, ei, j = 1, 2,

3, ..., 8. Combining these autocorrelation and cross-correlation functions, the following equations (16) and (17) are obtained:

ES 2 347 129 T3

According to equations (16) and (17), when α = 2, Figure 22A illustrates the addition of two autocorrelation functions, and Figure 22B illustrates the addition of two cross-correlation functions between the two frame synchronization words within of the same class. Similarly, according to equations (16) and (17), when α = 4, Figure 22C illustrates the addition of four autocorrelation functions, and Figure 22D illustrates the addition of four cross-correlation functions between the four synchronization words of plot of two classes E and F.

Since the autocorrelation function of the frame synchronization words C1-C8 According to this preferred embodiment having the lowest offset coefficient, single check frame synchronization confirmation is feasible by applying the positive threshold value in (a) of the output autocorrelation function of Fig. 22C. In addition, double check frame synchronization confirmation is also achieved by setting the negative threshold value in (b) of the output cross-correlation function of Fig. 22D.

Figure 23A illustrates the pilot bit configurations on uplink DPCCH with Npilot = 2, 3 and 4, and Figure 23C illustrates the pilot bit configurations in uplink DPCCH with Npilot = 2, 3 and 4 according to an alternative embodiment compared to figure 23A. In addition, Figures 23E and 23F illustrate the pilot bit configurations in uplink DPCCH with Npilot = 5, 6, 7 and 8. The shaded parts of Figures 23A, 23C, 23E and 23F can be used for frame sync words, and the pilot bit value other than the frame sync word is 1. The Figures 23B and 23D illustrate the mapping relationship between the frame sync words of Figure 21, and the shaded frame sync words of Figures 23A and 23D, respectively. Furthermore, Figure 23G illustrates the mapping relationship between the frame sync words of Figure 21, and the shaded frame sync words of Figures 23E and 23F.

The various descriptions above for uplink DPCCH when L = 16 are easily applicable to this preferred embodiment when L = 15, including circuit correlators (with some modifications) and general characteristics. For example, as shown in frame sync words C1-C8 of Figure 21, each word has substantially the same number of 1 and 0. In this preferred embodiment, the result of b1-b0 is plus or minus one, for example, close to zero. Also, when the number of intervals is 15, that is, odd, the result of b3-b4 is equal to plus or minus one, for example, close to zero. Also, since two frame sync words are used for Npilot = 2, 3 and 4 and there are fifteen time slots in a radio frame, the number of pilot bits used for synchronization is 30 per frame. For Npilot = 5, 6, 7 and 8, since four sync words are used for fifteen time slots in one radio frame, the number of pilot bits used for sync is 60 per frame. Furthermore, the result of adding two or four autocorrelation functions and cross-correlation functions between two or four frame sync words corresponds to Figs. 22A-22D.

The Random Access Channel (RACH) is an uplink transport channel that is used to carry UE control information. The RACH can also carry short user packets. The RACH is always received from the whole cell. Figure 23H illustrates the random access channel structure. The 10 ms message is divided into 15 slots, each of length Tslot = 2560 chips. Each interval has two parts, a data part carrying layer 2 information and a control part carrying layer 1 control information. The data and control parts are transmitted in parallel.

The data part includes 10 * 2k bits, where k = 0, 1, 2, 3. This corresponds to a spreading factor of 256, 128, 64, and 32 respectively for the message data portion. The control part has 8 known pilot bits to support channel estimation for coherent detection and 2 bits of rate information. This corresponds to a spreading factor of 256 for the message control part. Figure 23I illustrates the random access message control fields and there are always 8 pilot symbols per slot for channel estimation. Due to the unique characteristics of the frame sync words according to the preferred embodiment, the frame sync words C1-C8 they can be used in the RACH pilot bit configuration for channel estimation. Figure 23J illustrates the RACH pilot bit configuration, and the mapping ratio is the same as the mapping ratio illustrated in Figure 23G for Npilot = 8. Due to the new characteristics of the C frame sync words1 -C8, which can also be used solely for channel estimation, it is easy to reuse the pilot configurations, allowing commonality between different uplink channels.

Figure 24A illustrates pilot symbol configurations on downlink DPCH when Npilot = 2, 4, 8 and 16. The shaded portions of Figure 24A can be used for frame sync symbols, each symbol having a frame sync word for the I-channel branch and another frame sync word for the I-channel branch. Q-channel branch, and the pilot symbol value other than the frame sync word is

eleven. Figure 24B illustrates the mapping relationship between frame sync words C1 -C8 of Figure 21 and the pilot symbol shaded patterns of Figure 24A.

Figure 24C illustrates the downlink DPCH pilot symbol configurations for the diversity antenna using STTD. For diversity pilot symbol configuration on downlink DPCH, STTD is applied to shaded pilot symbols # 1 and # 3 for Npilot = 8, and # 1, # 3, # 5 and # 7 for Npilot = 16. The unshaded pilot symbols # 0 and # 2 for Npilot = 8 and 0 #, # 2, # 4 and # 6 for Npilot = 16 are encoded so that they are orthogonal to the pilot symbol of Figure 24A. However, the diversity pilot configuration for downlink DPCH with Npilot = 4 undergo STTD encoding since STTD encoding requires two symbols. Since the STTD encoding pilot symbol configuration is orthogonal to the configuration

As an ordinary pilot symbol ES 2 347 129 T3, the STTD encoding pilot pattern can also be used for feedback mode diversity antenna verification. Figure 24D illustrates the mapping relationship between frame sync words C1-C8 of Figure 21 and the pilot symbol shaded patterns of Figure 24C.

Figure 25A illustrates the pilot symbol configurations for downlink SCCPCH for Npilot = 8 and 16, and Figure 25B illustrates the mapping relationship of frame sync words C1-C8 of Figure 21 and the shaded patterns of pilot symbols of Figure 25A. In addition, Figure 25C illustrates the downlink SCCPCH pilot symbol configurations for Npilot = 8 and 16 for the diversity antenna using STTD, and Figure 25D illustrates the mapping relationship between the C frame sync words1-C8 of Figure 21 and the pilot symbol shaded patterns of Figure 25C.

As can be appreciated, the various descriptions above for downlink DPCH when L = 16 are easily applicable to this preferred embodiment when L = 15, including circuit correlators (with some modifications) and general characteristics. Furthermore, the result of adding two or four autocorrelation functions and cross-correlation functions between two or four frame sync words corresponds to Figs. 22A-22D.

In order to evaluate the performance of the frame sync words according to the preferred embodiment for 15 slots per frame, the following events and parameters are first defined:

H1: The event that the output of the autocorrelator exceeds the predetermined threshold in zero interval deviation.

H2: The event that the output of the autocorrelator exceeds the predetermined threshold in zero interval deviation or the output of the cross correlator is less than -1 x (default threshold) in interval deviation 7.

H3: the event that the auto-correlator exceeds the predetermined threshold in interval deviation except zero.

H4- The event that the output of the cross-correlator is less than -1 x (default threshold) in interval deviation except 7.

PS: probability of a frame synchronization confirmation success.

PFA: probability of a false alarm.

Frame synchronization is confirmed if the output of the correlator using the frame synchronization word exceeds the predetermined threshold. The success of the frame synchronization confirmation is determined when the frame synchronization is confirmed SR successive. Otherwise, the frame synchronization confirmation failure is determined. Thus, the probability of a frame synchronization confirmation success is defined by (Pr or b (H,))Mr . single purchase

(18)

The probability of a false alarm can be expressed as

PFA= Prob (H3) = Prob (H4) (19)

The parameters in Figure 26A are used to evaluate the performance of the pilot bit pattern on uplink DPCCH over AWGN. Figure 26B illustrates the PS frame sync confirmation success probability on uplink DPCCH with Npilot = 6 per AWGN channel. In addition, Figure 26C illustrates the probability of a false alarm PFA on uplink DPCCH with Npilot = 6 per AWGN channel. The PS and PFA they are given as a function of the Eb / N0 ratio (Eb = energy per bit, N0 = noise power spectral density).

The single check and double check frame sync confirmation PS with SR = 3 on uplink DPCCH is less than 0.945 and 0.99 at -5dB, respectively. In addition, a gain of approximately 4dB is obtained using the double check method compared to the single check method. According to figure 26C, the probability of a false alarm with normalized threshold = 0.6 at -5dB is less than 2.5 x10_4. The pilot configuration can be used for frame synchronization confirmation since a perfect frame synchronization confirmation success with false zero alarm was detected at Eb / N0 = 0dB when the double check frame synchronization confirmation method was used.

ES 2 347 129 T3

Fig. 27 is a comparison graph between the embodiments for 15 time slots and 16 slots. Including the various advantages for L = 16, the pilot bit / symbol patterns for L = 15 according to the preferred embodiment have additional advantages. Using this property / characteristics of the frame sync words, a double check frame sync scheme can be obtained. There is a significant gain of approximately 4dB using the double check frame sync confirmation method compared to the single check method. However, in the case of 15 bins, the complexity of the correlator circuit is doubled since an auto-correlator is used for positive peak detection and a cross correlator for positive peak detection.

Since the autocorrelation function of the 15-slot frame sync words has the lowest offset coefficient, the single check frame sync confirmation method can also be employed, although, in the 16-slot case, there are some problems due to lag coefficients of +4 or -4. The 15-slot pilot configurations are well suited for frame sync confirmation as a perfect frame sync confirmation success was detected with zero false alarm at Eb/ N0 = 0dB on uplink DPCH when double check frame sync confirmation method was used. Due to the various advantages of the preferred embodiment, the 15 slot pilot bit / symbol patterns have again been accepted by 3GPP.

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Priority claims50

Priority claims
Document	Office	Kind	Date
19990008630	Republic of Korea	A	1999-03-15
19990008630	Republic of Korea	A	1999-03-15
19990012856	Republic of Korea	A	1999-04-12
19990012856	Republic of Korea	A	1999-04-12
19990012857	Republic of Korea	A	1999-04-12
19990012857	Republic of Korea	A	1999-04-12
19990015722	Republic of Korea	A	1999-04-30
19990015722	Republic of Korea	A	1999-04-30
19990019505	Republic of Korea	A	1999-05-28
19990019505	Republic of Korea	A	1999-05-28
19990019506	Republic of Korea	A	1999-05-28
19990019506	Republic of Korea	A	1999-05-28
19990019610	Republic of Korea	A	1999-05-29
19990019610	Republic of Korea	A	1999-05-29
19990023140	Republic of Korea	A	1999-06-19
19990023140	Republic of Korea	A	1999-06-19
19990023141	Republic of Korea	A	1999-06-19
19990023141	Republic of Korea	A	1999-06-19
19990023568	Republic of Korea	A	1999-06-22
19990023568	Republic of Korea	A	1999-06-22
19990023937	Republic of Korea	A	1999-06-24
19990023937	Republic of Korea	A	1999-06-24
19990026689	Republic of Korea	A	1999-07-02
19990026689	Republic of Korea	A	1999-07-02
19990034212	Republic of Korea	A	1999-08-18
19990034212	Republic of Korea	A	1999-08-18
1285699	–	–	–
1572299	–	–	–
1950599	–	–	–
1961099	–	–	–
1999000863000302094	–	–	–
2314099	–	–	–
2314199	–	–	–
2356899	–	–	–
2393799	–	–	–
2668999	–	–	–
3421299	–	–	–
KR19990008630	–	–	–
KR19990012856	–	–	–
KR19990012857	–	–	–
KR19990015722	–	–	–
KR19990019505	–	–	–
KR19990019506	–	–	–
KR19990019610	–	–	–
KR19990023140	–	–	–
KR19990023141	–	–	–
KR19990023568	–	–	–
KR19990023937	–	–	–
KR19990026689	–	–	–
KR19990034212	–	–	–

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GB0006262D0	United Kingdom	D0	2000-05-03
GB0006264D0	United Kingdom	D0	2000-05-03
EP1037407A2	European Patent Office (EPO)	A2	2000-09-20
EP1039654A2	European Patent Office (EPO)	A2	2000-09-27
KR20000060382A	Republic of Korea	A	2000-10-16
CN1273462A	China	A	2000-11-15
CN1273467A	China	A	2000-11-15
GB2350037A	United Kingdom	A	2000-11-15
KR20000066033A	Republic of Korea	A	2000-11-15
KR20000066034A	Republic of Korea	A	2000-11-15
KR20000066040A	Republic of Korea	A	2000-11-15
KR20000067709A	Republic of Korea	A	2000-11-25
GB2350760A	United Kingdom	A	2000-12-06
DE10012284A1	Germany	A1	2000-12-14
JP2000349703A	Japan	A	2000-12-15
KR20000075106A	Republic of Korea	A	2000-12-15
KR20000075107A	Republic of Korea	A	2000-12-15
KR20000075164A	Republic of Korea	A	2000-12-15
EP1067733A1	European Patent Office (EPO)	A1	2001-01-10
WO0103376A2	World Intellectual Property Organization (WIPO)	A2	2001-01-11
KR20010003025A	Republic of Korea	A	2001-01-15
KR20010003026A	Republic of Korea	A	2001-01-15
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KR20010003582A	Republic of Korea	A	2001-01-15
AU6838100A	Australia	A	2001-01-22
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KR20010018316A	Republic of Korea	A	2001-03-05
WO0103376A3	World Intellectual Property Organization (WIPO)	A3	2001-06-28
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GB2350037B	United Kingdom	B	2001-09-19
KR100304938B1	Republic of Korea	B1	2001-09-26
BR0001674A	Brazil	A	2001-10-16
EP1039654A3	European Patent Office (EPO)	A3	2001-10-24
KR100308151B1	Republic of Korea	B1	2001-11-14
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KR100339337B1	Republic of Korea	B1	2002-06-03
US6452471B1	United States of America	B1	2002-09-17
KR100331872B1	Republic of Korea	B1	2002-11-23
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AT237208T	Austria	T	2003-04-15
ATE237208T1	Austria	T1	2003-04-15
US6548822B1	United States of America	B1	2003-04-15
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CN1124708C	China	C	2003-10-15
EP1037407A3	European Patent Office (EPO)	A3	2003-10-15
DE69906715T2	Germany	T2	2003-10-16
JP3463015B2	Japan	B2	2003-11-05
US6721299B1	United States of America	B1	2004-04-13
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US2005018754A1	United States of America	A1	2005-01-27
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HK1077134A1	Hong Kong, China	A1	2006-02-03
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KR100710344B1	Republic of Korea	B1	2007-04-23
EP1850511A2	European Patent Office (EPO)	A2	2007-10-31
EP1850511A3	European Patent Office (EPO)	A3	2007-11-07
US7317749B2	United States of America	B2	2008-01-08
US7457268B2	United States of America	B2	2008-11-25
US2008298438A1	United States of America	A1	2008-12-04
US7496132B2	United States of America	B2	2009-02-24
CN100483972C	China	C	2009-04-29
EP2081306A1	European Patent Office (EPO)	A1	2009-07-22
US2009196271A1	United States of America	A1	2009-08-06
US2009196278A1	United States of America	A1	2009-08-06
JP4318963B2	Japan	B2	2009-08-26
EP2099143A1	European Patent Office (EPO)	A1	2009-09-09
US7602841B2	United States of America	B2	2009-10-13
US7616681B2	United States of America	B2	2009-11-10
US7643540B2	United States of America	B2	2010-01-05
EP1039654B1	European Patent Office (EPO)	B1	2010-02-10
AT457554T	Austria	T	2010-02-15
ATE457554T1	Austria	T1	2010-02-15
US2010067517A1	United States of America	A1	2010-03-18
DE60043800D1	Germany	D1	2010-03-25
EP1037407B1	European Patent Office (EPO)	B1	2010-07-07
AT473562T	Austria	T	2010-07-15
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ES2415884T3	Spain	T3	2013-07-29

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Emitter with pilot signal synchronisation

Abstract

Term

ES 2 347 129 T3

DESCRIPTION

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Priority claims50

Members106

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