Video copy protection process enhancement to introduce horizontal and vertical picture distortions

The present invention relates to a method and apparatus for modifying a video signal subject to copy protection.

Video anticopy processes are well known. An example is U.S. Patent No. 4,631,603 which describes the modification of a video signal so that a television receiver will still provide a normal color picture from the modified video signal while the video tape recording of the modified video signal produces generally unacceptable pictures.

To achieve this, a plurality of pseudo-sync pulses is added to the conventional video signal during the vertical blanking interval, and each of the pseudo-sync pulses is followed by a positive pulse of suitable amplitude and duration. As a result, the automatic gain control system in a videotape recorder will make a false measurement of video level which causes an improper recording of the video signal. The result is unacceptable picture quality during playback.

Thus, this prior art "basic anticopy process" causes an abnormally low amplitude video signal to be recorded when a copy is attempted. Some of the effects observed when the illegal copy is relayed are horizontal tearing (positional displacement) and vertical displacement of the picture. Whether this occurs or not is often largely dependent on the picture content, i.e. presence of white (light) and black (dark) areas in the picture. Therefore this prior art process, while generally providing excellent copy protection, with some combinations of videotape recorders (such as VCRs) and television sets provides a picture viewable by persons willing to tolerate a poor quality picture.

WO-A-91/16791 describes a method and an apparatus for preventing unauthorized copying of video signals on tape. A number of image lines with their corresponding line synchronization pulses are removed and additional pulses are substituted. A tape recording apparatus does not recognize the inserted pulses and iso frame synchronization is disturbed. Also, an additional pulse is added after a colour synchronization signal. This can adversely affect the % amplification control of a tape recording apparatus. An amplification of this effect can be obtained by providing a further additional pulse oppositely directed to said additional pulse and also after the colour synchronization signal.

It is an object of the invention to seek to enhance the known copy protection.

According to a first aspect of the present invention there is provided Claim 1.

In an embodiment, said waveform is added to said video signal by blanking a portion of the video signal and adding the waveform to said blanked portion.

In a preferred embodiment, only active video is blanked.

In an embodiment of the invention in which the waveform is added into horizontal lines of the video signal, the right edge of the picture is replaced by a "checker" pattern appearing (like a checker board) of black and gray rectangles. The width of this checker pattern is chosen to be within the overscan (not viewed) part of the picture when displayed on a standard television receiver. It will be understood that with an abnormally low signal amplitude, when the picture content is light (such as mid gray), the left edge of the black rectangle in certain video lines will trigger an early horizontal retrace as being a negative-going (towards blanking level) transition. When the picture content is dark, the right edge of the gray rectangle (adjacent to a dark picture area), in certain video lines will trigger an early retrace on each line as also being a negative-going transition. (The description of video waveforms herein follows the convention of positive amplitude being white and negative amplitude being black).

The horizontal modification checker pattern may be generated at a rate slightly asynchronous to the video field repetition rate, so that the checker pattern appears to slowly move up or down the picture, at a rate of about 1 second for any given point to migrate from the bottom to the top of the picture or vice versa. The checker pattern has no effect on the picture when an original (authorized) cassette is replayed since no signal conditions are present in the TV set which are in any way abnormal.

However, when an illegal (unauthorized or pirated) copy of the cassette is replayed using a videotape recorder, the signal attenuation resulting from the prior art copy protection process described above, in combination with the checker pattern, causes the television set horizontal retrace to occur early in each video line where either the black or gray rectangle is present, depending on picture content and the characteristics of the videotape recorder and TV set. The black checkers and gray checkers each may cause a transition of sufficient amplitude depending on the previous active video picture content. If the picture content is light (white), the left edge of the black checker causes a negative-going transition to black; if the picture content is dark, the right edge of the gray checker causes a negative-going transition from gray to the following dark area (typically blanking level). The difference between lines ending in black or gray in turn causes a horizontal displacement to the picture information, i.e. a wiggle, which moves slowly up or down the picture.

The tendency of a television set to retrace (perform the horizontal flyback early) is exploited by providing the light to dark transition (the left edge of the black checker or the right edge of the gray checker) prior to the location in the video line of the genuine horizontal line synchronization (sync) signal. The early retrace so triggered causes the picture information on the succeeding line to be advanced, i.e. displaced horizontally to the right by an amount equal to the distance between the negative transition and the location of the leading edge of the genuine horizontal sync signal. This displacement causes a "tearing" (horizontal repositioning) of picture information.

A somewhat similar modification in the vertical picture sense inserts alternating dark and white bands in place of active video in the last few lines of selected video fields in the lower overscan portion of the picture just prior to the vertical blanking interval, and/or extending into the first few lines of the vertical blanking interval.

This vertical rate modification may be implemented in several ways. In one embodiment several of the active video lines (five or so) immediately prior to the vertical sync signal are made to alternate between blanking level and gray level (typically about 30% of peak white) at a rate of about 1 to 5 cycles per second. This can cause drum servo unlock in the copying videotape recorder, or erroneous vertical retrace in the TV set, causing the picture from the unauthorized copy to exhibit vertical instability (jump up and down) at that particular rate, substantially degrading the quality of the image. In another version, two to five lines of alternating (modulated) white-black-white are inserted at the end of each or alternate video fields, with the same result of loss of vertical lock in a copying videotape recorder or viewing TV set to interpretation of the inserted pattern as a vertical sync signal when the video signal amplitude has been reduced through AGC response to a copy protection signal.

These vertical modifications may be extended into the first few lines of the subsequent vertical blanking interval.

Thus, methods in accordance with embodiments of the invention ensure optimum conditions in terms of picture content for causing the maximum level of subjective degradation (1) to the replayed picture quality of the unauthorized copy and (2) to the recording and playback functions of videotape recorders.

The television set in response to the horizontal and vertical modifications erroneously performs the horizontal or vertical retrace at an abnormal point. In the same way that a TV set will misinterpret the signal, both the recording videotape recorder when the copy is made or the playback videotape recorder when the copy is replayed can also be affected. In this case it is the color circuitry of the videotape recorder which is affected, with resultant picture degradation additional to that caused by the basic anticopy process. This is an additional effect to what has been descried so far. This is because of the special way a videotape recorder processes the color information. The picture distortions include inaccurate color rendition and intermitted or permanent loss of color. The modifications thus further destroy the entertainment value of the illegal copy, over and above the degradation of the picture quality caused by the above-described basic prior art copy protection process.

A third modification which may be made to the video signal involves narrowing horizontal sync pulses. In combination with a copy protected video signal having reduced signal amplitude when re-recorded (copied), this narrowing causes the sensing of spurious vertical sync signals, by a videotape recorder or TV set, causing vertical retrace to take place at other than the beginning of a field and so further degrading picture quality. This modification narrows the width (duration) of the horizontal sync pulses on certain lines (such as lines 250-262) of the video field. These narrowed horizontal sync pulses, when combined with a video signal that is of diminished amplitude, trigger a spurious vertical retrace in many TV sets and videotape recorders, further degrading the displayed picture. Narrowing the horizontal sync pulses where the checker patterns exist (lines 10-250) also enhances the checker pattern distortion when an illegal copy is made.

It has been observed that the degradation of the picture quality caused by methods of the invention is particularly useful where the prior art basic copy protection process provides relatively small degradation of picture quality or relatively small degradation of videotape recorder recording or playback. Thus the combination of the prior art process with the present process severely reduces the entertainment value of the illegal copy on a much larger combination of videotape recorders and TV receivers than does the basic prior art process by itself.

Provision of the horizontal checker pattern or vertical modification only in the overscan portion of the television picture ensures that when the original recording or signal is viewed there is no visibility of the checker pattern or vertical modification, and indeed the presence thereof is not known to the viewer of the original recording.

In other embodiments, the process user might trade off picture area for effectiveness. (The user may elect to trade off visibility of the process when the "legal" recording is played, in order to enhance the process anticopy effectiveness.) Thus, the modifications may in violation of broadcast TV standards extend into the viewable portion of the video field, but still be acceptable in many applications. Furthermore, in another embodiment, the process trades off deviations from accepted signal standards to further enhance the anticopy effectiveness.

The modified signal in any case is displayed normally on any TV receiver or monitor, providing the signal is of the correct amplitude. When the modified signal amplitude is reduced, as on an illegal copy the conditions are optimised for the TV receiver to display or for a videotape recorder to playback a distorted picture. This will occur in a back-to-back video tape recorder copying situation using two videotape recorders when the recording being (illegally) copied is provided with the basic anticopy process, for example, of U.S. Patent No. 4,631,603.

The video signal modifications described above, in addition to causing lack of horizontal or vertical stability in a TV receiver, also additionally have similar effects as described above on a typical videocassette (videotape) recorder, both during recording and playback. VCRs use the leading edge of the horizontal sync pulse to correctly position the burst gate. If the burst gate is incorrectly positioned, the color burst is not sampled properly and loss of color or distorted color results. The horizontal modification causes misinterpretation of the position of the leading edge of horizontal sync. This will occur in the VCRs involved in both the recording and playback of a (copy protected) copy, resulting in color loss/distortion. This effect can also be caused independently in the TV set. In the same way that a TV set will tend to lose vertical lock as a result of this process, so will a VCR. The result is a loss of drum servo lock in the VCR.

The modifications disclosed herein ensure that the required conditions for maximum picture disruption are always present, rather than relying on chance (the particular picture being displayed) that these conditions occur. Therefore the above processes which may include the horizontal and/or vertical modifications and/or horizontal sync pulse narrowing have substantial value in enhancing the basic prior art copy protection process, and more generally enhance any copy protection process which reduces the amplitude of the video signal which is recorded when an unauthorized copy is attempted.

Horizontal jitter with illegal copying of videotapes may be caused by post horizontal pseudo sync pulses of approximately -20 IRE amplitude (-40 IRE equals normal sync amplitude) and a width of about 1-2 µs varying in position in about a range of 1-2 µs after color burst.

While the embodiments are disclosed herein specifically in the context of the NTSC television standard, they may be applied to SECAM or PAL television standard with appropriate modification.

Embodiments of the present invention will hereinafter be described, by way of example, with reference to the accompanying drawings, in which: <ul id="ul0001" list-style="none" compact="compact"><li>Figures 1a and 1b show respectively a normal picture and a modified picture with a horizontal modification checker pattern and the location of a vertical modification:</li><li>Figures 2a and 2b show a picture resulting from a video signal of normal amplitude, respectively without and with a checker pattern;</li><li>Figures 3a, 3b and 3c show the picture of Figures 2a and 2b displayed respectively on a television set with a video signal of reduced amplitude, without and with the checker pattern and vertical modification:</li><li>Figure 4 shows a portion of a video signal with a checker pattern:</li><li>Figures 5a and 5b show respectively a portion of a video signal with a vertical modification not extending into the horizontal and vertical blanking interval and with a vertical modification extending into the vertical blanking interval;</li><li>Figure 5c shows an additional vertical modification extending into the horizontal blanking interval;</li><li>Figures 6a, 6b and 6c show a circuit for modifying video signals in accordance with an embodiment of the invention;</li><li>Figures 7a, 7b show waveforms illustrating the operation of the circuit of Figures 6a, 6b and 6c;</li><li>Figure 8 shows a detail of a flicker generator of the circuit of Figure 6b;</li><li>Figure 9 shows another embodiment of a circuit for modifying a video signal;</li><li>Figure 10 shows a prior art sync separator circuit;</li><li>Figures 11 a to 11o show video waveforms illustrating horizontal sync pulse narrowing;</li><li>Figure 12a shows a block diagram of a circuit for horizontal sync pulse narrowing;</li><li>Figure 12b shows waveforms illustrating the operation of the circuit of Figure 12a;</li><li>Figures 13a, 13b show an embodiment of a circuit for horizontal sync pulse narrowing;</li><li>Figures 14a, 14b show block diagrams of apparatus for combining sync pulse narrowing with horizontal and vertical modifications of a video signal;</li><li>Figure 15 shows a circuit for enhancing a checker pattern using post-sync pulses; and</li><li>Figures 16a to 16e show waveforms illustrating the operation of the circuit of Figure 15.</li></ul>

Figure 1a shows a normal television picture 10, (without showing any actual video information), i.e. including the left and right overscan portions 14, 16 and top and bottom overscan positions 7, 9. The part of the picture inside the doted line 13 is the visible video 11.

The overscan portion of a television picture, as is well known, is that portion of the television picture not viewable on a standard television set. Because of design limitations and aesthetic considerations, standard TV sets are adjusted by the manufacturer to display somewhat less than 100% of the transmitted picture area. The portions of the television image which are not normally viewable are called the overscan area. These portions are viewable on a professional-type video monitor with underscan capability. However, all standard television receivers operate in an overscan mode, and hence the added checker pattern and the modified lines at the end of each field would not be viewable on such standard television receivers as sold in the United States and elsewhere.

Figure 1b shows a modified television picture 12 also including the overscan portions 14, 16. In the right-side overscan portion 16, a checker pattern 20 of alternating gray rectangles 24 and black rectangles 26 is provided. This checker pattern information 24, 26 provides the copy protection enhancement as described below. In the display of the picture 12 on a standard TV set the checker pattern 20 would not be seen since it is in overscan area 16. The vertical signal modification is inserted in the bottom overscan area 9 and therefore is also not visible.

Figure 2a shows a video field 30, including the left and right overscan portions 32, 34, including in the active video 36 a vertical and horizontal picture element 38 (such as for instance a cross). This field 30 is in accordance with the prior art and the checker pattern and vertical modification signal are clearly not included. This is also without any reduction of signal amplitude, i.e. without provision of the prior art copy protection process.

Figure 2b shows the field 30 with the addition of a checker pattern 42 in overscan area 34 outside border 13, and with the addition of a vertical modification pattern 87 to lower overscan portion 9. Since there is normal signal amplitude present, the checker pattern 42 and/or vertical pattern 87 have no effect on the appearance of the cross 38 which is shown normally. It is to be understood that Figure 2b is what would appear on a monitor showing the entire area and would not appear on a normal television receiver.

It is not possible to show a graphic representation of the effect of these signals on a VCR. A TV set will display artifacts due to the abnormally low signal amplitude; the VCRs used to record and replay the copy can also be affected. In this instance, the servo systems of the VCRs will be disturbed, resulting in positionally unstable pictures.

Figure 3a shows a picture 50 resulting from reduced signal amplitude, i.e. in accordance with the prior art copy protection process, acting on a relatively insensitive VCR, but without the addition of the checker pattern. This figure shows only the actual viewable portion (inside border 13 of Figures 2a, 2b) of the picture on a standard television receiver. As can be seen, the cross 38 is displayed normally because in this case the picture content is such that there is no horizontal displacement. This is a case where the prior art copy protection process provides inadequate copy protection, because the picture is viewable.

Figure 3b shows the effect of the presence of the checker pattern 42 of Figure 2b when the reduced signal amplitude is present, i.e. when the prior art copy protection process is used in conjunction with the checker pattern. Again in Figure 3b the overscan portion is not shown. Here it can be seen that the cross 38 suffers from multiple horizontal "tears" 43 which occur at the location of the transition from gray checker 46 to black checker 44 (and vice versa) of the checker pattern 42 of Figure 2b. As shown in the enlarged view of Figure 3c, portions 43 of the vertical part of cross 38 are horizontally displaced by an amount dependent on the distance between the left edge of the black portions 44 of the checker pattern and the location of the true horizontal sync signal in each line (not shown). Clearly, the picture 50 of Figure 3b is substantially degraded. The effect is further enhanced (not shown) by moving the checker pattern 42 up or down slowly in the vertical direction so that the horizontal displacements are seen to move, i.e. "wiggle". This provides a virtually unviewable picture and hence substantial copy protection.

The checker pattern 42 of Figure 2b includes typically five black rectangles 44 each alternating with one of the mid-gray rectangles 46. (Fewer such rectangles are shown in Figure 2b for clarity). It has been found that maximum picture degradation occurs with approximately five gray to black transitions and five black to gray transitions per picture height.

The signal level of the black rectangles 44 is set to be between blanking level and black level for NT-SC (black level and blanking level are the same for PAL or SECAM signals), and at black level for PAL and SECAM, and the amplitude of the mid-gray rectangles 46 is approximately 30% of peak white level. The checker pattern 42 induces the zig-zag type pattern as shown Figure 3b. In alternative embodiments, there might be only one black rectangle 44 or two, three or four or more black rectangles 44 per field 30 of Figure 2b. Also the sizes (heights and widths) of the black rectangles 44 need not be uniform.

The process causes early horizontal retrace in a low video signal amplitude environment by providing a negative-going transition, i.e. from the instantaneous picture level at the start point of the black rectangles 44 to black level prior to the horizontal sync signals on at least certain lines of the picture. The checker pattern 42 shown in Figure 2b is one such pattern which causes the intended effect.

The typical duration, (width) of the checker pattern 42 is approximately 1.0 to 2.5 microseconds, as determined by the requirement that the checker pattern normally is not introduced into the displayed portion of a standard television picture, i.e. is limited to the overscan portion, and also does not infringe upon the normal horizontal blanking period.

In other embodiments, the horizontal sync pulse is narrowed and allowing the checker pattern to be wider. This would provide a greater horizontal displacement when the reduced amplitude video signal is displayed, but result in a nonstandard original video signal, which however is acceptable for certain non-broadcast applications. Also, the particular amplitudes of the mid-gray 46 and/or black rectangles 44 need not be exactly as described above. Any effects resulting from the changed relative position of leading edge of horizontal sync pulse and the color burst can be corrected by a corresponding relocation and/or expansion of the color burst.

Figure 4 shows the horizontal blanking interval 60 for a single video line, with a portion of the checker pattern present. The horizontal sync pulse 62 conventionally starts 1.5 microseconds after the start of the horizontal blanking interval 60. Active video 66, 68 occurs both before and after the horizontal blanking interval 60. However, in accordance with the invention, a portion 70 of the active video 66 just prior to the horizontal blanking interval 60 has been replaced by either a mid-gray level signal 74 or by a black level signal 76. (The gray level 74 and the black level 76 are both shown in Figure 4 only for purposes of illustration.) The loss of portion 70 of the active video 66 is not problematic, since as explained above in a standard television receiver this portion of active video is not visible anyway, being in the overscan portion of the picture.

The transition 80 from the active video level 66 down to the black level 76 appears to the television receiver to be a horizontal sync signal. This effect (as explained above) only occurs when the video signal being displayed has reduced amplitude due to the copy protection process.

The presence of the gray level 74 (the gray portions of the checker) additionally ensures that the entire picture is not shifted to the right. This would be the case if for instance there was a solid black stripe down the right hand side of the picture. The alternating gray and black levels provide the zig zag effect shown in Figure 3b, which has been found to be intolerable for viewing by virtually any individual. Also shown in Figure 4 is a conventional color burst 82 riding on the back porch 84 of the horizontal blanking interval 60.

It will be appreciated from Figure 4 that the only modification to the video signal is the removal of the small portion of active video 70 and the substitution therefore of either the gray level 74 or black level 76.

The above described wiggle enhancement causes the checker pattern to move slowly from the bottom to the top of the picture or vice versa. It is found that if this takes approximately one second for a given transition to migrate from the bottom of the picture to the top of the picture or vice versa, this causes optimum reduction of entertainment value of the picture. This moving wiggle effect is provided by using a frequency of the square wave that generates the checker pattern being slightly offset 5 from the fifth harmonic of field rate, i.e. between 295 Hz and 305 Hz, for NTSC television. The corresponding frequency for PAL or SECAM systems is 245 to 255 Hz. This nonsynchronicity provides the desired slow movement of in the checker pattern. As noted above, even if such) asynchronicity is not present and the checker pattern is static, there is still substantial benefit from the present process. The frequency of the signal generating the checker pattern can be adjusted to maximize the degradation of the picture quality when the low amplitude signal is replayed and displayed. Frequencies between 180 and 360 Hz for NTSC and 150 to 300 Hz for PAL (3 to 5 times the field rate) typically result in an optimum effect. The frequency may be varied with time to ensure optimum effect on a variety of playback and viewing equipment.

The checker pattern need not be present on every field.

The above description is directed to horizontal picture information; the video signal modification and the consequent effect of this modification are in the horizontal picture direction. Modification of vertical information may also be provided and may take several forms. In one embodiment, groups of 1 to 4 lines in the lower overscan portion of a video field have their active video replaced alternatively with white or black. In another embodiment, the last few video lines immediately prior to the vertical sync pulse are blanked, as are the first few lines of the following vertical blanking interval, and the original picture video and vertical sync pulse therein are replaced with either a high level (such as mid gray which is about 30% peak white, or actual peak white) or a low level (in the range of black down to blanking level) signal as shown at 87 in Figures 1b, 2b and described above.

These vertical modifications are normally not visible to the viewer since the modified active video lines are restricted to those lines falling in the overscan area 9 at the bottom of the picture of Figure 1b. (Also, the modified lines will be in a similar location to the head switch point when video from a VCR is considered, and video on these lines is unusable in any case as a result of disturbances occurring at and after the head switch point.)

In a standard NTSC video signal (or in other standards) as is well known, the first three lines of the vertical blanking interval each include two equalization pulses, and the following three lines each include two "broad" vertical sync pulses. Normally vertical retrace begins shortly after the first of these vertical sync pulses.

The first vertical modification embodiment is shown in Figure 5a. (Line numbers here refer to the second field of an NTSC video frame.) Lines 517, 518, 519 have their active video portions replaced with a peak white (1.0 volt nominal) signal; the same is done in lines 523, 524, 525. In lines 520, 521, 522 the active video is replaced with a black (0 volt nominal) signal. Instead of groups of three lines, the groups may be 0 to 5 or more lines, and the white and black signals may be modulated or switched in amplitude. Thus in the last several lines of each field the pattern of the white and black signals changes dynamically between fields.

The second vertical modification embodiment (Figure 5b) blanks the last two active video lines (lines 524 and 525 for instance) in a video field and the first three lines (lines 1, 2, 3 for instance) of the immediately following VBI. These two active lines are in the lower overscan portion 9 (Figure 16) of the TV picture. Then a mid gray (30% of peak white) video signal 87 is generated and inserted in these five blanked lines on a periodic basis. When the mid gray signal is not on (indicated by vertical arrows at lines 524, ..., 3), these blanked lines "fool" the vertical sync circuitry of most TV receivers into performing the vertical retrace at the beginning of the first of these five lines, rather then normally five lines later at the beginning of the vertical sync pulses. Thus vertical retrace is advanced by five lines. When these five lines are at mid gray, vertical retrace is initiated at its proper location by normal vertical sync. It is to be understood that the number of such blanked lines and the amplitude of the inserted waveform may vary in other embodiments.

As shown in Figure 5b, lines 4-6 (only 1-4 are shown) are as in a standard signal, as are lines 517 to 523. The modification is only to lines 524, 525, 1, 2 and 3; the active video portions of lines 524, 525 and the corresponding portions of lines 1-3 are blanked (to black) or have a mid gray signal at about 0.3 volts inserted. (It is to be understood that this amplitude is nominal, without consideration of the amplitude reduction effect of the associated prior art copy protection process). Figure 5b shows a portion of a field with the mid-gray level. As stated above, the gray signal is switched on and off ("oscillates") at a rate typically between 1 Hz and 10 Hz. In the version oscillating at 1 Hz, there are 30 consecutive video fields with five lines having active video at blanking level, followed by 30 consecutive video fields with the five lines at 30% gray of Figure 5b. As shown in Figure 5b, the color burst in lines 524 to 3 may be blanked (or not).

This oscillation causes the picture to "jump" up and down by 5 lines once per second (the oscillation rate) which has been found to be extremely irritating to the viewer as suggested at "x" in Figure 3b. That is to say, on the fields where the vertical modification of Figure 5b is present, the vertical retrace occurs early by five lines, followed by the fields where the vertical retrace occurs normally. The early vertical retrace occurs because the overall video amplitude has been reduced for instance to a maximum (peak white to sync tip) of 0.4 volts from the NTSC standard 1.0 volts due to the presence of the prior art copy protection signals. The vertical sync separator of the TV receiver then perceives the first of the five blanked lines as being the first vertical sync (broad) pulse and so retraces vertically shortly thereafter.

In another version of the vertical modification (not shown) instead of the last two lines of one field and the first three lines of the next field being modified as in Figure 5b, the modification is wholly to the last five lines (lines 521, 522, 523, 524, 525) of active video of one field; this avoids producing an "illegal" (non-standard) video signal. A variation of this vertical modification is to relocate about 3 lines or more like lines 524, 525, and in Figure 5b to lines after the vertical sync area (i.e., lines 22-24). In some TV sets this causes extra jumping because the TV set "sees" two vertical sync pulses one at the right time i.e., line 4 and one at about line 23.

It is to be understood that the vertical modification need not extend over the entire active video portion of a horizontal line. It has been found that providing the modification over about 1/2 of the duration of active video in a line is sufficient to generate the premature vertical retrace.

In yet another embodiment of the vertical modification (similar in most respects to that of Figure 5a) as shown in Figure 5c, the horizontal blanking interval is removed (blanked) on lines 517, 518, 519, 523, 524, 525 where the white pulses are added. Therefore (like that of Figure 5b) this is also an "illegal" (non-standard) video signal, but is acceptable for many non-broadcast applications. The elimination of horizontal blanking on these lines increases AGC gain reduction (in VCR AGC circuits). The white pulses on lines 517, 518, 519 and 523, 524, 525 may be present in each field or modulated or switched in amplitude. Moreover, these lines with white pulses may change locations by a few lines from field to field or some multiple of field rate as to induce vertical blurring effects when an illegal copy is made and viewed on a TV set. The groups of white pulses may extend over zero to four lines.

The vertical modifications to the video signal have no effect when applied to a TV monitor as a part of an original (authorized) signal. However, if the video signal amplitude is reduced sufficiently, for example by an anticopy process, the TV monitor will tend to incorrectly detect the vertical sync information, with vertical instability resulting as described above.

Furthermore, if the vertically modified signal is applied to a VCR in conjunction with an anticopy process which results in a reduced amplitude video signal within the recording VCR, when a recording is made the VCR's drum servo will tend to be disturbed. This is because VCR's typically require a "clean" vertical sync signal to maintain correct phase, and the presence of a jittering vertical sync signal causes the VCR to lose lock. When the recording is replayed the visible effect is vertical instability of the picture plus intermittent noise bands which appear as the drum servo loses lock. (This is similar to a variable tracking error.)

In other words, the vertical rate waveform modifications function similarly to the horizontal rate waveform modification described above, except that vertical disturbances are induced rather than horizontal. The two techniques combined are more effective in terms of picture quality degradation than either one on its own. Sweeping the pulse rate of the vertical waveforms increases effectiveness to more TV sets, i.e., the frequency is varied between for instance 2 Hz and 10 Hz over a period of about 20 seconds. Sweeping the checker frequencies also will cause the horizontal tearing to go up and down resulting in a more irritating picture when an illegal copy is made.

Circuitry for inserting the above-described horizontal and vertical modifications is shown in block form in Figure 6a.

The main video signal path includes an input clamp amplifier Al; a sync pulse narrowing circuit 96; a mixing point 98 at which the waveform components of the horizontal checker and the vertical modification (jitter inducing) waveforms are added; and an output line driver amplifier A2. In this case also the video input signal into the circuit of Figure 6a may have the last 9 lines of each field blanked to a reference level. U.S. Patent 4,695,901 shows a switching circuit for blanking.

The process control and signal generation path includes a sync separator 100; control circuit 102; circuits (see Figure 6b) to generate the required signal voltages which will be added to the main video signal; and a switch selection system 104 (Figure 6a) which applies the required signal voltages under the control of the control circuit 102. (Note that in the drawings certain parts designations, e.g. U1, R1, OS1, A1 are on occasion repeated for certain components. These are not intended to represent the identical component unless explicitly indicated.)

The input video is DC restored by the input video clamp amplifier A1. (Amplifier A1 is a commercially available part, for example the Elantec EL2090.) Amplifier Al ensures that the video signal (at blanking) is at a known pre-determined DC level before adding any additional waveform components to that video signal.

The resulting clamped video signal is applied to the mixing point 98 with a source impedance Ro, typically greater than 1000 ohms. The added pulse signals to be injected are applied to the mixing point 98 with a source impedance less than 50 ohms. When it is required to modify the input video signal, for example with a checker component, the appropriate signal is selected and applied to the mixing point at a low source impedance, which overrides the input video signal from amplifier A1 and effectively replaces the input video signal with the required signal. When the input signal is to remain unchanged, the switch elements 104 are all in the open state, with the result that the video signal passes unchanged to the output line driver amplifier A2. The resulting video signal at the mixing point 98 is applied to line driver amplifier A2 to provide standard output signal level and output impedance. An output of the video clamp amplifier A1 is applied to the sync separator 100 (this is a commonly available part, for example the National Semiconductor LM 1881.) Sync separator 100 provides the composite sync pulses and frame identification signal required by the process control circuit 102.

The process control circuit 102 generate the control signals to turn on the signal selection switches 104 at the precise time (and for the required duration) that the various signals are to replace the input video signal.

All of the various signals which are to replace the original (input) video consist of a high or low steady state DC signal level. For example the checker signal "high" is a mid-gray level, typically of about 30% of peak white: the checker signal "low" is black level or blanking level. These various signal levels are generated (see Figure 6b) from potentiometers VR₁, VR₂, VR₃, VR₄ which provide adjustable signal levels (or alternatively from voltage divider resistors for fixed preset signal levels) connected across appropriate supply voltage lines. This signal is applied to the appropriate selection switch elements respectively 104-1, 104-2, 104-3, 104-4 via unity gain operational amplifiers A5 to ensure the required low output impedance into the mixing point 98.

The control circuit 102 generates the appropriate switch selection control pulses for the checker pattern and vertical modification signals (see Figure 6a). Checker pulses are applied only to selected lines; one example is to start the checker pattern at the 10th line containing picture information (i.e. after the end of vertical blanking) and end it 10 lines before the last line containing picture information (i.e. 10 lines before the start of the succeeding vertical blanking interval). Similarly, the vertical jitter modification signals are be applied only to selected lines, for example the last nine lines prior to the vertical blanking interval. Hence, both the checker pattern and vertical modification signals require control signals with both horizontal and vertical rate components.

The video input signal "video in" (see Figure 6c showing detail of Figure 6a) is buffered by amplifier A3 and coupled to sync separator via coupling capacitor C1 and a low-pass filter including resistor RI and capacitor 5 C2. Sync separator 100 provides composite sync pulses and frame identification square wave signals. The composite sync pulses are applied to a phase-locked loop (PLL) 110. The phase control ("phase adj. ") of PLL 110 using potentiometer VR₆ is adjusted so that the horizontal rate output pulse starts at the required start point of the checker, typically 2µs before the start of horizontal blanking (Figure -7a). The output signal of PLL 110 is used to derive the horizontal rate component f_H of both the checker and vertical modification signals. The burst gate output signal of sync separator 100 is inverted by inverter U5 which provides a clamping pulse for clamp amplifier Al (part number EL2090).

The frame identification square wave output ("frame pulse") of sync separator 100 is applied to a one-shot circuit OS1 to provide a frame identification pulse of approximately 1µs duration. This one-shot output signal f_v is used to derive the vertical rate component of both the checker and vertical modification signals. The horizontal-rate phase-locked loop component f_H from PLL 110 is applied to the clock input terminal of a memory-address counter 114. The frame (vertical)-rate one-shot output signal f_v is applied to the reset input terminal RS of counter 114. The memory address counter 114 output signals are applied to the memory 116, typically an EPROM which is programmed such that one of its data line output terminals provides a checker pulse enable (CPE) signal which is high during that portion of the picture period that the checker signal is to be present. A second EPROM data line output terminal provides an end-of-field identification (EFI) signal which is high during the lines at the end of each field which will have to include vertical modification signals.

The horizontal-rate phase-locked loop component f_H is also applied to a one-shot circuit OS2 which generates an end-of-line pulse (ELP) of the required duration of the checker pulses, typically 2µs (see Figure 7a).

The horizontal-rate phase-locked loop output signal f_H is also applied to another one-shot circuit OS3, providing an output pulse of approximately 13µs duration. The output of one-shot OS3 triggers another one-shot OS4 with an output pulse VJP of approximately 52µs duration. The timing and duration of pulse VJP define the position of the vertical modification inducing signal within the line time; i.e. pulse VJP is essentially on during the desired portion of the active horizontal line period.

The four signals ELP, VJP, CPE and EFI generate the required control signals for the signal selection switches 104-1, ..., 104-4 (see Figure 6b). The end of line pulse ELP is applied to a divider circuit 122 to derive the desired frequency to determine the checker frequency. The higher this frequency, the greater the number of checker dark-light-dark transitions per picture height. This frequency may be chosen within a wide range; a divider ratio of 52 (n = 52) provides a useful result. The divider 122 output signal is applied directly to one input terminal of 3-input AND gate U4. An inverted output signal of divider 122 is applied to the corresponding input terminal of second 3-input AND gate U5. The output portino of divider 122 can be a sweep oscillator circuit consisting of a pair of NE566 IC's. One NE566 is set nominally at 300 Hz and the other is set at 1 Hz. The output of the 1 Hz NE566 is fed to the frequency control input of the 300 Hz NE566. Both 3-input AND gates U4, U5 have the checker pulse enable (CPE) and end of line pulse (ELP) signals applied to their two other input terminals. The result is a high checker control (HVJ) signal at the output terminal of 3-input AND gate U4, and a low checker control (LVJ) signal at the output of 3-input AND gate U5.

A similar arrangement generates the required signals for the vertical modification control signals. An oscillator 126 (such as the commercially available part number NE555 or NE566) is configured to operate at low frequencies, typically between DC and 10 Hz. The oscillator 126 can be set to a high logic level output. Similarly the DC to 10 Hz signal output can be swept over a range of frequencies to upset as many TV sets as possible during playback of an illegal copy. This can be done as described above with a pair of NE566 IC's. The output signal of oscillator 126 is applied to one input of a 3-input AND gate U2. An inverted output signal of oscillator 126 is applied to the corresponding input terminal of a second 3-input AND gate U3. Also, each TV set may "resonate," or jitter more at unique frequencies sweeping the frequencies of oscillator 126 ensures wide coverage of different TV sets. The vertical jitter position (VJP) and end of field identification (EFI) signals (with signal EFI modified by flicker generator 130 and so designated EFI') are applied to the other two input terminals of 3-input AND gates U2, U3. The result is a high vertical jitter control (EFC H) signal at the output terminal of 3-input AND gate U2, and a low vertical jitter control (EFCL) signal at the output of 3-input AND gate U3.

It will be understood that with suitable modifications, the above apparatus will produce the added horizontal or vertical modifications after the normal horizontal or vertical sync signals, e.g. for the added vertical modifications at lines 22-24 of an NTSC television signal, so as to cause a video retrace.

The circuit of Figure 6b in conjunction with flicker generator circuit 130 via EFI' produces multiple vertical modification signal patterns.

Figure 6b shows the field or frame "flicker feature" generator 130 used in certain embodiments of the invention for modifying the horizontal and vertical modifications.

The following are achieved by this flicker feature: <ul id="ul0002" list-style="none" compact="compact"><li>1) Change the "polarity", i.e., invert the gray vs. black rectangles of the checker pattern at some particular multiple of field rate; this will for instance cause the attenuated video from an unauthorized copy to interleave the checker displacement, further degrading the viewability of the copy.</li><li>2) A field-by-field change of the position of the end of field (vertical modification) pulses causes the authorized copy to playback on a TV set an up/down flicked blur, because each field has a differently timed pseudocritical sync pulse position. This is achieved for example if: <ul id="ul0003" list-style="none" compact="compact"><li>EFI pulse is high on lines 255-257, and</li><li>EFI1 pulse is high on lines 258-260, and</li><li>EFI2 pulse is high on lines 261-262 and 1, and</li><li>EFI3 pulse is high on lines 21-23.</li></ul></li></ul>

Figure 8 shows the circuitry of flicker generator 130 of Figure 6b, and shows that these four pulses are multiplexed via multiplexer U10 (i.e., a CD4052) at a field rate by EPROM U8 (part number 27C16 or 2716). As a result, pseudo-vertical sync pulses occur differently in position depending on the field. In a simple example, EFI, EFI1, EFI2, EFI3 are stepped once per field. As a result, during playback of an unauthorized copy, the pseudo-vertical occur at lines 256 or 259 or 262 or 22 in successive fields or frames. As a result, the picture flickers because of the field rate vertical sync repositioning in the TV or VCR. EPROM U8 provides flexibility as to where the various end of field pulses are to be located as a function of time.

Figure 8 also shows how the checker pattern black vs. gray rectangles are inverted at some particular multiple 5 of field rate. The vertical sync pulses clock the 8 bit counter U7 (divide by 256, part number 74HC393). The outputs of counter U7 drive the address lines of the EPROM U8. The data output signal DO from EPROM U8 goes high to invert the checker pattern via switches SW1K, SW2K. The 3 flexibility of signal DO from EPROM U8 allows the invert commands on the checker pattern to happen pseudo-randomly or periodically, and also allows different flicker rates (i.e. every 2 fields or every 5 fields, etc.). EPROM U8 data lines D₁ and D₂ also drive multiplexer switch U10 (part number CD4052), similarly improving flexibility to generate output signal EFI'.

In Figure 6b the end of field and end of line pulses are switched through to override the video driving resistor R₀. Unless these switches have a low enough "on" resistance, video from the input program source will always superimpose on top of the end of field or end of line pulses. For example, a typical analog switch on resistance is about 100 ohms. The typical resistance R₀ is about 1000 ohms. With these values, 10% of the video superimposes on the end of line and end of field pulses. If the video goes to peak white, the end of field and end of line pulses will have a minimum of about 10% peak white (100 IRE) or 10 IRE thus rendering these added pulses useless.

To overcome these possible shortcomings, in another embodiment the added pulses are added then switched in via multi-pole switches that at the same time switch out the video source.

As shown in Figure 9, the end of field high and low states are generated by AND gate U23 with input from oscillator U22 (a 0.1 Hz to 10Hz oscillator) and input signals VJP and EFI. Switch SW103 switches between the 5 high and low states controlled by variable resistors R_B and R_A respectively. Amplifiers A10A, A10B are unity gain buffer amplifiers. To ensure against crosstalk of low states of EOF and checker pulses, switch SW103A is connected between switch SW103 and amplifier A100, and switch SW102A is connected between switch SW102 and amplifier A101. Gate U23A "and" gates switch SW103A to go to ground on all lines other than the EOF line locations. Likewise, gate U21A gates switch SW102A to ground at all times other than when the checker pulses are on. Otherwise, switches SW103A and SW102A are transparent to the EOF and checker pulses of switches SW103 and SW102, respectively. The output of switch SW103 is buffered by unity gain buffer amplifier A100 and summed into a summing amplifier A102. Similarly, switch SW102 receives the end of line high, low states generated via signal ELP, counter U20 (a divide by n counter), and signal CPE.

Variable resistors R_C and R_D provide adjustment for high and low end of line pulses respectively. Amplifier A101 buffers switch SW102 intosumming amplifier A102 via resistor R2. Amplifier A102 feeds summing amplifier A103. The post pseudo-sync pulse (PPS) is also summed into summing amplifier A103. The output of summing amplifier A103 is then: end of line pulses, end of field pulses and post pseudo-sync pulse (PPS). Switch SW101 switches in all of these pulses via OR gate U10 and inverter U11 during their coincident times, and switches in video at all other times. Amplifier A104 buffers output of switch SW101 and provide a video output "Video Out" containing video with the added pulses. Switch SW104A preblanks to video from the sync narrowing circuit to a voltage level VBLNK (i.e. O IRE) for the last active 9 lines of each TV field via "AND" gate U104B. Gate U104B has EPROM data output EFO (which turns high during the last 9 lines of the TV field) and VJP (active horizontal line pulse) at its two inputs.

A position modulation source for the PPS is controlled by voltage source Vgen. Source Vgen feeds resistor R20 with an inverted burst gate pulse into resistor R10 and capacitor C2 to form a variable delay into one shot U20. One shot U20 is approximately 1.5 µsec of variable position after burst of input video, and is gated out during the vertical blanking interval by signal CPE and NAND gate U21 B. Resistor R6 determines the amplitude of the PPS. Resistor R6 is typically set to -10 IRE to -20 IRE. The other input (U22A) of "NAND" gate U21 is normally high as to all PPS to be a constant amplitude pulse position sync. If U22A is pulsing (i.e., 300 Hz), the PPS signal is then turning on and off as well (at 300 Hz). Thus, the PPS can be a position modulated pulse, and pulse amplitude modulated sync pulse following burst.

A sync pulse narrowing circuit and method for enhancing the anticopy protection of video signals is used by itself or in cascade (as shown in Figure 6a block 96) with any of the signal modification techniques described above The reason to narrow the video signal sync (synchronization) pulses (mainly the horizontal sync pulses) is so that when an illegal copy is made, the attenuated video with reduced sync pulse width (duration) causes a playability problem when viewed on a TV set. This is because most TV set sync separators incorporate sync tip DC restoration. Because these TV set sync separators are typically driven by medium impedances, the sync pulses are partly clipped off. By narrowing the sync pulses, the sync pulses are even further clipped off. When an unauthorized copy is made of the video signal, especially with the above-described checker and/or end of field modification signal, the copy has a reduced amplitude video with reduced sync pulse width. As a result, the TV sync separator sees a severe loss in sync due to its own clipping from the narrowed sync width and the attenuation of the video itself. Thus, the TV set's sync separator does not "extract" sync properly and this causes the TV picture to be even less viewable, because the horizontal and/or vertical modification effects are more intense.

Figure 10 shows a typical prior art sync separator as used in many TV sets. This circuit operates when the inverted video is fed to the base of the transistor Q1 via a coupling capacitor C. The sync tips of the video signal charge up the capacitor C, just enough so that only the very tip of the sync pulses turn on the transistor. Resistor R_b biases the transistor so that the tips of sync are "sliced". The voltage Vc across C, is related to resistance R_b the driving resistance of the video. The larger resistance R_o, the more the amount of sync clipping is seen at V_b. If resistance R_b is too large, the transistor Q1 will start sync slicing into the video (blanking level) region, because the value of V_c is not charged up to an average level to allow a cut off of the transistor just below the sync tip level of inverted video.

Insufficient charging of capacitor C allows transistor Q1 to be turned on even when blanking level arrives. The base emitter impedance of transistor Ql is low when transistor Q1 is on. (This causes attenuation of the positive going sync pulses). Since charging capacitor C is a function of the sync pulses' width, narrowing the sync pulses makes the sync separator clip a portion of the narrowed sync more than a normal sync width. This is equivalent to sync slicing at a point closer to the video signal (i.e. video blanking level). Under normal video levels a narrowed sync pulse presents no playability problems on a VCR or TV. But when a narrowed sync pulse is recorded on an illegal copy of a copy protected cassette, the video signal is attenuated. This 5 attenuation with the narrowed sync causes the TV (during playback viewing) to not reliably extract the sync pulses and instead synchronize off parts of the video signal, i.e. blanking level.

Selectively narrowing certain horizontal sync pulses to close to zero pulsewidth (to less than 600 ns duration) so that the filter in a TV or VCR sync separator does not respond or that the sync separator coupling capacitor charges up negligibly is equivalent to there being no sync pulse in that area. These selected horizontal sync narrowed pulses near the end of the field can create a situation such that the sync separator will slice a blanked video line as a new (spurious) vertical pulse during playback. With a video signal from an illegal copy with attenuated video supplied to the TV, this situation then causes the VCR or TV to see two vertical pulses in one field, which can cause vertical jitter.

In one embodiment, the pulsation (modulation) frequencies of the end of the video field lines (those end of field lines having an amplitude 0 IRE to at least 10 IRE having parrowed horizontal sync pulses) are swept from about 1 Hz to 15 Hz. This advantageously causes the desired effect in a wide variety of TV sets.

Figure 11a shows a video signal waveform (Vin): this is inverted the video into the TV sync separator circuit in Figure 10, and is coupled to resistor R_o (where R_o = 0) of Figure 10. Figure 11b shows the effect of the coupling capacitor and resistor R_b. Note at Vb the video signal is ramping up towards the sync tip level. (This is a result of the RC time constant of resistor Rb and capacitor C since Rb&gt;&gt;Ro.)

Figure 11c shows narrowed horizontal sync pulses. The action of resistor R_o (where R_o now is medium resistance i.e. 200 to 1500 ohms), capacitor C, resistor R_b and transistor Q1 cause clipping action of the narrowed sync tip. Because the sync widths are narrower, capacitor C is not charged up sufficiently and causes more sync clipping. Recall that the charging of capacitor C is related to both the amplitude of the sync pulse and its pulse width, i.e. Vc is proportional to (sync pulse width) multiplied by (sync amplitude). The lower the voltage Vc the more the sync clipping action. Figure 11d shows this result at point in Figure 10 Vb.

Figure 11e shows an attenuated video source signal from an illegal copy with narrowed sync pulses where "A" indicates the presence of the checker pulses. The sync separator responds by clipping the sync pulses completely and as a result, parts of the video toward the end of line are interpreted as new sync pulses. Figure 11f shows this. The sync separator (inverter) transistor Q1 turns on during the clipped portion of video.

Figure 11g shows that by slicing parts of the video, the leading edge of sync is rendered unstable. This leading edge instability of the sync separator causes the TV to display an unstable image (i.e., shaking side to side). As shown by the arrows, the resulting unstable horizontal sync pulses are caused by sync narrowing or checker pulses.

Figure 11h shows what the output of the TV sync separator would have been for Figure 11d, which is a full level TV signal with narrowed sync. Thus the signal of Figure 11d poses no playability problems to a TV set. Only when the signal of Figure 11d is added to a copy protection signal and an illegal copy is made do playability problems become evident on the TV set, because the illegal copy results in an attenuated signal.

Figure 11 i shows with a full unattenuated TV signal that if selected lines near the end of a video field or after the vertical sync pulses (i.e. NTSC lines 256-259, lines 10-12) are narrowed with varying amplitude (i.e. switching from about blanking level to about 10-100 IRE), the sync separator transistor Q1 will start ramping up to slice into the picture area, i.e. "ZZ" of Figure 11j. This causes a wider pulse in the "ZZ" area, but not wide enough to cause a vertical sync pulse.

Figure 11k shows the sync separator output of the waveform of Figure 11j. If this waveform is to be accompanied by anticopy protection signals, the illegal copy will provide an attenuated signal to the TV sync separator as in Figure 11l. Figure 11l is an attenuated TV signal due to illegal copying with narrowed syncs accompanying the end of field lines.

Figure 11m shows the ramping action at point V_b via resistor Rb and capacitor C. The corresponding output of the sync separator shows at "y" a new (spurious) broad (vertical sync) pulse. This new pseudo-vertical sync pulse has been created when the narrowed horizontal sync pulses are with the end of field lines at blanking level. When the narrowed horizontal sync pulses are accompanied with 10 to 100 IRE, the TV sync separator only outputs narrow horizontal rate sync pulses, and no new broad pulses. This is because the 10 to 100 IRE levels are ignored entirely by the sync separator. By the switching in and out of blanking and greater than 10 IRE unit signals, the sync separator sees normal vertical sync sometimes followed by a spurious early or late vertical sync pulse (see Figure 11n). These spurious early and/or late vertical pulses then cause the TV to jitter up and down when playing back an illegal copy.

In some cases to get the same effect as above one can:

Narrow selected sync pulses to about zero, i. e. eliminate horizontal sync pulse so as to make TV sync separator to make spurious vertical sync pulse.

Reposition a few sync pulses with greater than 63.5 µs periods to cause the sync separator to malfunction and make a new spurious vertical sync pulse. This causes the ramping action of some sync separators to cause spurious vertical pulses.

Figure 11o shows a video signal which is free of spurious vertical sync pulses due to a video signal being above blanking, i.e. greater than about 10 IRE units in the area of the narrowed pulses. Thus if the level of the video signal is high enough relative to blanking level, the presence of narrowed horizontal sync pulses fails to generate a spurious vertical sync pulse.

As shown in the sync pulse narrowing circuit of Figure 12a, the video input signal (possibly already carrying the basic copy protection pulses) is input to terminal 160 where it is supplied to sync separator 162 and also to video adder 164. Sync separator 162 outputs separated horizontal sync (H sync) and vertical sync signals to line selector gate 166 which selects for instance lines 10 to 250 of each video field. The separated H sync pulses are also provided to one-shot circuit OS10 which in response outputs a signal of about 2 µs duration to AND gate U12, the other input of which is a line select signal indicating selected lines 10 to 250 from gate 166. In response, AND gate U12 outputs a signal representing a portion of H sync on each of these lines 10 to 250, which is scaled by amplifier 174. The output of scaling amplifier 174 is summed back into the original video signal at adder 164, the output of which is supplied to video out terminal 180.

Figure 12b shows a representation of the waveform at point Q of Figure 12a (the conventional H sync signal with color burst), and the signal at R which is the output of scaling amplifier 174. The summed result of Q and R ("video out" at lower part of Figure 12b) is seen at the video out terminal 180, which is a shortened H sync pulse with color burst.

Another circuit to perform sync narrowing with extended color burst envelope (extended burst is necessary to ensure color lock for TV sets if narrowed H syncs cause a color lock problem) is described hereinafter. Figure 13a, 13b show a circuit for introducing narrowed horizontal sync pulses throughout the active video field. Within this active field, an EPROM data output determines which lines get narrowed further. For example, this EPROM output (EPD1) can allow for lines 20-250 to have a 3.7 µs sync replaced pulse width, while lines 251-262 have a 2.0 µs sync replaced pulse width. Other combinations are possible dependent on programming EPD1 in EPROM U9. Also, another output from EPROM U9 can cause sync suppression in lines (i.e., lines 255 and/or 257) or so, before the location of the EOF pulses (this is done via AND gate U10 and EPD2 from EPROM U9). Repositioned horizontal sync narrowed sync is also possible after sync suppression in normal HBI is done.

Input video carrying any combinations of: the basic anticopy process, end of field pulses, and checker process or normal RS170 type video is DC sync restored by video amplifier Al to OV (equal to blanking level). Amplifier A1 outputs into sync separator circuit U2 which in turn outputs composite sync and a vertical pulse between 1 µs and 20 µs, To generate a burst gate to lock input video's burst to circuit 2015, care must be taken not to generate a burst gate pulse when pseudo sync pulses are present (i.e., if input video has the basic anticopy process). Thus, one shot U3 takes composite (and pseudo) sync and one shots a non-retriggerable pulse of about 45 µs, long enough to ignore equalizing and vertical 2H pulses in the vertical blanking interval and also the pseudo sync pulses that may be present (usually in the first 32 µs of the TV lines 10-20). One shot U10 delays the leading edge of input video sync by 5 µs and triggers one shot U11, a 2 µs one shot to be coincident with the input video's color burst.

Amplifier A1 drive a chroma bandpass filter amplifier A91 to input into burst phaselock loop circuit 2105. The output of PLL circuit 2105 is now a continuous wave subcarrier locked in phase with the input video's color burst. PLL Circuit 2011 adjusts the regenerated subcarrier phase to be correct at amplifier A5 output. Frame sync pulse from sync separator U2 resets address counter U8 for EPROM U9. Counter U8 is incremented by a horizontal rate pulse from amplifier A3. EPROM U9 outputs each data line that contain particular TV lines high or low in the active field.

One of the advantages of the circuit of Figures 13a and 13b is that the regenerated narrowed sync can be placed anywhere in the horizontal blanking interval (HBI). This becomes advantageous especially if the new narrowed sync can start 1 µs in advance (before) input video's horizontal sync. With a 1 µs advance in new narrowed horizontal sync and the PPS pulse, the horizontal instability with an illegal copy having the basic anticopy process results in 1 µs more in horizontal jitter. By advancing the narrowed H sync pulse, a greater time distance exists between the narrowed H sync pulse and the PPS, yielding proportionally greater instability when an illegal copy is played back.

To generate an advance narrowed H sync, the output of one shot U2 is a 45 µs pulse coincident with the leading edge of input sync is "squared" up via 32 µs one shot U4. The filter including components R1, L1 and C1 bandpass filters the output of one shot U4 into a 15.734 KHz sine wave.

By adjusting inductor L1, a sinewave in advance (or behind) of input video's H sync is produced. Comparator A3 converts this sinewave into pulses whose edges are leading or lagging the video input's leading sync edge. The "tracking" ability of filter R1, L1, C1 (with a Q of 4) to generate waveforms synchronous to the input video is, in general, better than most horizontal PLL's when the video input is from a VCR. The output of amplifier A3 then goes to 14 µs one shot U5, to generate an HBI gate signal to replace old (input) sync and burst with new narrowed sync and extended burst.

One shot U6 sets a nominal narrowed sync delay of 0.5 µs from the beginning of the input video HBI (of one shot U5's leading edge) and one shot U7 triggers off a new narrowed sync pulse. Components R2, R3 and Q1 form a switch to narrow the pulse further by shorting out transistor Q1 (emitter to collector) and via command of EPD1 (i.e., for lines 251-262 each field EPD1 is low, and high elsewhere). The output of one shot U7 is then pulses of 3.7 µs from lines 20 to 250 and pulses of 2 µs from 251 to 262. Triggering off the trailing edge of one shot U7 is one shot U12, the output of which is the extended burst gate which (about 5.5 µs pulse width).

The output of one shot U12 gates a color burst from circuit 2011 via switch SW22, and the band pass filter (3.58 Mhz) amplifier A4 shapes the extended burst envelope from switch SW22 output and couples to summing amplifier A5, via extended burst amplitude adjustment resistor R10. Narrowed H sync from one shot U7 is "anded" via gate U13 with signal EPD2 which is generally high, except for the few lines on which narrowed sync is to be suppressed, which enhances the end of field pulses. The output of gate U 13 sums into amplifier A5 via narrowed sync amplitude control resistor R8. The output amplifier of A5 is then narrowed sync plus extended color burst. Switch SW25 switches the output of amplifier A5 via AND gate U14 through OR gate U20, which switches amplifier A5 output during the HBI via one shot U5 output and EPD3, (active field location pulses i.e., lines 20-262).

Buffer amplifier A22 then outputs video from input with new narrowed H sync and extended color burst. To gate in a repositioned sync pulse (EOFRSP) in the end of field location, one shot U16 is 10 µs to 40 µs in length from the leading sync edge of input video. Gate U16 couples to gate U17 a 2 µs to 4 µs wide pulse that is delayed about 10 µs to 40 µs from the input video's leading sync edge. The output of gate U16 is enabled via AND gate U18 and EPD4 from EPROM U9. Signal EPD4 is then high at certain lines at the end of the field after sync suppression is activated via EPD2. Gate U16 drives summing amplifier A5 via EOFRSP amplitude adjustment resistor R85. Gate U 16 also turns switch SW25 on during activation of EOFRSP through OR gate U20 to insert the repositioned sync pulse (EOFRSP). Thus the output of amplifier A2 has input video, narrowed sync and possibly 1 or 2 lines of suppressed sync (no sync) or/and a few lines of repositioned narrowed H-sync.

The sync pulse narrowing is effective even if not all horizontal sync pulses in a video signal are so narrowed. It has been determined that even a relatively small number of narrowed horizontal sync pulses provide a spurious vertical retrace. For instance, three to six consecutive video lines with a narrowed horizontal sync pulse are adequate for this purpose. It is preferred to group together the narrowed horizontal sync pulses in consecutive (or at least relatively close together) lines to generate the spurious vertical retrace.

Other circuitry for sync pulse narrowing, in the context of removal of copy-protection signals, is disclosed in U.S. PatentsNos 5,157,510, and U.S. Patent No. 5,194,965.

Figures 14a and 14b show block diagrams of two apparatuses for combining the above described sync pulse narrowing with the earlier described prior art copy protection process and horizontal and vertical signal modifications.

Figure 14a shows the first such apparatus, with program video supplied to circuitry block 204, for adding the prior art copy protection signals including the added AGC and pseudo-sync pulses. The next block 206 (shown in detail in Figure 6a) adds (1) the checker pattern and (2) the vertical rate signal modifications to the end of each of selected fields. Then the sync pulse narrowing circuitry block 208 (shown in varying detail in Figures 12a and Figures 13a and 13b) further modifies the video signal, which is output at terminal 209, for instance, to a master duplicator VCR in a video cassette duplication facility. It has also been observed that the prior art basic anticopy process was improved by just adding in conjunction the sync narrowing process.

Alternatively, in Figure 14b the input program video signal is first subject to the sync pulse narrowing circuitry block 208, and to the copy protect and checker pattern and vertical rate signal modification circuitry blocks 204, 206 (shown here combined into one block) and hence supplied to output terminal 210.

It is to be understood that other apparatuses may also provide the disclosed video signal modifications, i.e. the checker pattern, end of field vertical pattern, sync narrowing, and equivalents thereof.

Figure 15 shows a circuit to add post-pseudo sync pulses to enhance anticopy effectiveness (i.e., further degrade viewability) when an illegal copy is made with the above described basic anticopy process of U. S. Patent 4,631,603.

Video with the basic anti-copy process and the enhancements described above is input to resistor R9. Amplifier A1 buffers input video and couples it via capacitor C1 into the sync separator U6. The vertical sync output of sync separator U6 resets a 12 bit counter U1. Counter U1 is clocked by horizontal sync to a PLL U2 that is locked to composite sync. EPROM U3 selects on which lines the post-pseudo sync (PSS) may appear. A pseudorandom distribution of post-pseudo sync may be used, as selected by EPROM U3. Signal D0 (an output of EPROM U3) inhibits one shot OS3 accordingly. The burst gate signal from sync separator U6 is inverted and low pass filtered by capacitor C2 and resistor R2. Voltage Vgen sums in a signal (i.e., 300 Hz triangle wave form) into capacitor C2. This causes a time varying threshold difference into one shot OS3 and thus causes a position change. The output of one shot OS3 is a fixed pulse (i.e., 1.5 µs duration) with pulse position modulation for example of ± 1µs. The output of one shot OS3 blanks out any video to blanking level via switch SW1 and adds a pulse by variable R7 to generate a post pseudo-sync pulse. Summing amplifier A3 inverts the output pulse of one shot OS3 to maintain the correct shape of the added post pseudo-sync pulse. Figures 16a to 16e show waveforms at various points in the circuit of Figure 15, as labelled. The amplitude of the post pseudo sync may be amplitude modulated via VGen2 and voltage controlled amplifier A41 which is a multiplying amplifier. The output of amplifier A41 varies in amplitude according to VGen2, being 0V when the post pseudo sync pulse is off.