MIMO antenna apparatus controlling number of streams and modulation and demodulation method

BACKGROUND OF THE INVENTION

00011. Field of the Invention

0002The present invention relates to an antenna apparatus for use in a radio communication apparatus which is controlled so as to achieve high-speed communication with increased communication capacity as well as keep high communication quality in mobile communication through a mobile telephone or the like. The present invention particularly relates to a MIMO antenna apparatus controlling the number of streams and the modulation and demodulation method, and a radio communication apparatus provided with the MIMO antenna apparatus.

00032. Description of the Related Art

0004There has been known an antenna apparatus using MIMO (Multi-Input Multi-Output) technique for simultaneously transmitting and/or receiving radio signals on a plurality of channels using a plurality of antenna elements, and such antenna apparatus includes, for example, a MIMO antenna apparatus disclosed in the Japanese patent laid-open publication No. 2004-266586 (referred to as “a first prior art document” hereinafter).

0005A mobile communication system with the MIMO antenna apparatus of the first prior art document is configured in its sender side as follows: a transmission signal is channel-encoded into number M of signals by a channel encoder, these number M of signals are modulated into number M of complex modulated signals (modulated symbols) by number M of modulators respectively, these number M of complex modulated signals are then multiplied to a complex matrix consisting of number M*L of complex coefficients by a complex matrix operation unit such that number L of complex signals are generated, and these number L of generated complex signals are transmitted through number L of transmitting antenna elements respectively. In this configuration, the complex matrix operation unit performs a matrix operation so as to weight the number M of modulated signals with different complex weight coefficients respectively, and this reads to achieving the beam forming on the radio signals transmitted from the number L of transmitting antenna elements respectively. Thus, the mobile communication system of the first prior art document is intended to attain transmission diversity effect, as well as the beam forming for suppressing interference waves. Furthermore, the invention of the first prior art document provides a data transmission method in which the modulation method and transmission rate are appropriately controlled even under a dynamically variable propagation channel environment, by virtue of the diversity effect. Moreover, the mobile communication system equipped with the MIMO antenna apparatus of the first prior art document is configured in its receiver side as follows: number N of received signals that have been received through number N of receiving antenna elements are multiplied to a complex matrix consisting of N*M complex coefficients by a MIMO demodulator such that number M of complex signals (received symbols) are generated, the number M of complex signals are demodulated into number M of demodulated signals by number M of demodulators respectively, and then, the number M of demodulated signals are channel-decoded into a received data by a channel decoder. In this configuration of the receiver side MIMO demodulator, the influences of noises and interferences can be minimized by employing the MMSE (Minimum Mean Square Error) algorithm for reducing interferences.

0006Thus, according to the first prior art document, the mobile communication system equipped with the MIMO antenna apparatus can be provided, such that at the sender side of the mobile communication system, a high-speed data communication through multiplexed channels can be achieved by multiplying the number M of modulated signals to the complex matrix consisting of the number M*L of elements so that the number L of complex signals are generated and transmitting the number L of complex signals through the number L of transmitting antenna elements respectively, and at the receiver side of the mobile communication system, the limit of interference can be extended by reducing the interferences in the MIMO demodulator.

0007Moreover, there has been known a prior art MIMO antenna apparatus having transversal filters, and such antenna apparatus includes, for example, a MIMO antenna apparatus disclosed in the Japanese patent laid-open publication No. 2005-065197 (referred to as “a second prior art document” hereinafter).

0008A MIMO-OFDM receiver equipped with the MIMO antenna apparatus of the second prior art document is configured to eliminate interference waves by transversal filters each provided for each one of a plurality of receiving antenna elements, and then to perform MIMO demodulation. In this way, the radio signals can be received by using MIMO, even in an environment including the interference waves. Therefore, according to the technique of the second prior art document, the MIMO-OFDM receiver can be provided, which can suppress the interferences, compensate for deterioration of accuracy in timing recovery and channel estimation, and achieve high-speed signal transmission in any case. Thus, according to the second prior art document, the MIMO-OFDM receiver equipped with the MIMO antenna apparatus is provided, which can receive radio signals by using MIMO and achieve the high-speed radio transmission even in the environment including interference waves, by eliminating the interference waves by means of the transversal filters each provided for each one of the receiving antenna elements and then performing the MIMO demodulation,

0009However, the prior art MIMO antenna apparatus of the first prior art document has the following problems. The first prior art document discloses the MIMO antenna apparatus which can attain the transmit diversity effect as well as achieve the beam forming for suppressing the interference waves, by providing the sender side with the number M of modulators and the number L of transmitting antenna elements, in order to increase the data transmission rate as high as possible. However, since the MIMO antenna apparatus of the first prior art document has many transmitting antenna elements, it is quite difficult to mount a number of antenna elements on a small-sized apparatus with a size of one wavelength or less, such as a mobile telephone. Moreover, even if the MIMO antenna apparatus of the first prior art document is employed at a base station of the mobile telephone system, the cost increases and the control becomes more complicated in response to an increase in the number of antenna elements.

0010Meanwhile, the prior art MIMO antenna apparatus of the second prior art document using the plurality of transversal filters has the following problems. This prior art MIMO antenna apparatus can suppress the interference waves since the transversal filters are provided for the respective receiving antenna elements, however, the size of receiver circuit becomes disadvantageously larger. In other words, it is impossible to configure this prior art MIMO antenna apparatus into a small-sized form, and to use this prior art MIMO antenna apparatus in a battery-operated mobile radio apparatus.

SUMMARY OF THE INVENTION

0011The object of the present invention is therefore to overcome the aforementioned problems, and to provide a MIMO antenna apparatus which can achieve high quality and high-speed communication even in a small-sized MIMO antenna apparatus by performing both of the interference suppression and the MIMO demodulation process when a desired receiving quality has not been attained, as well as provide a mobile radio communication apparatus provided with the MIMO antenna apparatus

0012In order to achieve the aforementioned objective, according to one aspect of the present invention, a MIMO antenna apparatus is provided that receives a plurality of radio signals modulated and transmitted by a sender-side radio station apparatus using a MIMO (Multi-Input Multi-Output) communication method with a number of data streams and a modulation and demodulation method. The MIMO antenna apparatus includes a plurality of antenna elements, detection means, MIMO demodulation means, radio transmission means, and control means. The plurality of antenna elements receive the plurality of radio signals, respectively. The detection means detects respective received signal levels of the plurality of radio signals. The MIMO demodulation means performs MIMO demodulation of the plurality of radio signals to generate a first demodulated signal, and determines a signal quality of the first demodulated signal. The radio transmission means wirelessly transmits a control signal to the sender-side radio station apparatus, and the control signal controls the MIMO communication method used by the sender-side radio station apparatus. The control means controls the sender-side radio station apparatus by making the radio transmission means transmit the control signal, and controlling the MIMO demodulation means, so as to change, based on the received signal levels and the signal quality, at least one of the number of data streams and the modulation and demodulation method for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means. In the case that the signal quality of the first demodulated signal is lower than a first threshold value, (1) when the received signal levels of all of the plurality of radio signals are equal to or larger than a second threshold value, the control means decreases the number of data streams for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means; and (2) when the received signal level of at least one of the plurality of radio signals is smaller than the second threshold value, the control means changes the modulation and demodulation method for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means to a modulation and demodulation method with a transmission rate lower than a current transmission rate.

0013Moreover, in the MIMO antenna apparatus, in the case that the signal quality of the first demodulated signal is equal to or larger than the first threshold value, when the received signal levels of all of the plurality of radio signals are equal to or larger than the second threshold value, the control means changes the modulation and demodulation method for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means to a modulation and demodulation method with a transmission rate higher than the current transmission rate.

0014Further, in the MIMO antenna apparatus, in the case that the control means has decreased the number of data streams for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means to a certain number, when number of times of demodulation performed by the MIMO demodulation means exceeds a certain maximum number of times of demodulation, the control means increases the number of data streams for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means.

0015Furthermore, the MIMO antenna apparatus further includes adaptive demodulation means and switch means. The adaptive demodulation means generates a second demodulated signal when the number of data streams is one, by weighting and demodulating the plurality of radio signals such that a main beam of the MIMO antenna apparatus is directed to a desired wave signal. The switch means is operable to input the plurality of radio signals into one of the MIMO demodulation means and the adaptive demodulation means. In the case that the control means have controlled the switch means to make the switch means input the plurality of radio signals into the MIMO demodulation means and the signal quality of the first demodulated signal is smaller than the first threshold value, (1) when the received signal levels of all of the plurality of radio signals are equal to or larger than the second threshold value, the control means decreases the number of data streams for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means to one, and controls the switch means to make the switch means input the plurality of radio signals into the adaptive demodulation means; and (2) when the received signal level of at least one of the plurality of radio signals is smaller than the second threshold value, the control means changes the modulation and demodulation method for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means to a modulation and demodulation method with a transmission rate lower than a current transmission rate.

0016Moreover, in the MIMO antenna apparatus, the adaptive demodulation means weight the plurality of radio signals by performing recurrent and repetitive processes such that the main beam of the MIMO antenna apparatus is directed to a desired wave signal.

0017Further, in the MIMO antenna apparatus, in the case that the control means have controlled the switch means to make the switch means input the plurality of radio signals into the MIMO demodulation means and the signal quality of the first demodulated signal is equal to or larger than the first threshold value, when the received signal levels of all of the plurality of radio signals are equal to or larger than the second threshold value, the control means changes the modulation and demodulation method for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means to a modulation and demodulation method with a transmission rate higher than the current transmission rate.

0018Furthermore, in the MIMO antenna apparatus, in the case that the control means have controlled the switch means to make the switch means input the plurality of radio signals into the adaptive demodulation means, when number of times of demodulation performed by the adaptive demodulation means exceeds a maximum number of times of demodulation, the control means controls the switch means to make the switch means input the plurality of radio signals into the MIMO demodulation means, and increases the number of data streams for the MIMO communication method used by the sender-side radio station apparatus and the MIMO demodulation means.

0019Moreover, in the MIMO antenna apparatus, the radio transmission means transmits the control signal to the sender-side radio station apparatus using at least one of the plurality of antenna elements.

0020According to the another aspect of the present invention, a radio communication apparatus provided with the MIMO antenna apparatus is provided.

0021Since the present invention has the above-stated configurations, the present invention can decrease the number of data streams for the MIMO communication method, and/or change the modulation and demodulation method for the MIMO communication method, based on the signal quality of the demodulated signal and the respective signal levels of the received signals. Therefore, according to the present invention, the MIMO antenna apparatus can be provided which, even if it is small in size, can adaptively control the number of data streams and the modulation and demodulation method for the MIMO communication method in the case that the desired receiving quality is not achieved, and further, can perform the high quality and high-speed communication by carrying out both the interference wave suppression and the MIMO demodulation process. Additionally, according to the present invention, the mobile radio communication apparatus with such MIMO antenna apparatus can be provided.

0022The advantageous effects derived from typical aspects of the invention disclosed in the present application will be briefly described as follows. In a MIMO radio communication incorporating the adaptive modulation, if the signal quality of the demodulated signal is equal to or lower than a threshold value, the respective received signal levels are obtained for the antenna elements constituting the MIMO antenna apparatus. If these received signal level are equal to or larger than a predetermined receiving power, the sender-side radio station apparatus is instructed to decrease the number M of transmitted data streams by one. When the number of data streams is decreased to one, the adaptive demodulation means may be used to control the amplitudes and phases of the plurality of received signals. Accordingly, a main beam of the MIMO antenna apparatus can be directed to a desired wave signal and nulls of the MIMO antenna apparatus can be directed to interference wave signals. If the signal quality of the demodulated signal is lower than the threshold value, the sender-side radio station apparatus is instructed to use a modulation and demodulation method with a lower transmission rate for data transmission. Thus, high-speed and high signal quality communication can be achieved through utilizing both of the high-speed radio transmission by the MIMO communication and the interference wave suppression technique using the adaptive array antenna.

BRIEF DESCRIPTION OF THE DRAWINGS

0023These and other objects and features of the present invention will become clear from the following description taken in conjunction with the preferred embodiments thereof with reference to the accompanying drawings, throughout which like parts are designated by like reference numerals, and in which:

0024<figref idref="DRAWINGS">FIG. 1</figref> is a block diagram showing a configuration of a MIMO antenna apparatus according to a first preferred embodiment of the present invention;

0025<figref idref="DRAWINGS">FIG. 2</figref> is a block diagram showing a configuration of a MIMO antenna apparatus according to a modified preferred embodiment of the first preferred embodiment of the present invention;

0026<figref idref="DRAWINGS">FIG. 3</figref> is a perspective view showing a configuration of a mobile radio communication apparatus equipped with the MIMO antenna apparatus according to a first implemental example of the first preferred embodiment of the present invention;

0027<figref idref="DRAWINGS">FIG. 4</figref> is a perspective view showing a configuration of a mobile radio communication apparatus equipped with the MIMO antenna apparatus according to a second implemental example of the first preferred embodiment of the present invention;

0028<figref idref="DRAWINGS">FIG. 5</figref> is a perspective view showing a configuration of a mobile radio communication apparatus equipped with the MIMO antenna apparatus according to a third implemental example of the first preferred embodiment of the present invention;

0029<figref idref="DRAWINGS">FIG. 6</figref> is a perspective view showing a configuration of a mobile radio communication apparatus equipped with the MIMO antenna apparatus according to a fourth implemental example of the first preferred embodiment of the present invention;

0030<figref idref="DRAWINGS">FIG. 7</figref> is a flowchart showing a control flow of MIMO adaptive control process performed by the controller <b>5</b> shown in <figref idref="DRAWINGS">FIG. 1</figref>;

0031<figref idref="DRAWINGS">FIG. 8</figref> is a sub-routine flowchart showing a control flow of SISO communication process of Step S<b>11</b> shown in <figref idref="DRAWINGS">FIG. 7</figref>;

0032<figref idref="DRAWINGS">FIG. 9</figref> is a graph showing instantaneous CNR and BER for explaining determination based on a threshold value in the MIMO adaptive control process shown in <figref idref="DRAWINGS">FIG. 7</figref>;

0033<figref idref="DRAWINGS">FIG. 10</figref> is a graph showing time-averaged CNR and BER for explaining determination based on a threshold value in the MIMO adaptive control process shown in <figref idref="DRAWINGS">FIG. 7</figref>;

0034<figref idref="DRAWINGS">FIG. 11</figref> is a block diagram showing a configuration of the MIMO antenna apparatus according to a second preferred embodiment of the present invention;

0035<figref idref="DRAWINGS">FIG. 12</figref> is a block diagram showing a configuration of a MIMO antenna apparatus according to a modified preferred embodiment of the second preferred embodiment of the present invention;

0036<figref idref="DRAWINGS">FIG. 13</figref> is a flowchart showing a first part of a control flow of MIMO adaptive control process performed by the controller <b>5</b> shown in <figref idref="DRAWINGS">FIG. 11</figref>; and

0037<figref idref="DRAWINGS">FIG. 14</figref> is a flowchart showing a second part of the control flow of MIMO adaptive control process performed by the controller <b>5</b> shown in <figref idref="DRAWINGS">FIG. 11</figref>.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

0038The preferred embodiments according to the present invention will be described below in a detailed manner with reference to the attached drawings. In the whole drawings in which the preferred embodiments of the present invention are explained, the parts having similar functions are denoted by the same reference numerals, respectively, and accordingly, they are not explained repeatedly.

First Preferred Embodiment

0039<figref idref="DRAWINGS">FIG. 1</figref> is a block diagram showing a configuration of a MIMO antenna apparatus according to a first preferred embodiment of the present invention. Referring to <figref idref="DRAWINGS">FIG. 1</figref>, the MIMO antenna apparatus according to the present preferred embodiment will be described below. Referring to <figref idref="DRAWINGS">FIG. 1</figref>, three different radio signals transmitted from a sender-side radio station apparatus (not shown) using a certain MIMO communication method are received through three receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b</i>, <b>1</b><i>c</i>, respectively, and the respective received radio signals are inputted into an analog/digital (A/D) converter circuit <b>2</b>. The A/D converter circuit <b>2</b> includes three A/D converters each corresponding to each one of the input radio signals, performs an A/D conversion process on each one of the radio signals by these A/D converters individually, and outputs the processed signals (hereinafter, referred to as “received signals”) to both of a MIMO demodulator circuit <b>3</b> and a signal level detection circuit <b>4</b>. The MIMO demodulator circuit <b>3</b> performs a MIMO demodulation process on the three received signals to output one demodulated signal, as well as determines a bit error rate (BER) of the demodulated signal as a basis representing a signal quality of the demodulated signal, and outputs the determined result to a controller <b>5</b>. As the signal quality, a packet error rate or a throughput (e.g., in the rate of the received data) can be used in place of the BER. The signal level detection circuit <b>4</b> detects respective signal levels of the three received signals and outputs the detected results to the controller <b>5</b>. The signal level detection circuit <b>4</b> detects the signal levels in the form of, for example, carrier-to-noise power ratios (CNRs) or signal-to-interference plus noise power ratios (SINRs). Further, the MIMO demodulator circuit <b>3</b> informs to the controller <b>5</b> of the number of times by which demodulation processes on data of the received signals are performed (hereinafter, referred to as “the number of times of demodulation”), e.g., in units of a predetermined amount of data (such as the number of bits or the number of packets). The controller <b>5</b> performs a MIMO adaptive control process based on the information on the BER and the signal levels as described below with reference to <figref idref="DRAWINGS">FIGS. 7 and 8</figref>, and accordingly, changes a communication method used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b>.

0040In the present preferred embodiment, the communication method used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b> is specified by the number of data streams for a communication and a modulation and demodulation method for the communication. More specifically, the MIMO antenna apparatus and the sender-side radio station apparatus can selectively execute one of MIMO communications each utilizing one, two or three data streams. If the number of data streams is one, such MIMO communication is also referred to as “SISO (Single-Input Single-Output) communication”. Additionally, the MIMO antenna apparatus and the sender-side radio station apparatus can perform a MIMO communication (or a SISO communication) in which one of a plurality of modulation and demodulation methods with different transmission rates is selectively used. For example, the MIMO antenna apparatus and the sender-side radio station apparatus can communicate with each other by selectively using one of BPSK, QPSK, 16QAM and 64QAM (these are listed in ascending order for the transmission rate). The modulation and demodulation method to be used is not limited to one of those mentioned above, but can be changed according to an implemental example. When the controller <b>5</b> is to change the communication method used in the sender-side radio communication apparatus and in the MIMO demodulator circuit <b>3</b> (i.e., to change at least one of the number of data streams and the modulation and demodulation method), the controller <b>5</b> transmits a control signal through a radio transmitter circuit <b>6</b> and a transmitting antenna element <b>7</b> connected to the radio transmitter circuit <b>6</b>, for requesting the sender-side radio communication apparatus to change a modulation process for the communication method used in the sender-side radio communication apparatus (i.e., the MIMO communication or the SISO communication), as well as changes a demodulation process for the communication method used in the MIMO demodulator circuit <b>3</b> (i.e., the MIMO communication or the SISO communication).

0041It is preferable that if necessary, the MIMO antenna apparatus according to the present preferred embodiment includes high-frequency filters each separating a signal at a predetermined frequency from each of the radio signals received through the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c</i>, and high-frequency amplifiers each amplifying the signals, in front of the A/D converter circuit <b>2</b>. It is also preferable that if necessary, the MIMO antenna apparatus according to the present preferred embodiment includes high-frequency circuits such as mixers for the frequency conversion of the respective received signals outputted from the A/D converter circuit <b>2</b>, intermediate-frequency circuits, and signal processing circuits etc., in front of the MIMO demodulator circuit <b>3</b>. For simplicity, the above-mentioned constituent elements are not described or shown in the specification and the drawings of the present application.

0042As an example, the MIMO antenna apparatus having three receiving antenna elements will be described in this specification. Alternatively, the MIMO antenna apparatus may be configured to have two receiving antenna elements or four or more receiving antenna elements. Moreover, the MIMO antenna apparatus having one transmitting antenna element will be described in this specification as an example. Alternatively, the MIMO antenna apparatus may be configured to have a plurality of transmitting antenna elements.

0043As described so far, the MIMO antenna apparatus according to the present preferred embodiment is configured so that the controller <b>5</b> reduces the number of data streams for the MIMO communication method and/or changes the modulation and demodulation method for the MIMO communication method, based on the signal quality of the demodulated signal and the signal levels of the respective received signals. Therefore, according to the present preferred embodiment, the MIMO antenna apparatus can be provided which, even if it is small in size, can perform a high quality and high-speed communication by adaptively controlling the number of data streams and the modulation and demodulation method for the MIMO communication method in the case that the desired receiving quality is not achieved.

0044<figref idref="DRAWINGS">FIG. 2</figref> is a block diagram showing a configuration of a MIMO antenna apparatus according to a modified preferred embodiment of the first preferred embodiment. The MIMO antenna apparatus according to the modified preferred embodiment is characterized in that the transmitting antenna <b>7</b> shown in <figref idref="DRAWINGS">FIG. 1</figref> is integrated with one of the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c </i>for MIMO reception (in the example of <figref idref="DRAWINGS">FIG. 2</figref>, the transmitting antenna is integrated with the antenna element <b>1</b><i>c</i>). Referring to <figref idref="DRAWINGS">FIG. 2</figref>, the antenna element <b>1</b><i>c </i>is equipped with an antenna duplexer <b>21</b> at its bottom. A radio signal received through the antenna element <b>1</b><i>c </i>is inputted into an A/D converter <b>2</b> via the antenna duplexer <b>21</b>, whereas a radio signal outputted from a radio transmission circuit <b>6</b> excites the antenna element <b>1</b><i>c </i>via the antenna duplexer <b>21</b>. The antenna duplexer <b>21</b> is used to separate a received signal from a transmitted signal in the case that the received signal and the transmitted signal differ in frequency. As an alternative, the transmitting antenna element <b>7</b> may be integrated with either the receiving antenna element <b>1</b><i>a </i>or <b>1</b><i>b</i>. With the above-stated configuration, the MIMO antenna apparatus according to the modified preferred embodiment shown in <figref idref="DRAWINGS">FIG. 2</figref> can reduce the number of antenna elements in the apparatus, and accordingly, the MIMO antenna apparatus can be efficiently implemented in a small-sized mobile radio communication terminal.

0045Furthermore, in the modified preferred embodiment shown in <figref idref="DRAWINGS">FIG. 2</figref>, one configuration is taken for instance in which only one receiving antenna element is used as the transmitting antenna element, however, the present invention is not limited to such configuration. The MIMO antenna apparatus can be configured to use, as transmitting antenna elements, two or more of the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c</i>. By configuring in such manner, the antenna gain is expected to improve even during transmission in virtue of the beam forming effect of array antenna. Moreover, when two or more of the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c </i>are used as transmitting antenna elements, it is possible to provide the transmission diversity, typically including the switching diversity based on switch control, or to achieve the MIMO transmission. Accordingly, the radio signals can be transmitted in more stable manner and at higher speed. Moreover, in the modified preferred embodiment shown in <figref idref="DRAWINGS">FIG. 2</figref>, the configuration with the antenna duplexer <b>21</b> has been exemplarily described for separating the received signal and the transmitted signal, however, the present invention is not limited to such configuration. The MIMO antenna apparatus may be configured to employ a switch or a circulator. The switch is the best suited to the case that the signals are transmitted in time intervals different from those for receiving signals, and the circulator can be employed even when there is no difference in frequency or in time between the transmitted signal and the received signal.

0046Referring to <figref idref="DRAWINGS">FIGS. 3 to 6</figref>, implemental examples are described below, in each of which the MIMO antenna apparatus according to the present preferred embodiment is implemented as a mobile radio communication apparatus. <figref idref="DRAWINGS">FIG. 3</figref> is a perspective view showing a configuration of a mobile radio communication apparatus equipped with the MIMO antenna apparatus according to a first implemental example of the present preferred embodiment.

0047The mobile radio communication apparatus shown in <figref idref="DRAWINGS">FIG. 3</figref> is configured as a folding mobile telephone which includes an upper housing <b>31</b> and a lower housing <b>32</b> each substantially shaped in a rectangular parallelepiped, and in which the upper housing <b>31</b> and the lower housing <b>32</b> are connected to each other by a hinge unit <b>33</b>. The upper housing <b>31</b> is configured to include a loudspeaker <b>35</b> and a display <b>36</b>, and the lower housing <b>32</b> is configured to include a keyboard <b>37</b> and a microphone <b>38</b>. In the upper housing <b>31</b>, a strip-shaped conductor <b>1</b><i>aa </i>is provided so as to be proximate to a left side of the upper housing <b>31</b> and to be in parallel to a longitudinal direction of the mobile radio communication apparatus. The strip-shaped conductor <b>1</b><i>aa </i>is electrically connected to a hinge conductor lab that constitutes a part of the hinge unit <b>33</b>. The strip-shaped conductor <b>1</b><i>aa </i>and the hinge conductor lab act as the receiving antenna element <b>1</b><i>a </i>as a whole. Similarly, in the upper housing <b>31</b>, a strip-shaped conductor <b>1</b><i>ba </i>is provided so as to be proximate to a right side of the upper housing <b>31</b> and to be in parallel to the longitudinal direction of the mobile radio communication apparatus. The strip-shaped conductor <b>1</b><i>ba </i>is electrically connected to a hinge conductor <b>1</b><i>bb </i>that constitutes a part of the hinge unit <b>33</b>. The strip-shaped conductor <b>1</b><i>ba </i>and the hinge conductor <b>1</b><i>bb </i>act as the receiving antenna element <b>1</b><i>b </i>as a whole. In the lower housing <b>32</b>, the receiving antenna element <b>1</b><i>c </i>is provided which is made of a strip-shaped conductor and folded into U-shape. In the implemental example shown in <figref idref="DRAWINGS">FIG. 3</figref>, a part of the receiving antenna element <b>1</b><i>c </i>is provided so as to penetrate into a boom unit <b>34</b> that protrudes from a lower end of the lower housing <b>32</b>. Alternatively, the entire receiving antenna element <b>1</b><i>c </i>may be provided in the lower housing <b>32</b>. Additionally, the transmitting antenna element <b>7</b> made of a rod-shaped conductor is provided so as to protrude from the lower housing <b>32</b>. The mobile radio communication apparatus has a radio communication circuit <b>39</b> including the A/D converter circuit <b>2</b>, the MIMO demodulator circuit <b>3</b>, the signal level detection circuit <b>4</b>, the controller <b>5</b>, the radio transmitter circuit <b>6</b> and the like shown in <figref idref="DRAWINGS">FIG. 1</figref>. The A/D converter circuit <b>2</b> of the radio communication circuit <b>39</b> is connected to the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c</i>, and the radio transmitter circuit <b>6</b> of the radio communication circuit <b>39</b> is connected to the transmitting antenna element <b>7</b>.

0048<figref idref="DRAWINGS">FIG. 4</figref> is a perspective view showing a configuration of a mobile radio communication apparatus equipped with the MIMO antenna apparatus according to a second implemental example of the present preferred embodiment. In the second implemental example, the rod-shaped antenna element <b>7</b> shown in <figref idref="DRAWINGS">FIG. 3</figref> is removed. Instead of the antenna element <b>7</b>, a radio communication circuit <b>39</b> further includes an antenna duplexer <b>21</b>, and one of the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c </i>(e.g., the receiving antenna element <b>1</b><i>a</i>) is used to serve as both the receiving antenna element and the transmitting antenna element. According to the mobile radio communication apparatus in the implemental example shown in <figref idref="DRAWINGS">FIG. 4</figref>, a more compact mobile radio communication apparatus than the implemental example shown in <figref idref="DRAWINGS">FIG. 3</figref> can be provided by virtue that the antenna element protruding outside of the apparatus is removed.

0049<figref idref="DRAWINGS">FIG. 5</figref> is a perspective view showing a configuration of a mobile radio communication apparatus equipped with the MIMO antenna apparatus according to a third implemental example of the present preferred embodiment. In this configuration, the mobile radio communication apparatus has two receiving antenna elements <b>1</b><i>a </i>and <b>1</b><i>b </i>provided in the upper housing <b>31</b> and one transmitting antenna element <b>7</b> provided in the lower housing <b>32</b>. The mobile radio communication apparatus may optionally include an antenna duplexer <b>21</b> in the radio communication circuit <b>39</b> and use one of the receiving antenna elements <b>1</b><i>a </i>and <b>1</b><i>b </i>to serve as both of the receiving antenna element and the transmitting antenna element, for providing the transmission diversity using the two transmitting antenna elements.

0050<figref idref="DRAWINGS">FIG. 6</figref> is a perspective view showing a configuration of a mobile radio communication apparatus equipped with the MIMO antenna apparatus according to a fourth implemental example of the present preferred embodiment. In this configuration, the mobile radio communication apparatus has two antenna elements <b>1</b><i>a </i>and <b>1</b><i>b </i>in the upper housing <b>31</b> and uses one of the antenna elements <b>1</b><i>a </i>and <b>1</b><i>b </i>to serve as both of the receiving antenna element and a transmitting antenna element. By configuring in such manner, an internal structure of the mobile radio communication apparatus can be significantly simplified as compared with those of the mobile radio communication apparatus according to the other implemental examples.

0051The operation principle of the MIMO antenna apparatus according to the present preferred embodiment will be described below.

0052The MIMO communication system falls under a technique for increasing a transmission capacity and for increasing a total transmission rate in relation to a plurality of signal sequences after MIMO demodulation, by employing a plurality of antenna elements in each of a transmitter and a receiver and spatially multiplexing the plurality of signal sequences simultaneously transmitted in the same frequency band. In the present specification, the MIMO communication system is described based on an eigenmode transmission scheme by way of example. It is supposed that the number of antenna elements in each of the transmitter and the receiver is n, then the received signal y is expressed by the following equation: <br /><i>y=Hx+w</i>  (1),<br /> where symbol y denotes a received signal and is of a vector with a size of n, and each element of the vector denotes a signal received through each one of the antenna elements of the receiver. Symbol H denotes a matrix with a size of n*n, the matrix is called “channel matrix”, and each element HU of the matrix denotes a propagation coefficient between a j-th antenna element of the transmitter and an i-th antenna element of the receiver, i.e., amounts of phase rotation and amplitude attenuation for the signal transmitted between these antenna elements. Furthermore, symbol x denotes a transmitted signal and is of a vector with a size of n, and each element x_iof the vector is a signal transmitted from each one of the antenna elements of the transmitter and orthogonal to the other signals. Symbol w is of a vector with a size of n, and each element of the vector denotes a thermal noise received through each one of the antenna elements of the receiver.

0053For obtaining the channel matrix H at the receiver, the receiver stores therein a predetermined pilot signal x in advance, the transmitter transmits this known pilot signal x to the receiver, and the receiver calculates the channel matrix H by using the equation (1) based on the pilot signal x previously stored in the receiver and the received signal y (i.e., the transmitted pilot signal x).

0054Then, by carrying out a singular value decomposition (SVD) on the channel matrix H, the following equation (2) is obtained:

0055<maths id="MATH-US-00001" num="00001"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><mi>H</mi><mo>=</mo><mrow><mrow><mi>U</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><mi>Σ</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><msup><mi>V</mi><mi>H</mi></msup></mrow><mo>=</mo><mrow><munderover><mo>∑</mo><mrow><mi>i</mi><mo>=</mo><mn>1</mn></mrow><mi>q</mi></munderover><mo>⁢</mo><mrow><msub><mi>σ</mi><mi>i</mi></msub><mo>⁢</mo><msub><mi>u</mi><mi>i</mi></msub><mo>⁢</mo><msubsup><mi>v</mi><mi>i</mi><mi>H</mi></msubsup></mrow></mrow></mrow></mrow><mo>,</mo></mrow></mtd><mtd><mrow><mo>(</mo><mn>2</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0001.tif" /><br /> where symbols U, Σ and V denote matrixes each with a size of n*n, and the matrix Σ consists of σ_i(0≦i≦q) at i-th row and an i-th column elements and 0 at the other elements. Further, symbol u_idenotes i-th column vector of the matrix U, and is orthogonal to the other column vectors, and similarly, symbol v_idenotes i-th column vector of the matrix V, and is orthogonal to the other vectors. Symbol q denotes a rank of the channel matrix H, and let q=n in the following description. A superscript H denotes a complex conjugate transposition. Further, the matrixes U and V satisfy the following equation (3): <br />U^HU=I_n  (3), and<br />V^HV=I_n  (4),<br /> where the symbol I_nis a identity matrix with a size of n*n.

0056Moreover, by carrying out eigenvalue decomposition (EVD), the following equation (5) is obtained:

0057<maths id="MATH-US-00002" num="00002"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><msup><mi>HH</mi><mi>H</mi></msup><mo>=</mo><mrow><mrow><mi>U</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><mi>Σ</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><msup><mrow><msup><mi>V</mi><mi>H</mi></msup><mo>⁡</mo><mrow><mo>(</mo><mrow><mi>U</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><mi>Σ</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><msup><mi>V</mi><mi>H</mi></msup></mrow><mo>)</mo></mrow></mrow><mi>H</mi></msup></mrow><mo>=</mo><mrow><mrow><mi>U</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><mi>Σ</mi><mo>⁢</mo><mstyle><mspace width="0.3em" height="0.3ex" /></mstyle><mo>⁢</mo><msup><mi>Σ</mi><mi>H</mi></msup><mo>⁢</mo><msup><mi>U</mi><mi>H</mi></msup></mrow><mo>=</mo><mrow><munderover><mo>∑</mo><mrow><mi>i</mi><mo>=</mo><mn>1</mn></mrow><mi>q</mi></munderover><mo>⁢</mo><mrow><msub><mi>λ</mi><mi>i</mi></msub><mo>⁢</mo><msub><mi>u</mi><mi>i</mi></msub><mo>⁢</mo><msubsup><mi>u</mi><mi>i</mi><mi>H</mi></msubsup></mrow></mrow></mrow></mrow></mrow><mo>,</mo></mrow></mtd><mtd><mrow><mo>(</mo><mn>5</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0002.tif" /><br /> where symbol λ_idenotes eigenvalues of a channel matrix product HH^Hand satisfies λ_i=σ_i².

0058A vector u_i^His orthogonal to the other row vectors of the matrix UH, and used as weight coefficients (amplitudes and phases) for the signals transmitted from the respective antenna elements of the transmitter. The vector u_iis orthogonal to the other column vectors of the matrix U, and used as weight coefficients (amplitudes and phases) for the signals received at the respective antenna elements of the receiver. By using the weight coefficients in such manner, a directivity that the signals are orthogonal to one another can be obtained.

0059Now, according to the equation (1), respective powers of the received signals are represented as: Hx(Hx)^H=HH^Hxx^H. The matrix xx^Hrepresents respective powers of the transmitted signals. It is to be noted that since the respective elements of the vector x are the signals orthogonal to one another, the matrix xx^His a diagonal matrix diag [x₁x₁*, x₂x₂*, . . . , x_nx_n*] and the matrix HH^His a diagonal matrix diag [λ₁, λ₂, . . . , λ_q]. Namely, by employing the orthogonal weight coefficients for the respective antenna elements in each of the transmitter and the receiver, a plurality of propagation channels can be separated, and in this case, the respective powers of the received signals are λ_ix_ix_i*. If all the signals x₁are equal to each other, the powers of the received signals in the respective propagation channel are proportional to the eigenvalues λ_i.

0060Here, it is specifically described how to derive the powers of received signals, by taking a MIMO communication system as an example in which a transmitter has two antenna elements and a receiver has two antenna elements. In this case, the channel matrix H, and the transmitted signal vector x including the signals transmitted from the antenna elements of the transmitter are expressed by the following equations (6) and (7), respectively:

0061<maths id="MATH-US-00003" num="00003"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><mi>H</mi><mo>=</mo><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>H</mi><mn>11</mn></msub></mtd><mtd><msub><mi>H</mi><mn>12</mn></msub></mtd></mtr><mtr><mtd><msub><mi>H</mi><mn>21</mn></msub></mtd><mtd><msub><mi>H</mi><mn>22</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow></mrow><mo>,</mo><mi>and</mi></mrow></mtd><mtd><mrow><mo>(</mo><mn>6</mn><mo>)</mo></mrow></mtd></mtr><mtr><mtd><mrow><mi>x</mi><mo>=</mo><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>x</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>x</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>.</mo></mrow></mrow></mtd><mtd><mrow><mo>(</mo><mn>7</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0003.tif" />

0062Now, suppose that the symbol w denotes a noise vector (ratio in amplitude with respect to the transmitted signal vector x) including the noises received through the antenna elements of the receiver, then a received signal vector y is expressed by the following equation (8):

0063<maths id="MATH-US-00004" num="00004"><math overflow="scroll"><mtable><mtr><mtd><mtable><mtr><mtd><mrow><mi>y</mi><mo>=</mo><mrow><mrow><mi>H</mi><mo>·</mo><mi>x</mi></mrow><mo>+</mo><mi>w</mi></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mrow><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>H</mi><mn>11</mn></msub></mtd><mtd><msub><mi>H</mi><mn>12</mn></msub></mtd></mtr><mtr><mtd><msub><mi>H</mi><mn>21</mn></msub></mtd><mtd><msub><mi>H</mi><mn>22</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>x</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>x</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow></mrow><mo>+</mo><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>w</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>w</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>y</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>y</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>.</mo></mrow></mrow></mtd></mtr></mtable></mtd><mtd><mrow><mo>(</mo><mn>8</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0004.tif" />

0064Next, a covariance matrix R_yyof the received signal vector y is calculated from the following equation (9):

0065<maths id="MATH-US-00005" num="00005"><math overflow="scroll"><mtable><mtr><mtd><mtable><mtr><mtd><mrow><msub><mi>R</mi><mi>yy</mi></msub><mo>=</mo><mrow><mi>y</mi><mo>·</mo><msup><mi>y</mi><mi>H</mi></msup></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>y</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>y</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>·</mo><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>y</mi><mn>1</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>y</mi><mn>2</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow><mo>.</mo></mrow></mrow></mrow></mtd></mtr></mtable></mtd><mtd><mrow><mo>(</mo><mn>9</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0005.tif" />

0066The vector y^Hin the equation (9) is expressed by the following equation (10):

0067<maths id="MATH-US-00006" num="00006"><math overflow="scroll"><mtable><mtr><mtd><mtable><mtr><mtd><mrow><msup><mi>y</mi><mi>H</mi></msup><mo>=</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>y</mi><mn>1</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>y</mi><mn>2</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mrow><mrow><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>x</mi><mn>1</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>x</mi><mn>2</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>H</mi><mn>11</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>H</mi><mn>12</mn><mo>*</mo></msubsup></mtd></mtr><mtr><mtd><msubsup><mi>H</mi><mn>21</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>H</mi><mn>22</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>w</mi><mn>1</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>w</mi><mn>2</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow><mo>.</mo></mrow></mrow></mtd></mtr></mtable></mtd><mtd><mrow><mo>(</mo><mn>10</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0006.tif" />

0068Generally speaking, in the MIMO communication system, different signals transmitted from the different antenna elements of the transmitter are uncorrelated to one another. The meaning of term “uncorrelated signals” is described below. It is supposed that a transmitted signal sequence is a one-dimensional signal sequence consisting of elements “−1” and “1”. For example, consider a case that each of the transmitted signal vectors x₁and x₂includes the following four elements: <br /><i>x</i>₁=(1,−1,1,1)  (11), and<br /><i>x</i>₂=(1,1,−1,1)  (12).

0069Under a definition of “correlation”, i.e., a sum of products of the corresponding elements in the respective signal sequences divided by the length of the signal sequences, a correlation value R₁₂between the transmitted signal vectors x₁and x₂is expressed by the following equation (13): <br /><i>R</i>₁₂=(1*1+(−1)*1+1*(−1)+1*1)/4=0  (13).

0070Namely, if the correlation value R₁₂is 0, the transmitted signal vectors x₁and x₂are uncorrelated to each other. Conversely, the correlation value R₁₂is 1 in the case that the transmitted signal vectors x₁and x₂are equal, i.e., x₁=x₂. Furthermore, the noise vector is uncorrelated to the transmitted signal vectors, and the noise vectors received through different antenna elements are uncorrelated to one another.

0071Accordingly, as the powers of the received signals, an expectation of the covariance matrix R_yyof the equation (9) can be calculated by the following equation (14):

0072<maths id="MATH-US-00007" num="00007"><math overflow="scroll"><mtable><mtr><mtd><mtable><mtr><mtd><mrow><msub><mi>R</mi><mi>yy</mi></msub><mo>=</mo><mi /><mo>⁢</mo><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>y</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>y</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>y</mi><mn>1</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>y</mi><mn>2</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mi /><mo>⁢</mo><mrow><mrow><mrow><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>H</mi><mn>11</mn></msub></mtd><mtd><msub><mi>H</mi><mn>12</mn></msub></mtd></mtr><mtr><mtd><msub><mi>H</mi><mn>21</mn></msub></mtd><mtd><msub><mi>H</mi><mn>22</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>x</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>x</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>x</mi><mn>1</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>x</mi><mn>2</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>H</mi><mn>11</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>H</mi><mn>21</mn><mo>*</mo></msubsup></mtd></mtr><mtr><mtd><msubsup><mi>H</mi><mn>12</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>H</mi><mn>22</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow><mo>+</mo></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mi /><mo>⁢</mo><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>w</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>w</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>·</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>w</mi><mn>1</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>w</mi><mn>2</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mi /><mo>⁢</mo><mrow><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>H</mi><mn>11</mn></msub></mtd><mtd><msub><mi>H</mi><mn>12</mn></msub></mtd></mtr><mtr><mtd><msub><mi>H</mi><mn>21</mn></msub></mtd><mtd><msub><mi>H</mi><mn>22</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>H</mi><mn>11</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>H</mi><mn>21</mn><mo>*</mo></msubsup></mtd></mtr><mtr><mtd><msubsup><mi>H</mi><mn>12</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>H</mi><mn>22</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow><mo>+</mo><mrow><mo>[</mo><mtable><mtr><mtd><msup><mrow><mo></mo><msub><mi>w</mi><mn>1</mn></msub><mo></mo></mrow><mn>2</mn></msup></mtd><mtd><mrow><msub><mi>w</mi><mn>1</mn></msub><mo>⁢</mo><msubsup><mi>w</mi><mn>2</mn><mo>*</mo></msubsup></mrow></mtd></mtr><mtr><mtd><mrow><msub><mi>w</mi><mn>2</mn></msub><mo>⁢</mo><msubsup><mi>w</mi><mn>1</mn><mo>*</mo></msubsup></mrow></mtd><mtd><msup><mrow><mo></mo><msub><mi>w</mi><mn>2</mn></msub><mo></mo></mrow><mn>2</mn></msup></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mi /><mo>⁢</mo><mrow><mrow><mi>H</mi><mo>·</mo><msup><mi>H</mi><mi>H</mi></msup></mrow><mo>+</mo><mrow><mo>[</mo><mtable><mtr><mtd><msup><mrow><mo></mo><msub><mi>w</mi><mn>1</mn></msub><mo></mo></mrow><mn>2</mn></msup></mtd><mtd><mn>0</mn></mtd></mtr><mtr><mtd><mn>0</mn></mtd><mtd><msup><mrow><mo></mo><msub><mi>w</mi><mn>2</mn></msub><mo></mo></mrow><mn>2</mn></msup></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mrow><mo>=</mo><mi /><mo>⁢</mo><mrow><mrow><mi>H</mi><mo>·</mo><msup><mi>H</mi><mi>H</mi></msup></mrow><mo>+</mo><mrow><msup><mrow><mo></mo><mi>w</mi><mo></mo></mrow><mn>2</mn></msup><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><mn>1</mn></mtd><mtd><mn>0</mn></mtd></mtr><mtr><mtd><mn>0</mn></mtd><mtd><mn>1</mn></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mrow></mrow><mo>,</mo></mrow></mtd></mtr></mtable></mtd><mtd><mrow><mo>(</mo><mn>14</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0007.tif" /><br /> where the following equation (15) is employed from the assumption on the transmitted signal vectors:

0073<maths id="MATH-US-00008" num="00008"><math overflow="scroll"><mtable><mtr><mtd><mtable><mtr><mtd><mrow><msub><mi>R</mi><mi>xx</mi></msub><mo>=</mo><mrow><mrow><mo>[</mo><mtable><mtr><mtd><msub><mi>x</mi><mn>1</mn></msub></mtd></mtr><mtr><mtd><msub><mi>x</mi><mn>2</mn></msub></mtd></mtr></mtable><mo>]</mo></mrow><mo>⁡</mo><mrow><mo>[</mo><mtable><mtr><mtd><msubsup><mi>x</mi><mn>1</mn><mo>*</mo></msubsup></mtd><mtd><msubsup><mi>x</mi><mn>2</mn><mo>*</mo></msubsup></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mrow><mo>[</mo><mtable><mtr><mtd><msup><mrow><mo></mo><msub><mi>x</mi><mn>1</mn></msub><mo></mo></mrow><mn>2</mn></msup></mtd><mtd><mrow><msub><mi>x</mi><mn>1</mn></msub><mo>⁢</mo><msubsup><mi>x</mi><mn>2</mn><mo>*</mo></msubsup></mrow></mtd></mtr><mtr><mtd><mrow><msub><mi>x</mi><mn>2</mn></msub><mo>⁢</mo><msubsup><mi>x</mi><mn>1</mn><mo>*</mo></msubsup></mrow></mtd><mtd><msup><mrow><mo></mo><msub><mi>x</mi><mn>2</mn></msub><mo></mo></mrow><mn>2</mn></msup></mtd></mtr></mtable><mo>]</mo></mrow></mrow></mtd></mtr><mtr><mtd><mrow><mo>=</mo><mrow><mrow><mo>[</mo><mtable><mtr><mtd><mn>1</mn></mtd><mtd><mn>0</mn></mtd></mtr><mtr><mtd><mn>0</mn></mtd><mtd><mn>1</mn></mtd></mtr></mtable><mo>]</mo></mrow><mo>.</mo></mrow></mrow></mtd></mtr></mtable></mtd><mtd><mrow><mo>(</mo><mn>15</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0008.tif" />

0074According to the operation principle of the MIMO antenna apparatus described above, a transmission capacity C_MIMOof the MIMO communication system is obtained by the following equation (16):

0075<maths id="MATH-US-00009" num="00009"><math overflow="scroll"><mtable><mtr><mtd><mrow><mrow><msub><mi>C</mi><mi>MIMO</mi></msub><mo>=</mo><mrow><mrow><msub><mi>log</mi><mn>2</mn></msub><mo>⁢</mo><mrow><mo></mo><mrow><msub><mi>I</mi><mi>n</mi></msub><mo>+</mo><mrow><mfrac><mi>SNR</mi><mi>n</mi></mfrac><mo>⁢</mo><msup><mi>HH</mi><mi>H</mi></msup></mrow></mrow><mo></mo></mrow></mrow><mo>=</mo><mrow><munderover><mo>∑</mo><mrow><mi>i</mi><mo>=</mo><mn>1</mn></mrow><mi>q</mi></munderover><mo>⁢</mo><mrow><msub><mi>log</mi><mn>2</mn></msub><mo>⁡</mo><mrow><mo>(</mo><mrow><mn>1</mn><mo>+</mo><mrow><mfrac><mi>SNR</mi><mi>n</mi></mfrac><mo>⁢</mo><msub><mi>λ</mi><mi>i</mi></msub></mrow></mrow><mo>)</mo></mrow></mrow></mrow></mrow></mrow><mo>,</mo></mrow></mtd><mtd><mrow><mo>(</mo><mn>16</mn><mo>)</mo></mrow></mtd></mtr></mtable></math></maths><img file="US7792084B2_D0009.tif" /><br /> where symbol SNR denotes a total transmitted signal power-to-noise ratio, i.e., satisfies SNR/n=x₁x_i*. The unit of the transmission capacity C_MIMOis [bit/sec/Hz]. On the other hand, in case of normal one-to-one communication (SISO) in which the transmitter employs one antenna element and the receiver employs one antenna element, a transmission capacity C_SISOis obtained by the following equation (17): <br /><i>C</i>_SISO=log₂(1+<i>SNR·hh</i>*)  (17),<br /> where symbol h denotes a propagation coefficient, and the unit of the transmission capacity C_SISOis [bit/sec/Hz].

0076It is supposed that for example, hh*=λ_i=λ and SNR·λ/n>>1 for simplification of comparison between the equations (16) and (17). In this case, the transmission capacity C_MIMOexpressed by the equation (16) is calculated as shown in the following equation (18): <br /><i>C</i>_MIMO<i>=n</i>·(log₂(<i>SNR</i>·λ)−log₂(<i>n</i>))  (18).

0077Furthermore, the transmission capacity C_SISOexpressed by the equation (17) is calculated as shown in the following equation (19): <br /><i>C</i>_SISO=log₂(<i>SNR</i>·λ)  (19).

0078In a case of n=4 and SNR*λ=1024, for example, the MIMO transmission capacity C_MIMO=4*(10−2)=32 [bit/sec/Hz] and a SISO transmission capacity C_SISO=10 [bit/sec/Hz]. Therefore, it is understood that the MIMO transmission capacity increases more than the SISO transmission capacity.

0079In such manner, the MIMO antenna apparatus spatially multiplexes signals and increases the transmission capacity by allocating to each of the signal sequences the directivity that signals are orthogonal to one another, and accordingly, the total transmission rate of the MIMO-demodulated signal sequences can be improved.

0080According to the equation (16), it can be seen that the greater the eigenvalues λ_icalculated from the channel matrix H become, the more the MIMO transmission capacity increases. This means that higher-rate transmission can be achieved as the respective elements of the channel matrix H increase, since the eigenvalues λ_iare obtained by the respective elements of the channel matrix H. Moreover, as expressed in the equation (1), the received signal vector includes the thermal noise vector w. Because thermal noise components can not be eliminated in the actual receiver, it causes errors when calculating the eigenvalues λ_ifrom the channel matrix H. Accordingly, in order to improve the transmission rate of the MIMO antenna apparatus, the powers of the received signals are to be made as large as possible.

0081On the other hand, if interference waves are present, the equation (1) is expressed by the following equation (20): <br /><i>y=Hx+H</i>_i<i>+w</i>  (20),<br /> where symbol H_idenotes a vector with a size of n, and each element thereof denotes interference wave signals received through each of the antenna elements of the receiver. The term “interference wave signals” means cochannel interference wave signals arrived from a neighboring base station with the same frequency, or desired wave signals which have been arrived as delayed signals due to transmission via different long paths. In an analog radio communication such as television broadcast or radio broadcast, the delayed wave signals degrade, for example, the quality of screen appearance as ghosts in the television broadcast. In contrast, in a digital radio communication, thermal noises, cochannel interference wave signals, and delay wave signals directly affect a desired wave signal as bit errors of the desired wave signal, and degrade the signal quality of the desired wave signal.

0082In the equation (20), if the respective elements of the vectors H_iand w are sufficiently smaller than the respective elements of the vector Hx, high-speed communication can be achieved due to high SINR. However, if the respective elements of the vectors H_iand w reach unnegligible levels, the performance of the error rate of the demodulated signal is greatly deteriorated. For example, in case of QPSK modulation, a SINR of about 13 dB is needed to satisfy an error rate of 10⁻⁶.

0083Then, according to the equation (20), the causes for degrading the quality of the demodulated signal are classified into a factor of the interference wave vector H_iand a factor of the thermal noise vector w. Since the thermal noises are determined by a bandwidth of the modulated signal and the noise performance of the receiver, the variations of the thermal noises depending on surrounding environment are small. Namely, the deterioration of the SINR occurs mainly when the received signal levels decrease. On the other hand, even when the received signal levels are large, if the signal levels of the interference wave signals are also large, the SINR is relatively small. Accordingly, if the signal quality of the demodulated signal is deteriorated, it is important to judge whether the deterioration results from the decreases in the received signal levels or from the presence of the interference wave signals. In this case, the signal quality is a bit error rate (BER), a packet error rate, or a throughput. Considering the above-stated operation principle, a method for controlling the MIMO antenna apparatus according to the present preferred embodiment will be described below.

0084<figref idref="DRAWINGS">FIG. 7</figref> is a flowchart showing a control flow of MIMO adaptive control process performed by the controller <b>5</b>. In the initial state, the MIMO antenna apparatus and the sender-side radio station apparatus perform a MIMO communication using three data streams and a certain modulation and demodulation method. The MIMO antenna apparatus is receiving radio signals by using all of its three receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c</i>. Referring to <figref idref="DRAWINGS">FIG. 7</figref>, in Step S<b>1</b>, the controller <b>5</b> makes the MIMO demodulator circuit <b>3</b> demodulate the respective received signals outputted from the A/D converter circuit <b>2</b> to output one demodulated signal, and determine the BER of the demodulated signal as the signal quality of the demodulated signal, and further, the controller <b>5</b> obtains the result of the determination from the MIMO demodulator circuit <b>3</b>. In Step S<b>2</b>, the controller <b>5</b> judges whether or not the BER of the demodulated signal is equal to or higher than a predetermined threshold value T<b>1</b>. If the BER is lower than the threshold value T<b>1</b>, the control flow goes to Step S<b>3</b>. If the BER is equal to or higher than the threshold value T<b>1</b>, the control flow goes to Step S<b>7</b>. At Step S<b>2</b>, in the case that the MIMO demodulator circuit <b>3</b> obtains an instantaneous BER (i.e., the BER measured for quite a short time interval), the threshold value T<b>1</b> for the BER is set to, for example, 10⁻⁶. In the case that the MIMO demodulator circuit <b>3</b> obtains a time-averaged BER for predetermined time interval in consideration of a multiple wave environment caused by the Rayleigh Fading, the threshold value T<b>1</b> is set to, for example, 10⁻². In Step S<b>3</b>, the controller <b>5</b> makes the signal level detection circuit <b>4</b> detect signal levels of the respective received signals based on the respective received signals outputted from the A/D converter circuit <b>2</b>, and obtains the results of the detection from the signal level detection circuit <b>4</b>. In Step S<b>4</b>, the controller <b>5</b> determines whether or not the received signal having the signal level smaller than a predetermined threshold value T<b>2</b> is present. If the signal levels of all the received signals are equal to or larger than the threshold value T<b>2</b>, the control flow goes to Step S<b>5</b>; otherwise, the control flow goes to Step S<b>6</b>.

0085In this case, the threshold value T<b>2</b> for the signal levels of the received signals depends on (a) the modulation and demodulation method used in the MIMO antenna apparatus and in the sender-side radio station apparatus (i.e., BPSK, QPSK, 16QAM or 64QAM), and (b) whether the signal quality of the demodulated signal and the signal levels of the respective received signals are obtained as instantaneous values or as time-averaged values. Referring to <figref idref="DRAWINGS">FIGS. 9 and 10</figref>, the determination of the signal levels of the respective received signals using the threshold value T<b>2</b> will be described as follows. In the graphs of <figref idref="DRAWINGS">FIGS. 9 and 10</figref>, the CNR is used as an example of the signal level of each received signal. <figref idref="DRAWINGS">FIG. 9</figref> is a graph showing the instantaneous CNR and BER. In this case, for each one of the plurality of modulation and demodulation methods, the threshold value for the CNR is set to a value corresponding to BER=10⁻⁶set as the threshold value for the instantaneous BER. Namely, if the modulation and demodulation method is BPSK, the CNR is set to 11 dB. If it is QPSK, the CNR is set to 14 dB. If it is 16QAM, the CNR is set to 21 dB. If it is 64QAM, the CNR is set to 27 dB. <figref idref="DRAWINGS">FIG. 10</figref> is a graph showing the time-averaged CNR and BER. In this case, for each one of the plurality of modulation and demodulation methods, the threshold value for the CNR is set to a value corresponding to BER=10⁻²set as the threshold value for the time-averaged BER. Namely, if the modulation and demodulation method is BPSK, the CNR is set to 14 dB. If it is QPSK, the CNR is set to 17 dB. If it is 16QAM, the CNR is set to 23 dB. If it is 64QAM, the CNR is set to 28 dB. The threshold value T<b>2</b> for the signal levels is not limited to the above values, but can be set to a value corresponding to an error-free signal level (e.g., in electric power) for each one of the plurality of used modulation and demodulation methods.

0086In Step S<b>5</b>, the controller <b>5</b> decreases the number of data streams for a MIMO communication used in the sender-side radio communication apparatus and in the MIMO demodulator circuit <b>3</b>. For example, if the sender-side radio communication apparatus and the MIMO antenna apparatus have been performing a MIMO communication using three data streams, the controller <b>5</b> changes the communication method so that the sender-side radio communication apparatus and the MIMO antenna apparatus perform a MIMO communication using two data streams or perform a SISO communication using one data stream. When the number of data streams has become one by decreasing the number of data streams in Step S<b>5</b> (i.e., when Step S<b>10</b> is YES), the control flow goes to a SISO communication process of Step S<b>11</b>; otherwise (i.e., Step S<b>10</b> is NO), the control flow goes to Step S<b>12</b>.

0087<figref idref="DRAWINGS">FIG. 8</figref> is a sub-routine flowchart showing the SISO communication process of Step S<b>11</b> of <figref idref="DRAWINGS">FIG. 7</figref>. Referring to <figref idref="DRAWINGS">FIG. 8</figref>, in Step S<b>14</b>, the controller <b>5</b> makes the MIMO demodulator circuit <b>3</b> continue the demodulation process (i.e., demodulation process of the SISO communication) only on a signal received through the receiving antenna element through which the signal having the largest signal level is received. In Step S<b>15</b>, the controller <b>5</b> determines whether or not the number of times of demodulation process performed by the MIMO demodulator circuit <b>3</b> exceeds a predetermined maximum number of times of demodulation. The maximum number of times of demodulation is determined as a period for monitoring the radio wave conditions. Alternatively, in Step S<b>15</b>, the controller <b>5</b> may determine whether or not a predetermined timeout period expires after the demodulation process performed by the MIMO demodulator circuit <b>3</b> continues for a predetermined time interval, instead of comparing the number of times of demodulation with the maximum number of times of demodulation. The demodulation process continues by repeating Step S<b>14</b> until it is determined in Step S<b>15</b> that the number of times of demodulation exceeds the maximum number of times of demodulation. If the number of times of demodulation exceeds the maximum number of times of demodulation, then in Step <b>16</b>, the controller <b>5</b> increases the number of data streams for the MIMO communication used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b>, and changes the communication method from the SISO communication to the MIMO communication. In Step S<b>16</b>, preferably, the controller <b>5</b> initializes the number of data streams to the maximum value (i.e., three). After increasing the number of data streams, the control flow returns to Step S<b>1</b>.

0088As an alternative, the process can be configured such that the controller <b>5</b> determines, in Step S<b>10</b>, whether or not the number of data streams has been decreased to a certain number other than one (e.g., 2), and if YES, the controller <b>5</b> performs only Step S<b>16</b> of <figref idref="DRAWINGS">FIG. 8</figref>, instead of the SISO communication process of Step S<b>11</b>. In this case, the range over which the number of the data streams varies is limited, and the number of data streams can be changed so as to perform only the MIMO communication and not to perform the SISO communication.

0089Referring back to <figref idref="DRAWINGS">FIG. 7</figref>, in Step S<b>6</b>, the controller <b>5</b> changes the modulation and demodulation method used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b> to a modulation and demodulation method with a lower transmission rate than the current transmission rate. For example, if the sender-side radio station apparatus and the MIMO demodulator circuit <b>3</b> have been performing a MIMO communication using 64QAM, the controller <b>5</b> changes the MIMO communication so as to use one of the modulation and demodulation methods of 16QAM, QPSK and BPSK. After changing the modulation and demodulation method, the control flow goes to Step S<b>12</b> of <figref idref="DRAWINGS">FIG. 7</figref>.

0090In Step S<b>2</b>, if the BER of the demodulated signal is equal to or higher than the threshold value T<b>1</b>, the control flow goes to Step S<b>7</b> as stated above. In Step S<b>7</b>, in the same manner as that of Step S<b>3</b>, the controller <b>5</b> makes the signal level detection circuit <b>4</b> detect the signal levels of the respective received signals based on the respective received signals outputted from the A/D converter circuit <b>2</b>, and obtains the results of the detection from the signal level detection circuit <b>4</b>. In Step S<b>8</b>, the controller <b>5</b> determines whether or not the received signal having the signal level smaller than the threshold value T<b>2</b> of Step S<b>4</b> is present. If the signal levels of all the received signals are equal to or larger than the threshold value T<b>2</b>, the control flow goes to Step S<b>9</b>; otherwise, the control flow goes to Step S<b>12</b>. In Step S<b>9</b>, the controller <b>5</b> changes the modulation and demodulation method used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b> to a modulation and demodulation method with a higher transmission rate than the current transmission rate. For example, if the sender-side radio station apparatus and the MIMO demodulator circuit <b>3</b> have been performing a MIMO communication using BPSK, the controller <b>5</b> changes the MIMO communication so as to use one of the modulation and demodulation methods: QPSK, 16QAM and 64QAM. After changing the modulation and demodulation method, the control flow goes to Step S<b>12</b>. In Step S<b>12</b>, the controller <b>5</b> makes the MIMO demodulator circuit <b>3</b> continue the demodulation process. In Step S<b>13</b>, the controller <b>5</b> determines whether or not the number of times of the demodulation process performed by the MIMO demodulator circuit <b>3</b> exceeds a predetermined maximum number of times of demodulation (e.g., equal to the maximum number of times of demodulation in Step S<b>15</b>). If the number of times of demodulation exceeds the maximum number of times of demodulation, the control flow returns to Step S<b>1</b>; otherwise, the control flow returns to Step S<b>12</b> at which the controller <b>5</b> makes the MIMO demodulator circuit <b>3</b> continue the demodulation process. In a modified preferred embodiment, when the BER of the demodulated signal is equal to or higher than the threshold value T<b>1</b> in Step S<b>2</b>, the control flow may return to Step S<b>1</b> and make the MIMO demodulator circuit <b>3</b> continue the demodulation process, without carrying out Steps S<b>7</b> to S<b>9</b>.

0091As described so far, the MIMO antenna apparatus according to the present preferred embodiment decreases the number of data streams for the MIMO communication method, and/or changes the modulation and demodulation method for the MIMO communication method, based on the signal quality of the demodulated signal and the signal levels of the respective received signals. Therefore, according to the present preferred embodiment, the MIMO antenna apparatus can be provided which, even if it is small in size, can perform a high quality and high-speed communication by adaptively controlling the number of data streams and the modulation and demodulation method for the MIMO communication method in the case that the desired receiving quality is not achieved. Additionally, according to the present preferred embodiment, the mobile radio communication apparatus with such MIMO antenna apparatus can be provided.

Second Preferred Embodiment

0092<figref idref="DRAWINGS">FIG. 11</figref> is a block diagram showing a configuration of a MIMO antenna apparatus according to a second preferred embodiment of the present invention. The MIMO antenna apparatus according to the present preferred embodiment is characterized by having, in addition to the constituent elements of the MIMO antenna apparatus shown in <figref idref="DRAWINGS">FIG. 1</figref>, an adaptive demodulator circuit <b>12</b>, and a switch circuit <b>11</b> for connecting an A/D converter circuit <b>2</b> to either a MIMO demodulator circuit <b>3</b> or the adaptive demodulator circuit <b>12</b>. The MIMO antenna apparatus according to the present preferred embodiment is also characterized in that if any interference wave signal is received, the switch circuit <b>11</b> is moved under predetermined conditions so that the adaptive demodulator circuit <b>12</b> performs a demodulation process using recurrent and repetitive calculations.

0093The switch circuit <b>11</b> includes three switches corresponding to three received signals outputted from the A/D converter <b>2</b>, respectively. These switches input the three received signals into either the MIMO modulator circuit <b>3</b> or the adaptive demodulator circuit <b>12</b>, under control of a controller <b>5</b>. If the three received signals are inputted into the adaptive demodulator circuit <b>12</b>, the amplitudes of these received signals are adjusted by amplitude adjusters <b>13</b><i>a</i>, <b>13</b><i>b </i>and <b>13</b><i>c</i>, respectively, and then, the phases of these received signals are adjusted by phase shifters <b>14</b><i>a</i>, <b>14</b><i>b </i>and <b>14</b><i>c</i>, respectively. The amounts of amplitude adjustment of the amplitude adjusters <b>13</b><i>a</i>, <b>13</b><i>b </i>and <b>13</b><i>c </i>and the amounts of phase shift of the phase shifters <b>14</b><i>a</i>, <b>14</b><i>b </i>and <b>14</b><i>c </i>are controlled by an amplitude and phase controller <b>17</b>, which obtains the three received signals, and performs calculations of weight coefficients (as described below in detailed manner) based on the obtained three received signals. The respective received signals that have been subjected to the amplitude adjustments and the phase shifts are combined by a combiner <b>15</b>. Subsequently, a demodulator <b>16</b> demodulates the combined received signal to output a demodulated signal. As a signal quality, a packet error rate or a throughput may be used in place of a bit error rate (BER). Further, each of the MIMO demodulator circuit <b>3</b> and the adaptive demodulator circuit <b>12</b> passes to the controller <b>5</b> the number of times of demodulation processes on data of the received signals (referred to as “the number of times of demodulation”) in units of, e.g., a predetermined amount of data (such as, the number of bits, or the number of packets). The controller <b>5</b> performs a MIMO adaptive control process based on the information on the BER, the signal levels, and the number of times of demodulation, as described below with reference to <figref idref="DRAWINGS">FIGS. 13 and 14</figref>, and accordingly, changes the communication method used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b>.

0094<figref idref="DRAWINGS">FIG. 12</figref> is a block diagram showing a configuration of a MIMO antenna apparatus according to a modified preferred embodiment of the present preferred embodiment. The MIMO antenna apparatus according to the modified preferred embodiment is characterized in that, a transmitting antenna <b>7</b> shown in <figref idref="DRAWINGS">FIG. 11</figref> is integrated with one of the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c </i>for MIMO reception (in the example of <figref idref="DRAWINGS">FIG. 12</figref>, the transmitting antenna element is integrated with the antenna element <b>1</b><i>c</i>), in a similar manner to the modified preferred embodiment of the first preferred embodiment shown in <figref idref="DRAWINGS">FIG. 2</figref>. With the above-stated configuration, the MIMO antenna apparatus according to the modified preferred embodiment shown in <figref idref="DRAWINGS">FIG. 12</figref> can reduce the number of antenna elements in the apparatus.

0095Generally speaking, in MIMO demodulation, a known signal (i.e., a reference signal) is stored in a receiver-side radio station apparatus in advance, a sender-side radio station apparatus transmits the same signal as this known signal to the receiver-side radio station apparatus, and the receiver-side radio station apparatus calculates a correlation between the known signal stored in advance and the received known signal, and accordingly, detects an amplitude and a phase of the received signal. In this case, for calculating the correlation, a complex conjugate of the known signal stored in the sender-side radio station apparatus in advance is multiplied by the received known signal. Further, if the known signal includes a plurality of bits, then correlations for the respective bits are calculated, and a sum or an average of the correlations can be used as a correlation value. Moreover, if different signal sequences (streams) are present, then the sender-side radio station apparatus transmits the same signal as the known signal to the receiver-side radio station apparatus at each of different times, and the receiver-side radio station apparatus estimates a propagation for each of the streams in order to achieve the MIMO demodulation. Nevertheless, if a strong interference wave signal(s) is present, the correlation can not be calculated at all. This is because the correlation between the known signal and the received signal is reduced, since the interference wave signals are added to the received signal.

0096Thus, if the interference wave signals are received, it would be impossible to perform a normal MIMO demodulation. Accordingly, it is needed to employ an interference suppression technique using an adaptive array antenna for controlling the received signal so that the received signal approaches the known signal. The adaptive array antenna works so as to improve the signal quality, and as a result, maximize the SINR. Particularly if the interference wave signals are not known, it is preferable to perform an adaptive control based on repetitive calculations. Since the adaptive demodulator circuit <b>12</b> is provided, the MIMO antenna apparatus according to the present preferred embodiment can perform the above-stated preferred process.

0097<figref idref="DRAWINGS">FIGS. 13 and 14</figref> are flowcharts showing a control flow of MIMO adaptive control process performed by the controller <b>5</b> shown in <figref idref="DRAWINGS">FIG. 11</figref>. Referring to FIG. <b>13</b>, in Step S<b>21</b>, the controller <b>5</b> initializes the switch circuit <b>11</b> to make the switch circuit <b>11</b> connect to the MIMO demodulator circuit <b>3</b>. In Step S<b>22</b>, the controller <b>5</b> makes the MIMO demodulator circuit <b>3</b> demodulate respective received signals outputted from the A/D converter <b>2</b> circuit <b>2</b> to output a demodulated signal and determine the BER of the demodulated signal as the signal quality of the demodulated signal, and further, the controller <b>5</b> obtains the result of the determination from the MIMO demodulator circuit <b>3</b>. In Step S<b>23</b>, the controller <b>5</b> determines whether or not the BER of the demodulated signal outputted from the MIMO demodulator circuit <b>3</b> is equal to or larger than a predetermined threshold value T<b>1</b>. If the BER of the demodulated signal is smaller than the threshold value T<b>1</b>, the control flow goes to Step S<b>24</b>. If the BER is equal to or larger than the threshold value T<b>1</b>, the control flow goes to Step S<b>29</b>. In this case, the threshold value T<b>1</b> for the BER is set in the same manner as that of Step S<b>2</b> of <figref idref="DRAWINGS">FIG. 7</figref>. In Step S<b>24</b>, the controller <b>5</b> makes the signal level detection circuit <b>4</b> detect the signal levels of respective received signals based on the respective received signals outputted from the A/D converter circuit <b>2</b>, and further, the controller <b>5</b> obtains the results of the detection result from the signal level detection circuit <b>4</b>. In Step S<b>25</b>, the controller <b>5</b> determines whether or not the received signal having a signal level smaller than a predetermined threshold value T<b>2</b> is present. If the signal level of at least one received signal is smaller than the threshold value T<b>2</b>, the control flow goes to Step S<b>26</b>; otherwise, the control flow goes to Step S<b>32</b> of <figref idref="DRAWINGS">FIG. 14</figref>. In this case, the threshold value T<b>2</b> for the signal levels is set in the same manner as that of Step S<b>4</b> of <figref idref="DRAWINGS">FIG. 7</figref>. In Step S<b>26</b>, in a manner similar to that of Step S<b>6</b> of <figref idref="DRAWINGS">FIG. 7</figref>, the controller <b>5</b> changes the modulation and demodulation method used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b> to a modulation and demodulation method with a lower transmission rate than a current transmission rate. In Step S<b>27</b>, the controller <b>5</b> makes the MIMO demodulator circuit <b>3</b> continue the demodulation process. In Step S<b>28</b>, in a manner similar to that of Step S<b>13</b> of <figref idref="DRAWINGS">FIG. 7</figref>, the controller <b>5</b> determines whether or not the number of times of demodulation process performed by the MIMO demodulator circuit <b>3</b> exceeds a predetermined maximum number of times of demodulation. If the number of times of demodulation process performed by the MIMO demodulator circuit <b>3</b> exceeds the maximum number of times of demodulation, the control flow returns to Step S<b>22</b>; otherwise, the control flow returns to Step S<b>27</b> at which the controller <b>5</b> makes the MIMO demodulator circuit <b>3</b> continue the demodulation process.

0098If the BER of the demodulated signal is equal to or larger than the threshold value T<b>1</b> in Step S<b>23</b>, the control flow goes to Step S<b>29</b> as stated above. Steps S<b>29</b> to S<b>31</b> are the same as Steps S<b>7</b> to S<b>9</b> of <figref idref="DRAWINGS">FIG. 7</figref>, respectively. In Step S<b>29</b>, the controller <b>5</b> makes the signal level detection circuit <b>4</b> detect the signal levels of the respective received signals based on the respective received signals outputted from the A/D converter circuit <b>2</b>, and obtains the results of the detection from the signal level detection circuit <b>4</b>. In Step S<b>30</b>, the controller <b>5</b> determines whether or not the received signal having the signal level smaller than the same threshold value T<b>2</b> as that used in Step S<b>25</b> is present. If the signal levels of all the received signals are equal to or larger than the threshold value T<b>2</b>, the control flow goes to Step S<b>31</b>; otherwise, the control flow goes to Step S<b>27</b>. In Step S<b>31</b>, in a manner similar to that of Step S<b>9</b> of <figref idref="DRAWINGS">FIG. 7</figref>, the controller <b>5</b> changes the modulation and demodulation method used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b> to a modulation and demodulation method with a higher transmission rate than the current transmission rate. After changing the modulation and demodulation method, the control flow goes to Step S<b>27</b>.

0099If the signal levels of all the received signals are equal to or larger than the threshold value T<b>2</b> in Step S<b>25</b>, the control flow goes to Step S<b>32</b> of <figref idref="DRAWINGS">FIG. 14</figref> as stated above. In Step S<b>32</b>, the controller <b>5</b> changes the communication method so as to decrease the number of data streams for the MIMO communication used in the sender-side radio station apparatus and in the MIMO demodulator circuit <b>3</b> to one, and perform a SISO communication. In Step S<b>33</b>, the controller <b>5</b> makes the switch <b>11</b> connect to the adaptive demodulator circuit <b>12</b>. In Step S<b>34</b>, the controller <b>5</b> makes the adaptive demodulator circuit <b>12</b> demodulate the respective received signals outputted from the A/D converter circuit <b>2</b>. The adaptive demodulator circuit <b>12</b> weights and demodulates the respective received signals, such that a main beam of the MIMO antenna apparatus is directed to a desired wave signal, or such that a main beam of the MIMO antenna apparatus is directed to a desired wave signal and nulls of the MIMO antenna apparatus are directed to interference wave signals. The weighting (i.e., the calculations of weight coefficients) by the adaptive demodulator circuit <b>12</b> will be described below in detailed manner. Next, in Step S<b>35</b>, the controller <b>5</b> determines whether or not the number of times of demodulation process performed by the adaptive demodulator circuit <b>12</b> exceeds a predetermined maximum number of times of demodulation (e.g., the same number as the maximum number of times of demodulation in Step S<b>28</b>). If the number of times of demodulation exceeds the maximum number of times of demodulation, the control flow goes to Step S<b>36</b> in order to monitor again the conditions of the desired wave signal and the interference wave signals for the MIMO communication; otherwise, the control flow returns to Step S<b>34</b> at which the controller <b>5</b> makes the adaptive demodulator circuit <b>12</b> continue the demodulation process. In Step S<b>36</b>, the controller <b>5</b> changes the communication method used in the sender-side radio station apparatus to MIMO, and the control flow then returns to Step S<b>21</b> of <figref idref="DRAWINGS">FIG. 13</figref>. In this case, the change of the communication method in Step S<b>36</b> includes, for example, increasing the number of data streams for the communication method used in the sender-side radio station apparatus preferably to its maximum value (i.e., three).

0100As stated so far, according to the present preferred embodiment, it is possible to implement the MIMO antenna apparatus capable of performing process for the interference wave suppression, including the use of the adaptive demodulation, depending on the conditions of the desired wave signal and the interference wave signals. Particularly, if the desired wave signal is strong (i.e., Step S<b>23</b> is YES), the controller <b>5</b> make the signal level detection circuit <b>4</b> detect the signal levels of the received signals in Step S<b>29</b>, and in this case, if the signal levels of the received signals are larger than the threshold value (i.e., the threshold value T<b>2</b> of Step S<b>25</b>) for switching the demodulation method to the adaptive demodulation (i.e., Step S<b>30</b> is YES), the sender-side radio station apparatus is instructed to change the modulation and demodulation method for the transmitted radio signals to the modulation and demodulation method with the higher transmission rate (e.g., by increasing the number of levels in the multi-level modulation and demodulation method) in Step S<b>31</b>. Accordingly, a high-speed and high signal quality communication can be achieved. Furthermore, a time period for re-monitoring the radio wave conditions can be determined by setting the maximum number of times of demodulation used in Steps S<b>28</b> and S<b>35</b>, and accordingly, it is possible to implement the MIMO antenna apparatus capable of optimally dealing with a change in the propagation environment of the desired wave signal and the interference wave signals.

0101The demodulation process performed by the adaptive demodulator circuit <b>12</b> in Step S<b>34</b> will be described below. In the present preferred embodiment, the amplitude and phase controller <b>17</b> performs the adaptive demodulation process by the repetitive calculations using only the received signals of the three receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c</i>. Needless to say, this process can be changed depending on the number of receiving antenna elements.

0102The signals received through the respective receiving antenna elements <b>1</b><i>a </i><b>1</b><i>b </i>and <b>1</b><i>c </i>are converted into digital signals by the A/D converter circuit <b>2</b>, and inputted into the amplitude and phase controller <b>17</b> via the switch circuit <b>11</b>. In the present preferred embodiment, these digital signals can be regarded as a vector including three elements. The amplitude and phase controller <b>17</b> determines the amplitude adjustment amounts of the amplitude adjusters <b>13</b><i>a</i>, <b>13</b><i>b </i>and <b>13</b><i>c </i>and the phase shift amounts of the phase shifters <b>14</b><i>a</i>, <b>14</b><i>b </i>and <b>14</b><i>c</i>, so as to optimize the signal quality (e.g., BER) of the signal obtained as a result of combining the respective amplitude-adjusted and phase-sifted received signals by the combiner <b>15</b> into the combined output signal and then demodulating the combined output signal by the demodulator <b>16</b>. A method for calculating the amplitude adjustment amounts of the amplitude adjusters <b>13</b><i>a</i>, <b>13</b><i>b </i>and <b>13</b><i>c </i>and the phase shift amounts of the phase shifters <b>14</b><i>a</i>, <b>14</b><i>b </i>and <b>14</b><i>c </i>(hereinafter, referred to as “weight coefficients”) will be described below.

0103A weight coefficient w_irelated to each of the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c </i>is defined by the following equation (21): <br /><i>Wi=Ai*</i>exp(<i>j*φi</i>)  (21).

0104In the equation (21), symbol j denotes the imaginary unit, and a parameter i has values 1, 2 and 3, each of which corresponds to the signal received through each one of the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c</i>. Further, symbol Ai denotes an amplitude adjustment amount and symbol φi denotes a phase shift amount. In the following description, For simplicity, a method for calculating a weight coefficient w(t) for one received signal s(t) received through one of the receiving antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c </i>will be described.

0105Several methods for calculating the weight coefficient are known. In the present preferred embodiment, take for instance a method using the steepest gradient (least means squares: LMS). With this method, the receiver-side radio station apparatus, in which the adaptive demodulation process is performed, stores a known signal sequences (or a reference signal) r(t) in advance, the sender-side radio station apparatus transmits a desired wave signal including the known reference signal r(t) to the receiver-side radio station apparatus, and then the receiver-side radio station apparatus controls the amplitude adjustment amount and the phase shift amount for the received desired wave signal so that the received desired wave signal approaches the stored reference signal. In the present preferred embodiment, the reference signal r(t) is assumed to be stored in the amplitude and phase controller <b>17</b>. Specifically, the amplitude and phase controller <b>17</b> controls one of the amplitude adjusters <b>13</b><i>a</i>, <b>13</b><i>b </i>and <b>13</b><i>c </i>and one of the phase shifters <b>14</b><i>a</i>, <b>14</b><i>b </i>and <b>14</b><i>c</i>, so as to multiply a digital signal s(t), which is received through one of the antenna elements <b>1</b><i>a</i>, <b>1</b><i>b </i>and <b>1</b><i>c</i>, converted by A/D converter circuit <b>2</b> and inputted into the adaptive demodulator circuit <b>12</b>, by a weight coefficient w(t) including an amplitude component and a phase component. Then, a residual error e(t) is calculated between the signal obtained by multiplying the digital signal s(t) by the weight coefficient w(t), and the reference signal r(t). The residual error e(t) is obtained as expressed by the following equation (22): <br /><i>e</i>(<i>t</i>)=<i>r</i>(<i>t</i>)−<i>w</i>(<i>t</i>)*<i>s</i>(<i>t</i>)  (22).

0106The residual error e(t) has either a positive or negative value. Therefore, a minimum value of a square of the residual error e(t) obtained by the equation (22) is recurrently calculated (i.e., the repetitive calculations are performed). Accordingly, a weight coefficient w(t, m+1) of an (m+1)-th repetition is obtained as expressed by the following equation (23) using an m-th weight coefficient w(t, m): <br /><i>w</i>(<i>t,m+</i>1)=<i>w</i>(<i>t,m</i>)+<i>u*s</i>(<i>t</i>)*<i>e</i>(<i>t,m</i>)  (23).

0107In the equation (23), symbol u is referred to as “step size”. If the step size u is large, the number of repetitive calculations, by which the weight coefficient converges so as to yield the minimum value, can be advantageously reduced. However, if the step size u is too large, the weight coefficient disadvantageously oscillates near the minimum value. Therefore, it is necessary to take due care of selecting the step size depending on the system to be used. Conversely, if the step size u is set small, although the weight coefficient can stably converge so as to yield the minimum value, the number of repetitive calculations increases. The more the number of repetitive calculations increases, the longer the time for calculating the weight coefficient is required. Providing that the time for calculating the weight coefficient is longer than the time during which the surrounding environment varies (e.g., several milliseconds), it is impossible to improve the signal quality using the weight coefficient. Thus, when determining the step size u, it is necessary to select the conditions for convergence as rapid and stable as possible. Furthermore, the residual error e(t, m) in the equation (23) is defined by the following equation (24): <br /><i>e</i>(<i>t,m</i>)=<i>r</i>(<i>t</i>)−<i>w</i>(<i>t,m</i>)*<i>s</i>(<i>t</i>)  (24).

0108The equation (23) is recurrently updated using the value expressed by the equation (24). It is to be noted that the maximum number of repetitive calculations for calculating the weight coefficient is set so that the for calculating the weight coefficient is not longer than the time for switching the radio system.

0109In the present preferred embodiment, the weight coefficient calculation method based on the steepest gradient method has been described by way of example, however, the present invention is not limited to such method. For example, RLS (Recursive Least-Squares) method or SMI (Sample Matrix Inversion) method can be used, in which the weight coefficient can be determined faster. If one of these alternative methods is used, then calculation time is shorten, but the calculation by the amplitude and phase controller <b>17</b> is more complicated.

0110Moreover, if the modulation method of signal sequences is a constant envelope modulation having a constant envelope such as digital phase modulation, CMA (Constant Modulus Algorithm) can also be used.

0111As stated so far, according to the present preferred embodiment of the present invention, it is possible to implement the MIMO antenna apparatus capable of performing the adaptive demodulation process, which, when the signal quality of the demodulated signal is equal to or smaller than the threshold value T<b>1</b>, obtains the received signal levels in relation to the respective antenna elements constituting the MIMO antenna apparatus, and performs an MIMO communication optimum for the radio environment including the desired wave signal and the interference wave signals based on the obtained received signal levels.

0112According to the present invention, the MIMO antenna apparatus decreases the number of data streams for the MIMO communication method, and/or changes the modulation and demodulation method for the MIMO communication method, based on the signal quality of the demodulated signal and the signal levels of the respective received signals. Therefore, according to the present preferred embodiment, the MIMO antenna apparatus can be provided which, even if it is small in size, can perform a high quality and high-speed communication by performing both the interference wave suppression and the MIMO demodulation process in the case that the desired receiving quality is not achieved. Additionally, according to the present preferred embodiment, the mobile radio communication apparatus with such MIMO antenna apparatus can be provided.

0113As another modified preferred embodiment of the second preferred embodiment, it is possible to configure a MIMO antenna apparatus so as to employ a MIMO communication with two data streams for a radio communication, in the case that one interference wave signal appears while performing the MIMO communication with three data streams. In such MIMO antenna apparatus, the MIMO demodulation can be achieved by performing the repetitive adaptive control for each data stream.

0114As stated so far, according to the present preferred embodiments, the MIMO antenna apparatus can be provided which, even if it is small in size, can perform a high quality and high-speed communication by adaptively controlling the number of data streams and the modulation and demodulation method for the MIMO communication method, or alternatively, by performing both the interference wave suppression and the MIMO demodulation process, in the case that the desired receiving quality is not achieved. Additionally, according to the present preferred embodiments, the mobile radio communication apparatus with such MIMO antenna apparatus can be provided.

0115Although the present invention has been fully described in connection with the preferred embodiments thereof with reference to the accompanying drawings, it is to be noted that various changes and modifications are apparent to those skilled in the art. Such changes and modifications are to be understood as included within the scope of the present invention as defined by the appended claims unless they depart therefrom.