Adaptive receiver having adaptive array unit and equalizer unit

CROSS REFERENCE TO RELATED APPLICATION

This application is based on and incorporates herein by reference Japanese Patent Application No. 2000-333292 filed on Oct. 31, 2000.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to an adaptive receiver used in multi-carrier transmission systems for transmitting data in parallel through frequency division.

2. Description of Related Art

In recent years, attention is paid to an OFDM (Orthogonal Frequency Division Multiplexing) system for transmitting data in parallel through frequency division as a modulation system used for broad band communication using radio wave. According to this OFDM system, data can be transmitted using a longer period, and therefore influence of frequency selective fading is reduced. Moreover, in this OFDM system, inter-symbol interference can be prevented even if a delayed radio wave is received by adding a copy signal of the own symbol called as a guard interval.

Even when this OFDM system is used, the feature is lessened to a large extent because the orthogonal property is lessened in the environment where a long-delayed signal which appears after a long period of delay is received after a plurality times of reflection at walls or in the case where the preceding signal wave exists because of synchronization with the delayed wave. The orthogonal property is lessened as shown in FIG. 18A to FIG. <b>18</b>C.

In FIG. 18A, the delayed wave is within a guard interval. In this case, the orthogonal property is never destroyed because a part (indicated as A in the figure) generating interference with other symbol is cut off with elimination of the guard interval at the time of demodulation. In FIG. 18B, a signal wave exceeding the guard interval appears. In this case, since the part generating interference with the other symbol enters a FFT window, the orthogonal property of carrier is destroyed at the time of demodulation. In FIG. 18C, synchronization is set up with the delayed signal wave. Similarly to the case of FIG. 18B, since the part generating interference with the other symbol enters the FFT window, the orthogonal property of carrier is destroyed at the time of demodulation.

An adaptive array antenna is proposed to effectively control an unwanted signal wave (such as delayed wave exceeding the guard interval, preceding wave or interference wave) having a lower correlation to such a desired signal wave. Here, the adaptive array antenna is a device comprising an array antenna made up of a plurality of antenna elements and an adaptive arithmetic unit for calculating a complex weight for changing amplitude and phase of an output signal of each antenna element in view of combining the signal waves by multiplying the receiving signals of antenna with a complex weight to extract the desired signal wave and suppress the unwanted wave.

Moreover, the arithmetic operation by the adaptive arithmetic unit is called as an adaptive algorithm, several algorithms have been reported. For example, algorithms LMS (Least Means Square) and CMA (Constant Modulus Algorithm) can be listed as those based on an MMSE (Minimum Mean Square Error). The LMS is the algorithm for calculating the optimum complex weight by minimizing a difference between a reference signal as a desired array response and an actual array output signal. Moreover, the CMA is the algorithm that can be applied to a constant envelope signal to calculate an optimum complex weight to recover a signal distorted in a multipath environment to an original constant envelope signal. Moreover, the additional algorithms are MSN (Maximum Signal to Noise Ratio) for calculating the complex weight to obtain a maximum SNR (Signal to Noise Ratio) of array output and DCMP (Directionally Constrained Minimization of Power) for minimizing the power under the precondition that the incoming direction of the desired signal wave is known.

Moreover, JP-A-10-93323 (U.S. Pat. No. 6,087,986) teaches an adaptive antenna and multi-carrier radio communication system. This system conducts an adaptive arithmetic operation based on LMS, RLS (Recursive Least Squares) algorithm for extracting the known signal called as pilot data inserted into the receiving signal and then updating the complex weight to minimize an error from the known signal prepared in the receiver side. JP-A-10-210099 also teaches an adaptive receiver which realizes CMA in a frequency range for updating the complex weight to make constant the spectrum after the adaptive combining.

The unwanted wave having lower correlation can be controlled effectively by utilizing the above adaptive array antenna. However, the unwanted wave (delayed signal wave within the guard interval) having higher correlation cannot be controlled effectively and thereby the demodulation characteristic is not satisfactory. This is because, a propagation path in the adaptive array antenna is estimated by comparing two reference signals, one resulting after combining the receiving signal weighted by the adaptive array antenna and the other being a stored known signal, and hence the weighting by the adaptive array antenna influences on the propagation path estimation value.

SUMMARY OF THE INVENTION

It is therefore an object of the present invention to provide an adaptive receiver which can effectively control not only an unwanted signal wave of lower correlation but also an unwanted signal wave of higher correlation.

It is another object of the present invention to remove influence of weighting in an adaptive array antenna on estimation of a propagation path estimation value.

According to the present invention, an adaptive receiver includes an adaptive array unit and an equalizer unit. In the adaptive array unit, receiving signals of an array antenna are weighted by multiplying with a complex weight calculated by an adaptive arithmetic unit, and adaptively combined. In the equalizer unit, propagation path estimation values are calculated from the receiving signals by a propagation path estimating unit, weighted with the complex weight by a complex weight adjusting unit, and adaptively combined. An output signal of the adaptive receiver is produced based on the combined signal and the combined propagation path estimation value.

BRIEF DESCRIPTION OF THE DRAWINGS

The above and other objects, features and advantages of the present invention will become more apparent from the following detailed description made with reference to the accompanying drawings. In the drawings:

FIG. 1 illustrates an adaptive receiver according to a first embodiment of the present invention;

FIG. 2 illustrates a signal format used in the first embodiment;

FIGS. 3A to <b>3</b>D illustrate converging characteristic and constellation results when a simulation is executed in the first embodiment;

FIGS. 4A and 4B illustrate allocation of antennas and simulation conditions used in the simulation of FIG. 3;

FIG. 5 illustrates an adaptive receiver according to a second embodiment of the present invention;

FIG. 6 illustrates an adaptive receiver according to a third embodiment of the present invention;

FIG. 7 illustrates an adaptive receiver according to a fourth embodiment of the present invention;

FIG. 8 illustrates an adaptive arithmetic unit in the fourth embodiment;

FIG. 9 illustrates a modification of the fourth embodiment;

FIG. 10 illustrates an adaptive receiver according to a fifth embodiment of the present invention;

FIG. 11 illustrates an arrangement of symbol (time axis) and a carrier (frequency) of a SP system used in the fifth embodiment;

FIG. 12 illustrates a modification of the fifth embodiment;

FIG. 13 illustrates a modification of the fifth embodiment;

FIG. 14 illustrates a modification of the fifth embodiment;

FIG. 15 illustrates a modification of the fifth embodiment;

FIG. 16 illustrates a modification of the fifth embodiment;

FIG. 17 illustrates a modification of the fifth embodiment; and

FIGS. 18A-18C illustrate lessening of orthogonal property of a carrier when OFDM system is introduced.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

First Embodiment

Referring first to FIG. 1, an adaptive receiver includes an adaptive array unit <b>10</b> and an equalizing unit <b>20</b>. The adaptive array unit <b>10</b> is composed of an array antenna (made up of four antenna elements) <b>11</b>, an RF/IF circuit and an AD converter (RF/IF ADC) <b>12</b>, a guard interval removing unit (GIR) <b>13</b>, an high speed Fourier transforming unit (FFT) <b>14</b>, a complex weight adjusting unit <b>15</b>, an adder unit <b>16</b> and an adaptive arithmetic unit <b>17</b>.

Signals processed in this embodiment is formatted as shown in FIG. <b>2</b>. That is, the signal includes a preamble which is known. As regards this signal format, IEEE802.11a (radio LAN specification, packet communication), for example, is used. The known data of this preamble is used for timing detection, auto gain control (AGC), auto frequency control (AFC) and propagation path estimation.

OFDM signal transmitted from a transmitter (not shown) is received by the array antenna <b>11</b> made up of a plurality of antenna elements via a multipath signal wave propagation environment. The signal received by the array antenna <b>11</b> is sampled by the RF/IF ADC <b>12</b> into a digital baseband signal. This baseband signal is OFDM-demodulated by the GI removing unit <b>13</b> and FFT <b>14</b>. The OFDM demodulation signal is then inputted to the complex weight adjusting unit <b>15</b> and the adaptive arithmetic unit <b>17</b>.

In the complex weight adjusting unit <b>15</b>, the OFDM demodulation signals from the FFT <b>14</b> are multiplied with a signal (complex weight) from the adaptive arithmetic unit <b>17</b> for the weighting, respectively. By this weighting process, the phase and amplitude of the OFDM demodulation signal are adjusted. The weighted OFDM demodulation signals are combined in the adder unit <b>16</b> and are then outputted as output signals (demodulation signals after the adaptive combination) of the adaptive array unit <b>10</b>. The demodulation signals after this adaptive combination are fed back to the adaptive arithmetic unit <b>17</b>.

In the adaptive arithmetic unit <b>17</b>, the complex weight is updated using the OFDM demodulation signals of four systems from the FFT <b>14</b> and the feedback signal from the adder unit <b>16</b>. In this adaptive arithmetic unit <b>17</b>, MMSE, CMA, MSN and DCMP or the like are used as an adaptive algorithm.

The equalizing unit <b>20</b> is composed of a propagation path estimating unit <b>21</b>, a complex weight adjusting unit <b>22</b>, an adder unit <b>23</b> and a divider unit <b>24</b>.

The propagation path estimating unit <b>21</b> divides the known signal of the preamble provided in the OFDM demodulation signal by the known signal previously stored in the receiver side based on the respective OFDM demodulation signals from the FFT <b>14</b> to calculate a propagation path estimating value. For the ordinary equalization of the OFDM signal, a method has been proposed whereby the inverse characteristic of the propagation path is estimated by dividing the known signal stored in the receiver side by the received known signal and the receiving data is multiplied with such an inverse characteristic. In addition to the method for equalization, by dividing the received known signal by the known signal stored in the receiver side to estimate the propagation path and then dividing the receiving data by such a propagation path.

In this embodiment, however, the inverse characteristic of the propagation path cannot be used because the adaptive combination is performed, as will be explained later. Therefore, in this embodiment, the propagation path estimation value is calculated by dividing the known signals received by each antenna by the known signal stored in the receiver side, respectively.

This calculated propagation path estimation value is stored in a memory within the propagation path estimating unit <b>21</b> and is then outputted to the complex weight adjusting unit <b>22</b>. The propagation path estimation value stored in the memory is updated whenever the propagation path estimation value is newly calculated.

The complex weight adjusting unit <b>22</b> executes the weighting by multiplying the propagation path estimation value from the propagation path estimating unit <b>21</b> with the signal from the adaptive arithmetic unit <b>17</b>. In this case, the propagation path estimation values from the propagation path estimation unit <b>21</b> are multiplied with a complex weight the same as that used for the weighting process in the complex weight adjusting unit <b>22</b>. The weighted propagation path estimation values are added in the adder unit <b>23</b> to attain the propagation path estimation value after the adaptive combining process.

The demodulation signal after the adaptive combination outputted from the adaptive array unit <b>10</b> is divided, in the divider unit <b>24</b>, by the propagation path estimation value after the adaptive combining process. It is then outputted to a demodulation unit (not illustrated) of the latter stage as the demodulation signal equalized with the adaptive array unit <b>10</b> and equalizer <b>20</b>.

FIGS. 3A to <b>3</b>D illustrate the converging characteristic and constellation results when a simulation is executed. FIG. 4A illustrates layout of the antenna used for the simulation, while FIG. 4B illustrates the simulation condition. Moreover, the signal format conforms to IEEE802.11a.

From FIG. 3A, it can be confirmed that the adaptive array unit <b>10</b> can certainly control a signal wave (delayed wave <b>3</b>) on the outside of the guard interval with lower correlation but results in a lower control effect for signal waves (delayed waves <b>1</b>, <b>2</b>) within the guard interval. Here, the guard interval length is set to 800 ns. Moreover, a complementary signal wave is not a synchronized desired wave but the delayed wave <b>1</b>. As a result, the constellation circulates on the concentric circles and therefore, synchronous detection is impossible. However, a smooth demodulation characteristic can be obtained as illustrated in FIG. 3C by combining the adaptive array unit <b>10</b> and equalizer <b>20</b>. FIG. 3D illustrates the demodulation characteristic when the signal is received by only one antenna and ordinary equalization is executed. From a comparison of these demodulation characteristics, it is understood that a more excellent equalizing capability can be attained through a structure combining the adaptive array unit <b>10</b> and equalizer <b>20</b> as in the case of this embodiment.

Moreover, this embodiment is also superior from the point that the propagation path estimation value is calculated at the timing of using the desired signal wave but it is conducted as if the propagation path estimation value were obtained at the timing of the delayed signal wave because the propagation path estimation values are combined adaptively. Where the CMA is used as the adaptive algorithm, the erroneous complement of the signal results in a problem but it can be avoided in this embodiment.

Second Embodiment

In a second embodiment illustrated in FIG. 5, an adaptive arithmetic unit <b>171</b> is constructed to execute the adaptive arithmetic operation on the signal before OFDM demodulation.

The signal (signal in the time domain or region) from RF/IF ADC <b>12</b> is inputted to the adaptive arithmetic unit <b>171</b>. In this adaptive arithmetic unit <b>171</b>, MMSE is used as the adaptive algorithm to prepare a reference signal in the time domain of the preamble signal and calculate the complex weight to minimize any errors for the received signal in the time domain. The signals in the time domain from the RF/IF ADC <b>12</b> are weighted with the signal from the adaptive arithmetic unit <b>171</b> in the complex weight adjusting unit <b>15</b> and moreover, are then added in the adder unit <b>16</b>. The signal in the time domain after the adaptive combining is inputted to the adaptive arithmetic unit <b>171</b> and is demodulated by the OFDM demodulation method with the GI removing unit <b>13</b> and FFT <b>14</b>.

In the equalizer <b>20</b>, the signal in the time domain from the RF/IF ADC <b>12</b> is demodulated by the OFDM demodulation method in GI removing unit <b>221</b> and an FFT <b>222</b> and is then inputted to the propagation path estimating unit <b>21</b>. Thereafter, as in the first embodiment, the propagation path estimation value is calculated in the propagation path estimating unit <b>21</b>, the propagation path estimation value is weighted in the complex weight adjusting unit <b>22</b> and these propagation path estimation values are combined in the adder unit <b>23</b> to provide the propagation path estimation value after the adaptive combining.

The demodulation signal after the adaptive combining outputted from the adaptive array unit <b>10</b> is divided, in the dividing unit <b>24</b>, by the propagation path estimation value after the adaptive combining. It is then outputted to the demodulation unit (not shown) as the demodulation signal equalized by the adaptive array unit <b>10</b> and equalizer <b>20</b>.

Third Embodiment

In a third embodiment illustrated in FIG. 6, the equalizer <b>20</b> in the second embodiment is modified.

The equalizer <b>20</b> is composed of a buffer memory <b>223</b>, a complex weight adjusting unit <b>224</b>, an adder unit <b>225</b>, a GI removing unit <b>226</b>, an FFT <b>227</b>, a propagation path estimating unit <b>21</b> and a divider unit <b>24</b>.

The preamble signal among the signals in the time domain outputted from the RF/IF ADC <b>12</b> is stored in the buffer memory <b>223</b>. That is, the known signal before demodulation is extracted and stored in this buffer memory <b>223</b>. The signal stored in the buffer memory <b>223</b> is weighted with the signal from the adaptive arithmetic unit <b>171</b> in the complex weight adjusting unit <b>224</b>, added in the adder unit <b>225</b> and is then demodulated by the OFDM modulation method with the GI removing unit <b>226</b> and FFT <b>227</b>. The propagation path estimation value is calculated in the propagation path estimating unit <b>21</b> with the signal outputted from this FFT <b>227</b>.

As in the case of the second embodiment, the demodulation signal after the adaptive combining outputted from the adaptive array unit <b>10</b> is divided by the propagation path estimation value in the divider unit <b>24</b>. It is then outputted to the demodulation unit in the latter stage as the demodulation signal equalized with the adaptive array unit <b>10</b> and equalizer <b>20</b>.

In this embodiment, since the signal outputted from the FFT <b>227</b> is attained after the adaptive combining, a propagation path inverse characteristic estimating unit <b>228</b> and a multiplier unit <b>229</b> may be substituted for the propagation path estimating unit <b>21</b> and divider unit <b>24</b>. In this case, in the propagation path inverse characteristic estimating unit <b>228</b>, the known signal stored in the receiver side is divided by the received known signal to estimate the inverse characteristic of the propagation path. The equalization can be realized by multiplying the demodulation signal after the adaptive combining with such an estimation value in the multiplier unit <b>229</b>.

Fourth Embodiment

In a fourth embodiment illustrated in FIGS. 7 and 8, the adaptive arithmetic unit <b>172</b> executes the adaptive arithmetic operation between the signal in the time domain from the RF/IF ADC <b>12</b> and the signal on the frequency axis demodulated with the OFDM demodulation method by the GI removing unit <b>13</b> and FFT <b>14</b>.

In this case, the adaptive arithmetic unit <b>172</b> cannot realize the adaptive arithmetic operation using the existing algorithm because one input is the signal on the time axis, while the other input is the signal on the frequency axis. Therefore, it is requested here that both signals are set as either a signal on the time axis or a signal on the frequency axis. For this purpose, an IFFT (inverse high speed Fourier transforming unit) <b>1721</b> (FIG. 8) is provided in the adaptive arithmetic unit <b>172</b>. The correlation vector calculated from the signal on the frequency axis demodulated by the OFDM demodulation method from the FFT <b>14</b> is converted to the signal on the time axis and the adaptive arithmetic operation is executed with the algorithm, as in the case of the second embodiment using such a converted signal.

Here, it is also possible to introduce the structure illustrated in FIG. 9 by adapting the adaptive arithmetic unit of this embodiment to the third embodiment.

Fifth Embodiment

In a fifth embodiment illustrated in FIG. 10, SP system signal format using a scattered pilot (SP), of which the propagation path estimation value is updated with the passage of time, is used as the signal format. FIG. 11 illustrates the allocation of the symbol (time axis) and carrier (frequency) in this PS system. The pilot carrier (known signal) is allocated in adequate positions within a four-symbol unit. In the case of this SP system, the preamble is not allocated in the heading position of a packet, the equalizer <b>20</b> used in the first to fourth embodiments cannot be used.

Therefore, the equalizer <b>20</b> in this embodiment is composed, as illustrated in FIG. 10, of a known signal extracting unit <b>230</b>, the propagation path estimating unit <b>21</b> and the divider unit <b>24</b>. Moreover, it is also possible that the adaptive array unit <b>10</b> can introduce a structure similar to that in the second to fourth embodiments in addition to that of the first embodiment, as illustrated in FIG. <b>12</b> and FIG. <b>13</b>.

In the structure in FIG. 10, the known signal extracting unit <b>230</b> extracts the known signal inserted into the demodulation signal after the adaptive combining outputted from the adaptive array unit <b>10</b> in the unit with a predetermined number of symbols (four symbols, for example). The propagation path estimating unit <b>21</b> divides the known signal extracted by the known signal extracting unit <b>230</b> with the known signal previously stored in the receiver side to calculate the propagation path estimation value. This calculated propagation path estimation value is stored in the memory within the propagation path estimating unit <b>21</b> and is then updated in the four-symbol unit.

Next, the demodulation signal after the adaptive combining outputted from the adaptive array unit <b>10</b> is divided by the propagation path estimation value in the divider unit <b>24</b> and is then outputted to the demodulation unit in the latter stage as the data equalized with the adaptive array unit <b>10</b> and equalizer <b>20</b>.

Since the signal outputted from the adaptive array unit <b>10</b> is the signal after the adaptive combining even in this embodiment, it is also possible that the propagation path inverse characteristic estimating unit <b>228</b> and the multiplier unit <b>229</b> are substituted for the propagation path estimating unit <b>21</b> and divider unit <b>24</b>.

In this embodiment, it is of course possible that the adaptive arithmetic unit <b>17</b> updates the complex width for every symbol as in the case of the first embodiment. However, since the propagation path estimating unit <b>21</b> updates the propagation path estimation value in the unit with a predetermined number of symbols (four symbols, for example), it is preferable that the adaptive arithmetic unit <b>17</b> does not update the complex weight during the period of the predetermined number of symbols. This example will be explained by reference to FIG. <b>14</b>.

The adaptive arithmetic unit <b>17</b> updates the complex weight in the four-symbol unit. Here, it is assumed that the adder unit <b>16</b> outputs the four-symbol data (D) <b>2</b>-<b>1</b>, <b>2</b>-<b>2</b>, <b>2</b>-<b>3</b> and <b>2</b>-<b>4</b> using the complex weight W<b>2</b>. After this output, the adaptive arithmetic unit <b>17</b> outputs the next complex weight W<b>3</b>. The known signal extracting unit <b>230</b> extracts the known signal from the four-symbol data <b>2</b>-<b>1</b>, <b>2</b>-<b>2</b>, <b>2</b>-<b>3</b> and <b>2</b>-<b>4</b>. At this timing, since the propagation path estimating unit <b>21</b> outputs the propagation path estimation value Cest<b>1</b> calculated based on the known signal extracted before the four symbols, the four-symbol data <b>2</b>-<b>1</b>, <b>2</b>-<b>2</b>, <b>2</b>-<b>3</b> and <b>2</b>-<b>4</b> are equalized with the propagation path estimation value Cest<b>1</b>.

Moreover, in this case, the signal outputted from the propagation path estimating unit <b>21</b> is delayed by as much as the time of the four symbols from the demodulation signal after the adaptive combining outputted from the adder unit <b>16</b>. In order to eliminate such a time delay, it is sufficient to delay the data to be equalized by as much as the four symbols using a delaying unit, such as the buffer. For example, as illustrated in FIG. 15, a buffer <b>231</b> is provided before the divider unit <b>24</b>. Thereby, the four-symbol data <b>1</b>-<b>1</b>, <b>1</b>-<b>2</b>, <b>1</b>-<b>3</b> and <b>1</b>-<b>4</b> can be equalized with the propagation path estimation value Cestl calculated based on the known signal extracted from the four-symbol data <b>1</b>-<b>1</b>, <b>1</b>-<b>2</b>, <b>1</b>-<b>3</b> and <b>1</b>-<b>4</b>. The Cest<b>2</b> in the figure indicates the propagation path estimation value calculated based on the known signal extracted from the four-symbol data <b>2</b>-<b>1</b>, <b>2</b>-<b>2</b>, <b>2</b>-<b>3</b> and <b>2</b>-<b>4</b>.

Moreover, this embodiment may be modified as illustrated in FIG. <b>16</b>. In this case, the adaptive arithmetic unit <b>17</b>, complex weight adjusting unit <b>15</b> and adder unit <b>16</b> execute the adaptive arithmetic operation in the unit of each symbol by a structure similar to that of the first embodiment. Thereafter, the complex weight updated for each symbol by such calculation is held in a sample-hold unit <b>18</b> as in the unit with a predetermined number of symbols (four symbols, for example) and the adaptive combining is conducted with a complex weight adjusting unit <b>151</b> and an adder unit <b>161</b> using the held complex weight. The structure of the equalizer <b>20</b> in the subsequent stage may be identical to that illustrated in FIG. 14, or may be formed with the addition of the buffer <b>231</b> illustrated in FIG. 15 as illustrated in FIG. <b>17</b>.

In the embodiments illustrated in FIG. 14 to FIG. 17, it is possible to introduce the structures of the second to fourth embodiments as the structure of the adaptive array unit <b>10</b> and moreover, it is also possible to use the propagation path inverse characteristic estimating unit <b>228</b> and multiplier unit <b>229</b> in place of the propagation path estimating unit <b>21</b> and the divider unit <b>24</b>.

Moreover, the present invention is not only limited to the adaptive receiver utilizing the OFDM transmission system but can also be widely adapted to that utilizing a multi-carrier transmission system.