Communications circuitry supporting high-Q antenna

PRIOR AND RELATED APPLICATIONS

This Application is a continuation of U.S. application Ser. No. 16/697,207 filed Nov. 27, 2019, which claims the benefit of U.S. Provisional Application No. 62/771,883, filed Nov. 27, 2018, the disclosures of which are incorporated by reference into the present Specification. In addition, this Application is related by subject matter to U.S. application Ser. No. 16/697,210 filed Nov. 27, 2019.

TECHNICAL FIELD

Embodiments described herein generally relate to electronics and wireless communications and, more particularly, to high-quality-factor (high-Q) resonant circuitry for driving and reading communications devices.

BACKGROUND

A radio-frequency identification (RFID) reader generates electromagnetic fields to energize and interrogate a RFID tag or other compatible communications device located within communication range of the reader. The RFID tag may use the energy supplied by the reader's driving signal, or another source of power, to communicate information to the reader using RF signaling. RFID has found applications in a wide variety of areas, including asset tracking, security, supply chain logistics, manufacturing, testing and measurement, and myriad others.

In one type of application, biocompatible RFID tags have been proposed for use with implantable medical devices for transcutaneous communication. These types of applications present several notable challenges to system designers. For one, the body tends to absorb and attenuate RF signals, particularly high-frequency RF signals, which are able to carry higher bandwidths. In addition, the transmit power of RFID readers for use in implantable-tag applications is often limited for safety reasons. Since an implanted tag is not visible in the absence of imaging instruments, achieving an optimal positioning and alignment between the reader and the tag can be particularly difficult. Moreover, some patients, such as children or animals, tend to have difficulty keeping still during reading of the tag. These challenges compound to make RFID-based implantable sensors difficult to implement in practice.

Related challenges may be found in other applications. For example, underwater environments, longer-range reading, and RFID reading in RF-noisy environments, each exacerbate the difficulty of reliably reading RFID tags.

High quality-factor (Q) radio circuitry has been proposed for use in RFID systems. High-Q radio communications use a specially-designed antenna and radio front end circuitry to emit a particularly strong RF field for a given transmit power, in a narrow frequency band, using principles of electromagnetic resonance. High-Q RFID readers and tags can improve communications performance in environments where distance, signal attenuation, or interference may pose challenges. However, high-Q systems also introduce particular challenges of their own. For instance, a high-Q transmitter in a RFID reader may overload the tag. In addition, a high-Q system tends to be very sensitive to frequency deviations and instability. Also, high-Q RF communication systems tend to suffer from group delay, where different frequencies experience different amounts of time delay in the receiver.

Solutions are needed to address these, and other, challenges in RFID reading applications.

BRIEF DESCRIPTION OF THE DRAWINGS

In the drawings, which are not necessarily drawn to scale, like numerals may describe similar components in different views. Like numerals having different letter suffixes may represent different instances of similar components. Some embodiments are illustrated by way of example, and not limitation, in the figures of the accompanying drawings.

<figref idref="DRAWINGS">FIG. 1</figref> is a diagram illustrating a use case scenario of a RFID reader communicating with a RFID tag via RFID signaling according to examples of the embodiments.

<figref idref="DRAWINGS">FIG. 2</figref> is a simplified, high-level, block diagram illustrating certain portions of a RFID reader according to some example embodiments.

<figref idref="DRAWINGS">FIG. 3</figref> is a block diagram illustrating a transmitter circuit portion of the RFID reader of <figref idref="DRAWINGS">FIG. 2</figref> in greater detail according to an example embodiment.

<figref idref="DRAWINGS">FIG. 4</figref> is a block diagram illustrating an example embodiment of a receiver circuit portion of the RFID reader of <figref idref="DRAWINGS">FIG. 2</figref> in greater detail according to an example embodiment.

<figref idref="DRAWINGS">FIG. 5</figref> is a schematic diagram illustrating a signal conditioning arrangement of the receiver circuit portion of <figref idref="DRAWINGS">FIG. 4</figref> according to an example embodiment.

<figref idref="DRAWINGS">FIG. 6</figref> is a spectrum graph illustrating a narrow pass band associated with a high-Q antenna, superimposed over frequency components of a signal to be received.

<figref idref="DRAWINGS">FIG. 7</figref> is a graph illustrating frequency components having different amplitudes due to reception of the signal by a high-Q antenna.

DETAILED DESCRIPTION

Aspects of the embodiments are generally directed to high-Q radio communications technology. As discussed above, there are numerous applications in the field of RFID where high-Q RFID readers may be employed, including in transcutaneous measurement or communications with implantable devices. Likewise, high-Q RFID readers may be used in other RFID applications that may benefit from the advantages afforded by the high-Q operational characteristics. It should also be noted that principles of the embodiments are applicable to RF-communications applications outside the sphere of RFID. For example, telemetry and data collection, measurement and process control, networking, and many other applications, may benefit from aspects of the embodiments. Accordingly, the scope of the claims should not be limited to any particular application or embodiment unless such a limitation is expressly stated in those claims.

<figref idref="DRAWINGS">FIG. 1</figref> is a diagram illustrating an example use case scenario of a RFID reader <b>100</b> communicating with RFID tag <b>110</b> via RFID signaling <b>120</b>. RFID tag <b>110</b> in this example is implanted in patient <b>130</b>. RFID signaling <b>120</b> may be adapted for passive RFID tag reading, or active RFID tag reading. Passive RFID reading uses RFID tag <b>110</b> that does not have a power source apart from reader <b>100</b>. In active RFID reading, tag <b>110</b> has a power source apart from any driving signal.

In the passive RFID tag case, RFID signaling <b>120</b> includes transmission of driving signal <b>124</b> by RFID reader <b>100</b>, which powers RFID tag <b>110</b> to enable the latter to transmit information signal <b>126</b>. Information signal <b>126</b> may be a static tag ID signal, or it may be a variable-information signal such as a sensor reading, for instance.

In the active RFID tag case, RFID driving signaling <b>124</b> may be either included in, or omitted from, RFID signaling <b>120</b>. In some active RFID examples, driving signal <b>124</b> is replaced by a lower-power interrogation signal that prompts RFID tag <b>110</b> to transmit information signal <b>126</b>. In other examples, RFID tag <b>110</b> independently transmits information signal <b>126</b> periodically or continuously, without being prompted.

According to various embodiments, RFID signaling <b>120</b> is facilitated by high-Q antenna and resonant (e.g., tank) circuitry. In the present context, high-Q antenna and associated transmission circuitry means a quality factor Q of at least 100.

In related embodiments, as depicted, RFID reader <b>100</b> is configurable to communicate with remote receiver <b>142</b> via long-distance RF signaling <b>140</b>. Remote receiver <b>142</b> may be used to receive results or data collected via RFID signaling <b>120</b>. Data for multiple instances of RFID tag readings may be collected and stored in database <b>144</b> coupled to remote receiver <b>142</b>. The multiple RFID tag readings may correspond to one, or multiple different, RFID tags.

In some embodiments, long-distance RF signaling <b>140</b> is facilitated by the same RF hardware components as RFID signaling <b>120</b>. Given the greater transmission range to be achieved for long-distance RF signaling <b>140</b>, the transmission circuitry drives substantially greater power to the antenna compared to the driving signal power for transmission of RFID signaling <b>120</b>. For instance, long-distance RF signaling <b>140</b> may utilize at least 100 times the transmission power of RFID signaling <b>120</b>. In another example, long-distance RF signaling <b>140</b> may utilize at least 500 times the transmission power of RFID signaling <b>120</b>.

<figref idref="DRAWINGS">FIG. 2</figref> is a simplified, high-level, block diagram illustrating certain portions of RFID reader <b>100</b> according to some example embodiments. It will be understood that RFID reader <b>100</b> may have additional subsystems that are omitted from the example depicted in <figref idref="DRAWINGS">FIG. 2</figref> for the sake of clarity. As depicted, RFID reader <b>100</b> includes transmitter circuit <b>202</b> and receiver circuit <b>204</b>. Transmitter circuit <b>202</b> includes power control subcircuit <b>210</b>, and resonance control subcircuit <b>212</b>.

Power control subcircuit <b>210</b> is constructed to dynamically adjust the transmission power to correct for variations in the signal propagation path that affect the signal strength of the transmitted signal. Examples of such variations include variations in signal transmission distance, variation in positioning relative to a RFID tag or remote receiver, movement or introduction of obstructions such as reflective objects, variation of the dielectric properties of the space through which the signal propagates (e.g., moisture), or the like. Resonance control subcircuit <b>212</b> is constructed to adjust the transmission circuit impedance to establish or maintain resonance at the carrier frequency of the transmitted driving signal <b>124</b>. In some examples, as described in greater detail below, the carrier frequency of driving signal <b>124</b> may remain fixed while various environmental variations may affect the resonance characteristics of the system; accordingly, resonance control subcircuit <b>212</b> may advantageously correct for the environmental variations.

High-Q antenna <b>216</b> is coupled to transmitter circuit <b>202</b>, as well as to receiver circuit <b>204</b>. In another embodiment (not shown), separate high-Q antennas are provided for transmitter circuit <b>202</b> and receiver circuit <b>204</b>.

Receiver circuit <b>204</b> includes variable-gain control and multi-path split subcircuit <b>220</b>, multi-path filtering subcircuitry <b>222</b>, multi-path temporal alignment control subcircuitry <b>224</b>, and high-dynamic-range (HDR) sense signal conditioner subcircuitry <b>226</b> according to the example depicted. Variable-gain control and multi-path split subcircuit <b>220</b> is constructed to amplify and dynamically adjust the received baseband signal gain to produce a baseband signal within a defined range for further signal conditioning, and to split the amplified received baseband signal into multiple parallel paths. Multi-path filtering subcircuitry <b>222</b> includes independent bandpass filtering in each of the multiple parallel paths. Multi-path temporal alignment control subcircuitry <b>224</b> includes all-pass filtering, independently in each of the parallel paths, to adjust the respective group delays. Multi-path temporal alignment control subcircuitry <b>224</b> produces multiple received data signals having the substantially matched amplitude and group delay.

In some embodiments, receiver circuit <b>204</b> further includes high-dynamic-range (HDR) sense signal conditioner subcircuitry <b>226</b>. HDR sense signal conditioner subcircuitry <b>226</b> may be used to support received-signal-strength-based locating of a signal emitter. For example, in a surgical application, a RFID marker-tag may be implanted at a particular anatomical site to be used as a marker. The RFID marker-tag may be used to mark the location of a nerve or other anatomical structure or node to be preserved. Similarly, the RFID marker-tag may be used to mark a structure to be excised or treated, such as a tumor or ablation site, for instance.

<figref idref="DRAWINGS">FIG. 3</figref> is a block diagram illustrating transmitter circuit <b>202</b> in greater detail according to an example embodiment. Controller <b>302</b>, which may be implemented using a microprocessor, a digital signal processor (DSP), a field-programmable gate array (FPGA), or the like, oversees and dynamically adjusts the operation of the various components of transmitter circuit <b>202</b>. Controller <b>302</b> supplies transmit power control signaling <b>304</b>A to variable power supply <b>306</b>, and resonance control signaling <b>304</b>B to resonance control circuit <b>318</b>. Controller <b>302</b> also supplies data stream <b>308</b> to modulator <b>312</b>. Controller <b>302</b> includes memory <b>303</b> allocated to store ID numbers of known RFID tags, which may be individually addressed or interrogated using RFID signaling <b>120</b>.

Variable power supply <b>306</b> produces variable supply power <b>310</b> for use by power RF amplifier <b>316</b> to produce driving signal <b>124</b>. Variable supply power <b>310</b> is dynamically adjusted in response to power control signaling <b>304</b>A.

In related embodiments, controller <b>302</b> selectively controls generation of modulated RF signal <b>314</b> for transmission to remote receiver <b>142</b>, or RFID tag <b>110</b> (<figref idref="DRAWINGS">FIG. 1</figref>). Accordingly, controller <b>302</b> issues power control signaling <b>304</b>A for variable power supply <b>306</b> to call for diverse supply power provision. In some embodiments, variable supply power <b>310</b> may be adjusted from less than 10 V to more than 50 V. In related embodiments, variable supply power may be adjusted from less than 10 V to more than 100 V. As an example, variable supply power may be adjusted from less than 10 V to more than 150 V. As another example, variable supply power may be adjusted from less than 10 V to more than 200 V. Since power is proportional to the square of the voltage, variable power supply <b>306</b> facilitates transmission power variation by factors of 100, 500, 1000, or more.

Modulator <b>312</b> modulates a RF carrier wave using data stream <b>308</b> to produce modulated RF signal <b>314</b>, which is fed to power RF amplifier <b>316</b>. Modulator <b>312</b> may apply a suitable analog or digital modulation technique such as, for example, amplitude modulation (AM), phase modulation (PM), frequency modulation (FM), amplitude shift keying (ASK), phase shift keying (PSK), frequency shift keying (FSK), quadrature amplitude modulation (QAM), or any variant or combination of one or more of these techniques, such as binary phase shift keying, quadrature phase shift keying, on-off keying, etc.

Power RF amplifier <b>316</b> amplifies modulated RF signal <b>314</b> based on the level of variable supply power <b>310</b>, to produce driving signal <b>124</b>, which is fed to high-Q resonant antenna <b>320</b>. The use of variable supply power <b>310</b> allows power RF amplifier <b>316</b> to vary the amplitude of driving signal <b>124</b> over a wide range (e.g., from less than 10 volts to hundreds of volts, as discussed above). Variation of supply power <b>310</b> may be performed to maintain a relatively stable emitted electromagnetic field in continuously-changing conditions (such as, for example, as the spacing between the RFID reader and the RFID tag <b>110</b> varies), or for different selectable signal recipients (e.g., remote receiver <b>142</b>), which may be located at substantially different distances from RFID reader <b>100</b>.

Resonance control circuit <b>318</b> adjusts the reactance of high-Q resonant antenna <b>320</b> based on resonance control signaling <b>304</b>B. As depicted in the example shown in <figref idref="DRAWINGS">FIG. 3</figref>, resonance control circuit <b>318</b> may be magnetically coupled to high-Q resonant antenna <b>320</b>, with a variable magnetic bias. However, any suitable coupling technique (e.g., adjustable capacitive coupling) may be employed. In addition, various other embodiments of resonance control circuit <b>318</b> may utilize a variable capacitor arrangement or a combination of variable inductance and variable capacitance to adjust the reactance of the L-C resonant network formed by resonance control circuit <b>318</b> and high-Q resonant antenna <b>320</b>. In an example embodiment, resonance control circuit <b>318</b> adjusts the reactance of high-Q resonant antenna <b>320</b> by varying a direct current through an inductor to adjust the inductor's magnetic bias.

The resonance frequency of the electromagnetic field depends on the transmission circuitry, which is made variable by resonance control circuit <b>318</b>, the geometry and reactance of high-Q resonant antenna <b>320</b>, along with the characteristic impedance of the environment in which the electromagnetic field is to be propagated. As the environmental characteristics may vary (e.g., due to changing positioning of the antenna relative to objects in the vicinity of the emitted field, to a body of a patient (in the case of a biomedical application), to conductive or magnetic materials, or the like, the resonance frequency may vary. Accordingly, in some embodiments, a feedback control system is provided to align the resonance frequency of the electromagnetic field with the carrier frequency of RFID signaling <b>120</b> or long-distance RF signaling <b>140</b>.

In a related type of embodiment, the feedback control system is provided to align the resonance frequency of the electromagnetic field with a sideband frequency near the carrier frequency of RFID signaling <b>120</b> or long-distance RF signaling <b>140</b>. In another related type of embodiment, the feedback control system is provided to align the resonance frequency of the electromagnetic field with a harmonic of the carrier frequency (or sideband near the carrier frequency) of RFID signaling <b>120</b> or long-distance RF signaling <b>140</b>.

Field sensor <b>328</b> operates in the feedback loop of the feedback control system according to these embodiments. Field sensor <b>328</b> may be coupled to the emitted field itself, with the latter depicted via feedback coupling <b>330</b> as one example. Feedback coupling <b>330</b> may be capacitive or magnetic according to various approaches that may be taken.

Field sensor <b>328</b> produces phase error signal <b>332</b> and amplitude error signal <b>334</b>, each to be provided to controller <b>302</b>. Each error signal <b>332</b>, <b>334</b> indicates the measured variation from a nominal condition. For instance, at resonance, the phase offset angle is nominally 90 degrees; hence, the phase error signal <b>332</b> may represent the difference between the measured phase offset and 90 degrees. Amplitude error signal indicates the difference between the measured electromagnetic field amplitude and an expected nominal value.

In controlling the parameters of driving signal <b>124</b>, controller <b>302</b> adjusts variable power supply <b>306</b> with transmit power control signaling <b>304</b>A in response to amplitude error signal <b>334</b> so as to minimize the amplitude error. Likewise, controller <b>302</b> adjusts resonance control circuit <b>318</b> with resonance control signaling <b>304</b>B in response to phase error signal <b>332</b> so as to minimize the phase error.

<figref idref="DRAWINGS">FIGS. 4A and 4B</figref> are block diagrams illustrating an example embodiment of receiver circuit <b>204</b>. Subcircuitry of receiver circuit <b>204</b>, namely, variable-gain control and multi-path split subcircuit <b>220</b>, multi-path filtering subcircuitry <b>222</b>, and multi-path temporal alignment control subcircuitry <b>224</b> are depicted in <figref idref="DRAWINGS">FIG. 4A</figref> according to example embodiments. HDR sense signal conditioner subcircuitry <b>226</b> is depicted in <figref idref="DRAWINGS">FIG. 4B</figref> according to an example.

Referring to <figref idref="DRAWINGS">FIG. 4A</figref>, demodulator and amplifier <b>422</b> accepts as its input a modulated RF signal. The modulated RF signal may be as received at the high-Q antenna, or it may have been conditioned to some extent (e.g., amplified, filtered, etc.) at this point. The modulated RF signal may have been originated by a RFID tag, or other device in communication with receiver circuit <b>204</b>.

The modulated RF signal may have a certain bandwidth, or a plurality of baseband frequency components that are modulated onto a RF carrier wave. As described in greater detail below, use of the high-Q antenna may tend to complicate the accurate recovery of the baseband signal from received RF signal by imparting group delay and frequency-dependent attenuation, which may distort the demodulated baseband signal.

According to an aspect of the embodiments, receiver circuit <b>204</b> includes multiple receive paths. As illustrated, this example has first receive path <b>420</b>A, and second receive path <b>420</b>B. Each receive path <b>420</b>A/B receives the demodulated baseband signal as its input. Each receive path includes low-pass filter <b>424</b>A/B, which feeds into signal conditioning arrangements <b>426</b>A/B. Each signal conditioning arrangement <b>426</b>A/B includes bandpass filter <b>428</b>A/B, all-pass filter <b>430</b>A/B, and amplifier <b>432</b>A/B.

Bandpass filters <b>428</b>A and <b>428</b>B are tuned to different center frequencies, which may correspond respectively to different frequency components of the baseband signal. All-pass filters <b>430</b>A and <b>430</b>B are individually controllable to apply a specific time delay to its respective receive path <b>420</b>A/B. Amplifiers <b>432</b>A and <b>432</b>B are also individually controllable to apply a specific gain to its respective receive path <b>420</b>A/B.

The control of all-pass filters <b>430</b>A/B and amplifiers <b>432</b>A/B is provided via amplitude/time controller circuit <b>434</b>, based on feedback supplied by ratio detector <b>436</b>. Ratio detector <b>436</b> compares the temporal alignment and the relative amplitudes of outputs <b>433</b>A and <b>433</b>B from respective signal conditioning arrangement <b>426</b>A/B, and feeds error signaling <b>437</b> to amplitude/time controller <b>434</b>. In turn, amplitude/time controller <b>434</b> generates compensation control signaling <b>435</b>A and <b>435</b>B respectively to each signal conditioning arrangement <b>426</b>A/B. As a result of the operation of control loops individually controlling signal conditioning arrangements <b>426</b>A and <b>426</b>B, the recovered baseband signaling of each receive path <b>420</b>A/B is equalized and temporally aligned.

Outputs <b>433</b>A and <b>433</b>B from respective signal conditioning arrangement <b>426</b>A/B are also fed to mixer <b>438</b>, which combines the outputs from receive paths <b>420</b>A/B to produce recovered baseband signal <b>439</b>. Recovered baseband signal <b>439</b> is fed to automatic gain controller <b>444</b> and digital signal processor (DSP) block <b>442</b>.

Automatic gain controller <b>444</b> compares the amplitude of recovered baseband signal <b>439</b> against a target amplitude, and generates amplitude correction signal <b>445</b> to adjust the gain of demodulator and amplifier circuitry <b>422</b> such that the target amplitude is approached.

DSP block <b>442</b> includes analog-to-digital converter (ADC) circuitry (e.g., sampling, quantization, encoding, etc.) and a DSP (e.g., processor core, memory, etc.) that executes signal-processing algorithms to read and interpret recovered baseband signal <b>439</b>. In some embodiments, DSP <b>442</b> generates frequency-selection signaling <b>443</b>A, <b>443</b>B, to be respectively provided to all-pass filter <b>430</b>A and <b>430</b>B to set or adjust the center frequency subject to delay.

Referring now to <figref idref="DRAWINGS">FIG. 4B</figref>, HDR sense signal conditioner subcircuitry <b>226</b> according to the example depicted includes front-end amplifier <b>450</b> that receives the RF signal. The RF signal may include a signal component originated by a tag or other signal emitter having a signal output, such as a sense signal. The signal output may be an analog signal having a particular waveform or frequency used to convey information or to signal a presence of the tag or signal emitter. HDR sense signal conditioner subcircuitry <b>226</b> according to some embodiments is specifically adapted to receive, and measure, the sense signal.

Front-end amplifier <b>450</b> may be a fixed-gain low-noise amplifier (LNA), for example. Band-pass filter (BPF) <b>452</b> is tuned to the frequency of the sense signal. High-dynamic-range (HDR) amplifier <b>454</b> provides a variable gain to accommodate a wide range of received signal amplitudes. In the embodiment depicted, amplifier circuit <b>456</b> has a feedback loop with a switchable impedance network <b>458</b> provided to facilitate the variable gain. The switchable impedance network <b>458</b> according to an example provides step-wise adjustment (e.g., 2 dB, 3 dB, 5 dB, 8 dB, etc.). HDR amplifier <b>454</b> produces conditioned signal <b>460</b> that is fed to DSP <b>442</b> (e.g., via an analog-to-digital converter (ADC) input—not separately shown). Gain control signal <b>462</b> is provided from DSP <b>442</b> to switchable impedance network <b>458</b> in order to select and adjust the feedback impedance.

In a related embodiment, amplifier circuit <b>456</b> may have a fixed gain, with a switchable impedance network positioned at its input rather than in its feedback loop. In another embodiment, the switchable impedance network may be positioned at the output of amplifier circuit <b>456</b> rather than in its feedback loop.

Advantageously, with the variable impedance provided by HDR amplifier <b>454</b> accommodates a wide range of signal amplitudes at its input, and outputs conditioned signal <b>460</b> having an amplitude corresponding to the scale of the A/D input of DSP <b>442</b>. Accordingly, the resolution of the A/D input and hence the accuracy of the sampling of the RF signal may be optimized. As an example, where the A/D input has a defined maximum input limit, the HDR amplifier may be set with a gain to produce the conditioned signal <b>460</b> at an amplitude that is between the maximum input limit, and one-half of the maximum input limit. In another example, the HDR amplifier may be set with a gain to produce the conditioned signal <b>460</b> at an amplitude that is between the maximum input limit, and two-thirds of the maximum input limit.

<figref idref="DRAWINGS">FIG. 5</figref> is a schematic diagram illustrating signal conditioning arrangement <b>426</b> in greater detail according to an example embodiment. Input node <b>502</b> is coupled to the output of low-pass filter <b>424</b>. Compensation control signaling <b>435</b> is provided to gate of transistor Q<b>1</b>, which is configured to operate as a variable-resistance transmission gate. Together with resistor R<b>1</b> and capacitor C<b>1</b>, the variable-resistance transmission gate of Q<b>1</b> varies the time constant and quality factor Q at the non-inverting input of operational amplifier OP<b>1</b>.

Operational amplifiers OP<b>1</b> and OP<b>2</b> are arranged as a dual-amplifier bandpass resonant circuit using capacitors C<b>1</b> and C<b>2</b> along with the amplification gain, to perform amplification and bandpass filtering of the input signal at input node <b>502</b>. Transistor Q<b>1</b> controls the quality factor, Q, of the resonance characteristics of signal conditioning arrangement <b>426</b>, along with a time delay. Accordingly, these components add a variable delay before the amplification stage provided by operational amplifier OP<b>3</b>.

In a related example, capacitor C<b>2</b> is variable, and electronically controlled by frequency selection signaling <b>443</b>. Adjustment of the capacitance value of capacitor C<b>2</b> in this manner provides controllable variability of the frequency that is subject to delay. As an example, frequency selection signaling <b>443</b> may be supplied by DSP <b>442</b> separately to each signal conditioning arrangement <b>426</b>. Thus, for instance, referring to <figref idref="DRAWINGS">FIG. 4A</figref>, signal conditioning arrangement <b>426</b>A may be tuned to a different frequency from signal conditioning arrangement <b>426</b>B.

<figref idref="DRAWINGS">FIG. 6</figref> is a spectrum graph illustrating a narrow pass band associated with a high-Q antenna, superimposed over frequency components of a signal to be received. The RF signal to be received may be an amplitude-modulated (AM) signal that includes carrier wave CW, lower sideband LSB, and upper sideband USB. Each sideband USB, LSB has a first baseband frequency component BFC<b>1</b> and a second baseband frequency component BFC<b>2</b>. Pass band PB associated with the high-Q antenna has a narrow bandwidth, which may be narrower than the entire RF signal. When passing through the high-Q antenna, baseband frequency component BFC<b>2</b> is attenuated to the amplitude indicated at <b>602</b>. Frequency component BFC<b>2</b>, being located closer to the center frequency of pass band PB, is attenuated to a lesser extent, or not at all. As a result, when the RF signal is demodulated, the baseband frequency components, BFC<b>1</b> and BFC<b>2</b>, may have different amplitudes.

<figref idref="DRAWINGS">FIG. 7</figref> is a graph illustrating the frequency components having different amplitudes due to reception of the signal by a high-Q antenna. As shown, baseband frequency component BFC<b>2</b> has a smaller amplitude than baseband frequency component BFC<b>1</b>. Operation of receiver circuit <b>204</b> serves, in part, to equalize these amplitudes with the application of differing amounts of gain in the receive paths. In addition, receiver circuit <b>204</b> serves to apply differing amounts of time delay to the different receive paths in order to achieve temporal alignment between baseband frequency components BFC<b>1</b> and BFC<b>2</b>.

ADDITIONAL NOTES & EXAMPLES

Example 1 is a radio-frequency (RF) transmitter circuit comprising: a controller circuit to generate transmission control signaling; a modulator circuit to modulate a RF carrier wave having a fixed frequency with a baseband signal; a RF driver circuit to be coupled to an antenna, the RF driver circuit to amplify the modulated carrier wave for transmission via the antenna; a power control circuit to dynamically adjust supply power to the RF driver circuit in response to the transmission control signaling, wherein the supply power controls a degree of amplification applied by the RF driver circuit to control a strength of the transmission; a field sensor coupled to the antenna and configured to measure a resonance condition of the transmission; a resonance control circuit to dynamically adjust a resonance frequency of the antenna, in response to the transmission control signaling, to maintain resonance of the transmission at the fixed frequency of the carrier wave; wherein the controller circuit generates the transmission control signaling in response to a measured strength and the resonance condition of the transmission.

In Example 2, the subject matter of Example 1 includes, the antenna, wherein the antenna has a quality factor Q of at least 100.

In Example 3, the subject matter of Examples 1-2 includes, the antenna, wherein the resonance control circuit is magnetically coupled to the antenna.

In Example 4, the subject matter of Examples 1-3 includes, wherein the field sensor outputs a phase error signal for use by the controller, the phase error signal representing an extent of deviation from resonance of the transmission.

In Example 5, the subject matter of Example 4 includes, wherein the field sensor further outputs an amplitude error signal for use by the controller, the amplitude error signal representing an extent of deviation from a target amplitude of the transmission.

In Example 6, the subject matter of Examples 1-5 includes, wherein the transmission control signaling includes resonance control signaling supplied to the resonance control circuit, and power control signaling supplied to the power control circuit.

In Example 7, the subject matter of Examples 1-6 includes, wherein the controller circuit is to supply the baseband signal to the modulator circuit.

In Example 8, the subject matter of Examples 1-7 includes, wherein the RF transmitter circuit is part of a radio-frequency identification (RFID) reader device, and wherein the transmission is a RFID driving signal to activate a RFID tag.

In Example 9, the subject matter of Examples 1-8 includes, wherein the transmission control signaling includes first indicia corresponding to relatively shorter-distance transmission, and second indicia corresponding to relatively longer-distance transmission, wherein the second indicia calls for a higher supply power than supply power called for by the first indicia.

In Example 10, the subject matter of Example 9 includes, wherein the RF driver circuit is constructed to generate: at a first time, a first modulated carrier wave corresponding to the relatively shorter-distance transmission at the supply power called for by the first indicia; and at a second time, a second modulated carrier wave corresponding to the relatively longer-distance transmission at the supply power called for by the second indicia.

In Example 11, the subject matter of Examples 9-10 includes, wherein the relatively shorter-distance transmission comprises a radio-frequency identification (RFID) tag driving signal to activate a RFID tag, and wherein the relatively longer-distance transmission comprises a data-communication signal to be received by a remote receiver.

In Example 12, the subject matter of Examples 9-11 includes, wherein the higher supply power called for by the second indicia is at least 100 times greater than the supply power called for by the first indicia.

In Example 13, the subject matter of Examples 1-12 includes, wherein the power control circuit to is to dynamically adjust supply power to the RF driver circuit over a range of less than 10 V to greater than 100 V.

Example 14 is a radio-frequency (RF) transmitter circuit comprising: a controller circuit to generate transmission control signaling that includes, first indicia corresponding to relatively shorter-distance transmission, and second indicia corresponding to relatively longer-distance transmission; a modulator circuit to modulate a RF carrier wave having a fixed frequency with a baseband signal; a RF driver circuit to be coupled to an antenna, the RF driver circuit to amplify the modulated carrier wave for transmission via the antenna; a power control circuit to dynamically adjust supply power to the RF driver circuit in response to the transmission control signaling, wherein the supply power controls a degree of amplification applied by the RF driver circuit to control a strength of the transmission, wherein a relatively lower strength of transmission corresponds to the first indicia, and a relatively higher strength of transmission corresponds to the second indicia; wherein RF driver circuit is constructed to generate: at a first time, a first modulated carrier wave corresponding to the relatively shorter-distance transmission at the supply power called for by the first indicia; and at a second time, a second modulated carrier wave corresponding to the relatively longer-distance transmission at the supply power called for by the second indicia.

In Example 15, the subject matter of Example 14 includes, wherein the relatively shorter-distance transmission comprises a radio-frequency identification (RFID) tag driving signal to activate a RFID tag, and wherein the relatively longer-distance transmission comprises a data-communication signal to be received by a remote receiver.

In Example 16, the subject matter of Examples 14-15 includes, wherein the higher supply power called for by the second indicia is at least 100 times greater than the supply power called for by the first indicia.

In Example 17, the subject matter of Examples 14-16 includes, wherein the power control circuit to is to dynamically adjust supply power to the RF driver circuit over a range of less than 10 V to greater than 100 V.

In Example 18, the subject matter of Examples 14-17 includes, wherein the power control circuit to is to dynamically adjust supply power to the RF driver circuit over a range of less than 10 V to greater than 200 V.

In Example 19, the subject matter of Examples 14-18 includes, the antenna, wherein the antenna has a quality factor Q of at least 100.

Example 20 is a radio frequency (RF) receiver circuit for receiving a transmitted signal, the RF receiver circuit comprising: a receive signal input; demodulator and amplification circuitry coupled to the receive signal input, the demodulator and amplification circuitry to extract a baseband signal from the transmitted signal, the baseband signal including a first baseband frequency component and a second baseband frequency component that is different from the first baseband frequency component; a multi-path signal-recovery circuitry arrangement having an input coupled to the demodulator and amplification circuitry to receive the baseband signal, and comprising a first receive path and a second receive path parallel to the first receive path, with each receive path to independently carry the baseband signal, wherein the first receive path includes, a first signal conditioning arrangement and the second receive path includes a second signal conditioning arrangement; wherein the first signal conditioning arrangement includes a first bandpass filtering tuned to the first baseband frequency component, and first controllable-gain amplification and first controllable-delay circuitry; wherein the second signal conditioning arrangement includes a second bandpass filter tuned to the second baseband frequency component; and a control loop to independently adjust at least the first controllable-gain amplification and controllable delay circuitry to increase temporal and amplitude alignment of the baseband signal between the first and the second receive paths; and a mixer circuit coupled to the first receive path and the second receive path, the mixer circuit to combine respective outputs from the first and the second receive paths to produce a corrected recovered baseband signal.

In Example 21, the subject matter of Example 20 includes, an antenna coupled to the receive signal input, wherein the antenna has a quality factor Q of at least 100.

In Example 22, the subject matter of Examples 20-21 includes, wherein the control loop includes a ratio detector to compare temporal alignment of the baseband signal in the first and the second receive paths, and to produce error signaling representing an extent of a temporal misalignment between the baseband signal in the first and the second receive paths.

In Example 23, the subject matter of Example 22 includes, wherein the control loop includes a controller to generate compensation signaling for the first controllable-delay circuitry based on the error signaling.

In Example 24, the subject matter of Examples 20-23 includes, wherein the second signal conditioning arrangement further includes a second controllable-gain amplification and second controllable-delay circuitry that are independently controllable from the first controllable-gain amplification and first controllable-delay circuitry.

In Example 25, the subject matter of Examples 20-24 includes, wherein the multi-path signal-recovery circuitry arrangement includes a first low-pass filter in the first receive path that outputs to the first signal conditioning arrangement, and a second low-pass filter in the second receive path that outputs to the second signal conditioning arrangement.

In Example 26, the subject matter of Examples 20-25 includes, wherein the demodulator and amplification circuitry provides an adjustable amplification gain, and wherein the RF receiver circuit further comprises an automatic gain controller to cause the demodulator and amplification circuitry to vary the adjustable amplification gain to achieve a target signal amplitude of the recovered baseband signal.

In Example 27, the subject matter of Examples 20-26 includes, wherein the RF receiver circuit is part of a radio-frequency identification (RFID) reader device, and wherein the transmitted signal is transmitted by a RFID tag.

In Example 28, the subject matter of Examples 20-27 includes, a processor circuit configured to measure a characteristic of an incoming signal; a signal interface coupled to the processor circuit and configured to facilitate the measurement of the characteristic of the incoming signal by the processor circuit; sense signal conditioning circuitry having a signal input, a signal output, and a gain control input, wherein the signal input is coupled to the receive signal input, the signal output is coupled to the signal interface, and the gain control input is coupled to an output of the processor circuit; the sense signal conditioning circuitry including a variable-gain amplification subcircuit configured to amplify the incoming signal at the signal input by an adjustable gain amount in response to a gain control signal at the gain control input; and wherein the processor circuit is further configured to produce the gain control signal.

In Example 29, the subject matter of Example 28 includes, wherein the characteristic of the incoming signal is signal amplitude.

In Example 30, the subject matter of Examples 28-29 includes, wherein the signal input is configured to receive a RF signal.

In Example 31, the subject matter of Examples 28-30 includes, wherein the signal input is configured to receive the transmitted signal.

In Example 32, the subject matter of Examples 28-31 includes, wherein the variable-gain amplification subcircuit is electrically configurable to a selectable gain from among a set of discrete gain settings.

In Example 33, the subject matter of Examples 28-32 includes, wherein the variable-gain amplification subcircuit includes a set of switchably-selectable impedance elements, and wherein the gain control signal selects the impedance elements.

In Example 34, the subject matter of Example 33 includes, wherein the set of switchably-selectable impedance elements are in a feedback loop of an amplifier circuit.

In Example 35, the subject matter of Examples 28-34 includes, wherein the signal interface is constructed to accept a range of amplitudes up to a maximum input limit, and wherein the processor circuit is configured to generate the gain control signal to cause the variable-gain amplification subcircuit to amplify the incoming signal to an amplitude that is between the maximum limit and one-half of the maximum limit.

In Example 36, the subject matter of Examples 28-35 includes, wherein the incoming signal is transmitted by a signal emitter, and wherein the processor circuit is configured to estimate a distance to the signal emitter based on the characteristic of the incoming signal.

Example 37 is a radio frequency (RF) receiver circuit for receiving a transmitted signal, the RF receiver circuit comprising: a receive signal input; demodulator and amplification circuitry coupled to the receive signal input, the demodulator and amplification circuitry to extract a baseband signal from the transmitted signal, the baseband signal including a first baseband frequency component and a second baseband frequency component that is different from the first baseband frequency component; a multi-path signal-recovery circuitry arrangement having an input coupled to the demodulator and amplification circuitry to receive the baseband signal, and comprising a first receive path and a second receive path parallel to the first receive path, with each receive path to independently carry the baseband signal, wherein the first receive path includes, a first signal conditioning arrangement and the second receive path includes a second signal conditioning arrangement; a processor circuit configured to measure a characteristic of an incoming signal; a signal interface coupled to the processor circuit and configured to facilitate the measurement of the characteristic of the incoming signal by the processor circuit; sense signal conditioning circuitry having a signal input, a signal output, and a gain control input, wherein the signal input is coupled to the receive signal input, the signal output is coupled to the signal interface, and the gain control input is coupled to an output of the processor circuit; the sense signal conditioning circuitry including a variable-gain amplification subcircuit configured to amplify the incoming signal at the signal input by an adjustable gain amount in response to a gain control signal at the gain control input; and wherein the processor circuit is further configured to produce the gain control signal.

In Example 38, the subject matter of Example 37 includes, an antenna coupled to the receive signal input, wherein the antenna has a quality factor Q of at least 100.

In Example 39, the subject matter of Examples 37-38 includes, wherein the characteristic of the incoming signal is signal amplitude.

In Example 40, the subject matter of Examples 37-39 includes, wherein the signal input is configured to receive a RF signal.

In Example 41, the subject matter of Examples 37-40 includes, wherein the signal input is configured to receive the transmitted signal.

In Example 42, the subject matter of Examples 37-41 includes, wherein the variable-gain amplification subcircuit is electrically configurable to a selectable gain from among a set of discrete gain settings.

In Example 43, the subject matter of Examples 37-42 includes, wherein the variable-gain amplification subcircuit includes a set of switchably-selectable impedance elements, and wherein the gain control signal selects the impedance elements.

In Example 44, the subject matter of Example 43 includes, wherein the set of switchably-selectable impedance elements are in a feedback loop of an amplifier circuit.

In Example 45, the subject matter of Examples 37-44 includes, wherein the signal interface is constructed to accept a range of amplitudes up to a maximum input limit, and wherein the processor circuit is configured to generate the gain control signal to cause the variable-gain amplification subcircuit to amplify the incoming signal to an amplitude that is between the maximum limit and one-half of the maximum limit.

In Example 46, the subject matter of Examples 37-45 includes, wherein the incoming signal is transmitted by a signal emitter, and wherein the processor circuit is configured to estimate a distance to the signal emitter based on the characteristic of the incoming signal.

Example 47 is at least one machine-readable medium including instructions that, when executed by processing circuitry, cause the processing circuitry to perform operations to implement of any of Examples 1-46.

Example 48 is an apparatus comprising means to implement of any of Examples 1-46.

Example 49 is a system to implement of any of Examples 1-46.

Example 50 is a method to implement of any of Examples 1-46.

The above detailed description includes references to the accompanying drawings, which form a part of the detailed description. The drawings show, by way of illustration, specific embodiments that may be practiced. These embodiments are also referred to herein as “examples.” Such examples may include elements in addition to those shown or described. However, also contemplated are examples that include the elements shown or described. Moreover, also contemplated are examples using any combination or permutation of those elements shown or described (or one or more aspects thereof), either with respect to a particular example (or one or more aspects thereof), or with respect to other examples (or one or more aspects thereof) shown or described herein.

Publications, patents, and patent documents referred to in this document are incorporated by reference herein in their entirety, as though individually incorporated by reference. In the event of inconsistent usages between this document and those documents so incorporated by reference, the usage in the incorporated reference(s) are supplementary to that of this document; for irreconcilable inconsistencies, the usage in this document controls.

In this document, the terms “a” or “an” are used, as is common in patent documents, to include one or more than one, independent of any other instances or usages of “at least one” or “one or more.” In this document, the term “or” is used to refer to a nonexclusive or, such that “A or B” includes “A but not B,” “B but not A,” and “A and B,” unless otherwise indicated. In the appended claims, the terms “including” and “in which” are used as the plain-English equivalents of the respective terms “comprising” and “wherein.” Also, in the following claims, the terms “including” and “comprising” are open-ended, that is, a system, device, article, or process that includes elements in addition to those listed after such a term in a claim are still deemed to fall within the scope of that claim. Moreover, in the following claims, the terms “first,” “second,” and “third,” etc. are used merely as labels, and are not intended to suggest a numerical order for their objects.

The above description is intended to be illustrative, and not restrictive. For example, the above-described examples (or one or more aspects thereof) may be used in combination with others. Other embodiments may be used, such as by one of ordinary skill in the art upon reviewing the above description. The Abstract is to allow the reader to quickly ascertain the nature of the technical disclosure. It is submitted with the understanding that it will not be used to interpret or limit the scope or meaning of the claims. Also, in the above Detailed Description, various features may be grouped together to streamline the disclosure. However, the claims may not set forth every feature disclosed herein as embodiments may feature a subset of said features. Further, embodiments may include fewer features than those disclosed in a particular example. Thus, the following claims are hereby incorporated into the Detailed Description, with a claim standing on its own as a separate embodiment. The scope of the embodiments disclosed herein is to be determined with reference to the appended claims, along with the full scope of equivalents to which such claims are entitled.