Adaptive signal receiving device of antenna

Adaptive antenna receiving device

<p>101-1,101-2,101-N. . . antenna</p><p>102-1,102-2,102-N. . . Band pass filter (BPF)</p><p>103. . . Beam forming part</p><p>104-1,104-2,104-H. . . Reverse expansion</p><p>104. . . Transmission detection department</p><p>105b. . . Transmission detection department</p><p>105c. . . Transmission detection department</p><p>106-1,106-2,106-L. . . Adaptive beam forming part</p><p>106a-1,106a-2,...,106a-L. . . Adaptive beam forming part</p><p>106b-1, 106b-2,..., 106b-L. . . Adaptive beam forming part</p><p>106d-1, 106d-2,..., 106d-L. . . Adaptive beam forming part</p><p>107. . . Addition part</p><p>108. . . Data Judgment Department</p><p>121-1,121-2,121-H,124-l,124-2,124-H. . . Complex multiplier</p><p>122. . . . Retarder</p><p>123. . . Waiting State Control Department</p><p>123b. . . Waiting state control unit</p><p>125. . . Adder</p><p>126. . . Transmission path estimation section</p><p>127. . . Complex conjugate value calculation section</p><p>128. . . Complex multiplier</p><p>129. . . Interference amount estimation department</p><p>130. . . Normalization Department</p><p>141. . . Addition part</p><p>151-1,151-M. . . Adaptive beam forming group</p><p>151d-1,151dM. . . Adaptive beam forming group</p><p>201-1,201-2,201-N. . . antenna</p><p>202-1,202-2,202-N. . . Band pass filter (BPF)</p><p>203-1,203-2,203-N. . . Reverse expansion</p><p>204. . . Transmission detection department</p><p>205-1,205-2,205-N. . . Beam forming part</p><p>206. . . Addition part</p><p>207. . . Data Judgment Department</p><p>221-1, 221-2, 221-N. . . Complex multiplier</p><p>222. . . Retarder</p><p>223. . . Waiting State Control Department</p><p>224. . . Addition part</p><p>225. . . Complex multiplier</p><p>226. . . Complex conjugate value calculation section</p><p>227. . . Complex multiplier</p><p>228. . . Subtractor</p><p>229. . . Transmission path estimation section</p><p>300. . . Transmission path estimation section</p><p>301. . . Average power value calculation unit</p><p>302. . . Threshold value calculation unit</p><p>303. . . Judgment Department</p><p>304. . . Transfer selection</p><p>401-1,401-2,401-H. . . Beam transmission detection unit</p><p>401b-1,401b-2,. . . ,401b-H. . . Transfer selection</p><p>402. . . Transfer selection</p><p>403. . . Transmission path estimation section</p><p>404. . . Average power calculation unit</p><p>405. . . Threshold value calculation unit</p><p>406. . . Judgment Department</p><p>407. . . Beam selection part</p>

Figure 1 shows the structure of the first embodiment of the adaptive antenna receiving device of the present invention;

Figure 2 shows the structure of the transmission detection unit;

Figure 3 shows the shape of H fixed beams generated by the beam forming part;

Figure 4 shows the structure of the second implementation mode of the adaptive antenna receiving device of the present invention;

Figure 5 shows the structure of the third embodiment of the adaptive antenna receiving device of the present invention;

Figure 6 shows the structure of the transmission detection unit;

Figure 7 shows the structure of the fourth embodiment of the adaptive antenna receiving device of the present invention;

Figure 8 shows the structure of the fifth embodiment of the adaptive antenna receiving device of the present invention;

Figure 9 shows the structure of the conventional receiving device;

Figure 10 shows the structure of the conventional transmission detection unit;

Figure 11 shows the format of the sending time slot; and

Figure 12 shows an example of the impulse response of the frequency selective attenuation transmission path.

[Technical Field to which the Invention belongs]

The present invention relates to an adaptive antenna receiving device of a mobile communication system, which adopts the symbol division multiple connection (CDMA) mode of spread spectrum modulation method. The present invention particularly relates to an adaptive antenna receiving device, even if the surrounding buildings The reflection, refraction, and scattering of electric waves caused by terrain cause multiple waves to interfere with each other on the frequency-selective attenuation transmission path, and the present invention is also compatible with the frequency-selective attenuation transmission path.

[Prior Art]

The following describes the conventional receiving device. The literature "DS-CDMA adaptive array antenna diversified indoor transmission experimental characteristics" Information Technology Report of the Society of Electronic Information and Communications RCS98-94 p.33-38 September 1998" and "Continuous Rake reception in broadband DS-CDMA" The characteristics of the indoor experiment, the information technology bulletin CS99-129 p.57-62 of the Society of Electronics, Information and Communication Technology, October 1999, records the conventional receiving device.

Figure 9 shows the structure of the above-mentioned conventional receiving device. In Figure 9, 201-1, 201-2, and 201-N are N antennas, 202-1, 202-2, and 202-N are bandpass filters (BPF), and 203-1, 203-2, and 203-N are reverse expansion parts, and 204 For the transmission detection part, 205-1, 205-2, and 205-N are the beam forming parts, which receive the reverse unfolded signal affected by the multiple waves, and form a beam for each of the L transmissions. 206 is the addition part, and 207 is the Data Judgment Department.

In addition, in each of the above beam forming parts, 221-1, 221-2, and 221-N are complex multipliers, 222 is a delay, 223 is a waiting state control part, 224 is an adder, 225 is a complex multiplier, and 226 is a complex conjugate. In the value calculation unit, 227 is a complex multiplier, 228 is a subtractor, and 229 is a transmission path estimation unit that estimates the transmission path for each transmission.

In addition, FIG. 10 shows the structure of the transmission detection unit 204 described above. In Figure 10, 300 is the transmission path estimation unit, 301 is the average power value calculation unit, 302 is the threshold value calculation unit, 303 is the judgment unit, and 304 is the transmission selection unit, which detects from the signal after reverse expansion. Multiple passes out.

In addition, Figure 11 shows the format of the sending time slot. The sending time slot is composed of the navigation symbol part (known series) and the data part. In addition, Figure 12 shows an example of the impulse response of the frequency selective attenuation transmission path. In the mobile communication system, the waves (multiple waves) passing through multiple transmission paths will interfere with each other due to the reflection, refraction, and scattering of radio waves caused by surrounding buildings and terrain. This shows the situation where a signal composed of multiple waves is input to the receiving antenna.

Here, FIG. 9 and FIG. 10 are used to explain the operation of the above-mentioned conventional receiving device. The signals from the mobile stations receiving signals on the N antennas 201-1~N pass through the BPF202-1~N and are limited to a predetermined frequency band. On the reverse expansion parts 203-1~N of the signal after receiving the band limitation, the same series as the expansion symbol series used by the transmitting end is used to perform reverse expansion.

On the transmission detection unit 204, one antenna output is used, and L transmissions are selected from the reversely expanded signals affected by the multiple waves. Specifically, in the transmission detection unit 204, the transmission path estimation unit 300 first uses the serial symbols set in each time slot to perform equal addition to all symbols in one time slot to obtain the instantaneous transmission path estimation value. . Next, the average power value calculation unit 301 uses the estimated value of the transmission path to perform power averaging between several time slots to calculate the average power delay profile. Next, the threshold calculation unit 302 regards the transmitted power with the smallest power in the average power delay profile as noise, and then sets the power with a larger ΔdB as the threshold for transmission selection based on this minimum transmitted power . Secondly, the judging unit 303 compares the average power delay profile with the threshold value, treats the transfer with an average power value greater than the threshold value as a multiple transfer of the required signal, and outputs the location information and transfer power value of the transfer over time. .

In addition, on each beam forming part, due to H/W or S/W conventions, generally L transmissions set in advance are signal processed. Therefore, in the transfer detection unit 204, the transfer selection unit 304 will finally select L effective transfers in sequence from the party with the larger average power value transferred. Then, the selected transfer position that changes with time is regarded as transfer position information, and is input to each beam forming part. In addition, the signal after the reverse expansion is separated at each transmission detected by the transmission detecting part 204 and transmitted to the respective beam forming parts 205-1~L.

On the beam forming parts 205-1~L, a beam is formed for each detected transmission. In addition, here, the beam forming portion 205-1 performs signal processing on the first transmission, and then the beam forming portion 205-2~N performs signal processing on the second to Lth transmissions.

Here, the operation of each of the above-mentioned beam forming parts will be described in detail. The waiting state control unit 223 calculates the waiting state according to an adaptive algorithm such as LMS (Least Mean Square), and multiplies the received signal from each antenna on the complex multipliers 221-1~N. In the complex waiting state used to form the beam. In the adder 224, the complex waiting state synthesizes the received signals of the multiplied antennas, and generates a signal synthesized by the antennas with directivity.

The transmission path estimation unit 229 uses the navigation symbols provided in each time slot (refer to FIG. 11) to calculate the first transmission path estimation (complex value). The complex conjugate value calculation unit 226 calculates the complex conjugate value of the estimated transmission path value. In the complex multiplication 225, the complex conjugate value is multiplied by the synthesized signal output from the adder 224, weighted according to the ratio of the signal amplitude, and the phase variation is removed, and then the signal is output.

At the adder 206 that simultaneously receives the first to Lth transmitted signals, the phase-equalized signal is synthesized for each transmission. Finally, in the data judging unit 207, a rigid judgment is made on the output of the adding unit 206, and the result is output as a demodulation result. In addition, the above-mentioned demodulation result is regarded as a reference signal when forming each transmitted light beam, so it is divided and transmitted to each beam forming part.

Next, using the beam forming unit 205-1 corresponding to the first transmission, a method of determining the waiting state for each antenna will be explained using an adaptive algorithm. First, the complex multiplier 227 multiplies the output of the data judging unit 207 and the output of the transmission path estimation unit 229 to generate a reference signal. Next, at the subtractor 228, the output of the complex multiplier 227 and the output of the adder 224 are subtracted to generate the first transmitted error signal e ₁ (k). Finally, on the waiting state control unit 223, the error signal e is received ₁ (k) According to the normalized LMS of the adaptive algorithm, the waiting state is updated as shown in equation (1).

<maths><img file="TW522673B_D0001.tif" /></maths>

Among them, ||. || represents the standard rate value, k represents the k-th sampling time (t=kT _S :T _S Is the sampling period), * represents the complex conjugate value. Furthermore, X ₁ (k) is the first vector representation of the reverse spread signal received on each antenna, X ₁ (k)=[X ₁ (1,k),X ₁ (2,k),...,X ₁ (N,k) ^T ,W ₁ (k) is the first vector representation of the waiting state transmitted to each antenna, W ₁ (k)=[W ₁ (1,k),W ₁ (2,k),...,W ₁ (N,k) ^T . In addition, W ₁ (k) the initial value W ₁ (0)=[1,0,...,0], μ is the step size, and τ is the delay time required for the previous series of processing input to the waiting state control unit 23.

As described above, on the conventional receiving device, in the above-mentioned frequency selective attenuation transmission path, an adaptive algorithm is used for the detected L transmissions to form light beams respectively, and weighted synthesis is performed according to the estimated value of the transmission path ( RAKE synthesis), by which, on the one hand, the interference signal can be brought to zero, and on the other hand, the SIR (signal to interference power ratio) related to the desired signal can be improved.

However, as described above, in the conventional receiving device, in the initial state before the beam is formed on the adaptive array antenna, the moving direction of the multiple transmission from the mobile station to the base station is unknown, so it is generally impossible to form a clear A directional beam, and an antenna with a wide range of directivity is used. Therefore, there is a problem, that is, when performing transmission detection on an antenna, if there is a large amount of interference at the same time, it is difficult to measure the accuracy according to the quality of the transmitted signal.

Furthermore, in the conventional receiving device, in the initial state when the light beam is formed on the adaptive array antenna based on the result of the transmission detection, the basis is the same as the above reason, and an antenna is used to set the initial value of the waiting state. . In this case, it takes a lot of time to process the light beam according to the adaptive algorithm. Therefore, when the transmitting end of the mobile station performs signal processing before the base station finishes forming the light beam, in order to meet the quality required by the receiving end of the base station , Requires a lot of signal power. Therefore, there is a problem, that is, at the receiving end of the base station, the instantaneous interference power increases, and it is difficult to obtain the ideal channel capacity.

In addition, on the conventional receiving device, even if the detected transmission is a transmission with a small receiving power, it needs to operate an adaptive algorithm for each transmission. Therefore, there is a problem, that is, in adaptability. The increase in the time before the end of the algorithm'before the end' cannot sufficiently suppress the interference power.

Therefore, the present invention provides an adaptive antenna receiving device that can further reduce the specifications of hardware and software in order to detect the accurate transmission corresponding to the quality of the signal transmitted from prison and improve the receiving quality.

[Summary of Invention]

In order to solve the above problems and achieve the objective, the adaptive antenna receiving device of the present invention is characterized by comprising: a beam forming device (equivalent to the beam forming part 103 in the embodiment described later), which uses a plurality of antennas to form a fixed direction The light beam; the reverse spreading device (equivalent to the reverse spreading part 104-1~H), which respectively performs reverse spreading processing on the plural beam signals corresponding to the above-mentioned fixed directional beam; transmission detection device (equivalent to In the transmission detection section 105), it detects multiple waves on the transmission path based on the plural reversely expanded signals obtained respectively, and outputs the transmission position information as the detection result; transmission path estimation device (equivalent to transmission path estimation Section 126), which estimates the transmission path of the adaptive beam synthesis signal for each transmission based on the above-mentioned transmission position information; a complex multiplication device (equivalent to the complex multiplier 121-1~H), which performs the inverse expansion of the above-mentioned complex signals Multiply each of the above-mentioned transmission path estimation results; the adaptive beam forming device (equivalent to the retarder 122, the waiting state control unit 123, the complex multiplier 124-1~H, and the adder 125), which uses all the transmitted A plurality of complex number multiplication results and data determination results are used to operate an adaptive algorithm for each transfer, thereby generating a waiting state for each transfer, using the waiting state and the above-mentioned plural backward expansion signals to form an adaptability for each transfer Beam synthesis signal; phase equalization device (equivalent to complex multiplier 128), which uses each of the above-mentioned transferred adaptive beam signals to perform phase equalization processing corresponding to the above-mentioned transmission path estimation result; transfer synthesis device (equivalent to the addition unit 107), which synthesizes all the adaptive beam signals whose phases are equalized; and a data judging device (equivalent to the data judging part 108), which judges the data contained in the above-mentioned transmitted and synthesized signal.

The adaptive antenna receiving device of the present invention is characterized by including an interference amount estimation device (equivalent to the interference amount estimation section 129), which is further based on the known series attached to the transmission time slot, from each of the above-mentioned transmissions The adaptive beam synthesis signal estimates the amount of interference; and a normalization device (equivalent to the normalization unit 130), which normalizes the adaptive beam signal after the phase equalization according to the estimated interference amount for each transmission; wherein, The above transmission combining device synthesizes all the adaptive beam signals whose transmission is normalized.

The adaptive antenna receiving device of the present invention is characterized in that it includes: a beam transmission detection device (equivalent to the beam transmission detection part 401-1~H), which uses the signal after the reverse expansion of each beam to obtain the transmission Position and transmission power value; the transmission selection part (equivalent to transmission selection part 402), which starts from the side with the larger transmission power value, sequentially selects a predetermined number of transmissions from the transmissions with different transmission positions, and uses the selection result as the location information The above-mentioned beam delivery detection device further includes: an equal summing device (equivalent to the transmission path estimation unit 403), which uses a known serial pair set in the time slot unit of the signal after the reverse expansion of each of the above-mentioned beams All symbols in one time slot are processed by equal phase addition; the average power delay profile device (equivalent to the average power value calculation unit 404), which uses the above equal phase addition results to calculate the power between several time slots Averaging processing to generate an average power delay profile; a threshold value generating device (equivalent to the threshold value calculation unit 405), which generates a threshold value for selecting transmission based on the above average power delay profile; and a comparison device ( It corresponds to the determination unit 406), which compares the average power delay profile with the threshold value, and outputs the transfer position and the transfer power value of the transfer exceeding the threshold value.

The adaptive antenna receiving device of the present invention is characterized by comprising: a light beam forming device which uses a plurality of antennas to form a light beam with a fixed directivity; and a reverse expansion device which respectively corresponds to the plurality of light beams with a fixed directivity. The light beam signal is reversely expanded; the transmission detection device (equivalent to the transmission detection section 105b) detects the multiple waves on the transmission path based on the plural reversely expanded signals obtained respectively, and outputs the multiple waves in order to transmit The position information and the predetermined beam selection information required for the operation of the adaptive algorithm are used as the detection result; the transmission path estimation device, which estimates the transmission path of each transmission adaptive beam synthesis signal based on the transmission position information; the complex multiplication device, It multiplies the above-mentioned plural reversely expanded signals by the above-mentioned transmission path estimation result of each transmission; adaptive beam forming device (equivalent to delay 122, waiting state control unit 123b, complex multiplier 124-1~H, The addition unit 125), which uses all the delivered complex multiplication results, data determination results, and the above-mentioned beam selection information to operate an adaptive algorithm to generate a common waiting state for all transfers, and use the common waiting for all transfers The state and the above-mentioned plural inversely expanded signals form an adaptive beam synthesis signal for each transmission; a phase equalization device that uses each of the above-mentioned adaptive beam signals to perform phase equalization processing corresponding to the above-mentioned transmission path estimation result ; The transfer synthesis device, which synthesizes all the adaptive beam signals after the phase is equalized; and the data determination device, which determines the data contained in the above-mentioned transfer synthesis signal.

The adaptive antenna receiving device of the present invention is characterized by comprising: a plurality of adaptive beam forming groups (equivalent to adaptive beam forming groups 151-1~H), the structure of which is a combination of the above-mentioned transmission path estimation device and complex multiplication Device, adaptive beam forming device, phase equalization device, and transfer combining device; and a group combining device (equivalent to the addition unit 141), which further combines the output of the above-mentioned adaptive beam forming group; wherein, the above-mentioned data is determined The device determines the data contained in the signal output by the above-mentioned group synthesis device.

The adaptive antenna receiving device of the present invention is characterized by comprising: a plurality of adaptive beam forming groups (equivalent to adaptive beam forming groups 151d-1~M), the structure of which is a combination of the above-mentioned transmission path estimation device and complex multiplication The device, the adaptive beam forming device, the phase equalization device, the interference amount estimation device that estimates the amount of interference from the adaptive beam synthesis signal transmitted from each of the above-mentioned adaptive beam synthesis signals based on the known series attached to the transmission time slot, and the interference amount estimation device according to the A normalization device that normalizes the adaptive beam signal after the above-mentioned phase equalization is carried out by transmitting the estimated interference amount, and is formed by combining all the transmission and synthesis devices that transmit the normalized adaptive beam signal; and a group combining device; (Corresponding to the adding unit 141), which further synthesizes the output of the adaptive beam forming group; wherein the data determining device determines the data contained in the signal output by the group synthesizing device.

The adaptive antenna receiving device of the present invention is characterized by comprising: a beam transmission detection device, which uses the signal after the reverse expansion of each light beam to obtain the transmission position and the transmission power value; Starting from the party with the greater power value, it selects a predetermined number of transfers from the transfers with different transfer positions in turn, and outputs the selected result as position information; the above-mentioned beam transfer detection device also includes: an equal summing device, which is set in The known series of the time slot unit of the signal after the reverse expansion of each beam mentioned above performs equal addition processing for all symbols in a time slot; the average power delay profile device uses the above equal addition result The power between several time slots is averaged to generate an average power delay profile; a threshold value generating device, which generates a threshold value for selecting transmission based on the above average power delay profile; a comparison device, which Comparing the above average power delay profile with the above threshold value, output the transmission position and the transmission power value of the transmission exceeding the threshold value; The transmitted power value calculates the sum of the transmitted power of all beams, selects the beam with the largest sum, and generates beam selection information as the selection result.

The characteristic of the adaptive antenna receiving device of the present invention is that when the adaptive algorithm is in the initial state, the above-mentioned adaptive beam forming device sets the waiting state for transmitting the detected beam to 1, and sets the waiting state for other beams Set to 0.

[Implementation Type of Invention]

Hereinafter, the implementation mode of the adaptive antenna receiving device of the present invention will be described in detail based on the drawings. In addition, the present invention is not limited to the scope of these embodiments.

Implementation Type One,

Figure 1 shows the structure of the first embodiment of the adaptive antenna receiving device of the present invention. In this embodiment, an adaptive antenna receiving device in a mobile communication system using a symbol division multiple connection (CDMA) method will be explained. In addition, regarding the format of the sending time slot, its structure is as shown in Figure 1 of the previous description.

In Figure 1, 101-1, 101-2, 101-N are N antennas, 102-1, 102-2, 102-N are bandpass filters (BPF), 103 is a beam forming part, which forms a plurality of fixed directional beams, 104 -1,104-2,104-H is the reverse expansion part, 105 is the transmission detection part, 106-1,106-2,106-L is the adaptive beam forming part, which uses an adaptive algorithm on the detected unit to adapt Method to form a light beam.

In addition, in each of the above-mentioned adaptive beam forming units, 121-1, 121-2, 121-H, 124-1, 124-2, 124-H are complex multipliers, 125 is an adder, and 126 is a transmission path estimation unit, which estimates the individual transmission In the transmission path, 127 is a complex conjugate value calculation unit, 128 is a complex multiplier, 122 is a delay, and 123 is a waiting state control unit.

Figure 2 shows the structure of the above-mentioned transfer detection unit 105. In Figure 2, 401-1, 401-2, and 401-H are the beam transmission detection parts, which are located in the 1, 2, and H beams, and 402 is the transmission selection part, which is selected from the output of each beam transmission detection part For the largest L transfers, the transfer detection unit 105 detects and transfers the reverse unfolding signals from the 1st to H fixed beams. In addition, in the above-mentioned beam propagation detection unit, 403 is a transmission path estimation unit, 404 is an average power calculation unit, 405 is a threshold value calculation unit, and 406 is a determination unit. In addition, the structure of each beam transmission detection unit is the same. Here, the structure of the beam transmission detection unit 401-1 is taken as an example for description.

The following figures are used to illustrate the operation of the adaptive antenna receiving device of this embodiment. First, the mobile station receives signals from the N antennas 101-1~N, and the signals from the mobile station pass through the BPF 102-1~N to limit the required frequency bands.

On the beam forming part 103, the band-limited signal is received to form H fixed beams. FIG. 3 shows the H fixed beam patterns generated by the beam forming part 103. As shown in FIG. On the reverse spreading part 104-1~N, according to the incident angle from the mobile station, the signal received on the H beams is the same as the spreading symbol series (PN series) used by the transmitting end The sequence is reversed.

On the transmission detection unit 105, the reverse-expanded signal that is affected by the multiple waves is used to detect transmission, starting from the one with the larger transmission power, and sequentially selecting the largest L transmissions with different transmission positions over time. Specifically, first, on the beam propagation detection unit 401-1, the propagation path estimation unit 403 uses the navigation symbols set in the time slot of the reverse spread signal of each beam #1 to compare all the Symbols are added together. Through this averaging process, the estimated value of the transmission path with reduced noise influence is obtained. Next, the average power calculation unit 404 uses the transmission path estimation value output by the transmission path estimation unit 403 to perform power averaging processing between several time slots, and calculates the average power delay profile within a preset time. Next, the threshold calculation unit 405 regards the transmitted power with the smallest power in the average power delay profile as noise and interference power, and uses any ΔdB greater than the transmitted power as the threshold for selecting the transmission. Finally, the judging unit 406 compares the output of the average power calculation unit 404 with the output of the threshold value calculation unit 405, and outputs the transfer position information indicating the instantaneous position of the transfer exceeding the threshold value and the transferred average power value. In addition, the second to H-th beam transmission detection units also perform the same signal processing as the first beam transmission detection unit 401-1.

In addition, in the transfer selection part 402, from the transfers with different transfer positions detected in the 1st to H beams, the largest L transfers are sequentially selected from the one with the largest transfer power value. Then, on the transmission selection part 402, the selected transmission space/time transmission position is regarded as the transmission position information, and is output to the adaptive beam forming part 106-1.

Here, taking the adaptive beam forming part 106-1 corresponding to the first transmission as an example, the operation of each adaptive beam forming part will be described. In addition, regarding the adaptive beam forming part corresponding to the 2nd to Lth transmission, since its structure is the same as that of the adaptive beam forming part 106-1 corresponding to the 1st transmission, the description is abbreviate|omitted.

On the adaptive beam forming part 106-1, according to the first transfer position information output from the transfer detection part 105, the first transferred reverse unfolding signal X is received from the reverse unfolding signals of the H beams _i (1,k),X _i (2,k),...,X _i (H,k) (where i represents the processing of the i-th transfer, where i=1).

On the complex multipliers 124-1~H, the first transmitted reverse expansion signal and the waiting state W of the complex value calculated by the waiting state control unit 123 _i (1,k),W _i (2,k),...,W _i (H,k) multiply complex numbers (where i represents the processing of the i-th pass, where i=1). In the addition unit 125, the output of the complex multipliers 124-1~H is added, and the result of this addition is the beam signal with directivity (adaptive beam synthesis signal).

The transmission path estimation unit 126 uses the navigation symbols provided in each time slot shown in FIG. 11 to calculate the transmission path estimation value (complex value) for the first transmission. In addition, the complex conjugate value calculation unit 127 calculates the complex conjugate value of the estimated value of the transmission path. Then, the complex multiplier 128 multiplies the output of the complex conjugate value calculation unit 127 and the output of the adder 125 to output a signal whose phase variation is weighted and removed in proportion to the signal amplitude.

Then, the adder 107 receives the signal output corresponding to the first pass and the signal output corresponding to the second to Lth passes that are output by the same processing, and synthesizes the adaptation of phase equalization for each pass. Sexual beam synthesis signal. In the data judging unit 108, a rigid judgment is made on the output of the adding unit 107, and the result is output as a demodulation result. In addition, the demodulation result of the data is distributed to each transmission unit, and is transmitted to the adaptive beam forming unit 106-1 to L corresponding to each transmission.

In addition, the output of the complex conjugate value calculation unit 127 is sent to the complex multipliers 121-1~H, and the complex multipliers 121-1~H are used to reversely expand the signals from the first to the H-th beams. The output of the complex conjugate value calculation unit 127 is complex multiplied to calculate the inversely expanded signal yi(1,k),yi(2,k ),...,Y _i (H,k) (where i represents the processing of the i-th transfer, where i=1). On the delayer 122, the output of each complex multiplier 121-1~H is input to the processing delay time τ minutes (τ is The amount of delay in discrete symbol units) to delay.

Next, regarding the adaptive algorithm used to form the adaptive light beam, taking the case of using SMI (Sample Matrix Inversion) as an example, the operation of the waiting state control unit 123, that is, the method of determining the waiting state for each light beam, will be described. In the waiting state control unit 123, the inverse spread signal y of the first to H-th beams corresponding to the first transmission whose delay amount has been adjusted is received from the delay unit 122 ₁ (1,k-τ),y ₁ (2,k-τ),...,y ₁ (H,k-τ) (where k represents the symbol number that displays the discrete time, and τ represents the processing delay). In addition, the reference signal d(kτ), which is a demodulation result, is received from the data determination unit 108 (where this is a complex conjugate value, k represents the symbol number showing the discrete time, and τ represents the processing delay amount).

In addition, when the output signal of the delayer 122 is represented by a vector, the signal vector for the first transmission is Y ₁ (k-τ)=[y ₁ (1,k-τ),y ₁ (2,k-τ),...,y ₁ (H,k-τ)] ^T Similarly, the waiting state vector output by the waiting state control unit 123 for the first transfer is W ₁ (k-τ)=FW ₁ (1,k-τ),W ₁ (2,k-τ),...,W ₁ (H,k-τ)] ^T 。

Therefore, the first transmitted wait state vector W ₁ (k) can be represented by formula (2).

W ₁ (k)=R _Y1Y1 (k-τ) ^-1 r _Y1d (k-τ) (2) where R _Y1Y1 (k) represents the input vector Y ₁ (k) the correlation array, r _Y1d (k) represents the correlation vector.

In addition, when k-τ&lt;1, or when the frame cannot be continuously transmitted in the form of packet transmission, regarding the wait state vector W ₁ In the initial state of (k), the transmission detection unit 105 will set the waiting state of the detected light beams from the 1st to H light beams to 1 according to the output transmission space position feedback (transmission detection information), and other Is set to 0 to form a beam. For example, when the position signal detected by the first beam is obtained for the first transmission, the responsive beam forming part 106-1 corresponding to the first transmission takes its waiting state for the first transmission Vector, set W ₁ (k)=[1,0,...,0] ^T 。

In addition, the above-mentioned correlation array R _Y1Y1 (k) can be expressed by formula (3). Among them, * represents the complex conjugate value.

<maths><img file="TW522673B_D0002.tif" /></maths>

in, ^H Is a symbol representing the inversion of the complex conjugate.

In addition, for the first passed correlation vector r _y1d (k-τ) can be represented by equation (4).

Secondly, use the first transmitted wait state vector w obtained by the above formula (2) ₁ (k), forming a beam of adaptive algorithm. Here, in order to associate the relevant array R _Y1Y1 The inverse array operation of (k) is simplified and also includes the correlation vector r _Y1d (k) Perform regression calculation processing according to the algorithm shown below. Correlation vector r _Y1d (k) can be calculated by equation (5).

r _Y1d (1)=Y ₁ (1)d*(1)r _Y1d (k)=βr _Y1d (k-1)+(1-β)Y ₁ (k)d*(k)k=2,3......(5) Among them, β is a real number parameter that satisfies 0&lt;β&lt;1 and controls the estimated time constant.

In addition, the correlation array R _Y1Y1 (k) can be calculated by equation (6).

<maths><img file="TW522673B_D0003.tif" /></maths>

Therefore, according to the above equations (5) and (6), R _Y1Y1^-1 (k-τ), r _Y1d After (k-τ), substituting the calculation result into equation (2), the waiting state vector W for the first transfer can be calculated ₁ (k).

In addition, in this embodiment, it has been explained that the SMI adaptive algorithm is used to determine the waiting state for forming the beam. However, the present invention does not necessarily have to use SMI. For example, RLS and LMS can also be used. The adaptive algorithm of knowledge.

In this way, the structure in this embodiment is that during error detection and transmission, a plurality of beams with preset directivity are used to cover the serviceable area, and the transmission is detected on a fixed directivity beam unit. In this way, when the amount of interference in the service area is large, the interference power of the fixed directional beam unit can also be suppressed, and the transmission detection can be carried out with good accuracy.

In addition, this embodiment has a structure that uses adaptive beam synthesis signals whose phases are equalized on each transmission, and uses an adaptive algorithm to form an adaptive beam on each transmission unit. In this way, on the one hand, the attenuation variation and the influence of interference in the service area can be reduced, and the communication quality can be improved on the other hand.

In addition, the structure in this embodiment is that in the initial state of the waiting state or when continuous transmission in the form of packet transmission is not possible, if the adaptive algorithm of the adaptive antenna is also in the initial state at this time, in the fixed direction The detected transmission on the sexual beam unit will be weighted according to the water rate of the signal before being combined. In this way, not only can the time before the end of the beam formation and the adaptive algorithm be shortened, but also the influence of interference in the service area can be further reduced, and the communication quality can be improved.

Implementation type two.

In this embodiment, in addition to the structure of the first embodiment, an interference amount estimation unit and a normalization unit that normalizes the interference amount calculated by the interference amount estimation unit are added. Here, for the sake of brief description, only a different operation from the implementation type is described.

Figure 4 shows the structure of the second embodiment of the adaptive antenna receiving device of the present invention. Here, the operations of the interference amount estimation unit and the normalization unit are explained. In addition, the format of the sending time slot is the same as that of the implementation type, and the structure in Figure 11 is used. In addition, for the same structure as the above-mentioned embodiment, the same symbols are used here, and the description thereof is omitted.

In Figure 4, 106a-1, 106a-2,..., 106a-L are the generalized beam forming parts, which are formed in a generalized manner by using a response algorithm on the detected transmission unit Light beam, 129 is the interference amount estimation unit, and 130 is the normalization unit.

The following is a brief description, and only the operation of the beam forming part 106a-1 of the reactive beam forming part corresponding to the first transmission will be explained. In the interference amount estimation unit 129, in order to obtain the output Z ₁ (K _s ,j) Calculate the amount of interference (where K _s Is the time slot, j is the Kth _s The j-th navigation symbol in a time slot), the R-th _S Navigation symbol P in two time slots _s (K _s ,j) add all the symbols and so on (where, |P _s (K _S ,j)|=1), calculate the (K)th in the first transmission _s Estimated value of transmission path for each time slot η ₁ (K _s ) (Where η ₁ (K _s ) Is plural). In other words, the interference amount estimation unit 129 uses the transmission path estimation value η ₁ (K _s ) And the composite signal Z of the first transmitted correspondence beam ₁ (K _s , J), as shown in equation (7), the Kth corresponding to the first transmitted response beam synthesis signal can be calculated _s The amount of interference in each time slot σ ₁² (K _s )。

<maths><img file="TW522673B_D0004.tif" /></maths>

Where P _s *(K _s ,j) is P _s (K _S ,j) is the complex conjugate value, P represents the number of navigation symbols in 1 time slot.

In addition, the interference amount estimation unit 129 calculates the obtained interference amount σ according to equation (8) ₁² (K _s ) Through the averaging of a plurality of time slots, calculate the Rth in the first transmitted adaptive beam synthesis signal _s Estimated value of interference for each time slot I ₁ (k).

<maths><img file="TW522673B_D0005.tif" /></maths>

Among them, S represents the number of time slots used for averaging.

Then, in the normalizing unit 130 that receives the output of the interference amount estimation unit 129 and the output of the complex multiplier 128, the output of the complex multiplier 128 is divided by the output of the interference amount estimation unit 129 to form a normalized interference amount. The first transmitted correspondence beam synthesis signal.

In this way, the structure in this embodiment is that when the position of the mobile station shifts instantaneously or mobile stations with different signal power levels due to different transmission speeds exist, they cannot be regarded as the same adaptive array. When the interference power of the beam unit formed by the antenna, the repellent beam combining signal of the transmission unit is weighted according to the interference amount, and then combined. In this way, the same effect as the above-mentioned embodiment can be obtained, and the receiving SIR can be maximized, so an ideal channel capacity can be obtained.

Implementation type three,

In this embodiment, the input signal to the waiting state control unit is composed of a plurality of fixed directional light beams, and the waiting state generated by the waiting state control unit is commonly used for all transmissions. In other words, there is one waiting state control unit of the base station receiver corresponding to one mobile station. Here, only a different operation from the implementation type is explained.

Figure 5 shows the structure of the third embodiment of the adaptive antenna receiving device of the present invention. In addition, the format of the sending time slot is the same as that of the implementation type, and the structure in Figure 11 is used. In addition, for the same structure as the above-mentioned embodiment, the same symbols are used here, and the description thereof is omitted.

In Figure 5, 105b is the transmission detection unit, 106b-1, 106b-2,..., 106b-L is the adaptive beam forming unit, which uses an adaptive algorithm on the detected transmission unit to adapt The light beam is formed by the method, and 123b is the waiting state control unit.

Fig. 6 shows the structure of the above-mentioned transfer detection unit 105b. In Figure 6, 401b-1, 401b-2,...,401b-H are the beam transmission detection parts where the 1, 2, ..., H beams are located, 402 is the transmission selection part, and 407 is the beam selection part. Select the beam with the best reception state from the plurality of fixed beams. On the transmission detection section 105b, the signal is detected and transmitted from the 1~H fixed beams in the reverse direction, and the beam with the better reception state is selected .

The following figures are used to describe in detail the operation of the adaptive antenna receiving device of this embodiment. In addition, only a different operation from the above-mentioned implementation mode is described here. In the transmission detection part 105b of this embodiment, in addition to the operation of the first embodiment, the beam selection part 407 uses the transmission position (time), the transmission position (space) and the information related to the transmission power value to calculate each The sum of the transmitted power of the light beams selects the light beam with the largest sum of transmitted powers, and then outputs the result of the light beam selection to the waiting state control unit 123b.

Next, the operations of the adaptive beam forming unit 106b-1 and the waiting state control unit 123b corresponding to the first transmission will be described. In addition, regarding the adaptive beam forming part corresponding to the 2nd to Lth transmission, the structure is the same as that of the adaptive beam forming part 106b-1 corresponding to the 1st transmission, so the description is abbreviate|omitted. Also, love this only shows a different operation from the above implementation type. On the adaptive beam forming part 106b-1, according to the first transmission position information output from the transmission detection part 105b, the first transmitted reverse spread signal X is received from the reverse spread signals of the H beams _i (1,k),x _i (2,k),...,x _i (H,k).

On the complex multipliers 124-1~H, the first transmitted reverse expansion signal and the waiting state control unit 123b calculated by the waiting state control unit 123b common complex value waiting state w(1,k),w(2, k),...,w(H,k) multiply complex numbers. The addition unit 125 performs addition processing on the outputs of the complex multipliers 124-1~H, and the addition result is a beam signal with directivity (adaptive beam synthesis signal).

The transmission path estimation unit 126 uses the navigation symbols provided in the time slot shown in FIG. 11 to calculate the transmission path estimation value (complex value) corresponding to the first transfer. In addition, the complex conjugate value of the estimated value of the transmission path is calculated in the complex conjugate value calculation unit 127. Then, in the complex multiplier 128, the output of the complex conjugate value calculation unit 127 and the output of the addition unit 125 are multiplied, and a signal weighted according to the signal ratio and phase fluctuation removed is output.

Then, at the adder 107, the signal output corresponding to the first pass is received and the signal output corresponding to the second to the Lth pass is output by the same process, and the phase equalized adaptation is synthesized for each pass Sexual beam synthesis signal. In the data judging unit 108, the output of the adding unit 107 is rigidly judged, and the result is output as the demodulation result. In addition, the demodulation result of the data is used as a reference signal and sent to the waiting state control unit 123b.

In addition, the output of the complex conjugate value calculation unit 127 is sent to the complex multipliers 121-1~H, and the first to H-th beams are respectively expanded in the reverse direction on the complex multipliers 121-1~H. The signal is multiplied by the complex number of the output of the complex conjugate value calculation unit 127 to calculate the inversely expanded signal y of the first to H-th beams from which the phase variation component caused by the attenuation is removed _i (1,k),y _i (2,k),. . . ,y _i (H,k) (where i represents the processing for the i-th transfer, where i=1). On the delayer 122, the output of each complex multiplier 121-1~H is input to the processing delay time τ minutes (τ is The amount of delay in discrete symbol units) to delay. In addition, the first to H beam signals received by the waiting state control unit 123b after complex multiplications delayed in each transmission are input with the accuracy of the symbol timing and matched with the delay time.

Next, taking the case of using SMI (Sample Matrix Inversion) in the adaptive algorithm for forming the adaptive beam as an example, the operation of the waiting state control unit 123b, that is, the method of determining the waiting state for each beam, will be described. In the waiting state control unit 123, the inverse spread signal y of the first to H-th beams corresponding to the first transmission whose delay amount has been adjusted is received from the delay unit 122 _l (1,k-τ),y _l (2,k-τ),. . . , Y ₁ (H,k-τ) (where k represents the symbol number showing the discrete time, and τ represents the processing delay). In addition, the reference signal d(k-τ) (wherein, it is a complex conjugate value) is received as a demodulation result from the data determination unit 108.

Here, the signal vector for the first transmission is Y _i (k-τ)=[y _i (1,k-τ),y _i (2,k-τ),. . . , Y _i (H,k-τ)] ^T , The waiting state vector output by the waiting state control unit 123b for all transfers is w(k)=[W(1,k),W(2,k),. . . ,W(H,k)] ^T . Therefore, the first transmitted wait state vector W ₁ (k) can be represented by formula (9).

W(k)=RYY(k-τ) ^-1 T _Yd (k-τ) (9) where R _YY (k) As shown in formula (10), it represents the vector Y of the synthesis of each transfer _i (k) Correlation array of signals.

<maths><img file="TW522673B_D0006.tif" /></maths>

L belt guarantees all transfers. In addition, the above r _Yd (k) As shown in equation (11), it represents the signal vector Y transmitted by Hexian _i (k) The correlation vector of the signal.

<maths><img file="TW522673B_D0007.tif" /></maths>

In addition, when k-τ&lt;1, or when the frame cannot be continuously transmitted in the form of packet transmission, the wait state vector W ₁ In the initial state of (k), the transmission detection unit 105b selects the signal according to the output beam, and sets the waiting state corresponding to the beam with the largest total transmission power from the first to H beams to 1, and the others to 0 , To form a beam. For example, when the beam selection signal with the largest total transmitted power of the first beam is obtained, the waiting state control unit 123b takes the waiting state vector and sets W(k)=[1,0,...,0] ^T 。

It uses the waiting state vector W(k) obtained by the above equation (9) to form the beam of the generality algorithm. Here, in order to associate the relevant array R _YY The inverse array operation of (k) is simplified and also includes the correlation vector r _Yd (k) Perform regression calculation processing according to the algorithm shown below. Correlation vector r _Yd (k) can be calculated by equation (12).

<maths><img file="TW522673B_D0008.tif" /></maths>

Among them, β is a real number parameter that satisfies 0&lt;β&lt;1 and controls the estimated time constant. In addition, the correlation array R _YY (k) can be calculated by equation (13).

<maths><img file="TW522673B_D0009.tif" /></maths>

Therefore, according to the above equations (12) and (13), R _YY^-1 (k-τ), r _Y1d After (k-τ), substituting the calculation result into equation (9), the waiting state vector W(k) can be calculated.

In addition, in this embodiment, it has been explained that the SMI adaptive algorithm is used to determine the waiting state for forming the beam. However, the present invention does not necessarily have to use SMI. For example, RLS and LMS can also be used. The adaptive algorithm of knowledge.

Further, in the present embodiment has a structure in patterns used in each pass through the phase equalized signal beam combiner adaptive signal transmission by all synthesized, and advantage with an adaptive algorithm to generate all the common transmission Waiting state. In this way, at the receiving end of the base station, only one adaptive algorithm corresponding to the fixed directional beam can be provided for one mobile station, thus greatly reducing the hardware and software specifications.

In addition, the structure in this embodiment is that in the initial state of the waiting state or when continuous transmission in the form of packet transmission is not possible, if the adaptive algorithm of the adaptive antenna is also in the initial state, by Select the beam with the largest total transmitted power from the fixed directional beams to run the adaptive algorithm. In this way, not only the time before the end of the adaptive algorithm can be shortened, but also the influence of interference in the service area can be further reduced, and the communication quality can be greatly improved.

Implementation type four,

In this embodiment, in addition to the third embodiment described above, it also deals with the situation where there is a large difference in the direction of arrival in the transmission. Specifically, in this embodiment, the adaptive beam shaping units 106b-1 to L, the waiting state control unit 123b, and the addition unit 107 are combined into a plurality of groups. Here, only the operations that are different from the implementation types are explained.

Figure 7 shows the structure of the fourth embodiment of the adaptive antenna receiving device of the present invention. In addition, the format of the sending time slot is the same as that of the implementation patterns one to three, and the structure in Figure 11 is used. In addition, for the same structure as the third embodiment described above, the same reference numerals are used here, and the description thereof will be omitted.

In Figure 7, 105c is the transmission detection unit, which has the same function as the previously described transmission detection unit 105, 141 is the addition unit, 151-1, 151-M are the adaptive beam forming groups, and the combination is suitable The sexual beam forming units 106b-1 to L, the waiting state control unit 123b, and the addition unit 107 are constituted.

The following figures are used to describe in detail the operation of the adaptive antenna receiving device of this embodiment. In addition, only operations that are different from the above-mentioned three implementation types are described here. For example, the above fixed beams are used to detect the transmission on the transmission selection part 402 in Figure 6, for the transmission of the fixed directional beams that exceed the adjacent fixed directional beams but are spatially different, a plurality of adaptability is set for each transmission. The light beams form groups to form light beams in an adaptive manner.

Then, the output of the adaptive beam forming group is further added in the adding unit 141, and the result of the addition is output to the data judging unit 108. In this way, the structure in this embodiment is that when the transmitted detection positions are effectively different in space, they can be approached in space, and the adaptive beams are appropriately formed on the group unit of the detected transmission. In this way, the same effect as the implementation type three can be obtained, and the adaptive light beam can be formed without increasing the number of waiting state control parts used to execute the adaptive algorithm.

Implementation Type Five

In this embodiment, in addition to the third embodiment described above, it also deals with the situation where there is a large difference in the direction of arrival in the transmission. Specifically, in this embodiment, the adaptive beam shaping units 106d-1 to L, the waiting state control unit 123b, and the addition unit 107 are combined into a plurality of groups. Here, only the operations that are different from the four implementation types are described.

Figure 8 shows the structure of the fifth embodiment of the adaptive antenna receiving device of the present invention. In addition, the format of the sending time slot is the same as that of implementation patterns 1 to 4, using the structure shown in Fig. 11. In addition, for the same structures as the above-mentioned embodiments 1 to 4, the same symbols are used here, and the description thereof is omitted.

In Figure 8, 106d-1, 106d-2,...,106d-L are adaptive beam forming parts, which use adaptive algorithms on the detected transmission units to form beams in an adaptive manner. 151d-1, 151dM are adaptive beam forming groups, which are composed of a combination of adaptive beam forming parts 106d-1 to L, a waiting state control part 123b, and an addition part 107. In addition, the interference amount estimation unit 129 and the normalization unit 130 in the adaptive beam forming units 106d-1~L perform the same operation as the second embodiment described previously, and use the navigation symbols in the time slot to estimate the interference amount.

In this way, the structure in this embodiment can obtain the same effect as the fourth embodiment, and normalize each transmission with the amount of interference, for example, even if the amount of interference on each adaptive beam formed is different. Different, it can also improve the reception SIR.

As explained above, with the present invention, the effect that can be obtained is to use the preset fixed directional beam to operate the adaptive algorithm, thereby reducing the amount of interference of each beam and increasing the SIR, so the adaptive algorithm can be used The method quickly forms an adaptive beam. In addition, the adaptive beam synthesis signal with the phase equalized on each transmission is used, and the adaptive algorithm is used to form an adaptive beam on each transmission unit. In this way, the achievable effect is to reduce the attenuation fluctuation and the influence of interference in the service area on the one hand, and improve the communication quality on the other hand.

With the present invention, when the position of the mobile station is shifted instantaneously or the mobile stations with different signal powers due to different transmission speeds exist, it cannot be regarded as the interference power of the beam unit formed by the same adaptive array antenna. When the adaptive beam synthesis signal of the transmission unit is weighted according to the amount of interference, it is synthesized. In this way, the achievable effect is to maximize the reception SIR, so an ideal channel capacity can be obtained.

With the present invention, during error detection and transmission, a plurality of beams with preset directivity are used to cover the serviceable area, and the transmission is detected on a fixed directivity beam unit. In this way, the effect that can be obtained is that when the amount of interference in the service area is large, the interference power of the fixed directional beam unit can also be suppressed, and the transmission detection can be carried out with good accuracy.

With the present invention, the adaptive beam synthesis signal whose phase is equalized on each transfer is used to synthesize the signal through all transfers, and the adaptive algorithm is used to generate a common waiting state for all transfers. In this way, the obtainable effect is that at the receiving end of the base station, only one adaptive algorithm corresponding to the fixed directional beam can be provided for one mobile station, thus greatly reducing the hardware and software specifications.

With the present invention, when the transmitted detection positions are effectively different in space, they can be approached in space, and adaptive beams can be appropriately formed on the group unit of the detected transmission. In this way, the obtainable effect is that the adaptive light beam can be formed without increasing the number of waiting state control units used to execute the adaptive algorithm.

With the present invention, each transmission is normalized by the amount of interference, and the effect that can be obtained is that even if the amount of interference on each adaptive beam formed is different, the reception SIR can be improved.

With the present invention, during error detection and transmission, a plurality of beams with preset directivity are used to cover the serviceable area, and the transmission is detected on a fixed directivity beam unit. In this way, the effect that can be obtained is that when the amount of interference in the service area is large, the interference power of the fixed directional beam unit can also be suppressed, and the transmission detection can be carried out with good accuracy.

According to the present invention, in the initial state of the waiting state, if the adaptive algorithm of the adaptive antenna is also in the initial state at this time, the adaptive algorithm is operated by selecting the beam with the largest transfer power from the fixed directional beams. In this way, the achievable effect can not only shorten the time before the formation of the beam and the end of the adaptive algorithm.

[Industrial Applicability of Invention]

As mentioned above, the adaptive antenna receiving device of the present invention is suitable for the mobile communication system of the number division multiple connection (CDMA) method. The CDMA method uses frequency conversion modulation processing and can be used for the reflection of radio waves caused by surrounding buildings and terrain. , Refraction, and scattering cause the frequency selective attenuation of multiple waves to interfere with each other on the transmission path.

Schematic description

Figure 1 shows the structure of the first embodiment of the adaptive antenna receiving device of the present invention;

Figure 2 shows the structure of the transmission detection unit;

Figure 3 shows the shape of H fixed beams generated by the beam forming part;

Figure 4 shows the structure of the second implementation mode of the adaptive antenna receiving device of the present invention;

Figure 5 shows the structure of the third embodiment of the adaptive antenna receiving device of the present invention;

Figure 6 shows the structure of the transmission detection unit;

Figure 7 shows the structure of the fourth embodiment of the adaptive antenna receiving device of the present invention;

Figure 8 shows the structure of the fifth embodiment of the adaptive antenna receiving device of the present invention;

Figure 9 shows the structure of the conventional receiving device;

Figure 10 shows the structure of the conventional transmission detection unit;

Figure 11 shows the format of the sending time slot; and

Figure 12 shows an example of the impulse response of the frequency selective attenuation transmission path.

Symbol description of main components

101-1,101-2,101-N. . . antenna

102-1,102-2,102-N. . . Band pass filter (BPF)

103. . . Beam forming part

104-1,104-2,104-H. . . Reverse expansion

104. . . Transmission detection department

105b. . . Transmission detection department

105c. . . Transmission detection department

106-1,106-2,106-L. . . Adaptive beam forming part

106a-1,106a-2,...,106a-L. . . Adaptive beam forming part

106b-1, 106b-2,..., 106b-L. . . Adaptive beam forming part

106d-1, 106d-2,..., 106d-L. . . Adaptive beam forming part

107. . . Addition part

108. . . Data Judgment Department

121-1,121-2,121-H,124-l,124-2,124-H. . . Complex multiplier

122. . . . Retarder

123. . . Waiting State Control Department

123b. . . Waiting state control unit

125. . . Adder

126. . . Transmission path estimation section

127. . . Complex conjugate value calculation section

128. . . Complex multiplier

129. . . Interference amount estimation department

130. . . Normalization Department

141. . . Addition part

151-1,151-M. . . Adaptive beam forming group

151d-1,151dM. . . Adaptive beam forming group

201-1,201-2,201-N. . . antenna

202-1,202-2,202-N. . . Band pass filter (BPF)

203-1,203-2,203-N. . . Reverse expansion

204. . . Transmission detection department

205-1,205-2,205-N. . . Beam forming part

206. . . Addition part

207. . . Data Judgment Department

221-1, 221-2, 221-N. . . Complex multiplier

222. . . Retarder

223. . . Waiting State Control Department

224. . . Addition part

225. . . Complex multiplier

226. . . Complex conjugate value calculation section

227. . . Complex multiplier

228. . . Subtractor

229. . . Transmission path estimation section

300. . . Transmission path estimation section

301. . . Average power value calculation unit

302. . . Threshold value calculation unit

303. . . Judgment Department

304. . . Transfer selection

401-1,401-2,401-H. . . Beam transmission detection unit

401b-1,401b-2,. . . ,401b-H. . . Transfer selection

402. . . Transfer selection

403. . . Transmission path estimation section

404. . . Average power calculation unit

405. . . Threshold value calculation unit

406. . . Judgment Department

407. . . Beam selection part