High frequency network communications over various lines

High frequency communications network on different lines

Full description

Background of the invention

The invention generally relates to power system communications. More specifically, the invention relates to a device that has the ability to send and receive digital information simultaneously at high rates and over long distances across power lines and the transformers of those lines, including shared coaxial cables for current. AC and DC, coaxial cables, and twisted pairs

pair lines twisted.

Power line buses are a well-known tool in the field of power system communications. The basic elements of these carriers are the transmitting and receiving ends, which include one or more line traps, one or more coupling capacitors, and other equipment for tuning and coupling. There is detailed information about describing the optimal structure of traditional power line buses, and it is found in the book Fundamentals of Electrical and Computer Engineering - Volume Two: Communications Control Systems and Means, published in 1983 by John Wiley Publishing House - pages 617-627, which is a book used as a reference in this article. Invention. There is an important problem associated with the use of power line carriers that was addressed in previous inventions, and it includes the need for these carriers to have one or more line traps, and one or more capacitors, with one or more coupling transformers.

coupling transformers or carrier frequency hybrid circuits and frequency connection cables.

All traditional couplers contain a transformer with a ferrite core or an iron core, which leads to distortion of the signal because the conversion function does not perform linearly between the coupler intended for transmitting and the other intended for receiving. Distortion occurs as a result of the presence of magnetic core material, which results in magnetic abandonment. For power line carriers used for distribution purposes, this distortion is severe, as the signal must be transmitted through at least three nonlinear devices in which iron core transformers are used, namely the distribution transformer and two power line couplers. The distortion occurring in these non-linear devices reduces communication speeds.

An important disadvantage associated with previous designs is the use of ferrite or iron core transfomers in signal coupling devices, where the inductance factor of the primary coil L1 (primary coil) is here changed to an unknown value due to the non-linearity of the core, which consequently leads to Not tuning the required frequency of the carrier wave. Also, the impedance of the primary coil at the required carrier wave frequency does not match the impedance occurring in the power line. In light of this, other designs have been developed in which the signal can be coupled to the power line with the minimum input impedance for transmission and reception using a coupling capacitor with a large capacity (about 0.5 microfarad uF), and this leads to a significant loss in the amount of coupling, up to 20 dB. At the carrier frequency.

US Patent Filed No. 344258/9 (Application No. 258) deals with a new coupler for phase shifting of linear forces, telephone, twisted pairs, and coaxial lines for both transmission and reception. Coupling devices for phase displacement of linear powers include a new transformer with an air-core or dielectric material and are used in both telephone line and coaxial, LAN, and power line connections through power line transformers. The phase shift line coupler also includes a network associated with the coupling capacitor to obtain impedance matching at approximately the lowest known value of the characteristic impedance of the line and also to obtain the maximum fixed signal transmission to the line. This resonance effectively consists of a band-pass filter in Carrier wave frequency. The entire contents of Application No. 258 have been used here as a reference for this text. The 258 order designs address many of the problems associated with previous designs that used iron-core or ferrite-core couplers that resonate at the characteristic impedance of the power line, creating clicks, oscillations, and nonlinearities in communications across many devices. Different power lines. The linear phase shift couplers in order 258 do not have taps in the communications frequency range, allowing linear communications to occur over a wide range of frequencies. However, the need remains for a system of communication across power lines with the ability to send and receive digital information simultaneously using high frequencies ranging between 200 - 500 MHz, so that this allows obtaining high communication rates using wide frequency ranges over long distances across power lines. And transformer those lines, including

This includes AC and DC cables, coaxial cables, and also twisted pair lines.

General description of the invention

The invention provides, in the first embodiment, a device for transmitting electrical signals via one or more electrical lines with distinct impedance. The device includes the following:

- A rate to modify electrical signals and produce a modified carrier signal with a frequency greater than or equal to 200 MHz.

- A transmitter that communicates electrically with the modulator and has an output impedance and sends the modulated carrier signal.

A coupling device connects the electric line to the transmitter and makes a match between the output impedance of the transmitter and the distinct impedance of the power line, while delivering the modulated carrier signal to the power line without significant distortion in phase 0.

In a second embodiment, the present invention provides a communications device that transmits electrical signals across one or more electrical lines with distinct impedance. This device includes the following:

- A modifier to modify electrical signals and produce a frequency-modulated carrier signal

More than or equal to 200 MHz.

- A transmitter that communicates electrically with the modulator and has a distinct output impedance, and the aforementioned transmitter sends the modulated carrier signal.

- A first coupling device that connects the electric line and the transmitter and makes a match between the transmitter’s output impedance and the distinct impedance of the power line, while delivering the modulated carrier signal to the power line without significant distortion in phase.

- A receiver that has an impedance to your input and works to receive the modulated carrier signal.

- A demodulator device that is electrically connected to the receiver and produces an unmodulated carrier signal with a frequency greater than or equal to 200 MHz by demodulating the modulated carrier signal.

- A second coupler connects between the power line and the receiver and works to match the input impedance of the receiver with the distinct impedance of the power line, while delivering the modulated carrier signal to the receiver without significant distortion occurring in the phase.

In a third embodiment, the present invention provides a communications device that transmits the electrical signal via...

One or more electrical lines of distinct impedance, including:

As follows :

- A first signal modulator that produces a first modulated carrier signal with a specific frequency greater than or equal to 200 MHz, and demodulates a second modified carrier signal with a specific frequency greater than or equal to 200 MHz.

- A first transmitter with an output impedance communicates with the first modem signal modulator and sends the first modified carrier signal.

- A first receiver with an input impedance connects the first modem signals to the modulator and receives the second modulated carrier signal.

- A first coupling device that connects the electric lines, the first transmitter, and the first receiver, and works to match the output impedance of the first transmitter and the input impedance of the first receiver with the impedance of the electric lines.

The first and second modified carrier signals were connected without significant distortion in those signals.

- A second signal modulator that produces a second modulated carrier signal, while removing the modulation of the first modulated carrier signal.

- A second transmitter with an input impedance is connected to the second modem signal modifier and transmits

The second modified carrier signal.

- A second connector with input impedance is connected to the modulator of the second modem signals and receives the first modulated carrier signal.

- A second coupling device connects the electric lines, the second transmitter, and the second receiver, and works to match the output impedance of the second transmitter and the input impedance of the second receiver, with the distinct impedance of the electric lines, then connects the first and second modified carrier signals without significant distortion in the phase.

phase.

Brief explanation of the drawings

The previous summary and the following detailed description can be better understood when viewed in conjunction with the attached figures and drawings. For the purposes of illustration in this invention, we present here only the shapes and drawings of the preferred embodiments. However, we must realize that this invention is not limited to the specific shapes or arrangements mentioned in this part. In the attached figures and drawings, similar numbers are used to indicate the corresponding elements in all of those figures and drawings, which are as follows: Figure - 1: A curve of the distinct impedance of the power line in the line coupling device presented by the present invention.

Figure - 2: A diagram of a network of power lines across a wide communication area according to the present invention.

Figure - 3: A box diagram of the half-duplex power line modem signal rate according to the present invention.

Figure - 4: A diagram of the full-duplex power line modem signal rate according to the invention

Present.

Figure - 5: Box diagram of the power line communication device according to the present invention. Figure - 6: A diagram of a rate at the first frequency for use in the power line communication device shown in Figure - 5.

Figure - 7: A diagram of a rectifier at the second frequency for use in the power line communication device shown in Figure - 5.

Figure - 8: A diagram of the demodulator at the first frequency for use in the power line communication device shown in Figure - 5. Figure - 9: A diagram of the second frequency demodulator for use in the power line communication device shown in Figure - 5. Figure - 10: A diagram of the Ethernet network interconnection for use in the power line communication device shown in Figure - 5.

Figure - 11: A diagram of the line coupler used in the power line communication device shown in Figure - 5 at the first group of frequencies.

Figure - 12: A diagram of the line coupler used in the power line communication device shown in Figure - 5 at the second group of frequencies.

Figure-13: A diagram of the power supply source used in the power line communication device shown in Figure-5.

Detailed description:

The present invention presents advanced aspects of the phase shift linear coupling device addressed in Application No. 258. It has been found that using high frequencies (500 MHz) in a line coupler with an air-core or a core made of an insulating material leads to better results due to the increased frequency range and the possibility of transmission to greater distances. High-frequency signals create a magnetic field around any type of wire, and this field is transmitted along the surface of the power line in the form of magnetic waves and bypasses transformers. Therefore, such high-frequency signals can be transmitted over long distances within a wide range.

In tight environments such as a coax cable, high-frequency signals (1 MHz or more) will only travel a short distance before disappearing. This is because the coax cable has a constant coefficient of inductance connected in series (L) with the capacitor connected in parallel (C), which results in a strong band-pass filter that can exclude signals of different frequencies at any distance. The coax cable may also produce a small magnetic field around the middle connector near the shield.

The invention provides a different environment in lines of force, which do not move easily from one point to another, but rather take a star shape. Since the values of (L) and (C) in power lines are not fixed, the band-pass filter in those lines is weaker than in the case of a coax cable. Also, due to the lack of shielding on the power lines, the conductor of the lines may cause It has a wide magnetic field around the wire compared to the field in the coax cable. In addition to that, changing the value of the distinct impedance (Zo) of the power lines, whether in terms of time, location, or the number of wires connected to each other at different points located on the power distribution network. Accordingly, the spread of electric/magnetic fields from digital signals to power lines may not stop, but rather those signals may be transmitted to greater distances than in the case of shared coax lines. High-frequency signals can also pass through transformers, power lines, which resemble a large capacitor connected in parallel, without causing a significant loss in signal strength when compatible with the power line, according to the present invention.

The importance of the line coupler in this invention lies in its ability to work as a tool for matching the distinct impedance of the power line. As stated in Application No. 258, the line coupler in the present invention includes a transformer with an air-core or a dielectric-core, with a coupling capacitor (Ceq). If any change occurs in the impedance of the primary coil of the transfonuer, this will not be significantly reflected in the secondary coil of the transformer, and vice versa. Therefore, the only impedance that can be observed by the power line is the resonance of the primary coil with the capacitor.

Ceq capacitor. This series resonance reduces the amount of impedance to approximately 1 ohm, but as the frequency level increases, the value of the impedance also increases, reaching 100 - 200 ohms. This depends on the type of impedance necessary for optimal compatibility with the power line resistance, and also on the capacitance. The bandwidth required for this. For example, Figure 1 shows the distinct impedance of the line coupler for the power line. If the value of that impedance is 100 ohm at Fl, a compatibility of 6 dB can occur in the range between 50 or (F4). To 250 ohm (F3) ohm. Reducing the impedance of the line coupler leads to greater compatibility in the frequency range capacity of power lines in which the impedance reaches 10 ohm.

As discussed in Application No. 258, the line coupler of the present invention has an important characteristic, which is the linearity of the phase obtained. The local impedances on the power lines are located at a distance of two feet from each other at different frequencies, and the highest degree of compatibility in these lines is achieved by using an inductance device (L) and a capacitor (C) that do not contain ferrite cores or iron cores because The line of forces consists of (C's) and (L's). In addition, reflections occur at the end of every line that does not have a terminal end. Core-ferrite or antenna-iron couplers are also characterized by their self-resonance around the frequency range of the communications of interest. It creates self-resonance and reflection in variable clicks in frequency space. In contrast, couplers have a heart

The core ferrite and the core iron of the present invention have self-resonance much higher than the frequency range of interest.

The air-core line coupler matches the distinct local impedance of the power line. Thus, reflections do not give rise to clicks in the frequency range of interest. A level of flatness in the frequency range ranging between 6-10 dB can be achieved by using the line coupler in this present invention so that there is compatibility with the power line. Such compatibility is achieved if the distinct impedance of the power line falls within the range that ranges between half the initial impedance of the line coupler and twice the initial impedance of that device, such that it ranges - for example - between 1 and 100 ohm in a frequency range ranging between 18 - 30 MHz. Assuming that there is a power line impedance of 50 ohms at 22 MHz, the degree of compatibility will range between 25 - 100 ohms, covering frequencies that range approximately between 21 - 30 MHz. Assuming that the initial impedance of the line coupler at 20 MHz is about 20 ohms, the agreement here occurs between about 18 and about 22 MHz, and the total agreement is between about 18-30 MHz for a frequency range of 10 dB and click-free.

The value of impedance in power lines usually ranges between 50 - 100 ohms for underground lines, and between 100 - 500 ohms for overhead lines. However, due to the presence of circuit breakers

Underground substations with many supply sources, the characteristic impedance value drops to 1 ohm at their locations on the power line. The line coupler is designed to accommodate the most common types of local impedance in power lines. For example, if the distinct impedance of the power line is 80 ohms, a degree of compatibility of 6 dB can be obtained by using air-core couplers, according to this invention, with a value ranging between 40 - 160 ohms at either Locations. The power line must be locally compatible, as the local impedance in this line may change in value every few feet. Since the characteristic impedance of a 120 volt power line is about 80 ohms, such a value is valid for compatibility at any location.

Since the secondary impedance is not changed significantly by the change in the characteristic impedance of the power line, a transmitter and receiver agreement of about 50 ohms can be obtained. Both sides of the transformer correspond regardless of the change in power line impedance. The secondary coil of the transformer is matched by the sender or receiver. The change in impedance of the primary coil of the transformer is not reflected in the secondary coil. Thus, a compatibility of 40-50 ohms is obtained at all times for the transmitter and receiver, regardless of the change in power line impedance.

As for the higher frequencies, which range - for example - between 200 - 500 MHz, the shape of the transformer with an air-core or a core with insulating material differs from that described in patent application No. 258. In this case, the line coupler may not have two solenoids or pneumatic coils with a common axis of different diameters and are closed.

With a magnetic wire, but it is smaller in size and resembles the shape of a chip filled with a plastic material or another non-conductive material such as resin, glue material, ceramic material, or any other solid non-conductive material (chip material). It is preferable that the line coupler contain very thin conductive plates separated from each other by chip material. It is preferable to make these plates from copper, although it is also possible to make them from silver, gold, or any other material that conducts positively or negatively. The paintings take any shape, whether rectangular, square, circular, etc., but the circular shape is preferred here. The size of transformers with multi-layer air-cores depends on the rate of use. For example, if the primary diameter of the line coupler (30 GHz) is less than 1 mm, the layer thickness will be less than about 0.1 mm, resulting in This has an inductance of 0.3 nanohertz. Likewise, the sizes of thin rectangular copper plates are about 2 mm in length and 0.1 g in thickness. The primary and secondary inductors are spaced about 0.5 mm towards the top, so that the devices appear like a very small capacitor. However, the present invention uses the terminal values in the inductance device to cause resonance in the capacitor to achieve compatibility with the power line impedance. Alternatively, panels can be formed directly in the chip by depositing metallic layers or coating with silicon. The coated silicon is a conductor in the event that it is active. For example, the DC voltage level turns on a transistor to make it active. Thus, when panels are formed from coated silicon, they may take the form of an active device such as a transistor or a diode. Of course, there are other designs of transformers with similar...

Air-core or dielectric-core, and these can be used without deviating from the content or scope of the invention. For example, a piece of coax cable can be used as an air-core transformer. The shield of the coax cable is the primary coil in the transformer, while the inner wire is the secondary coil in it. This axial type of air-core transformers can be used in very high-frequency communications whose frequency exceeds 500 MHz. Likewise, two copper or iron pipes (or a strip of aluminum or copper) can be placed inside each other. In this case, the outer tube or slice represents the primary coil in the air-core transformer, while the inner tube or slice represents the secondary coil. This design can also be used for frequencies exceeding 100 MHz.

In addition, research has recently been conducted to create solid-state transformers to convert medium voltage alternating current from a value of 7.6 kilovolts to 120 volts using a technology similar to that used in conversion regulators to convert direct current to alternating current, which is known. In the name of Gate Drier Control circuit technology. These transformers are mainly designed using semiconductor elements or components such as transistors or integrated circuits instead of using iron cores or heavy copper in traditional transformers. Solid-state transformers are also used in the couplers presented in the present invention. And he realizes

An experienced person in this field believes that it is possible to use other, simpler integrated circuits to make transformers used in couplers. According to this invention, it can imitate the integrated circuits used now that use active transistors and/or make an air-core transformer. The core has the necessary inductance and capacitance to function exactly like a conventional air-core transformer. Although the shape of the previously described line coupler differs from the one covered in Application No. 258, there is a similarity in performing the function of each. In the plates (or pipes or foils) that make up the line coupler in this invention, the coupling occurs inductively and capacitively, resulting in a transformer with an air-core or a dielectric-core. However, the pairing of the primary coil and the secondary coil in the transformer varies depending on the frequency value. Coupling occurs for the primary and secondary coils in a neutral manner in terms of electricity and magnetism (i.e., in a neutral manner in terms of inductance and capacitance) at frequencies less than 100 MHz, while coupling increases in terms of magnetism or love only when the degree of frequency exceeds 100. MHz MHz. If this degree is within 100 MHz, the trend here is the coupling between the primary coils and the secondary coils inductively.

As described in detail in Application No. 258, the communications device has multiple uses. This function is extended through the couplers covered in the present invention, which provide the opportunity to send data at high rates. For example, the present invention may use:

High frequency carrier waves (200 - 500 GHz) for transmission across power lines. By using the line coupler technology with an air-core or a dielectric-core, according to this invention, a communications speed across power lines of 1 Gbps can be achieved.

Referring now to the shapes and drawings in which the numbers represent the corresponding shapes or parts on the drawing, we find in Figure 2 that represents a box diagram of a power line wide area communications network (WAN) according to the present invention.

The Ethernet router (12) connects to the network structure in the same way that such a connection occurs in the Internet or intranet using a unit or switch (not shown in the figure) such as Nu Wave 3 terminal products. The router (12) is also connected to the power line modem signal modulator (14), whose role is connected to the line coupler (16) for the low-voltage power line, in order to cause duplication of the signals resulting from the power line modem signal modulator ( 14) Between the 11 kV power line (18) at the substation

substation (20).

Those experienced in this field realize that the router (12) can communicate with other devices in different applications and uses without deviating from the content or scope of the current invention. These other uses include - for example - the following:

1- Ethernet networks that cover a large area, with other service means in which the basic structure is linked to another network.

2- Telephone service applications in which the infrastructure is connected to the telephone center and to the time division multiplexer that identifies multiple telephone lines on the power line.

power line

3- Uses of television in which the basic structure is connected to a television transmission station broadcasting digitally to many television stations via the power line.

The Ethernet router (12) passes through a standard router. Through the line coupler (16) for the medium voltage power line, the power line modem (14) can modify or demodulate the Ethernet signals in the 11 kV power line (18). This will come later. A detailed discussion of the power line modem signal rate (14). It is preferable that the height of the line coupler (61) in the medium voltage power line be within 0.5 meters and its diameter

Within 0.2 metres, and placed on a porcelain insulator filled with resin. It is also preferable to use a transformer with a dielectric-core with the line coupler previously described, which takes the form of two small plates, each of which is placed in the form of a capacitor on top of the other, for operation at high frequency. Of course, other designs for a high-frequency transformer can be used here in the line coupler

(16) regarding the medium voltage power line, without deviating from the content or scope of the present invention.

The high-frequency signal - here the 100 Mbps Ethernet router signal is preferred - is transmitted across power lines (18), and through one or more distribution transformers (22, 24), and through magnetic waves and over power lines.

power lines low voltage power lines (26)(110-220 volts). This signal is picked up by one or more signal modulators (14) through low voltage couplers (28). It is preferable to place low voltage couplers (28) and power line modems (4 1) on low voltage power lines (26) before the low voltage power meters (not shown) entering the Buildings (30). The modem signal rectifier devices (14) in the power line are identical to the modem signal rectifier devices mated to the power lines (18). Here, low voltage couplers (28) can be designed according to the method described in Application 258, so that they are smaller in size than the line coupler (16) in the medium voltage power line. In low-voltage couplers (28), high-frequency transformers with an air-core or a dielectric core are used according to the previous description.

Ethernet switches (32) range from power line modulators (14). Ethernet switches distribute network data across power lines

Power lines to buildings (30) using a local communications network (LAN) for power lines in accordance with the present invention as mentioned below.

It is preferable to use the power line modem signal rate (14) at a frequency of 1.35 MHz in any transmission or reception operations. This frequency-carrying router is transmitted to distribution transformers (24,22) from the power lines

Medium voltage power lines (18), which range from 7-35 kV, to low voltage power lines (26), which range from 110-240 volts, all the way to buildings (30). It can be done via a carrier router

For the mentioned frequency, Ethernet network data is transmitted at a rate ranging between 10 - 100 Mpbs. Those experienced in this field realize that other frequencies can be used, such as 2.7 or 3.5 GHz, without deviating from the content or scope of this invention. In an alternative preferred embodiment, a carrier frequency of 30 MHz can be used to transmit Ethernet network data at a rate of 10, 100 Mbps, or 1 Gbps. In this case, the WAN network can cover a larger area on the power line and transmit data away from the substation (20) to the buildings (30). Therefore, neither the power line modem (14) nor the low voltage couplers (28) need to be placed on the low-voltage power lines (26) before they go to the power meters. Buildings (30). Alternatively, the power line modem (14) and low voltage couplers (28) can be placed inside buildings (30).

Those experienced in this field realize that although the current models are described as using Ethernet network systems to send and receive data, there are other data protocols that can be used through a WAN network without deviating from the content or scope of the present invention. Referring now to Figure 3, we find here the preferred image. For the power line modem signal rate (14). The Ethernet physical interface (38) links the power line modem (14) to an Ethernet card, image, or retransmission unit station (not shown), which may include any suitable connector with a pair of links. Duplex. Network data (encrypted Manchester data) is provided from the interface (38) to the main processing unit (CPU) (40), such as the Motorola MPC 8 SST, which transfers the encrypted information to and from the paallel bus interface (42). Memory (44) is used to temporarily store data on the parallel bus interface (42). The field-programmable FPGA port (46) - preferably the Xilinx Virtex and future respectively. The memory 48 - EPROM stores program instructions for both the FPGA (46) and the CPU (40). The FPGA (46) controls the transmit/receive switch (36) connected to the line coupler (34) and the power lines (48) on which the rectifier carries modem signals (14). Application No. 258 provides a detailed description

For the interface between the aforementioned line coupler (34) and power lines (48), in addition to the structure of the line coupler. As can be seen from the above, a transformer with an air-core or a dielectric-core must be used according to this invention with a line coupler (34).

A circuit is provided for interconnecting signals to and from the FPGA (46). For transmission, the signal leaves the FPGA (46) and passes through a transformer (50) from standard to digital (A/D). The overconversion of the carrier frequency is performed by the mixer (58) and the local oscillator (52). Both amplifiers (56) and filters (54) are used to interconnect the signal generated by the line coupler (34). Likewise, for reception operations, the signal passes through filters (54) and low-frequency amplifiers (56) and is down-converted by the mixer (58) and oscillator (58). There is an automatic gain control (AGC) that is done by the circuit (62), and then the signal is converted into a digital image by an analog/digital A/D transformer (60) to then be sent to the FPGA (46). The power line modem signal rate shown in Figure 3 is of the semi-multiple type, so that the carrier frequency values for transmission and reception are constant in both cases. Those experienced in this field realize that it is possible to perform AGC and over- and under-conversion using EPGA without the need for additional circuits.

additional circuitry.

The FPGA (46) can be programmed to use any desired modulation type. Although it is preferable to use an FM modulation system, the FPGA (46) can be programmed for use with any of the FSK or QPSK systems.

Or 16QAM, CDMA, ADSL, or any other type of modification without deviating from the content or scope of this invention. We must also realize that it is possible to change a specific type of FPGA (46) or CPU (40) without deviating from this invention, and in fact the FPGA (46) can be replaced with any type of DSP processor as described in Application 258. Figure 4 shows a complete multiplex system for the power line modem signals rate (14), which is very similar to the system described in Figure 3 except for the interface between the rate modem signals (14) and the power lines (48). It appears in Figure 4. The transfer switches for transmission and reception have been removed, and replaced with one coupler (34) operating at the first frequency (Fl) for the purpose of transmission, with a second coupler (34) operating at the second frequency (F2) second frequency. For reception purpose. For example, frequencies of 1.2 and 1.6 GHz can be used here for simultaneous transmission and reception operations via the power line (48). In addition to the difference in the rate structure of the modem signals (14), the EPROM program (48) must also be changed for the FPGA (46) in order for a complete reversal of the multiplication process to occur at two frequencies.

different.

We now move to Figure 5, which shows a box diagram of a power-line communications apparatus (10) according to the present invention, for use in a local network (LAN). The device (10) is coupled to a pair of power lines (48), and generally includes a modulator (64), a demodulator (66), an Ethernet interface (68), and a coupler (34). with

A source of power supply (70). The device (10) is connected in full duplication with the Ethernet card, the switch, and the Ethernet network (not shown in the drawing), and it works to send the Ethernet network data via power lines (48). During operation, the first communications device appatus (10), which represents the basic unit, is coupled with power lines (48), and it performs transmission operations at the first frequency (FI) and reception operations at the second frequency (2 F). The second communications device appaatus (10), which represents the sub-unit with the power lines (48), is also coupled, and performs transmission operations at the second frequency (F 2) and reception operations at the first frequency (F 1). As an example only, the device that will be described later uses a frequency value of 250 MHz for the frequency (f 1) with another value of 350 MHz for the frequency (F2) to thus obtain a signal from the Ethernet network of 10 Mbps via power lines. power lines. Those who are skilled in this field realize that it is possible to use other frequency values without deviating from the content or scope of this invention. For example, values of 2.44 and 5.80 GHz can be used, which are frequency bands that can be used without a license to obtain 100 Mbps of excitation to the Ethernet network via power lines.

Figure 6 shows details about the modulator (64) used in the basic unit (transmission at a frequency of 250 MHz). The modulator (64) is preferably of the FM type, which includes an oscillator (76), a modulator (74), with capacitors and inductors connected to it. The rectifier (64) also includes an RF transformer (72) and interconnection circuitry from the AUF interconnection slot to the Ethernet interface (68). The signal is transferred from the transformer through the circuits of the oscillator (74) and the rectifier (76), then through the LC filter circuit to output the modified signal. The values of capacitors and inductors are chosen based on the frequency of the carrier router, and in the case of the basic unit this value is 250 MHz.

Figure 7 shows the rate (64) of the sub-unit (transmitting at a frequency of 350 MHz), which is a device similar to that found in the basic unit with the exception of the values of the capacitors and inductors in the LC filter circuit. Here, the values of capacitors and inductors are chosen based on the frequency of the carrier wave, and in the case of the subunit, this value is 350 MHz.

Figure 8 shows details about the demodulator (66) in the basic unit (receiving at a frequency of 350 MHz). The modified FM input excitation is first sent through two RF amplifiers (78) and associated circuits between the amplifiers (78) containing Blinch & filters & to separate the noise from the other carrier frequency from the modified input signal, and here the LC values are chosen in filters

Blinch& based on the carrier wave frequencies used in the communications device (10). The modified signal is then coupled with the FM detector circuit (82) via an RF transformer (80). It is preferable that the detector circuit (82) be an MC131SSD. The output of the FM detector circuit (82) then passes through fast amplifiers (84) and filters (86) to generate an output signal from the Ethernet data extracted from the modulated signal inputs. Figure (9) shows a demodulator (66) for the subunit (receiving at 350 MHz). The slave demodulator (66) is similar to the master demodulator (66) except that the values of the inductors and capacitors in the Blinch filter are used on the modulated input signal. The values of the inductors and capacitors in the slave demodulator (66) are different due to the different frequency of the carrier being filtered out of the signal

Modified entry.

The previously mentioned demodulator model (66) is limited to an ethernet speed of 10 Mpbs because an MC13155DFM detector circuit and carrier frequencies of 250 and 350 MHz are used. The demodulator bandwidth (66) can be increased to obtain an Ethernet network speed of 100 Mbps by using an FM detector circuit.

It operates at a frequency range greater than 200 MHz and also uses carrier frequencies

Greater than 1 GHz.

Figure 0-1 shows the details of the interconnection (68) of the Ethernet network for each of the two units.

Basic and subsidiary. Two AC interfaces are included in the Ethernet interface (68). First, an AUI was provided for the Ethernet switch through the connector (88). Two lines run from the connector (88) directly to the modulator (64), and the output of the demodulator (66) is coupled to the connector (88) using an RF hansformer (92). Alternatively, a communications apparatus (10) can be connected to an Ethernet switch or Ethernet switch using an RJ-45 Ethernet twisted pair connector (94). When using the RJ-45 connector, an integrated circuit (96) is used, which is a 10Base-T transceiver or twisted pair adapter/AUI for the Ethernet network, preferably ML4658CQ, and an accompanying circuit as shown for the interconnection between the RJ-45 connector (94). And the AUI slot for the connector (88).

Figure (11) shows the line coupler (34) used in the master communications apparatus (10). Regarding transmission to power lines

(48), the rectifier output (64) first passes through the RF amplifier (96) and the low pass filter (98). The signal is then sent to a high-frequency coupler with an air-core or a dielectric-core according to the present invention comprising a transformer with an air-core or a dielectric-core (100) and a coupling capacitor. coupling capacitor (102) They couple the signal with power lines (48). The choice of LC values for the low pass filter (98) depends on the frequency of the carrier wave. The values of the coupling capacitor (Ceq) are chosen.

(102) to provide an impedance of 150 ohm compatible between the power lines (48) and the RF amplifier (96).

To receive signals from power lines (48), the input signals are first coupled

Of these lines, using a high-frequency coupling device that has an air-core or a dielectric-core and includes a transformer with an air-core or a dielectric-core (104) with a coupling capacitor (Ceq). ) and (106). The input signal is then sent via RF (108) and through a Blinch filter (110) to output the signal to a demodulator (66). And as on the side

Transmission: The LC values in the linch filter (110) are chosen based on the frequency of the carrier wave, and for the values of the coupling capacitor (106), the LC values are chosen to obtain a degree of impedance compatibility of 50 ohm between the power lines (48) and the RF amplifier.

(١٠٨).

Figure 12 shows the line coupler (34) in the secondary communications device (10), which is a device similar to the basic device (34) with the exception of the values of the inductors and capacitors.

In the Blinch filter (110), the values of the low band pass filter (98), and also the values of the coupling capacitors (106, 102). These values differ in the slave coupler (34) because the carrier wave frequencies for sending and receiving signals from power lines (48) are reflected from the master communications apparatus (10).

Finally, Figure 13 shows the power supply (70) used with the communications device (10). Here, the alternating current power is taken from the power lines (48) and then passes through the beads (112) to isolate the impedance in the power transformers (114) from the impedance in the power lines (48). The goal is to obtain a more stable bandwidth in power lines and a higher level of signals. As for direct current powers, they are generated by power transformers

power transformers (114) and rectifiers (116). Finally an output is produced

Direct current with different electrical voltages necessary for the communications device (10), using voltage regulators (118). As shown in Figure 13, separate power transformers (114), rectifiers (116), and voltage regulators (118) are used, in order to obtain from them the power necessary to operate the transmitting and receiving sides of the communications device (10). In this way, carrier wave frequencies of 250 and 350 MHz are isolated from each other. Those skilled in this field realize that there are changes that can be made to the previously described models without deviating from the content or scope of the current invention. Therefore, it must be understood here that the invention is not limited to a specific model that was disclosed, but rather is intended to cover modifications that may be included within

The framework of this invention. Specifically, despite the specific examples in which it was used

New coupling devices in this field can also be used in any other form of communication over power lines without deviating from the content and scope of the present invention. In addition, the couplers technology in this invention can be used in communication operations over any lines, such as telephone lines, coax lines, and/or twisted lines.

twisted pair lines and/or copper wire and/or electrical connections in trucks and buses electrical harness and/or in AC/DC power lines. Likewise, although Ethernet systems are discussed as transmission protocol systems in preferred embodiments of this invention, there are other communication systems that can be used in the communication device according to this invention.