Wireless communication device and method of response signal expansion
Abstract
FIELD: radio engineering, communication.SUBSTANCE: in a device a control part controls both a sequence ZC, which is used in primary expansion on an expansion part and a Walsh sequence, which is used in secondary expansion in an expansion part, to provide the possibility for a very small cyclic interval of ZC sequence shift to absorb noise components that remain in the response signal; the expansion part uses the ZC sequence set up with the help of the control part for primary expansion of the response signal; and the expansion part uses the Walsh sequence set up with the help of the control part for secondary expansion of the response signal, to which a CP prefix was added.EFFECT: increased accuracy of signals division with code compaction of a response signal in multiplexing.20 cl, 15 dwg
Term
1.7 yearsleft in the term
Expires 13 June 2028.
- Priority
- Filed
- Granted
- Today
- Expires
20 claims: 4 independent, 16 dependent
- 1A wireless device, comprising:a spreading unit configured to spread-spectrum signal ACK or NACK orthogonal sequence, which is one of a plurality of orthogonal sequences, and the sequence defined by the cyclic shift value that is one of the plurality of cyclic shifts, and is associated with said orthogonal sequence;and a transmission unit configured to transmit the ACK signal or NACK, characterized in that each of the plurality of orthogonal sequences is the orthogonal sequence, consisting of four codes and having a length of 4;a plurality of orthogonal sequences include a first orthogonal sequence and the second orthogonal sequence, the sequence consisting of two codes in the first half of the first orthogonal sequence is not orthogonal to the sequence consisting of two codes in the first half of the second orthogonal sequence, and a sequence consisting of code 2 in the second half of the first orthogonal sequence is not orthogonal to the sequence consisting of two codes in the second half of the second orthogonal sequence;and the cyclic shift value associated with the first orthogonal sequence is different from the cyclic shift value associated with the second orthogonal sequence. 1. Устройство радиосвязи, содержащее: блок расширения спектра, выполненный с возможностью расширения спектра сигнала АСК или NACK ортогональной последовательностью, которая представляет собой одну из множества ортогональных последовательностей, и последовательностью, заданной значением циклического сдвига, которое представляет собой одно из множества значений циклических сдвигов, и которое ассоциировано с упомянутой ортогональной последовательностью;и блок передачи, выполненный с возможностью передавать сигнал АСК или NACK, отличающееся тем, что каждая из множества ортогональных последовательностей представляет собой ортогональную последовательность, состоящую из 4 кодов и имеющую длину 4;множество ортогональных последовательностей включает в себя первую ортогональную последовательность и вторую ортогональную последовательность, причем последовательность, состоящая из 2 кодов в первой половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов в первой половине второй ортогональной последовательности, и последовательность, состоящая из 2 кодов во второй половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов во второй половине второй ортогональной последовательности;и значение циклического сдвига, ассоциированное с первой ортогональной последовательностью, отличается от значения циклического сдвига, ассоциированного со второй ортогональной последовательностью. 1. Устройство радиосвязи, содержащее: блок расширения спектра, выполненный с возможностью расширения спектра сигнала АСК или NACK ортогональной последовательностью, которая представляет собой одну из множества ортогональных последовательностей, и последовательностью, заданной значением циклического сдвига, которое представляет собой одно из множества значений циклических сдвигов, и которое ассоциировано с упомянутой ортогональной последовательностью;и блок передачи, выполненный с возможностью передавать сигнал АСК или NACK, отличающееся тем, что каждая из множества ортогональных последовательностей представляет собой ортогональную последовательность, состоящую из 4 кодов и имеющую длину 4;множество ортогональных последовательностей включает в себя первую ортогональную последовательность и вторую ортогональную последовательность, причем последовательность, состоящая из 2 кодов в первой половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов в первой половине второй ортогональной последовательности, и последовательность, состоящая из 2 кодов во второй половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов во второй половине второй ортогональной последовательности;и значение циклического сдвига, ассоциированное с первой ортогональной последовательностью, отличается от значения циклического сдвига, ассоциированного со второй ортогональной последовательностью.
- 15A method for spreading a response signal comprising the steps of:expanding the spectrum of the signal ACK or NACK sequence predetermined cyclic shift value that is one of the plurality of cyclic shifts and is associated with an orthogonal sequence;and broaden the spectrum of the signal ACK or NACK orthogonal sequence, which is one of a plurality of orthogonal sequences, characterized in that each of the plurality of orthogonal sequences is the orthogonal sequence, consisting of four codes and having a length of 4;a plurality of orthogonal sequences include a first orthogonal sequence and the second orthogonal sequence, the sequence consisting of two codes in the first half of the first orthogonal sequence is not orthogonal to the sequence consisting of two codes in the first half of the second orthogonal sequence, and a sequence consisting of code 2 in the second half of the first orthogonal sequence is not orthogonal to the sequence consisting of two codes in the second half of the second orthogonal sequence;and the cyclic shift value associated with the first orthogonal sequence is different from the cyclic shift value associated with the second orthogonal sequence. 15. Способ расширения спектра сигнала ответа, содержащий этапы, на которых: расширяют спектр сигнала АСК или NACK последовательностью, заданной значением циклического сдвига, который представляет собой одно из множества значений циклических сдвигов и которое ассоциировано с ортогональной последовательностью;и расширяют спектр сигнала АСК или NACK ортогональной последовательностью, которая является одной из множества ортогональных последовательностей, отличающийся тем, что каждая из множества ортогональных последовательностей представляет собой ортогональную последовательность, состоящую из 4 кодов и имеющую длину 4;множество ортогональных последовательностей включает в себя первую ортогональную последовательность и вторую ортогональную последовательность, причем последовательность, состоящая из 2 кодов в первой половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов в первой половине второй ортогональной последовательности, и последовательность, состоящая из 2 кодов во второй половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов во второй половине второй ортогональной последовательности;и значение циклического сдвига, ассоциированное с первой ортогональной последовательностью, отличается от значения циклического сдвига, ассоциированного со второй ортогональной последовательностью. 15. Способ расширения спектра сигнала ответа, содержащий этапы, на которых: расширяют спектр сигнала АСК или NACK последовательностью, заданной значением циклического сдвига, который представляет собой одно из множества значений циклических сдвигов и которое ассоциировано с ортогональной последовательностью;и расширяют спектр сигнала АСК или NACK ортогональной последовательностью, которая является одной из множества ортогональных последовательностей, отличающийся тем, что каждая из множества ортогональных последовательностей представляет собой ортогональную последовательность, состоящую из 4 кодов и имеющую длину 4;множество ортогональных последовательностей включает в себя первую ортогональную последовательность и вторую ортогональную последовательность, причем последовательность, состоящая из 2 кодов в первой половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов в первой половине второй ортогональной последовательности, и последовательность, состоящая из 2 кодов во второй половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов во второй половине второй ортогональной последовательности;и значение циклического сдвига, ассоциированное с первой ортогональной последовательностью, отличается от значения циклического сдвига, ассоциированного со второй ортогональной последовательностью.
- 18An integrated circuit for controlling the process, comprising:expanding the spectrum of the signal ACK or NACK sequence predetermined cyclic shift value that is one of the plurality of cyclic shifts and is associated with an orthogonal sequence;and expansion of the ACK signal or NACK orthogonal sequence, which is one of a plurality of orthogonal sequences, characterized in that each of the plurality of orthogonal sequences is the orthogonal sequence, consisting of four codes and having a length of 4;a plurality of orthogonal sequences include a first orthogonal sequence and the second orthogonal sequence, the sequence consisting of two codes in the first half of the first orthogonal sequence is not orthogonal to the sequence consisting of two codes in the first half of the second orthogonal sequence, and a sequence consisting of code 2 in the second half of the first orthogonal sequence is not orthogonal to the sequence consisting of two codes in the second half of the second orthogonal sequence;and the cyclic shift value associated with the first orthogonal sequence is different from the cyclic shift value associated with the second orthogonal sequence. 18. Интегральная схема для управления процессом, содержащим: расширение спектра сигнала АСК или NACK последовательностью, заданной значением циклического сдвига, который представляет собой одно из множества значений циклических сдвигов и которое ассоциировано с ортогональной последовательностью;и расширение спектра сигнала АСК или NACK ортогональной последовательностью, которая является одной из множества ортогональных последовательностей, отличающаяся тем, что каждая из множества ортогональных последовательностей представляет собой ортогональную последовательность, состоящую из 4 кодов и имеющую длину 4;множество ортогональных последовательностей включает в себя первую ортогональную последовательность и вторую ортогональную последовательность, причем последовательность, состоящая из 2 кодов в первой половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов в первой половине второй ортогональной последовательности, и последовательность, состоящая из 2 кодов во второй половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов во второй половине второй ортогональной последовательности;и значение циклического сдвига, ассоциированное с первой ортогональной последовательностью, отличается от значения циклического сдвига, ассоциированного со второй ортогональной последовательностью. 18. Интегральная схема для управления процессом, содержащим: расширение спектра сигнала АСК или NACK последовательностью, заданной значением циклического сдвига, который представляет собой одно из множества значений циклических сдвигов и которое ассоциировано с ортогональной последовательностью;и расширение спектра сигнала АСК или NACK ортогональной последовательностью, которая является одной из множества ортогональных последовательностей, отличающаяся тем, что каждая из множества ортогональных последовательностей представляет собой ортогональную последовательность, состоящую из 4 кодов и имеющую длину 4;множество ортогональных последовательностей включает в себя первую ортогональную последовательность и вторую ортогональную последовательность, причем последовательность, состоящая из 2 кодов в первой половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов в первой половине второй ортогональной последовательности, и последовательность, состоящая из 2 кодов во второй половине первой ортогональной последовательности, не является ортогональной к последовательности, состоящей из 2 кодов во второй половине второй ортогональной последовательности;и значение циклического сдвига, ассоциированное с первой ортогональной последовательностью, отличается от значения циклического сдвига, ассоциированного со второй ортогональной последовательностью.
Independent claims4
118 paragraphs in 4 sections, as filed
TECHNICAL FIELD
The present invention relates to an apparatus and method for expanding a radio signal response.
BACKGROUND
When the mobile communication ARQ (automatic repeat request) is applied to the data downlink from the radio communication apparatus "base station" (hereinafter abbreviated to "base station") to the wireless devices, "mobile station" (hereinafter abbreviated to "mobile station"). Thus, the mobile station returns a response signal representing error detection results of downlink data, to the base station. Mobile stations perform control CRC (cyclic redundancy check) data downlink, and if it finds CRC = OK (successfully) (ie, if no error is found), then the return ACK (acknowledgment), and if you find CRC = NG ( unsuccessfully) (i.e. if error is found), then returns NACK (negative acknowledgment) as a response signal to the base station. These response signals are transmitted to the base station using uplink control channels of communication such as a PUCCH (physical uplink control channel communications).
In addition, the base station transmits control information for the mobile stations to report the results of resource allocation of downlink data. This control information is transmitted to the mobile stations by using control channels, the downlink channels such as CCH L1 / L2 (the control channels are L1 / L2). Each channel CCH L1 / L2 takes one or a plurality of CCE. If one channel CCH L1 / L2 takes a plurality of CCE (control channel elements), the set of elements of CCE, busy channel CCH L1 / L2, consistent. Based on the number of elements CCE, required for the transfer of control information, the base station allocates to each mobile station an arbitrary channel CCH L1 / L2 of the plurality of channels CCH L1 / L2, maps control information to physical resources corresponding elements CCE, busy channel CCH L1 / L2, and performs transmission.
Furthermore, for effective use of resources of the downlink investigation is performed for the display elements between CCE PUCCH channels. According to this mapping, each mobile station may make a choice the PUCCH to use to transmit response signals from the mobile station, from the CCE elements, are mapped to physical resources on which control information indicate to the mobile station.
Furthermore, as shown in Figure 1, studies were performed to perform code division multiplexing using a plurality of extensions response signals from a plurality of mobile stations using a ZC sequence (ZC (Zadoff-Chu)) and Walsh sequences (Walsh) (cm . Non-Patent Document 1). In Figure 1, (W0, W1, W2, W3) represents a Walsh sequence with a sequence length of 4. As shown in Figure 1, in the mobile station a response signal ACK or NACK is first subjected to a first expansion of a symbol with a ZC sequence (with a sequence length of 12) in the frequency domain. Then the response signal subjected to the first extension, subject IFFT (inverse fast Fourier transform) associated with the W0-W3. Response signal extended in the frequency domain using ZC sequence with a sequence length of 12, was converted to the ZC sequence with a sequence length of 12 by this IFFT in the time domain. Then, the signal subjected to the IFFT is subjected to a second extension, using a Walsh sequence (with a sequence length of 4). Thus, one response signal is allocated to each of four symbols S0-S3. Similarly, using ZC sequences and Walsh sequences expand response signals of other mobile stations. In this case, different mobile stations use ZC sequences of different cyclic shift values in the time domain or different Walsh sequences. In this case the length of ZC sequences in the time domain is 12, so that it is possible to use twelve ZC sequences with cyclic shift values "0" - "11" generated from the same ZC sequence. Moreover, the length of Walsh sequences is 4, so that it is possible to use four different Walsh sequences. Therefore, under ideal communication conditions may be multiplexed with code division maximum of forty eight (12 × 4) response signals from mobile stations.
In this case there is no cross-correlation between ZC sequences of different cyclic shift values generated from the same ZC sequence. Therefore, in an ideal communication environment, as shown in Figure 2, a plurality of response signals subjected to expansion and code division multiplexed using ZC sequences of different cyclic shift values (0 to 11) can be separated in the time domain without any intercode interference by correlation processing in the base station.
However, due to the influence of, for example, differences in the time parameters in the transmission in mobile stations, multipath delay waves and frequency offsets, a plurality of response signals from a plurality of mobile stations do not always reach the base station simultaneously. For example, as shown in Figure 3, if transmission timings of the response signal, via extended ZC sequence with a cyclic shift value "0" is delayed with respect to the best transmission timings, the peak correlation with ZC sequences of cyclic shift value "0" may appear in the detection window for the ZC sequence with a cyclic shift value "1". Further, as shown in Figure 4, if the response signal expanded using ZC sequence with a cyclic shift value "0" has a delay wave, interference due to interference from the delayed wave may appear in the detection window for the ZC sequence with a cyclic shift value "1". Therefore, in these cases, the deteriorated performance of the separation between the signal response using extended ZC sequence with a cyclic shift value "0" and a response signal, via extended ZC sequence with a cyclic shift value "1". Thus, when using ZC sequence with adjacent cyclic shift values, the signal separation performance of response may deteriorate.
So far, if a plurality of response signals code division multiplexed by expansion using ZC sequences, a sufficient cyclic shift value difference (i.e. cyclic shift interval) is provided between ZC sequences, to an extent that causes no intercode interference between sequences ZC. For example, when the difference between the values of the cyclic shift ZC sequence is 4, only three ZC sequence with a cyclic shift value "0", "4" and "8" of twelve ZC sequence with a cyclic shift value "0" - "11" are used for first expansion response signals. Therefore, if Walsh sequences with a sequence length of 4 are used for the second extension response signals, it is possible to code division multiplex maximum twelve (3 × 4) response signals from mobile stations.
Non-Patent Document 1: Multiplexing capability of CQIs and ACK / NACKs form different UEs (ftp://ftp.3gpp.org/TSG_RAN/WGl_RLl/TSGRl_49/Docs/Rl-072315.zip).
Disclosure of invention
Problems to be solved by the present invention.
As described above, if a Walsh sequence with a sequence length of 4, (W0, W1, W2, W3) used for the second extension, one response signal is allocated to each of four symbols (S0-S3). Therefore, the base station that receives response signals from mobile stations needs to despread signals in the response time period of four symbols. On the other hand, if the mobile station moves fast, there is a high possibility that the channel conditions between the mobile station and the base station change during the above time period of four symbols. Therefore, when there exists a mobile station that moves fast, orthogonality between Walsh sequences that are used for the second extension may be violated. Thus, when there are mobile stations that are moving quickly, more likely that any intercode interference between Walsh sequences than between ZC sequences, and by performing signal separation response deteriorates.
Incidentally, when some of the plurality of mobile stations moves fast and the rest of mobile stations are in a stationary mode, the mobile stations in the stationary state, which are multiplexed with moving axially fast Walsh mobile stations, also under the influence of intercode interference.
Therefore, an object of the present invention to provide a radio communication apparatus and method for expanding a response signal that can minimize deterioration of the separation performance of response signals that are code division multiplexed.
Means for Solving the Problems
The radio communication apparatus of the present invention employs a configuration having a first spreading unit which performs a first expansion of the spectrum response signal using one of a plurality of first sequences that can be separated from each other because of different cyclic shift values; and link second spreading, which performs the second expansion of the spectrum response signal subjected to first spreading using one of a plurality of second sequences, wherein a difference between cyclic shift values of the first sequences associated with different adjacent second sequences, is less than a difference between cyclic shift values of the first sequence connected to the same second sequence.
Useful EFFECT
According to the present invention can minimize the deterioration of the separation performance of code division multiplexed response signals.
BRIEF DESCRIPTION OF THE DRAWINGS
1 - diagram shows a way to expand the spectrum of response signals (prior art);
2 - a diagram which shows correlation processing of response signals, enhanced by ZC sequences (in the case of the ideal communication environment);
Figure 3 - schematic diagram which shows correlation processing of response signals, enhanced by ZC sequences (when there is a difference in transmission timings);
4 - diagram shows the correlation signal processing response, extended by a sequence ZC (when there is a delay wave);
5 - a block diagram showing a configuration of a base station according to Embodiment 1 of the present invention;
Figure 6 - a block diagram showing a configuration of a mobile station according to Embodiment 1 of the present invention;
Figure 7 - schematic diagram show mappings between ZC sequences, Walsh sequences and PUCCH channels according to embodiment 1 of the present invention (variation 1);
8 - a diagram which shows the mapping between the first sequences, second sequences and PUCCH channels according to embodiment 1 of the present invention;
9 - diagram show mappings between ZC sequences, Walsh sequences and PUCCH channels according to embodiment 1 of the present invention (variation 2);
Figure 10 - a schematic diagram which shows the mapping between ZC sequences, Walsh sequences and PUCCH channels according to embodiment 1 of the present invention (variation 3);
11 shows Walsh sequences according to Embodiment 2 of the present invention;
12 - diagram show mappings between ZC sequences, Walsh sequences and PUCCH channels according to Embodiment 2 of the present invention;
13 - diagram show mappings between ZC sequences, Walsh sequences and PUCCH channels according to an embodiment 3 of the present invention (variation 1);
14 - diagram show mappings between ZC sequences, Walsh sequences and PUCCH channels according to an embodiment 3 of the present invention (variation 2); and
Figure 15 - a schematic diagram which shows a way to expand the reference signal.
PREFERRED EMBODIMENTS
Embodiments of the present invention will be explained in detail below with reference to the accompanying drawings.
(Embodiment 1)
5 shows a configuration of base station 100 according to this embodiment, and Figure 6 shows the configuration of mobile station 200 according to the present embodiment.
In this case, to avoid complicated explanation, Figure 5 shows components associated with transmission of downlink data and components associated with reception of uplink response signals to downlink data, which are closely related to the present invention, and illustration and an explanation of components associated with reception of uplink data will be omitted. Similarly, Figure 6 shows components associated with reception of downlink data and components associated with transmission of uplink response signals to downlink data, which are closely related to the present invention, and illustration and explanation of the components associated with the transmission of uplink data will be omitted.
Furthermore, in the following explanation, a case will be described where ZC sequences are used for the first extension, and a Walsh sequence used for second extension. In this case, the first expansion than ZC sequences, equally possible to use sequences that can be separated from each other because of different cyclic shift values. Similarly, for the second expansion is equally possible to use orthogonal sequences other than Walsh sequences.
Further, in the following explanation, a case will be described when using ZC sequence with a sequence length of 12 and Walsh sequences with a sequence length of 4, (W0, W1, W2, W3). However, the present invention is not limited to these sequence lengths.
Further, in the following explanation, twelve ZC sequence with a cyclic shift value "0" - "11" will be referred to as "ZC # 0" - "ZC # 11," and four Walsh sequences of sequence numbers "0" - "3" will be referred to as a «W # 0» - «W # 3."
Additionally, with the following explanation, the case when the channel CCH L1 / L2 # 1 takes an element CCE # 1, channel CCH L1 / L2 # 2 takes the element CCE # 2, channel CCH L1 / L2 # 3 takes the element CCE # 3, the channel CCH L1 / L2 # 4 takes an element CCE # 4 and CCE # element 5, the channel CCH L1 / L2 # 5 takes an element CCE # 6 and # 7 element CCE channel CCH L1 / L2 # 6 takes an element CCE # 8- # 11 etc.
Further, in the following explanation, the element number CCE numbers and PUCCH channel, determining the values of the cyclic shift ZC sequences and Walsh sequence numbers, are displayed on one-to-one basis. Thus, the element CCE # 1 is mapped to PUCCH # 1, channel element CCE # 2 is mapped to PUCCH # 2 channel element CCE # 3 is mapped to channel PUCCH # 3, etc.
In base station 100 shown in Figure 5, link 101 and control information generation unit 104 display accept as input resource allocation result of downlink data.
Unit 101 generates control information generating control information for carrying resource allocation result, on the basis of the mobile station, and outputs the control information to the link 102 encoding. Management information provided to the mobile station includes identifier information (ID) of the mobile station, to indicate which of the mobile stations control information is directed. For example, control information includes, as mobile station ID information, CRC masked number ID of the mobile station that transmits control information. Control information is encoded in unit of coding section 102, modulated in modulation link 103 and receives as input information to link the display 104 based on the mobile station. Further, the unit 101 control information generating allocates each mobile station is arbitrary channel CCH L1 / L2 of the plurality of channels CCH L1 / L2, based on the number of elements CCE, required for transmitting control information, and outputs the number of the element CCE, corresponding distribution channel CCH L1 / L2 , 104 to the link display. For example, when the number of elements CCE, required for transmitting control information to mobile station # 1 is one, and therefore the channel CCH L1 / L2 # 1 allocated mobile station # 1, unit 101 control information generating outputs the number of the element CCE # 1 to the link 104 display. Furthermore, when the CCE number of elements, required for transmitting control information to mobile station # 1 is four and therefore channel CCH L1 / L2 # 6 allocated mobile station # 1, unit 101 outputs the control information generating element numbers CCE # 8- # 11 to the link 104 displayed.
On the other hand, encoding unit 105 encodes transmission data for each mobile station (i.e. downlink data) and outputs the encoded transmission data to the link 106 retransmission control.
At initial transmission unit 106 controls the retransmission contains coded data transmission based on the mobile station and outputs the data to the link 107 modulation. Link 106 contains the retransmission control data transmission unit 106 is a retransmission control not accept as input ACK from each mobile station unit 116 solutions. Further, upon receiving as input a NACK of each mobile station from the link 116 solutions, i.e. upon retransmission, retransmission control unit 106 outputs transmission data transfer associated with this NACK, to the link 107 modulation.
Unit 107 modulates encoded transmission data received as input from unit 106 controls the retransmission, and outputs the result to the link 104 displayed.
When transmitting control information unit 104 maps the control information received as input from managers 103 modulation on a physical resource based on the number of the element CCE, received as input from managers 101 generating control information, and outputs the result to the link 108 IFFT . Thus, the display unit 104 displays control information on the subcarrier corresponding to the CCE number of the element, a plurality of subcarriers, comprising OFDM symbol, based on the mobile station.
On the other hand, when transmitting downlink data mapping unit 104 maps transmission data on a basis of a mobile station on a physical resource based on the resource allocation result, and outputs the result to the link 108 IFFT. Thus, based on the result of resource allocation unit 104 maps the transmission data on a subcarrier of a plurality of subcarriers, comprising OFDM symbol, based on the mobile station.
IFFT unit 108 generates an OFDM symbol by performing IFFT plurality of subcarriers on which display control information or data transfer, and outputs the OFDM symbol to a link 109 joining CP (cyclic prefix).
Link 109 attaches the attachment prefix CP is the same signal as a signal to the tail part of the OFDM symbol, to the header of the OFDM symbol as a prefix CP.
The radio transmitting unit 110 performs transmission processing such as D / A (digital-analog) conversion, amplification and up-conversion to OFDM symbol prefix CP, and transmits the result from antenna 111 to mobile station 200 (Figure 6).
On the other hand, radio receiving unit 112 receives a response signal transmitted from the mobile station 200, via antenna 111, and performs processing upon receiving such as downconversion and A / D (analog-digital) conversion of the response signal.
Prefix removal unit 113 removes the CP prefix CP, connected to the signal response processed at the reception.
Unit 114 despreads the response signal by a Walsh sequence that is used during the second expansion in the mobile station 200, and outputs the compressed signal response to the link 115 of the correlation processing.
The correlation processing unit 115 finds the correlation value between the response signal, received as input from the compression unit 114, i.e. a response signal, via extended ZC sequence and ZC sequence, which is used for expansion in the first mobile station 200, and outputs the correlation value to the link 116 solutions.
Solutions unit 116 detects the correlation peak based on the mobile station using the detection window set for the mobile station in the time domain, thereby recognizing a response signal based on the mobile station. For example, after the detection of the correlation peak in detection window # 1 for mobile station # 1, solutions unit 116 detects the response signal from mobile station # 1. Then solutions unit 116 decides whether the recognized response signal ACK or NACK, and outputs the ACK or NACK to the link 106 retransmission control based on the mobile station.
On the other hand, in mobile station 200 shown in Figure 6, the radio receiving unit 202 receives the OFDM symbol, transmitted from the base station 100 via antenna 201 and performs reception processing such as down-conversion and A / D conversion of the OFDM symbol .
Prefix removal unit 203 removes the CP prefix CP, connected to the OFDM symbol, subjected to reception processing.
Unit 204 FFT (Fast Fourier Transform) is control information or downlink data displayed on a plurality of subcarriers by performing the FFT OFDM symbol, and outputs the control information or downlink data to the link 205 extract.
When receiving the control information extracting unit 205 extracts the control information from a plurality of subcarriers and outputs it to the link 206 demodulation. This control information is demodulated in demodulating link 206, link 207 is decoded in the decoding and receiving as input link 208 in solutions.
On the other hand, upon receiving downlink data unit 205 extracting extracts the downlink data directed to the mobile station, from a plurality of subcarriers, based on the result of resource allocation received as input from unit 208 solutions, and outputs the downlink data 210 to the link demodulation. This downlink data is demodulated in demodulating link 210, link 211 is decoded in the decoding and receiving as input in CRC link control 212.
Control unit 212 performs CRC error detection of the decoded downlink data using CRC, generates an ACK if CRC = OK (i.e. when no error is found) and a NACK if CRC = NG (i.e. when error is found) in as a response signal, and outputs the generated response signal to the link 213 modulation. Further, in the case of CRC = OK (i.e. when no error is found), CRC unit 212 outputs the decoded downlink data as received data.
Solutions unit 208 performs "blind" detection of whether to send the mobile station the control information received as input from decoding unit 207. For example, solutions unit 208 decides that, if CRC = OK found (i.e. if error is found) as a result of demasking by the ID numbers of the mobile station, the control information directed to the mobile station. Additionally, solutions unit 208 outputs control information directed to the mobile station, i.e. resource allocation result of downlink data for the mobile station 205 to the link recovery. Additionally, the unit 208 decides which channel solutions PUCCH to use to transmit a response signal from the mobile station, from the number of the element CCE, associated with subcarriers on which display control information directed to the mobile station, and outputs a certain result (ie the number of the PUCCH ) 209 to the link control. For example, if control information is mapped to subcarriers corresponding element CCE # 1, the link 208 solutions of mobile station 200 allocated to the channel CCH L1 / L2 # 1 decides that the channel PUCCH # 1 is mapped to CCE # 1 is channel PUCCH for that mobile station. For example, if control information is mapped to subcarriers corresponding elements CCE # 8-CCE # 11, the link 208 solutions of mobile station 200 allocated to the channel CCH L1 / L2 # 6 decides that the channel PUCCH # 8, is mapped to CCE # 8, which has a minimum number of elements among CCE # 8-CCE # 11, is the PUCCH channel, directed to the mobile station.
Based on the channel PUCCH, received as input from unit 208 decision unit 209 controls the cyclic shift value sequence ZC, which is used for the first expansion in a link 214, the expansion and the Walsh sequence that is used during the second expansion in the link 217 extension . Thus, link 209 control sets the link 214 extension ZC sequence with a cyclic shift value, shown on the channel PUCCH, received as input from unit 208 solutions, and sets the link 217 extension Walsh sequence mapped to the channel PUCCH, the received as input from unit 208 solutions. Sequence of operations in a link control 209 will be described in detail later.
Link 213 modulates the response signal received as input from the control unit 212 CRC, and outputs the result to the link 214 extensions.
As shown in Figure 1, the expansion unit 214 performs a first expansion response signal using ZC sequences, a fixed control link 209, and outputs the response signal subjected to the first extension, a link 215 IFFT.
As shown in Figure 1, the IFFT unit 215 performs IFFT response signal subjected to the first extension, and outputs the response signal subjected to IFFT unit 216 at attachment prefix CP.
Link connection prefix CP 216 attaches the same signal as the tail part of the response signal subjected to an IFFT, to the title of the response signal as a prefix CP.
As shown in Figure 1, the expansion unit 217 performs a second extension response signal with a prefix CP by the Walsh sequence set in control link 209, and outputs the response signal subjected to second expansion unit 218 in the radio transmission.
The radio transmitting unit 218 performs transmission processing such as D / A conversion, amplification and frequency conversion to increase the response signal subjected to the second extension, and transmits the resulting signal from antenna 201 to base station 100 (Figure 5).
According to the present embodiment, the response signal subjected to two-dimensional spreading using first expansion ZC sequence and second expansion using Walsh sequences. Those. the present embodiment extends the response signal on the cyclic shift axis and the Walsh axis.
Further details will be explained the control sequence in a link control 209 (Figure 6).
If ZC sequences are used for the first extension response signal, as described above, a sufficient cyclic shift value difference (e.g. cyclic shift value difference of 4) provided between the ZC sequences, to the extent not appear when the intercode interference between ZC sequences. Therefore, it is unlikely violation of orthogonality between response signals subjected to the first extension, using ZC sequence with different cyclic shift. In contrast, as described above, when there exists a mobile station that moves fast, orthogonality between breach likely Walsh sequences used for the second extension.
Therefore, the present embodiment controls ZC sequences and Walsh sequences according to the mappings shown in Figure 7, so that the interference components which remain in the response signal subjected to compression in the compression member 114 (Figure 5) is taken up in a small difference between cyclic shift values of ZC sequences. Thus, the unit 209 controls the cyclic shift values of ZC sequences that are used for the first expansion in a link extension 214 and Walsh sequences that are used smiling during the second expansion in the expansion link 217, according to the display shown in Figure 7.
7 shows the channel PUCCH # 1 to ZC # 0 and W # 0, PUCCH # 2 channel to ZC # 4 and W # 0, PUCCH # 3 channel to ZC # 8 and W # 0, PUCCH # 4 channel to ZC # 1 and W # 1, channel PUCCH # 5 to ZC # 5 and W # 1, channel PUCCH # 6 to ZC # 9 and W # 1, channel PUCCH # 7 to ZC # 2 and W # 2, Channel PUCCH # 8 to ZC # 6 and W # 2, Channel PUCCH # 9 to ZC # 10 and W # 2, Channel PUCCH # 10 to ZC # 3 and W # 3, the channel PUCCH # 11 to ZC # 7 and W # 3, and channel PUCCH # 12 to # 11 and ZC W # 3.
Therefore, for example, upon receiving as input PUCCH channel # 1 from solutions unit 208, control unit 209 sets ZC # 0 in the link 214 to expand and W # 0 in the link 217 extension. Furthermore, for example, upon receiving as input PUCCH # 2 channel from link 208 solutions, control unit 209 sets ZC # 4 in the link 214 to expand and W # 0 in the link 217 extension. Furthermore, for example, upon receiving as input PUCCH # 4 channel from link 208 solutions, control unit 209 sets ZC # 1 in the link 214 to expand and W # 1 in the link 217 extension.
In this case, in Figure 7, ZC sequences for first expansion using W # 1 in second extension (i.e. ZC # 1, ZC # 5 and ZC # 9) was obtained by performing one cyclic shift of ZC sequences for first expansion using W # 0 in the second extension (i.e. ZC # 0, ZC # 4 and ZC # 8). Also, ZC sequences for first expansion using W # 2 in the second extension (i.e. ZC # 2, ZC # 6 and ZC # 10) is obtained by performing one cyclic shift of ZC sequences for first expansion using W # 1 the second extension (i.e. ZC # 1, ZC # 5 and ZC # 9). Also, ZC sequences for first expansion using W # 3 in second extension (i.e. ZC # 3, ZC # 7 and ZC # 11) is obtained by performing one cyclic shift of ZC sequences for first expansion using W # 2 the second extension (i.e. ZC # 2, ZC # 6 and ZC # 10).
Furthermore, in Figure 7, the difference between the cyclic shift values of ZC sequences, are displayed on different adjacent Walsh sequences, is less than a difference between cyclic shift values of ZC sequences, are displayed on the same Walsh sequence. For example, when the difference between cyclic shift values is 1 between ZC # 0 mapped to W # 0 and ZC # 1 mapped to W # 1, the difference between cyclic shift values is 4 between ZC # 0 and ZC # 4 displayed on W # 0.
Thus, in Figure 7, ZC sequence subjected to cyclic shift by one every time the sequence number is increased by one Walsh sequence. Thus, in the present embodiment, the minimum difference is 1 between the cyclic shift values of ZC sequences, displayed in adjacent Walsh sequences. In other words, in Figure 7, adjacent Walsh sequences are mapped to ZC sequences of different cyclic shift values and used for two-dimensional spreading response signals. Therefore, even when intercode interference between Walsh sequences occur due to violations of the orthogonality between Walsh sequences, it is possible to suppress the interference by intercode extension using sequence ZC. For example, referring to Figure 7, a response signal that is transmitted using PUCCH channel # 4 is subjected to two-dimensional spreading using ZC # 1 and W # 1 and the response signal that is transmitted using PUCCH # 7, the channel is subjected to two-dimensional spreading, using ZC # 2 and W # 2. Therefore, even when the intercode interference between W # 1 and W # 2 arise due to violation of the orthogonality between W # 1 and W # 2, it is possible to suppress the intercode interference by a slight difference between the cyclic shift values of ZC # 1 and ZC # 2.
On the other hand, in Figure 7, as ZC # 1 and ZC # 2 using ZC sequence with adjacent cyclic shift values, i.e. ZC sequences, between which a cyclic shift value difference is "1". Thus, orthogonality between ZC sequence can be disrupted, causing interference between sequences intercode ZC. However, in Figure 7, ZC sequences, between which a cyclic shift value difference is "1", is displayed on different Walsh sequences and used for two-dimensional spreading response signals. Therefore, even when intercode interference between ZC sequence arise from the violation of orthogonality between the ZC sequence, can be suppressed intercode interference by extension using Walsh sequences. For example, referring to Figure 7, a response signal that is transmitted using PUCCH channel # 4 is subjected to two-dimensional spreading using ZC # 1 and W # 1 and the response signal that is transmitted using PUCCH # 7, the channel is subjected to two-dimensional spreading, using ZC # 2 and W # 2. Therefore, even when there intercode interference between ZC # 1 and ZC # 2, it is possible to suppress the intercode interference by the difference between the sequences of W # 1 and W # 2.
Thus, the present embodiment eliminates a violation of the orthogonality of the Walsh axis (i.e. intercode interference between Walsh sequences), on the cyclic shift axis and eliminates the violation of the orthogonality of cyclic shift axis (i.e. intercode interference between ZC sequences), on the Walsh axis. In other words, the present embodiment compensates intercode interference between Walsh sequences caused by the violation of the orthogonality between the Walsh sequences, by extending the gain sequence ZC, and compensates intercode interference between sequences ZC caused by violation of the orthogonality between the sequences ZC, by expanding gain Walsh sequence . Therefore, according to the present embodiment can minimize the deterioration of the separation performance of code division response signals.
Figure 8 summarizes the display shown in Figure 7. Thus, Figure 8 shows a case where signals extend with the plurality of first sequences that can be separated from each other because of different cyclic shift values and a plurality of orthogonal second sequences. Thus, according to Figure 8, when the difference between cyclic shift values of the plurality of first sequences mapped to the same second sequence is «k», difference between cyclic shift values of the plurality of first sequences mapped to a plurality of adjacent second sequences is equal to «Δ »(Δ <k). Thus, the first sequence in Figure 8 are shifted by Δ every time the second sequence number is incremented.
Furthermore, as described above, the present embodiment can compensate intercode interference between Walsh sequences by extending the ZC sequence gain, and compensate intercode interference between ZC sequences by extending the gains of the Walsh sequence. Therefore it is possible to make a difference between cyclic shift values of ZC sequences, are displayed on the same Walsh sequence less than "4" in Figure 7. 9 shows a case where the difference is equal to "2". While the twelve PUCCH channel PUCCH # 1, PUCCH # 12-visible in Figure 7, twenty-four PUCCH channel PUCCH # 1, PUCCH # 24-9 available. In other words, while twelve code resources of forty-eight code resources are used in Figure 7, twenty-four code resources of forty-eight code resources are used in Figure 9. Thus, the present embodiment can increase the efficient use of limited resources and code to make the most efficient use of code resources.
Furthermore, if the display is used, as shown in Figure 10, it may equally lead to the same result as in the case of correspondences, shown in Figure 9.
(Embodiment 2)
As shown in Figure 11, when W # 0 (1, 1, 1, 1) and W # 1 (1, -1, 1, -1), first knots with two chips in W # 0 and W # 1 orthogonal to each other and second nodes with two elementary signals are orthogonal to each other. Similarly, when W # 2 (1, 1, -1, -1) and W # 3 (1, -1, -1, 1), first knots with two chips in W # 2 and W # 3 are orthogonal to each other, and second nodes with two elementary signals are orthogonal to each other. Therefore, if the change of channel condition is sufficiently small during two symbol time periods, the intercode interference can not occur between W # 0 and W # 1, and the intercode interference will not occur between W # 2 and W # 3. Therefore it is possible to divide the plurality of response signals subjected to code division multiplexing with the second expansion using W # 0 and W # 1, the first nodes to the two elementary signals and second knots with two chips. Similarly, we can split the set of response signals subjected to code division multiplexing by expansion using W # 2 and W # 3, the first knots with two elementary signals and second nodes with two chips.
Therefore, with the present embodiment, unit 209 controls the cyclic shift value sequence ZC, which is used for the first expansion in a link 214, the expansion and the Walsh sequence that is used during the second expansion in the link 217 extension according to the maps shown in 12. 12 is the value of cyclic shift ZC sequences, displayed in W # 0 and the cyclic shift values of ZC sequences, displayed on W # 1 are the same in 0, 2, 4, 6, 8 and 10, and the values of the cyclic shift ZC sequences displayed in W # 2 and the cyclic shift values of ZC sequences mapped to W # 3 are the same in 1, 3, 5, 7, 9 and 11.
In this case, for example, to separate the response signal subjected to second expansion W # 0 when W # 0, W # 1 and W # 2 are used for the second expansion at the same time, computes the sum of S0, S1, S2 and S3 in Figure 1. Thus it is possible to remove the response signal components that are extended by W # 1 and W # 2, from the received signal. However, if the mobile station that uses W # 1 and mobile station that uses W # 2 move fast, the difference is due to the channel change remains in the separated response signal as the intercode interference.
Thus, with respect to W # 1, S0 and S1 have different signs, and therefore the response signal component, which is extended by W # 1 is removed by adding S0 and S1. But intercode interference Δ # 1 by channel change remains in the separated response signal. If the channel change linearly, just intercode interference Δ # 1 remain in the separated response signal between S2 and S3. Therefore, interference intercode 2 × Δ # 1 is completely remain in the separated response signal.
On the other hand, with respect to W # 2, S0 and S1 have the same sign, and therefore response signal components that are extended by W # 2 are removed using the differences between characters S2 and S3. In this case intercode interference of 4 × Δ # 2 remain fully separated response signal.
Thus intercode interference between a plurality of response signals subjected to code division multiplexing is reduced by using a plurality of Walsh sequences in which the first components two elementary signals are orthogonal to each other and second nodes with two elementary signals are orthogonal to each other. Therefore, the present embodiment uses different Walsh sequences with little intercode interference (e.g., W # 0 and W # 1) in combination with ZC sequence having the same cyclic shift values, and uses different Walsh sequences with significant intercode interference (e.g., W # 0 and W # 2) in combination with ZC sequences of different cyclic shift values.
As described above, according to the present embodiment, by performing the second expansion response signals using Walsh sequences in which parts of the sequences shorter than the sequence length are orthogonal to each other, it is possible to improve the error resilience during fast movement of mobile stations.
(Embodiment 3)
In code division multiplexing via first enlargement using ZC sequences, i.e. when code division multiplexing on the cyclic shift axis, as described above, a sufficient difference is provided between the cyclic shift values of ZC sequences, to an amount which does not cause intercode interference between ZC sequences. Therefore, violation of orthogonality between the ZC sequence is unlikely. Furthermore, even if there exists a mobile station that moves fast, orthogonality between ZC sequences is not impaired. On the other hand, when code division multiplexed by the second expansion using Walsh sequence, i.e. when code division multiplexing on the Walsh axis, as described above, orthogonality between Walsh sequences is likely to be broken when it is a mobile station that moves fast. Therefore, when multiplexing code division response signals with a second expansion may be preferable to increase the average multiplexing axis cyclic shift, where it is unlikely that the orthogonality disrupted, and decrease the average multiplexing axis Walsh where a high possibility that the orthogonality disturbed. Furthermore, it may be preferable to equalize (unify) the multiplexing level on the Walsh axis between ZC sequences so that the multiplexing level on the Walsh axis was not extremely high only in a response signal subjected to first expand by a certain ZC sequence. Thus, when the response signal subjected to two-dimensional spreading and by the cyclic shift axis and the Walsh axis, it may be preferable to reduce the average multiplexing level on the Walsh axis and equalize (unify) the multiplexing levels on the Walsh axis between ZC sequences.
Thus, the present embodiment controls ZC sequence and Walsh sequences based on the maps shown in Figure 13. Thus, the unit 209 controls the cyclic shift value of the ZC sequence that is used for expansion in the first expansion link 214, and the Walsh sequence that is used during the second expansion in the expansion link 217 based on the mappings shown in Figure 13.
In this case, when displaying elements CCE # 1-CCE # 12 to PUCCH channels # 1-PUCCH # 12, as shown in Figure 13, the use probability P of physical resources for response signals (i.e. physical resources for PUCCH channel) corresponding to the number of the element, or CCE CCE priority level element, the element is reduced in order CCE # 1, CCE # 2 item ... element CCE # 11 and CCE # 12 element. Thus, when the CCE number of the element increases, the above probability P monotonically decreases. Therefore, the present embodiment displays on the PUCCH channel ZC sequences and Walsh sequences, as shown in Figure 13.
Thus, referring to the first and second rows along the Walsh axis (i.e. W # 0 and W # 1) 13, the multiplexed channel PUCCH # 1 and PUCCH # 6 channel and multiplexed channel PUCCH # 2 and PUCCH channel #5. Therefore, the amount of channel numbers PUCCH channel PUCCH # 1 and channel PUCCH # 6 "7" is the sum of channel numbers PUCCH channel PUCCH # 2 and channel PUCCH # 5 "7". Thus, on the Walsh axis PUCCH channel with small numbers and the channel PUCCH associated with large numbers and partitioned. The same applies to the channel PUCCH # 3, PUCCH # 4 channel and channel PUCCH # 7-PUCCH # 12. Further, the same applies to the third row (W # 2) and fourth row (W # 3) on the Walsh axis. Thus, at 13, between adjacent ZC sequences, the sum channel PUCCH numbers (i.e. the sum of components CCE numbers) of adjacent Walsh sequences is equal. Therefore, in Figure 13, the average multiplexing levels on the Walsh axis are substantially equal (substantially the same).
Also, to equalize (standardizing) the multiplexing level on the Walsh axis between ZC sequences, when the difference between cyclic shift values of ZC sequences, are displayed on the same Walsh sequence is "2" (9), preferably to control ZC sequences and Walsh sequences based on the mappings shown in Figure 14.
When displaying the elements CCE # 1 - CCE # 24 on channel PUCCH # 1-PUCCH # 24, as shown in Figure 14, the probability P of using natural resources for response signals corresponding to the number of the element, or CCE priority level elements CCE, decreases in the order of items CCE # 1, CCE # 2 item ... element CCE # 23 and CCE # 24 element. Thus, as described above, when the CCE number of the element increases, the above probability P monotonically decreases.
Turning to the first and third rows on the Walsh axis (ie W # 0 and W # 2) 14, multiplex channel PUCCH # 1 and channel PUCCH # 18, and multiplexed channel PUCCH # 2 and channel PUCCH # 17. Therefore, the sum of channel numbers PUCCH channel PUCCH # 1 and channel PUCCH # 18, "19" is the sum of channel numbers PUCCH channel PUCCH # 2 and channel PUCCH # 17, "19". Further, referring to the second and fourth rows along the Walsh axis (i.e. W # 1 and W # 3) 14, the multiplexed channel PUCCH # 12 and PUCCH channel # 19 and channel multiplexed PUCCH # 11 and PUCCH channel #20. Therefore, the sum of channel numbers PUCCH channel PUCCH # 12 and channel PUCCH # 19, "31" is the sum of channel numbers PUCCH channel PUCCH # 11 and channel PUCCH # 20, "31". Thus, on the Walsh axis PUCCH channels with small numbers of channels and PUCCH numbers are associated with large and distributed. The same applies to the channel PUCCH # 3, PUCCH # 10 channel, 13 channel PUCCH #-PUCCH # 16 and PUCCH # 21 channels-PUCCH # 24. Thus, in Figure 14, similar to 13, between adjacent ZC sequences, the sum channel PUCCH numbers (i.e. the sum of components CCE numbers) of adjacent Walsh sequences is equal. Therefore, in Figure 14, like Figure 13, the average multiplexing levels on the Walsh axis are substantially equal (substantially the same).
Thus, the present embodiment displays the channel PUCCH (ie elements CCE) sequences, which are used for the two-dimensional extension, based on the probability P of using natural resources for response signals corresponding to the number of the element, or CCE priority level elements CCE. Thus, the average multiplexing level on the Walsh axis, i.e. Expected values of the numbers of channels multiplexed on PUCCH Walsh axis are substantially equal (or substantially equal). Thus, according to the present embodiment, the multiplexing level on the Walsh axis is not extremely high only in a response signal subjected to first expand by a certain ZC sequence, so that it is possible to minimize the influence when orthogonality between Walsh sequences is broken. Therefore, according to the present embodiment can further reduce the deterioration in the separation performance of response signals subjected to code division multiplexing with the second extension.
Embodiments of the present invention are described above.
In addition, 7, 9, 10, 12, 13 and 14 show the case of using four Walsh sequences of W # 0-W # 3. But in the case of using two, three, five or more Walsh sequences, it is equally possible to implement the present invention in the same manner as above.
Furthermore, the above embodiment shows a configuration to compensate intercode interference between Walsh sequences by extending the ZC sequence gain. However, the present invention can be applied not only to cases where complete orthogonal sequences such as Walsh sequences are used for the second extension, but also to cases where, for example, incomplete orthogonal sequences such as P / N (PN) sequences used for the second extension. In this case, the intercode interference due to the incomplete orthogonality of P / N sequences offset by gain expansion ZC sequence. Thus, the present invention can be applied to any wireless devices that use sequences, which can be separated from each other based on the difference of values of the cyclic shift for the first expansion, and sequences that can be separated on the basis of differences of sequences, for the second extension.
Furthermore, by using the above embodiment has been described a case where a plurality of response signals from a plurality of mobile stations are multiplexed with code division. But it is equally possible to implement the present invention, even when a plurality of reference signals (e.g. pilot signals) from a plurality of mobile stations are multiplexed with code division. As shown in Figure 15, when three symbols of reference signals R0, R1 and R2 are generated from a ZC sequence (with a sequence length of 12), first ZC sequence subjected to IFFT together with orthogonal sequences (F0, F1, F2) with a sequence length of 3. this can be obtained IFFT ZC sequence with a sequence length of 12 in the time domain. Then, the signal subjected to IFFT expanding using orthogonal sequences (F0, F1, F2). Thus, one reference signal (i.e. ZC sequence) to three symbols partitioned R0, R1 and R2. Similarly, other mobile stations allocate one reference signal (i.e. ZC sequence) to three symbols R0, R1 and R2. In this case, individual mobile stations use ZC sequences of different cyclic shift values in the time domain or different orthogonal sequences. In this case, the sequence length of ZC sequences in the time domain is 12, so that it is possible to use twelve ZC sequences with cyclic shift values "0" - "11" generated from the same ZC sequence. Also, the sequence length of orthogonal sequences is 3, so that it is possible to use three different orthogonal sequences. Therefore, under ideal communication conditions may be multiplexed with code division maximum thirty-six (12 × 3) response signals from mobile stations.
Furthermore, the channel PUCCH, is used in the above embodiments is the channel for the return of an ACK or NACK, and therefore may be referred to as "channel ACK / NACK».
In addition, the mobile station may be referred to as "UE" (UE), the base station may be referred to "as the Node B", and a subcarrier may be referred to as a "tone." Additionally, the prefix CP may be referred to as «GI (Guard Interval)."
In addition, the error detection method is not limited to the control of CRC.
Furthermore, a method of performing transformation between the frequency domain and the time domain is not limited to IFFT and FFT.
Furthermore, using the above-described embodiment, a case is described in which the present invention is applied to mobile stations. However, the present invention can also be applied to a fixed radio communication terminal apparatus in a stationary state and a radio communication relay station apparatus that performs the same operations with a base station as a mobile station. Thus, the present invention can be applied to all wireless devices.
Although using the above embodiment described as an example a case in which the present invention is implemented with hardware, the present invention may be implemented by software.
Furthermore, each function block employed in the description of each of the above embodiments may be typically implemented as LSI (large scale integrated circuit) consisting of an integrated circuit. These may be individual chips or partially or totally contained on a single chip. In this case, use "BIS", but it may also be referred to as "IC", "system LSI", "very-large-scale integrated circuit (VLSI)," or "ultra LSI with the degree of integration" depending on differing extents of integration.
Additionally, the method of circuit integration is not limited to LSI's, and implementation is also possible using dedicated circuitry or general purpose processors. After LSI manufacture, use an FPGA (field programmable gate array) or a reconfigurable processor where connections and settings of circuit cells within an LSI can be reconfigured.
Additionally, if there integrated circuit technology that replaces LSI due to the advancement of semiconductor technology or a derivative other technology, of course, also possible to carry out function block integration using this technology. It is also possible to use biotechnology.
The disclosures of Japanese patent application number 2007-159580, filed 15 June 2007, and Japanese patent application number 2007-161966, filed 19 June 2007, which include descriptions, drawings and abstracts, are shown in their entirety by reference.
Industrial applications
The present invention can be applied, for example, mobile communication systems.
Contents4
Every citation, both ways
| Document | Relation | Office |
|---|---|---|
| JP2004253899A | Cites | Japan |
| RU2297731C1 | Cites | Russian Federation |
| WO0010277A1 | Cites | World Intellectual Property Organization (WIPO) |
| WO03026147A1 | Cites | World Intellectual Property Organization (WIPO) |
| WO2005099194A1 | Cites | World Intellectual Property Organization (WIPO) |
83 members in 13 offices
Priority claims14
| Document | Office | Kind | Date |
|---|---|---|---|
| 2007159580 | Japan | – | |
| 2007159580 | Japan | A | |
| 2007159580 | Japan | A | |
| 2007161966 | Japan | – | |
| 2007161966 | Japan | A | |
| 2007161966 | Japan | A | |
| 2008001526 | Japan | W | |
| 2008001526 | Japan | W | |
| 2007159580 | – | – | – |
| 2007161966 | – | – | – |
| JP2008001526 | – | – | – |
| JP20070159580 | – | – | – |
| JP20070161966 | – | – | – |
| WO2008JP01526 | – | – | – |
Members83
| Document | Office | Kind | |
|---|---|---|---|
| WO2008152819A1 | World Intellectual Property Organization (WIPO) | A1 | |
| MX2009011333A | Mexico | A | |
| EP2159925A1 | European Patent Office (EPO) | A1 | |
| KR20100031665A | Republic of Korea | A | |
| US2010118919A1 | United States of America | A1 | |
| CN101720531A | China | A | |
| JP2010136448A | Japan | A | |
| JP2010141923A | Japan | A | |
| JP4505043B2 | Japan | B2 | |
| JPWO2008152819A1 | Japan | A1 | |
| JP4546580B2 | Japan | B2 | |
| US2010296384A1 | United States of America | A1 | |
| US7848299B1 | United States of America | B1 | |
| RU2009146294A | Russian Federation | A | |
| EP2159925A4 | European Patent Office (EPO) | A4 | |
| US8009721B2 | United States of America | B2 | |
| JP4768862B2 | Japan | B2 | |
| JP2011176895A | Japan | A | |
| US2011249707A1 | United States of America | A1 | |
| JP2011211750A | Japan | A | |
| JP4846060B2 | Japan | B2 | |
| JP4872029B1 | Japan | B1 | |
| JP2012029302A | Japan | A | |
| US2012039258A1 | United States of America | A1 | |
| US2012063292A1 | United States of America | A1 | |
| US8179947B2 | United States of America | B2 | |
| EP2458759A2 | European Patent Office (EPO) | A2 | |
| JP4948662B2 | Japan | B2 | |
| US8199792B2 | United States of America | B2 | |
| EP2458759A3 | European Patent Office (EPO) | A3 | |
| JP2012151861A | Japan | A | |
| US8311079B2 | United States of America | B2 | |
| EP2159925B1 | European Patent Office (EPO) | B1 | |
| US2013034077A1 | United States of America | A1 | |
| KR20130019009A | Republic of Korea | A | |
| ES2397112T3 | Spain | T3 | |
| DK2159925T3 | Denmark | T3 | |
| RU2480908C2This record | Russian Federation | C2 | |
| EP2621119A1 | European Patent Office (EPO) | A1 | |
| EP2458759B1 | European Patent Office (EPO) | B1 | |
| ES2425780T3 | Spain | T3 | |
| DK2458759T3 | Denmark | T3 | |
| CN101720531B | China | B | |
| JP5350505B2 | Japan | B2 | |
| JP2014003678A | Japan | A | |
| CN103546227A | China | A | |
| CN103546228A | China | A | |
| RU2012158156A | Russian Federation | A | |
| KR101425249B1 | Republic of Korea | B1 | |
| KR101425326B1 | Republic of Korea | B1 | |
| JP5571835B2 | Japan | B2 | |
| JP2014212559A | Japan | A | |
| RU2537694C2 | Russian Federation | C2 | |
| EP2621119B1 | European Patent Office (EPO) | B1 | |
| US8953544B2 | United States of America | B2 | |
| ES2533346T3 | Spain | T3 | |
| US2015155910A1 | United States of America | A1 | |
| JP5740034B2 | Japan | B2 | |
| EP2892170A1 | European Patent Office (EPO) | A1 | |
| BRPI0812534A2 | Brazil | A2 | |
| HK1212117A1 | Hong Kong, China | A1 | |
| RU2014150994A | Russian Federation | A | |
| US9484982B2 | United States of America | B2 | |
| US2017026077A1 | United States of America | A1 | |
| CN103546227B | China | B | |
| CN103546228B | China | B | |
| RU2014150994A3 | Russian Federation | A3 | |
| RU2678334C2 | Russian Federation | C2 | |
| US10200083B2 | United States of America | B2 | |
| EP2892170B1 | European Patent Office (EPO) | B1 | |
| US2019149188A1 | United States of America | A1 | |
| EP3540989A1 | European Patent Office (EPO) | A1 | |
| PL2892170T3 | Poland | T3 | |
| ES2735877T3 | Spain | T3 | |
| BRPI0812534B1 | Brazil | B1 | |
| RU2019101507A | Russian Federation | A | |
| BR122019021860B1 | Brazil | B1 | |
| US10958303B2 | United States of America | B2 | |
| US2021194537A1 | United States of America | A1 | |
| RU2019101507A3 | Russian Federation | A3 | |
| RU2763957C2 | Russian Federation | C2 | |
| EP3540989B1 | European Patent Office (EPO) | B1 | |
| ES2968530T3 | Spain | T3 |
1 legal event, as the office reported them to INPADOC
Events
| Event | Code | |
|---|---|---|
| Official registration of the transfer of exclusive rightPC41 | PC41 |
Numbers
- Publication
- 0002480908
- Publication, DOCDB
- 2480908
- Publication, EPODOC
- RU2480908
- Application
- 200914629407
- Application, DOCDB
- 2009146294
- Application, EPODOC
- RU20090146294
Titles2
- Russian
- УСТРОЙСТВО БЕСПРОВОДНОЙ СВЯЗИ И СПОСОБ РАСШИРЕНИЯ СИГНАЛА ОТВЕТА
- English
- WIRELESS COMMUNICATION DEVICE AND METHOD OF RESPONSE SIGNAL EXPANSION
Classification
- CPC, 14
- H04B1/7103
- H04J13/0003
- H04J13/18
- H04L5/0055
- H04J13/0048
- H04J13/0062
- H04J13/0074
- H04L5/0053
- H04L1/1858
- H04W88/08
- H04B1/707
- H04L5/0016
- H04L5/005
- H04W72/52
- IPC, 4
- H04B1 707
- H04J11 00
- H04J13 00
- H04J13 18