Circuit and method of operation for an electrical power supply
30 claims: 3 independent, 27 dependent
- 1REIVINDICAÇÕES 1. Um circuito de carregamento de bateria compreendendo:um controlador de carga de bateria (20) configurado para receber potência a partir de uma porta de barramento de série universal «USB» (12) externa, e fornecer potência de saída para um dispositivo portátil (18) e uma bateria recarregável (24);o controlador de carga de bateria sendo ainda configurado para limitar a potência de saída de modo a que o dispositivo portátil e a bateria recarregável não possam absorver mais do que uma corrente máxima predeterminada disponível a partir da porta USB;e um circuito de deteção de tensão (30) configurado para medir uma queda de tensão ao longo do controlador de carga de bateria, e responder à queda de tensão ao longo do controlador de carga de bateria controlando a quantidade de corrente fornecida à bateria recarregável, de modo a que o dispositivo portátil receba uma quantidade predeterminada de potência necessária para funcionar e a bateria recarregável receba um remanescente da potência disponível a partir do controlador de carga de bateria.
- 20 circuito de carregamento de bateria da reivindicação 1, compreendendo ainda:um semicondutor de condução externo ao controlador de carga de bateria (20) e operãvel para transportar corrente de alimentação a partir da porta USB (12) para o dispositivo portátil (18) e a bateria recarregável (24), em que a corrente de alimentação passa através do semicondutor de condução externo em vez de através do controlador de carga de bateria.
- 30 circuito de carregamento de bateria da reivindicação ΕΡ1595324Β1 2, em que o circuito de deteção de tensão (30) inclui um amplificador operacional.
- 40 circuito de carregamento de bateria da reivindicação 3, em que o circuito de deteção de tensão (30) compreende:um amplificador operacional configurado para comparar um sinal de tensão do controlador de carga de bateria (20) com um sinal de tensão de referência, e configurado ainda para responder a uma diferença de tensão na qual o sinal de tensão é inferior à tensão de referência, reduzindo a corrente para a bateria recarregavel (24).
- 50 circuito de carregamento de bateria da reivindicação 3, em que o circuito de deteção de tensão (30) inclui um amplificador operacional para comparar a tensão na saída do controlador de carga de bateria (20) com uma tensão de referência.
- 60 circuito de carregamento de bateria da reivindicação 2, em que os componentes críticos de baixa potência do dispositivo portátil (18) são alimentados a partir do controlador de carga de bateria (20), e os componentes não críticos de elevada potência do referido dispositivo portátil são alimentados a partir da bateria recarregãvel (24) .
- 70 circuito de carregamento de bateria da reivindicação 6, em que os componentes críticos de baixa potência incluem pelo menos um de entre uma memória e um microprocessador.
- 80 circuito de carregamento de bateria da reivindicação 6, em que os componentes não críticos de elevada potência incluem pelo menos um de entre um sistema de iluminação posterior e um vibrador. ΕΡ1595324Β1
- 90 circuito de carregamento de bateria da reivindicação 2, em que o semicondutor’ de condução externo inclui um transístor.
- 100 circuito de carregamento de bateria da reivindicação 4, em que o circuito de amplificador operacional inclui ainda um divisor de tensão para reduzir o sinal de tensão do controlador de carga de bateria e o sinal de tensão de referência é reduzido proporcionalmente.
- 110 circuito de carregamento de bateria da reivindicação 2, em que a corrente máxima predeterminada que pode ser absorvida a partir do referido controlador de carga de bateria (20) é limitada por uma resistência externa a terra.
- 120 circuito de carregamento de bateria da reivindicação 1, compreendendo ainda:um comutador semicondutor acoplado entre o controlador de carga de bateria (20) e a bateria recarregável (24), o comutador semicondutor sendo controlado pelo circuito de deteção de tensão para limitar a quantidade de corrente fornecida à bateria recarregável (24).
- 130 circuito de carregamento de bateria da reivindicação 1, em que o controlador de carga de bateria (20) pode sei' configurado para definir a corrente máxima predeterminada, dependendo dos limites de corrente da porta USB (12).
- 140 circuito de carregamento de bateria da reivindicação 13, em que a corrente máxima predeterminada disponível a partir da porta USB (12) pode ser definida para cerca de 100 mA para uma porta USB de baixa potência e pode ser definida para cerca de 500 mA para uma porta USB de elevada potência. ΕΡ1595324Β1
- 150 circuito de carregamento de bateria da reivindicação 1, em que o controlador’ de carga de bateria (20) é ainda configurado para receber potência de uma fonte não USB.
- 160 circuito de carregamento de bateria da reivindicação 15, em que o controlador de carga de bateria (20) pode ser configurado para definir a corrente máxima predeterminada, dependendo de a potência ser recebida a partir da porta USB (12) ou da fonte não USB.
- 170 circuito de carregamento de bateria da reivindicação 15, em que a fonte não USB é um adaptador de ficha de CA.
- 180 circuito de carregamento de bateria da reivindicação 15, em que a fonte não USB é um adaptador CC/CC para utilização num automóvel.
- 190 circuito de carregamento de bateria da reivindicação 15, em que o controlador’ de carga de bateria (20) pode ser configurado para definir a corrente máxima predeterminada para um de uma multiplicidade de limites de corrente, dependendo de a potência ser recebida a partir de uma porta USB de baixa potência, de uma porta USB de elevada potência ou de uma fonte não USB.
- 200 circuito de carregamento de bateria da reivindicação 1, compreendendo ainda:um comutador semicondutor configurado para isolar a bateria recarregável do dispositivo portátil.
- 210 circuito de carregamento de bateria da reivindicação 20, em que o comutador semicondutor é ainda configurado para:alimentar o remanescente da potência à bateria recarregável. ΕΡ1595324Β1
- 22Q circuito de carregamento de bateria da reivindicação 21, em que o circuito de deteção de tensão é ainda configurado para:controlar a quantidade de corrente fornecida à bateria recarregavel através do comutador.
- 230 circuito de carregamento de bateria da reivindicação 21, em que o circuito de deteção de tensão é ainda configurado para:reduzir a quantidade de corrente fornecida à bateria recarregavel através do comutador;em que a quantidade reduzida de corrente é superior a 0.
- 240 circuito de carregamento de bateria da reivindicação 21, o circuito de deteção de tensão ainda configurado para:determinar uma queda de tensão com base numa comparação de uma primeira tensão ao longo do controlador de carga de bateria com uma tensão de referência.
- 250 circuito de carregamento de bateria da reivindicação 24, em que o circuito de deteção de tensão é ainda configurado para:restringir a quantidade de corrente fornecida à bateria recarregável através do comutador, com base na queda de tensão.
- 260 circuito de carregamento de bateria da reivindicação 1, em que a corrente máxima predeterminada está dentro de uma gama de potência que o controlador de carga de bateria é capaz de dissipar.
- 270 circuito de carregamento de bateria da reivindicação 26, em que o controlador de carga de bateria é ainda configurado para:detetar um estado de funcionamento;ΕΡ1595324Β1 em que a capacidade de potência é baseada no estado de funcionamento.
- 280 circuito de carregamento de bateria da reivindicação 27, em que estado de funcionamento é uma deteção de que a potência recebida é proveniente de uma fonte USB de elevada potência.
- 290 circuito de carregamento de bateria da reivindicação 26, em que o controlador de carga de bateria é ainda configurado para:fornecer uma corrente de alimentação máxima;em que a potência de saída é baseada na corrente de alimentação máxima.
- 30Um método para carregar uma bateria recarregável (24) para um dispositivo portátil (18) utilizando potência fornecida por uma porta de barramento de série universal «USB» (12), compreendendo:recebei' potência a partir da porta USB;fornecer a potência recebida à bateria recarregável e ao dispositivo portátil, em que a potência fornecida é limitada de modo a que a bateria recarregável e o dispositivo portátil não possam absorver mais do que uma quantidade máxima de corrente predeterminada disponível a partir da porta USB;medir, utilizando um circuito de deteção de tensão, uma queda de tensão ao longo de um circuito utilizado para fornecer a potência recebida à bateria recarregável e ao dispositivo portátil;e controlar a quantidade de corrente fornecida à bateria recarregável como uma função da queda de tensão medida, de modo a que o dispositivo portátil receba uma quantidade predeterminada da potência recebida, necessária para funcionar, e a bateria recarregável ΕΡ1595324Β1 receba um remanescente da potência recebida.
Independent claims30
201 paragraphs in 7 sections, as filed
DESCRIPTION
CIRCUIT AND METHOD OF OPERATION FOR ELECTRIC POWER
TECHNICAL FIELD
This invention generally relates to battery chargers, and more specifically to a method and apparatus for charging a battery in a portable communication device from a variety of power sources, including limited capacity sources such as a power node. full power of a computer data bus. Such a computer data bus would be a universal serial bus (USB) port.
BACKGROUND TECHNIQUE
With the current revolution in computing and information, portable electronic devices such as mobile phones, personal digital assistants (PDAs), digital receivers and wireless email devices are becoming very common. These portable devices are typically powered by internal batteries which have to be recharged periodically by an external power supply using a charged battery. Generally, battery chargers receive power from a standard AC power outlet and convert AC power to a low DC voltage to recharge a battery.
The battery chargers of these portable devices also generally employ a 'battery charge controller' to manage battery charging. These battery charge controllers offer features such as:
»Adjust voltage and current levels for the rechargeable battery;
• provide health signals to the handheld's main processor, or
ΕΡ1595324Β1 • if the charging is off, you have to operate one or more operating status LEDs;
• provide protection circuits such as overcurrent, undervoltage, reverse polarity and overtemperature protection circuits; and themselves when the source has been removed to minimize battery discharge.
Lithium-ion battery packs, for example, have to be charged according to a relatively strict algorithm so that they can be fully charged, charged and recharged many times, and safely operated. This loading algorithm generally proceeds as follows:
1. In a first phase, all states of high undervoltage or deep discharge are resolved. During this preload phase, the battery voltage is gradually withdrawn from a very low or off voltage state, usually at a rate of 1/10 of the normal charge current;
2. The battery is then charged at a constant current level until the voltage across the battery reaches its nominal level (consider 4.2 VDC). At this time, the battery will only be between 40% and 70% of its full capacity; and then
3 Battery charging continues at a constant voltage level (again, consider 4.2 VDC) until fully charged. In this mode, the current absorbed by the battery will decrease over time. When the charge current has dropped to 10% of the initial charge rate, or some other limit determined by the battery manufacturer, charging is stopped.
Charging must stop at this time as compensation charging is not acceptable for batteries
ΕΡ1595324Β1 lithium; An overload would damage the cells, possibly galvanizing the lithium metal and becoming dangerous.
Thus, lithium batteries are almost invariably used with battery charge controllers designed for their specific charging parameters.
Unfortunately, most battery charge controllers are designed to absorb from a high capacity power supply with a stable voltage that will not drift considerably in line with your current requirements. This is a problem when trying to use a limited power supply. Some computer data buses, such as universal serial bus (USB) buses, can be used to power external devices, but while these power supplies are very convenient, they have limited capacity.
Most personal computers (PC) and portable computers available today come with one or more USB ports as standard components. USB ports are designed to support data communication at speeds of 12 megabits and 1.5 megabits per second, support PnP (plug and play) installation software, and support dynamic connections (ie devices can be plugged in and unplugged while the PC is working). Thus, USB ports are often used as interfaces to connect keyboards, mice, game controllers, printers and scanners to a PC.
Similarly, USB ports are operable to provide limited power to connected external devices. The standard USB specification requires 'high power' USB ports to be operable to provide 4.75-5.25 VDC supply voltage and a current of at least 500 mA (often referred to as 'five units') . The specification for USB ports of
ΕΡ1595324Β1 'low power' requires a supply voltage of 4,405.25 Vdc and 100 mA current (referred to as 'one unit').
USB ports would seem to be a very logical choice as a power supply for portable devices for a number of reasons. For starters, USB ports provide a reduced DC power voltage, which is often very close to, or just above, the battery voltage being charged (many portable devices having battery voltages in the 2.54.5 range). VCC). Similarly, many portable devices may be operable to upload or download data or software to and from a personal computer or a portable computer (often referred to as 'synchronization'). Thus, many portable devices are provided with docking stations as shown in the network scheme of Figure 1. This is a pretty straightforward scheme, as the docking station 10 is connected to a USB 12 port of a personal computer (PC) 14 via a simple USB cable and 16 connectors. The handheld device 18 just needs to be installed. into the docking station 10 and an electronic connection is made to the PC 14.
If the USB 12 port has sufficient power, it makes much more sense to use the USB 12 port to provide portable device 18 charging power than to use a standalone AC charger. For example:
1. USB power will have less electrical noise than an AC charger unless the AC charger incorporates large capacitors or DC inductors;
2. an AC charger requires either a heavy transformer or an expensive power switch, neither of which would be required if USB power were used;
3 When applying USB power, the
The cable and connectors 16 used to connect the docking station 10 to the PC 14 can be used to carry either power or data, so no additional physical components would be required. In contrast, an AC power supply would have to be provided as a physical component independent of a USB data cable; and
4 There are no universal standards for AC power; A particular AC power supply may require 120 VGA or 240 VGA as input, and may provide 3, 4,5, 6, 7,5 or 9 VDC output, with one of a large set of connectors and possible different polarities. A traveler who forgets his AC power at home may not be able to find a suitable replacement.
By contrast, the USB standard is widely accepted, so a traveler whose mobile device is equipped with a USB connector is much more likely to find a charging source.
Thus, it would be clearly desirable to use USB power to charge portable devices. Unfortunately, however, as noted above, USB ports can only provide limited power. The problem becomes clear when considering the block diagram of figure 2. In this scenario, portable device 18 and battery charge controller 20 are connected to USB port 12 in parallel, and under charging states the control switch 22 will be toggled so that portable device 18 will absorb power from USB port 12. When battery 24 has been fully charged by battery charge controller 20 and USB port power 12 has been removed, control switch 22 is then toggled so that portable device 18 can absorb battery power 24. This type of circuit can may work in some circumstances but is not acceptable when the power supply is capable of
ΕΡ1595324Β1 limited.
If someone tries to power the handheld 18 and the battery charge controller 20 simultaneously from the USB port 12, it is very likely that an excessive charge will be imposed on the USB port 12. Overcharging the USB port 12 can lead to an undervoltage or low current state that can lead to a number of unwanted problems such as: battery 24 not being properly charged or permanently damaged, or portable device 18 malfunctioning or get damaged.
Alternatively, battery 24 and portable device 18 may be arranged as shown in Figure 3 so that they are both powered by battery charge controller 20. Although such a configuration would reduce the total power absorbed by portable device 18 and battery 24 In combination, there are a number of other problems:
1. more importantly, there is still no control over the total power that is absorbed from the USB port 12;
2. the power absorbed by the portable device 18 could disrupt the carefully configured protection and charging mechanisms of the battery charge controller 26;
3 portable device 18 and battery 24 compete arbitrarily for the available power and may adversely affect each other's operation. If the available voltage drops too low, or if insufficient current is available, either device may malfunction or fail completely;
4 if the battery 24 is in a deep discharge state when the power is turned on, the voltage directed to the portable device 18 will be reduced to the
ΕΡ1595324Β1 Battery level deeply discharged.
Typically, portable devices 18 will not be operable at such a low voltage level; and
5 the current that has to be supplied to the battery 24 and the portable device 18 has to be dissipated by the battery charge controller 20 or some external semiconductor. The more power dissipated, the larger the battery charge controller 20 (or the external semiconductor driven by the battery charge controller 20) will have to be. Generally, a semiconductor's ability to dissipate power varies with its surface area, so if power dissipation is doubled, the semiconductor will need to increase its surface area four times. New dedicated battery charge controllers could be developed which would be designed to operate on USB power and a portable device 18, but this would be a costly and complicated solution. Each battery charge controller would have to be designed to fit a specific pairing of a portable device 18 and a battery 24 because it would have to take into account the power consumption requirements of both components.
There is therefore a need for a method and apparatus that enables standard computer data buses, such as USB ports, to simultaneously power portable devices 18 and their associated battery charging circuits 20 without having to design new controllers. battery charge with very specific applications. This configuration must be provided taking into account the stringent operating parameters of battery charging circuits, the limited board physical area in portable devices, and the reliability and complexity of the design.
US 6252375 discloses a management system for
951595324Β1 energy and current increase and a method and apparatus for charging a battery for a computer peripheral. The current surge method is for use with a computer-powered peripheral subsystem, including a dynamic load, the dynamic load requiring greater power from time to time than the specified power available from the computer and bus or interconnect interface. specified. This method includes using a power node providing power as needed from the battery to the dynamic load so that the variable dynamic load does not exceed the specified power available from the computer and interconnect bus. The method includes monitoring the load current, and injecting current into the power node to increase the current carrying capacity of the computer and the peripheral bus. Preferably, the injection is performed selectively based on the monitoring results, e.g. , only when the detected load current is approaching a set threshold level. In addition, battery charging is performed only when it is determined that no current is being absorbed through the battery to avoid distorting the voltage reading. 0 It also serves to selectively charge the battery from the bus current during relatively inactive periods of peripheral dynamic charging. 0 The apparatus includes means for determining whether the battery is chargeable according to predefined chargeability criteria, and a battery charging circuit that responds to the means of selectively charging the battery only during periods when the peripheral charging current is limited. and there is enough current available on the computer bus to recharge the battery.
ΕΡ1595324Β1
DESCRIPTION OF THE INVENTION
It is therefore an object of the invention to provide a novel method and apparatus that allows standard battery charge controllers to be powered from standard computer data ports and other power sources that eliminate or mitigate at least one of disadvantages of the prior art.
One aspect of the invention is broadly defined as a battery charging circuit comprising: a semiconductor switch having an output connected to a rechargeable battery; a battery charge controller for receiving power from an external source, and providing output power to a portable device and semiconductor switch input, the current output of the battery charge controller being controllable; and a voltage sensing circuit for measuring voltage drop across the battery charge controller by modulating the semiconductor switch to reduce the amount of current supplied to the rechargeable battery when the voltage drop is too high; whereby the total power dissipated by the battery charge controller is controlled, the portable device receiving the power it needs to function and the rechargeable battery receiving all the additional available power.
Another aspect of the invention is defined as a battery charging circuit comprising: a battery charge controller connected to external electrical power and electrifying a battery and a portable device, and having a maximum current setting; and a regulating circuit for detecting voltage drop across the battery charge controller, and modulating the current to the battery to keep the power dissipated by the battery charge controller below a predetermined level.
A further aspect of the invention is defined as a method for charging a battery from a portable device.
951595324Β1 by means of an external power supply, the method comprising the steps of: connecting the input of a battery charge controller to the external power supply; connect the battery charge controller output in parallel to the handheld device and the input of a semiconductor switch; connect the output of the semiconductor switch to the battery; control the current output of the battery charge controller; measuring the voltage drop across the battery charge controller by modulating the semiconductor switch to reduce the amount of current supplied to the rechargeable battery when the voltage drop is too high; whereby the total power dissipated by the battery charge controller is controlled, the portable device receiving the power it needs to function and the rechargeable battery receiving all the additional available power.
Another aspect of the invention is defined as a power supply circuit comprising: means for measuring voltage drop across a battery charge controller that supplies power to a portable device and the input of a semiconductor switch in parallel; means for controlling the current output of the battery charge controller; and means for responding to voltage drop across the battery charge controller by modulating the semiconductor switch to reduce the amount of current supplied to the rechargeable battery when the voltage drop is too high; whereby the total power dissipated by the battery charge controller is controlled, the portable device receiving the power it needs to function and the rechargeable battery receiving all the additional available power.
These and other features of the invention will become more apparent from the following description, in which reference is made to the accompanying drawings, in which:
ΕΡ1595324Β1
Figure 1
Figure 2
Figure 3
Figure 4
Figure 5
Figure 6
Figures 7A, 7B and 7C
Figure 8 shows a physical configuration of a personal computer connected to a portable electronic device in a manner known in the art;
presents an electrical block diagram of a battery charging circuit and a portable device being powered in parallel;
presents an electrical block diagram of a battery and a portable device both being powered by a battery charge controller;
shows an electrical schematic diagram of a battery charging circuit in a broad embodiment of the invention; shows a time diagram of voltage, current and power curves for charging a lithium-ion battery in an embodiment of the invention; shows an electrical schematic diagram of a battery charging circuit in a simple embodiment of the invention; depict an electrical schematic diagram of a battery charging circuit in a comprehensive embodiment of the invention;
presents a flowchart of a method of operating a circuit
Carregamento1595324Β1 battery charging in an embodiment of the invention.
BEST MODE FOR CARRYING OUT THE INVENTION
As explained above, there is currently no effective configuration capable of powering either a rechargeable portable device 24 from a limited power supply.
A circuit that overcomes a set of problems in the art is presented as a block diagram in Figure 4. This figure shows a battery charging circuit built around a standard battery charge controller 20. In this embodiment of the invention, battery charge controller 20 receives power from an external source (V<sub>BUS</sub>) and supplies a portable device 18 and a rechargeable battery (s) 24 in parallel, but the battery 24 is supplied via a semiconductor switch Q1. 0 Current flow control through the semiconductor switch Q1 is modulated by a voltage sensing circuit 30 which measures the voltage drop across the battery charge controller 20 and reduces the current flow along the semiconductor switch Q1 to the battery. 24 when the voltage drop is too high.
Voltage sensing circuit 30 allows the total power consumption of the circuit to be deduced because the current output of the battery charge controller 20 is controllable, and the power is the product of the voltage drop and the charge controllers of. supplied to the same maximum. In the forms of the current. Most battery 20 known in the art type current control exemplary embodiment described hereinafter, for example, the maximum current output of the battery charge controller 20 is simply set by means of an external resistor R1.<sub>f</sub> of course, obviously, the output of
Corrente1595324Β1 current can also be controlled in many other ways (for example, being programmable, application specific, or defined by some form of analog or digital input signal).
Also in the embodiments described hereinafter, the voltage sensing circuitry 30 itself is provided by means of an operational amplifier (op. Amp). Thus, the voltage drop across the battery charge controller 20 can be simply measured by comparing the voltage at the input and output of the battery charge controller 20, as shown in figure 4. Alternatively, an input to the amp. op. may be taken from the output of the battery charge controller 20, while the other may be some reference voltage V<sub>REF;</sub> want emulating the input of V<sub>BUS</sub> to the battery charge controller 20, either being scaled in some way.
Thus, by monitoring the voltage drop across the battery charge controller 20 and knowing the maximum current that can be supplied, the total power is known. Using this information to modulate power for battery 24, the total power dissipated by battery charge controller 20 can be controlled.
Also, as this circuit modulates the available power for battery 24, this circuit can be configured to ensure that portable device 18 receives the power it requires to operate, whereas rechargeable battery 24 only receives power when excess capacity is available. .
The total power consumed can therefore be modulated to remain within the limits of the available power from the USB port 12, and within the power range that the battery charge controller 20 is capable of dissipating. This allows battery charge controllers 20 to be used 'as available' rather than having to design battery charge controllers 20.
Novos1595324Β1 new and larger that can dissipate sufficient power to power either the portable device 18 or the battery 24. This also allows the battery charge controller 20 or the external driving element to be kept physically small.
With this power modulation mechanism, there is no longer a competition for power between the handheld 18 and the battery 24. The battery 24 receives power only if there is more power available than the handheld 18 requires. This may seem inconsistent with battery charging requirements such as lithium cells, but circuit parameters can easily be configured to accommodate them.
As noted above, battery charge controllers are typically designed to fit a specific battery or battery family. For example, lithium batteries are charged in three phases:
1. resolve deep discharge states;
2. charging at constant current until the battery reaches a certain voltage level; and then
3 charging at constant voltage until the charging current drops to a certain extent.
During the initial treatment of deep discharge states, comparatively little current is supplied to the battery (typically 1/10 of the charge current). The circuit of the invention is therefore designed so that the very modest power requirement is very rarely denied to the battery.
The constant current charging phase absorbs the most power, but lithium cells do not suffer if the charging current is modulated or cycled during this phase. Thus, this is the phase that is most altered by the circuit of the invention. If portable device 18 is heavily used during this phase, the only negative impact will be that battery charging 24
ΕΡ1595324Β1 will take much longer.
During the constant voltage charging phase, the maximum current is less than that of the constant current phase and drops continuously as battery 24 is fully charged. More importantly, the battery voltage 24 remains at a constant and maximum level during this phase, so the total power dissipated by the battery charge controller 20 will be lower during the constant voltage phase than it was during the power phase. constant current.
As will be described in more detail hereinafter, the voltage sensing circuit 30 is designed to saturate the semiconductor switch Q1 when the full charge voltage level is reached (i.e. the semiconductor switch Q1 does not minimally restrict the flow of current at this time).
The change in power dissipation over time is shown in figure 5. Four curves are shown in this figure: battery voltage 24, marked with V<sub>BAT;</sub> the charge current, marked with I charge, the voltage drop across the battery charge controller 20, marked with Vqueda, θ the total dissipated power, marked with PBCC. Note that V<sub>DRO</sub>p varies inversely with respect to V<sub>BAT</sub>, and that the power dissipated by the battery charge controller 20 and the Icarga product θ Vqueda ·
Clearly, during the conditioning phase, the battery voltage, V<sub>BAT</sub>, is low, so V<sub>FALL</sub> will be high. However, I<sub>CHARGE</sub> θ also drops during this phase (about 1/10 of Icargamáx, the maximum load current) so the total dissipated power is modest.
During the constant current phase, the charging current increases to Icargamax, but the battery voltage, V<sub>BAT</sub>, drops as the battery becomes charged, so the power dissipated by the battery charge controller 20 drops over the course of this phase.
ΕΡ1595324Β1
When the constant voltage phase begins, the battery voltage has reached its fully charged level, Vcargatotal, so 3 Vqueda is at a minimum. As Icarga falls over the course of this phase, dissipated power also continues to fall (again noting that dissipated power is the product of Icarga θ V<sub>FALL</sub>) .
It is then clear that the highest power level is absorbed during the constant current phase. As noted above, charging of battery 24 may be safely cycled during this phase, so current restriction for battery 24 is permitted during this phase.
This circuit also allows the user to boot up their portable device 18 very quickly as it isolates battery 24 from portable device 18. If battery 24 and portable device 18 were connected when battery charge controller 20 attempted to condition a deeply discharged battery 24, the voltage on the portable device 18 would have been reduced to the level of the deeply discharged battery 24. Typically, this would be too low for the correct operation of portable device 18. With the circuit of the invention, battery 24 and portable device 18 are isolated by Q1. Even if the battery 24 is in a deep discharge state, the portable device 18 will still receive a sufficiently high voltage for proper operation.
The start-up time of the portable device 18 is therefore only limited by the activation time of the battery charge controller itself 20. A typical value of this start-up time is 1 mS-4 mS, although it may vary between controllers. battery charge 201 and one other.
Thus, the use of the circuit of Figure 4 allows computer data buses and similar limited capacity power supplies to simultaneously supply power to portable devices and batteries.
ΕΡ1595324Β1 downloaded.
A set of different embodiments of the invention will now be described. Each embodiment uses a very small number of simple and reliable components. Thus, the invention as a whole provides an effective solution that is economical, reliable and consumes minimal board space on a portable device.
Basic application
Figure 6 shows an electrical schematic diagram of a charging circuit employing four main components: an NCP1800 battery charge controller 50, a Q2 semiconductor, which serves as an external conducting element for battery charge controller 50, a operational amplifier (amp. op.) 52, and a MOSFET (metal-oxide-semiconductor field effect transistor) Q3, which controls the current to the rechargeable battery
24.
Battery Charge Controller NCP180 50 is a standard single cell lithium-ion battery charge controller as known in the art. The maximum current this device will supply is regulated by the resistance between the ISEL pin and ground. In this case, three resistors R2, R3 and R4 are used to set the maximum current levels for different operating conditions. The default condition is that only 100 mA (low power USB) is available, which sets the value for resistor R2. If it is detected that the device is connected to a high power USB source, then the MOSFET Q4 port will be powered up, and the resistance between ISEL and ground will be defined by the resistance of R2 and R3 in parallel.
Similarly, if it is detected that the circuit power source has even more power available (such as an automotive AC plug or adapter), then the MOSFET Q5 will be powered up so that the resistance
951595324Β1 between ISEL and ground is defined by the resistance of R2 and R4 in parallel. The circuit of Figure 6 will typically be included in the portable devices 18 themselves, or in a docking station 10, and should therefore also be operable with such large capacity power supplies.
The NCP1SQ 50 Battery Charge Controller manufacturer's application notes are available, which will help the configurator set specific parameters and values for resistors R2, R3 and R4 and conduction transistor Q2.
The voltage sensing portion of this circuit is provided by the amp. op. 52, together with resistors R5 and R6, and capacitor Cl. This circuit monitors the voltage on the collector side of Q2 (via voltage divider R5 and R6), and compares it to a reference level (in this case, V<sub>REF</sub> = * 3.3 V). If the voltage on the collector side of Q2 drops, then the voltage drop along Q2 increases and the power it has to dissipate increases. To reduce the power that has to be dissipated, amp. op. 52 restricts the current through Q3 increasing its drainage resistance.
Note that V<sub>REF</sub> can simply be supplied from V<sub>BUS</sub> and a voltage regulator. AV<sub>REF</sub> is used as an input to the amp. op. 52 instead of V<sub>BUS</sub> since the regulator will provide a constant output voltage, whereas V<sub>BU</sub>s has a wide range, making configuration more difficult. The values of resistors R5 and R6 are set simply by the need to scale the value of V<sub>BUS</sub> relative to the value of V<sub>REF</sub>.
Also, note that capacitor Cl is included in the circuit to smooth out fluctuations and prevent wobble.
As described above, this circuit allows portable device 18 to absorb power across Q2, without causing the combined absorptions of the device
181595324Β1 portable 18 and battery 24 exceed the power capacity of Q2. As portable device 18 absorbs power, the voltage on the collector side of Q2 drops and the current through Q3 is linearly regulated.
Power dissipation has to be set for the most pessimistic scenario. For example, if the maximum configuration parameters are as follows:
»Available up to 0.85 A;
• an input voltage could be as high as
V; and 'battery preloading 24 is completed at 3.0 V (this is when the highest charging current is supplied to the battery as shown in figure 5); then (6 V - 3 V) * 0.85 A = 2.55 W of power that would be dissipated by the external conduction element Q2 (note that on circuits not using such an element, all this power would be dissipated by the controller battery charge 50).
This external conducting element Q2 must dissipate heat generated by the current flowing through it. The more power dissipated, the greater the physical dimension of this passing element will be; generally, the surface area that a device requires increases with the square of power to dissipate. That is, if the power is doubled, a transistor with a surface area four times larger is required. The dimensions of the transistors are standard, so the preferred embodiment of this circuit is designed to employ SOT-23 (or superSOT-6) units, which are capable of dissipating up to 1.6 W. The next dimension is SOT-223. which is considerably larger with twice the power dissipation.
As noted above, power regulation for battery 24 is such that current always meets the needs of portable device 18, and
ΕΡ1595324Β1 any excess current (difference between input current and current for handheld 18) is supplied to battery 24. For example, suppose the circuit is connected to a high power USB port (500 mA available) and to a portable device 18, such as a Blackberry ™ portable device. When the BlackBerry goes into sleep, it may only require 0.3 mA0.7 mA, so the available current balance (499.3 mA-499.7 mA) can be supplied to battery 24. As soon as the BlackBerry reactivates, What happens periodically to perform cleaning tasks absorbs about 30 mA70 mA, depending on what you do. At this time, battery 24 receives 430 mA-470 mA. Analysis occurs when Blackberry must receive or transmit some data, or perform some other task. In either case, the power for battery 24 is dynamically self-adjusting.
When limited power is available, it is also desirable to turn off high power components while preserving power for the processor only. This is easily accomplished by connecting only the processor and memory of the portable device 18 to Q2, as shown in Figure 6, and by connecting other large power consumers alongside the Q3 battery. Consequently, if we are working with a limited current source (such as a 100 mA low power USB) and an overcurrent component such as a vibrator (typically 120 mA) or a backlight (typically 150 mA) ), if turned on, the voltage output of Q2 will begin to fall, causing Q3 to increase its RDS (drainage) resistance and preserve the current required for the processor.
Comprehensive application
The configuration shown in FIGS. 7A-7C uses the same basic circuits as FIG. 6, but adds several elements that provide additional advantages. These
ΕΡ1595324 :1 advantages include the following:
«The battery can be charged with an input voltage just above the battery level;
• starting up the portable device 18 when the battery is dead or not present is different from that of figure 6;
• treatment of incoming peaks from external power supply is improved; and • contrary to the battery charge controller manufacturer's instructions used in this application, the VCC and IN pins are powered separately to prevent back voltage leakage and potential lockout problems in the battery charge controller.
The specific configuration parameters for this embodiment of the invention may be summarized as follows:
1. constant current and constant voltage charging capabilities (as required for lithium-ion battery charging);
2. current selection for power supplies
100 mA, 500 mA and 750 mA;
3 operating the handheld 18 when the rechargeable battery 24 is weak, dead or not present;
4 starting and operating portable device 18 in less than 100 mS in cases where battery 24 is not present or dead;
5 conforms to USB suspend mode of operation (system should absorb less than 500 uA);
6 overvoltage protection above 5.8 V to a minimum of 10 V;
7 protection against a short in the battery connector;
8 allows charging with input voltage as low as portable device 18 needs for
951595324Β1 its safe operation;
9 voltage in the range 3.3 V - 3.6 V for the pull-up resistor (positive setting) on line D *;
10 provides means for connecting and disconnecting the voltage to the pull-up resistor on line D *;
11 battery presence indication, · and
12 Provides the operating state of the battery charge controller.
Following is the general description of this comprehensive application of the invention:
The circuit of Fig. 7A-7C centers around a Texas Instruments lithium-ion battery charge controller, bq24020, marked U909 in Fig. 7C. This battery charge controller provides the constant current and constant voltage modes required to charge lithium-ion cells, and supports externally programmable current limits. 0 its UVLO (undervoltage blocking limit) is provided by the PFI / PFO (U908) comparator (Texas Instruments TPS3103E15) as a reference, and its limit is set by the VBUS input resistor splitters. U908 is also used to ensure operation after initial startup of U909 to a minimum of 100mS. This provides a means of enumerating when operating on low / dead battery, or without battery. Overvoltage protection (OVP) is provided by the U912 which is set to ~ 5.8 V. 0 Charging state is provided by the U909 battery charge controller, which indicates whether or not the controller is supplying current to the pull-up resistor D * is a drop-down regulator and its capacity of same. The components that are external power is in this system. The voltage for supplied by U901 (one voltage, Toko TK71733SCL) via Q907 switching used for power use only when
ΕΡ1595324Β1 available through VBUS (U906, U905, etc.)
A U905 comparator (LMC7111A) and MOSFET Q908 are used to increase system voltage when running on a low / dead battery or without the battery. This closed circuit also 'directs' current to the system in either battery free or low battery states. This is because when the L_BAT voltage drops (due to system load) the U905 acts to turn off Q908, directing more current to the system (away from the battery).
Comparator U907 provides the battery presence status indicator.
The battery connector short circuit protection is a NAND (NO-E - U906 circuit) with charger activation functionality, thus automatically disabling the U909 battery charge controller when a short circuit occurs. The U909 Battery Charge Controller automatically restarts charging if the battery voltage drops below an internal limit, and automatically enters sleep mode when the VDC power is removed. Functioning theory
Note that the circuit inputs and outputs of figures 7A-7C can be summarized as follows:
<td>Signal</td><td>Connection</td><td>description</td>
<td>VBUS</td><td>To the source of food (USB or</td><td>Power input to the device used for the battery charging or the</td>
<td>CHRG__EN</td><td>Sign of control of system</td><td>Activates / deactivates the charger and the power supply to the system; Reset state: HIZ (pull-down resistor causes RST = LOW,</td>
<td>CHRG_A</td><td>Sign of control of</td><td>Activates the current limit of 450 mA for the charger; state of</td>
ΕΡ1595324Β1
<td>CHRG_B</td><td>Sign of control of</td><td>Enables 750mA current limit for the charger; state of</td>
<td>USB__CD</td><td>Sinnl's control of</td><td>HIGH whenever VBUS is above -2.1 V</td>
<td>CHRG_FLG</td><td>Sign of control of</td><td>Charger status warning; spare state: LOW</td>
<td>VBAT</td><td>The battery rechargeable</td><td>Rechargeable battery main power supply, power state reset: voltage value of the</td>
<td>L BAT</td><td>To device</td><td>Provides system power, state : voltage level of the</td>
VBUS, the input voltage, is displayed via Q904a to the USB input pin of the U909 battery charge controller. Q904 is used for QVP and is controlled by U912 (3.0 V undervoltage detector, National Semiconductor LMS33460) whose input voltage is supplied via resistor divider R937 and R925 * R926. Its open drain output keeps Q904 in saturation while VBUS / (R937 + R925 * R926) 0 $ 925 * R926) <3.0 V, which provides OVP above -5.8 V.
While USB input is present for the U909 battery charge controller, a current limit of 100 mA and 500 mA can be selected via CHRG_B (CHRG_B = LOW provides 100 A, and CHRG_B = HIGH provides 500 mA). Resistor R941 sets the LOW logic level as default for the U909 ISET2 input, thus allowing a preset current limit of important as it makes the USB specification during low / dead or without battery.
one operation lists the 500 mA
This is with the battery
100 bad. system according to operation with
A USB device is at 100 mA, until (if the host USB supports it).
resistor R940 provides a LOW input level per
ΕΡ1595324Β1 defaults to the Q905a port, which keeps it away from saturation (OFF) during reset mode and thus sets the Q904b port voltage to its original level (VBUS voltage level) which disables VBUS is present on the AC input of the U909 battery charge controller. The R932 and R936 resistors are pull-up resistors for Q904.
The 750 mA charging current (used for non-USB power supplies) can be selected by setting CHRG_A = HIGH, which sets Q905a to saturation (ON) and in turn puts Q904b to saturation (ON), showing VBUS voltage at the AC input of the U909 battery charge controller. Since an AC input for U909 provides overlap with the USB input (if the AC input voltage exceeds 1.5 V, the charging input-output path is preset for AC input) the charging current is now programmed by the resistor value R939.
capacitor C925 is used to prevent Q904b from conducting due to its surge-to-drain parasite capacity during rapid transient VBUS voltage responses (the drain-to-drain capacity would load the door if removed from its source in time). allows the port to load quickly at the VBUS level, keeping Q904b at saturation. Resistor R935 is used to limit the discharge current of C925 so that Q905a does not exceed its specified limits. R933 is a pulldown resistor that prevents an AC input to the U909 battery charge controller from floating. C926 and C927 are input shunt capacitors. It is important to keep the total input capacity below 10 uF to comply with the USB connection current specification.
The total current that the system absorbs from VBUS should not exceed 500 uA when in standby mode. This is mainly achieved by the very high operating current.
ΕΡ1595324Β1 low battery charge controller U909 (typically <100 uA) in OFF mode of operation. Q905b is used to disable the LBAT overvoltage / undervoltage when the U909 battery charge controller is not supplying any current to battery 24 and / or portable device 18. It does this by shortening the positive input of the U905, which causes its output to make Q908 go into saturation (ON).
U906b is used as a CHRG_FLG warning inverter only to make it compatible with the software and equipment of the rest of the system. R931 is a pull-up resistor for the CHRG__FLG open drain output.
U908 processor supervisor has a dual functionality. Its PFI (power failure input) input level is defined by resistor divider R937 * R925 and R926 to match the internal reference of U908 when VBUS drops below 3.3 V (or the LBAT voltage value defined by U905 and Q908 when operating on a low / dead battery, or without battery), leading to its open drain output (power failure output - PFO) going to GND. This would force the positive input node from U905 to go to GND and set Q908 to saturation (ON). This circuitry creates an undervoltage blocking limit (UVLO) for the L_BAT overvoltage / undervoltage circuit. This is important as the U909 can operate as low as 2.5 V, causing its status warning to indicate power supply to the system even though it does not (battery 24 internally disconnects below 2.5 V ). This state would cause the system to reset (to battery voltage levels below the default LBAT minimum) as the U905 / Q908 would attempt to maintain the LBAT voltage at the default value by turning off battery 24 and thinking that U909 battery charge is providing sufficient current.
ΕΡ1595324Β1
The second feature of U908 is the override on the U909-CE input pin, which provides power to the system for a minimum of 100 mS to properly start and enumerate on the USB-BUS. This is achieved by maintaining its drain outlet. RESET on GND before VBUS reaches 2.5 V and then 100 mS after. This keeps the U909 battery charge controller activated during this time.
U906a provides CHRG_EN NAND functionality and presence of short circuit in the battery connector. A shortened battery disables the U909 battery charge controller in the equipment. Having the voltage on the VBAT, the CHRG__EN control line could enable or disable the U909 battery charge controller (CHRG__EN = HIGH would activate the U909 battery charge controller by lowering the U908 MR input pin). R921 provides battery isolation and U906a input so that the current drain is limited to a maximum of 42 uA even if U906 creates HIZ (high impedance) inputs and outputs when no power is present in your VDC.
R924 provides a default LOW entry level for U906a during host processor reset. R920 is a pull-up resistor for CHRG_FLG making it valid only for as long as the U909 battery charge controller is activated.
U907 produces a battery presence indicator by monitoring the BAT_ID input of the battery pack. Its output would be at a HIGH logic level whenever the BAT__ID resistor was present and its pull-up would be provided by the BAT_CHK signal.
U901 Low Level Loss Voltage Regulator (ΤΟΚΟ TK71733SCL) provides 3.3 V regulated power to USB data line pull-up resistors as well as 3.3 V power to various components in the circuit charger and while an indicator that a
ΕΡ1595324Β1 external source is connected (EXT_PWR_CD). U901 has overcurrent and reverse polarity protection, integrated thermal break and short circuit protection.
U901 provides power for U906, U908, and U905 as well as 3.3 V voltage for the pull-up resistor. It is also used to provide indication of the presence of VBUS to the system (EXT_PWR_CD). R904 is used to limit current to the system input pin. C915 is an input bypass capacitor and C922 is an output filtering capacitor. C910 is used to filter out RF noise from RF circuits, and C912 is a shunt capacitor for internal reference.
Q907 is used to switch the USB_VPU voltage and allows smooth enumeration on the USB bus. R909 provides the default OFF state for P-FET and R905 provides the quick discharge of the USB__SFTCN control line (during RST or suspended startup without battery).
U904 supplies supply voltage to the USB sender-receiver integrated circuit (it is a standard voltage regulator as known in the art). It is activated when VBUS is present and automatically shuts off power when VBUS is OFF. C921 and C913 are output filtering capacitors. U904 can be optionally removed to reduce costs; R942 must then be completed to provide power to the USB transceiver integrated circuit. U904 will only be required if the transceiver integrated circuit does not meet the USB suspended current requirements (and our device can wake from sleep by reading only the D * / D- line responses).
U905 and Q908 are mainly used to keep L_BAT = VBAT when VBUS is not present, and to keep L_BAT at least 3.6 V when VBUS is present (while the charger is supplying system power) and battery voltage. is less than 3.6 V. It is also used to divide the total power dissipation in two (between the
ΕΡ1595324Β1 main charge element of the battery charge controller and Q908) to allow higher charging currents at all battery voltage levels.
Another important feature of these circuits is to allow proper USB enumeration when the battery is low / dead or not present, allowing the system to wake up to 15 mS when the battery is not present or dead. Once the U909 supplies all programmed current, U905 / Q908 will maintain the preprogrammed minimum voltage at L___BAT (3.5 V in our case) by varying the Q908 drain-to-source resistance.
The positive input of U905 is used as a reference and is defined by R934 and R913. C924 allows for a slow LBAT start-up time so that the U909 battery charge controller can supply all programmed current until Q908 requires an L_BAT voltage increase (if required). Resistor splitters R916 and R915 are used to set the 'minimum voltage' in L_BAT, while R914 provides a pull-down resistor for the Q908 port.
U907 provides indication of battery presence to the system. R927 and R929 are used to set the reference and R928 is a pull-up resistor for the U907 open drain output. BAT__ID is then presented to your negative entry and NO_BAT_N is set accordingly.
Preferred values for the components in this circuit are as shown in figures 7A-7C. These values will, of course, vary with application and configuration parameters.
Software embodiments
Instead of using only electronic equipment as shown above, the invention may also be applied using a combination of hardware and software components, including programmable devices such as digital signal processors (DSP), microcontrollers,
ΕΡ1595324Β1 Programmable Logic Gate Networks (FPGA), Application Specific Integrated Circuits (ASIC), and the like. This embodiment could be applied as shown in the flow chart of figure 8.
As with the embodiments described above, this method could be used to charge any rechargeable battery in a portable or similar electronic device. Any external power supply could be used, although the invention is most useful with limited capacity power supplies.
As shown in Figure 8, the method of the invention begins at step 90 by connecting the input of a battery charge controller 20 to the external power supply, preferably via a USB cable and connectors 16, and a base 10 for holding the portable device 18. The output of battery charge controller 20 is connected in parallel to the portable device 18 and the input of semiconductor switch Q1 at step 92, and the output of said semiconductor switch Q1 is connected to rechargeable battery 24 at step 94.
Next, the current output of the battery charge controller 20 is somehow controlled at step 96. As noted above, this can be done in many ways, for example a DAC (digital to analog converter) output of a The microcontroller may be used to send a suitable signal to the current control input of the battery charge controller 20.
The voltage drop across the battery charge controller 20 is then measured in step 98. This task can also be accomplished in many ways. For example, many microcontrollers supplied with integrated ADC (digital to analog converters) that could be used to perform this function.
As the current is controlled in step 96, and the voltage drop along the battery charge controller 20 is
Measured at step 98, this methodology can deduce the power dissipation for the battery charge controller 20. The method of the invention is therefore capable of controlling power dissipation by modulating the semiconductor switch Q1 in response to voltage drop across the battery charge controller 20 in step 100, reducing the amount of current supplied to the rechargeable battery 24 when the voltage drop is too high.
In this way, the total power dissipated by the battery charge controller 20 is controlled; the portable device 18 receiving the power it needs to function and the rechargeable battery 24 receiving all the additional available power.
The balance of the software code required to perform this algorithm would be quite obvious to one skilled in the art.
The method steps of the invention may be performed in executable instruction code sets stored in a variety of formats, such as object code or source code, integrated with code from other programs, applied as subroutines, by program calls. external or other techniques as known in the art.
Even the equipment embodiments of the invention could be encoded in a software form, such as the equipment development languages (HDL code) used to manufacture integrated circuits. This HDL or similar code could be stored on an electronic memory medium such as computer diskettes, CD-Rom, random access memory (RAM) and read only memory (ROM). Similarly, electronic signals representing this software code may also be transmitted via a communication network.
ΕΡ1595324Β1
Options and alternatives
While specific embodiments of the present invention have been shown and described, it is evident that changes and modifications may be made to such embodiments without departing from the true scope and spirit of the invention. For example:
1. The circuit of the invention could be used with any form of power supply that has USB ports.
2. Any form of electrical appliance could be charged with this circuit, including laptops, personal digital assistants (PDAs), cell phones, e-mail devices, and digital wireless reception; and
3 Any form of rechargeable battery could be used, including single or multiple cells of lithium ion, nickel cadmium, or other types.
Again, such applications will be apparent to one skilled in the art from the present explanations, and do not deviate from the invention.
INDUSTRIAL APPLICABILITY
The present invention provides a method and apparatus for charging a battery in a portable communication device from a variety of power sources.
Contents7
8 sheets
Sheet 1 Sheet 2 Sheet 3 Sheet 4 Sheet 5 Sheet 6 Sheet 7 Sheet 8
43 members in 16 offices
Priority claims8
| Document | Office | Kind | Date |
|---|---|---|---|
| 2419488 | Canada | A | |
| 2419488 | Canada | A | |
| 37218003 | United States of America | A | |
| 37218003 | United States of America | A | |
| 2419488 | – | – | – |
| 372180 | – | – | – |
| CA20032419488 | – | – | – |
| US20030372180 | – | – | – |
Members43
| Document | Office | Kind | |
|---|---|---|---|
| CA2419488A1 | Canada | A1 | |
| CA2562214A1 | Canada | A1 | |
| US2004164708A1 | United States of America | A1 | |
| AU2004213885A1 | Australia | A1 | |
| WO2004075371A1 | World Intellectual Property Organization (WIPO) | A1 | |
| MXPA05008887A | Mexico | A | |
| EP1595324A1 | European Patent Office (EPO) | A1 | |
| KR20050109499A | Republic of Korea | A | |
| BRPI0407728A | Brazil | A | |
| CN1751426A | China | A | |
| JP2006518580A | Japan | A | |
| CA2419488C | Canada | C | |
| AU2004213885B2 | Australia | B2 | |
| JP2008211966A | Japan | A | |
| JP4197189B2 | Japan | B2 | |
| US2010219797A1 | United States of America | A1 | |
| US7791319B2 | United States of America | B2 | |
| US7847520B2 | United States of America | B2 | |
| US2010308777A1 | United States of America | A1 | |
| US7906940B2 | United States of America | B2 | |
| US2011133702A1 | United States of America | A1 | |
| KR101052582B1 | Republic of Korea | B1 | |
| US7999514B2 | United States of America | B2 | |
| US2011260680A1 | United States of America | A1 | |
| CN1751426B | China | B | |
| CN102946122A | China | A | |
| EP2579422A2 | European Patent Office (EPO) | A2 | |
| US8541983B2 | United States of America | B2 | |
| EP2579422A3 | European Patent Office (EPO) | A3 | |
| EP1595324B1 | European Patent Office (EPO) | B1 | |
| PT1595324TThis record | Portugal | T | |
| DK1595324T3 | Denmark | T3 | |
| LT1595324T | Lithuania | T | |
| EP3145044A1 | European Patent Office (EPO) | A1 | |
| ES2609460T3 | Spain | T3 | |
| HUE030234T2 | Hungary | T2 | |
| CY1120011T1 | Cyprus | T1 | |
| EP2579422B1 | European Patent Office (EPO) | B1 | |
| ES2714683T3 | Spain | T3 | |
| EP1595324B2 | European Patent Office (EPO) | B2 | |
| EP3145044B1 | European Patent Office (EPO) | B1 | |
| ES2609460T5 | Spain | T5 | |
| ES2761801T3 | Spain | T3 |
Numbers
- Publication
- 1595324
- Publication, DOCDB
- 1595324
- Publication, EPODOC
- PT1595324T
- Application
- 47129796
- Application, DOCDB
- 04712979
- Application, EPODOC
- PT20040712979T
Titles2
- English
- CIRCUIT AND METHOD OF OPERATION FOR AN ELECTRICAL POWER SUPPLY
- Portuguese
- CIRCUITO E MÉTODO DE OPERAÇÃO PARA UMA ALIMENTAÇÃO ELÉTRICA
Classification
- CPC, 4
- G06F1/266
- H02J7/865
- H02J2207/30
- H02J7/92
- IPC, 1
- H02J7 00
