Signal transmission device, electronic device, and signal transmission method

The present invention relates to a signal transmission device, an electronic device, and a signal transmission method. More specifically, the present invention relates to a method of supplying a parameter (set value) for signal processing to a signal processing unit.

For example, LVDS (Low Voltage Differential Signaling) is a method for realizing high-speed signal transmission within one electronic device or between electronic devices located at a relatively short distance (for example, within a few centimeters to a few centimeters). Are known. However, with the recent increase in the capacity and speed of transmission data, there are problems such as an increase in power consumption, an increase in the influence of signal distortion due to reflection, and an increase in unnecessary radiation. For example, LVDS has reached its limit when transmitting signals such as video signals (including imaging signals) and computer images at high speed (real time) in a device.

In order to deal with the problem of high-speed transmission data, there is a method of increasing the number of wires and reducing the transmission speed per signal line by parallelizing signals. However, this measure leads to an increase in the number of input / output terminals. As a result, complicated printed circuit boards and cable wiring and an increase in the size of semiconductor chips are required. In addition, so-called electromagnetic field failure becomes a problem when high-speed and large-capacity data is routed by wiring.

Problems with LVDS and methods of increasing the number of wires are all due to the transmission of signals via electrical wiring. Therefore, as a method for solving the problem caused by transmitting signals by electrical wiring, a method of wirelessly transmitting electrical wiring has been proposed.

For example, Japanese Patent Application Laid-Open No. 2005-204221 and Japanese Patent Application Laid-Open No. 2005-223411 propose to wirelessly transmit signals in a housing and to apply a UWB (Ultra Wide Band) communication method. The UWB communication method in these two patent documents has a low carrier frequency, is not suitable for high-speed communication such as transmitting a video signal, and has a size problem such as a large antenna. Further, since the frequency used for transmission is close to the frequency of other baseband signal processing, there is also a problem that interference is likely to occur between the radio signal and the baseband signal. Further, when the transport frequency is low, it is easily affected by the drive system noise in the device, and it is necessary to deal with it.

On the other hand, Japanese Patent Application Laid-Open No. 10-256478 and US Pat. No. 5,547,948 describe that a carrier frequency in the millimeter wave band is used. Using a carrier frequency in the millimeter-wave band, which has a shorter wavelength, as in these two patent documents, can solve the problems of antenna size, interference, and the influence of drive system noise.

<p num="0007"><patcit num="1"><text>Japanese Patent Application Laid-Open No. 2005-204221</text></patcit><patcit num="2"><text>Japanese Patent Application Laid-Open No. 2005-223411</text></patcit><patcit num="3"><text>Japanese Unexamined Patent Publication No. 10-256478</text></patcit><patcit num="4"><text>U.S. Pat. No. 5,547,948</text></patcit></p>

<p num="0008"> By the way, when operating various signal processing units for wireless communication, generally, a setting value that defines the operation is given to the signal processing unit, that is, parameters are set. At this time, in order to correspond the set value (parameter) to the change of the environment surrounding the signal processing unit, it is common to provide a dynamic adjustment mechanism having a control circuit and an arithmetic circuit. For example, in a dynamic environment where the environment surrounding the signal processing unit changes greatly, such as outdoor wireless communication, it is almost essential to provide a dynamic adjustment mechanism.</p><p num="0009"> However, providing such a dynamic adjustment mechanism causes an increase in the circuit scale and also increases the power consumption. In a static environment where there is little change in the environment surrounding the signal processing unit or there is almost no change in the environment (in other words, the effect of environmental change can be ignored), such as wireless communication within or between devices. When used in, it is useless to provide a dynamic adjustment mechanism.</p><p num="0010"> Therefore, an object of the present invention is to provide an invention capable of executing parameter setting for wireless communication while suppressing an increase in circuit scale and an increase in power consumption.</p>

<p num="0011"> The signal transmission device according to the first aspect of the present invention is a transmission unit that transmits a signal processed signal for a transmission target signal as a radio signal, and a reception unit that receives a radio signal transmitted from the transmission unit. At least one of them is provided. Here, the transmission characteristics between the transmitting unit and the receiving unit are known. Then, at least one of the front stage of the transmission unit and the rear stage of the reception unit is further provided with a signal processing unit that performs predetermined signal processing based on the set value and a predetermined set value for signal processing. It is provided with a set value processing unit for inputting to the signal processing unit. Each signal transmission device described in the dependent section of the signal transmission device according to the first aspect of the present invention defines a further advantageous specific example of the signal transmission device according to the first aspect of the present invention.</p><p num="0012"> The electronic device according to the second aspect of the present invention relates to signal transmission in a so-called device, and is transmitted from a transmission unit and a transmission unit that transmit a signal processed signal for a signal to be transmitted as a radio signal. A receiving unit that receives the radio signal and a radio signal transmission path that enables wireless transmission between the transmitting unit and the receiving unit are arranged at predetermined locations in one housing. Here, the transmission characteristics between the transmitting unit and the receiving unit are known. Further, at least one of the front stage of the transmission unit and the rear stage of the reception unit has a signal processing unit that performs predetermined signal processing based on the set value, and a predetermined set value for signal processing. It is provided with a set value processing unit that inputs (preferably one corresponding to the transmission characteristics between the transmitting unit and the receiving unit) to the signal processing unit.</p><p num="0013"> The electronic device according to the third aspect of the present invention relates to so-called signal transmission between devices, and has a transmission unit that transmits a signal processed signal for a signal to be transmitted as a radio signal in one housing. A first electronic device arranged at a predetermined transmission point and a second receiving unit for receiving a radio signal transmitted from the transmitting unit are arranged at a predetermined receiving location in one housing. The whole of one electronic device is composed of the electronic devices of. Then, when the first electronic device and the second electronic device are arranged at a predetermined position, a wireless signal transmission path that enables wireless transmission is formed between the transmitting unit and the receiving unit. The transmission characteristics between the transmitting unit and the receiving unit are known. Further, at least one of the front stage of the transmission unit and the rear stage of the reception unit has a signal processing unit that performs predetermined signal processing based on the set value, and a predetermined set value for signal processing ( It is provided with a set value processing unit that inputs (preferably one corresponding to the transmission characteristic between the transmitting unit and the receiving unit) to the signal processing unit.</p><p num="0014"> In the signal transmission method according to the fourth aspect of the present invention, the signal processed for the transmission target signal is transmitted from the transmitting unit as a radio signal, and the radio signal transmitted from the transmitting unit is received by the receiving unit. .. At this time, the transmission characteristics between the transmitter and the receiver are known, and a predetermined set value for signal processing (preferably corresponding to the transmission characteristics between the transmitter and the receiver). Is input to the signal processing unit, and at least one of the front stage of the transmitting unit and the rear stage of the receiving unit further performs predetermined signal processing in the signal processing unit based on the input set value.</p><p num="0015"> Each of the electronic device according to the second aspect of the present invention, the electronic device according to the third aspect of the present invention, and the signal transmission method according to the fourth aspect of the present invention relates to the first aspect of the present invention. Various techniques / methods applied to the signal transmission device (techniques / methods of each signal transmission device described in the subordinate section of the signal transmission device according to the first aspect of the present invention) can be similarly applied.</p><p num="0016"> In each of the first to fourth aspects of the present invention, the transmission characteristics between the transmitting unit and the receiving unit are known, and each signal processing unit on the transmitting side and the receiving side is predetermined according to a set value (parameter). At that time, the set value processing unit inputs a predetermined set value for signal processing to the signal processing unit. In short, the set value for signal processing is set to a predetermined value (that is, a fixed value). Since the set value is not dynamically changed in response to changes in the environment, the parameter calculation circuit can be reduced and the power consumption can be reduced. Since it is not necessary to provide a dynamic adjustment mechanism, the parameter calculation circuit is not wasted even when it is used in a static environment where the influence of environmental changes can be ignored.</p>

<p num="0017"> According to the present invention, it is possible to execute parameter setting for wireless communication while suppressing an increase in circuit scale and an increase in power consumption.</p>

<figref num="1">FIG. 1 is a diagram showing a first basic configuration (first example) of the wireless transmission device of the present embodiment.</figref><figref num="2">FIG. 2 is a diagram showing a first basic configuration (second example) of the wireless transmission device of the present embodiment.</figref><figref num="3">FIG. 3 is a diagram showing a second basic configuration (first example) of the wireless transmission device of the present embodiment.</figref><figref num="4">FIG. 4 is a diagram showing a second basic configuration (second example) of the wireless transmission device of the present embodiment.</figref><figref num="5">5 (A) to 5 (C) are diagrams for explaining Example 1 (first example of the modulation function unit and the demodulation function unit).</figref><figref num="6">FIG. 6 is a diagram illustrating Example 2 (second example of the modulation function unit and the demodulation function unit).</figref><figref num="7">7 (A) to 7 (B) are diagrams for explaining the third embodiment.</figref><figref num="8">FIG. 8 is a diagram illustrating Example 4 (echo canceller technique during bidirectional communication).</figref><figref num="9">9 (A) to 9 (D) are diagrams for explaining the fifth embodiment (MIMO processing applied to the receiving side).</figref><figref num="10">10 (A) to 10 (B) are diagrams for explaining the operation method of MIMO processing applied to the receiving side.</figref><figref num="11">FIG. 11 is a diagram illustrating a calculation method of MIMO processing applied to the receiving side.</figref><figref num="12">12 (A) to 12 (C) are diagrams for explaining the relationship between the restrictions on antenna arrangement and the amount of MIMO processing (inverse matrix calculation amount).</figref><figref num="13">13 (A) to 13 (D) are diagrams for explaining the sixth embodiment (MIMO processing applied to the transmitting side).</figref><figref num="14">14 (A) to 14 (B) are diagrams for explaining the operation method of MIMO processing applied to the transmitting side.</figref><figref num="15">FIG. 15A is a diagram illustrating a calculation method of MIMO processing applied to the transmitting side.</figref><figref num="16">16 (A) to 16 (C) are diagrams for explaining the seventh embodiment (third example of the modulation function unit and its peripheral circuit).</figref><figref num="17">17 (A) to 17 (C) are diagrams for explaining Example 7 (third example of the demodulation function unit and its peripheral circuit).</figref><figref num="18">FIG. 18 is a diagram showing a configuration example of the phase amplitude adjusting unit.</figref><figref num="19">FIG. 19 is a diagram illustrating a first example of a configuration example on the transmitter side to which the injection synchronization method is applied.</figref><figref num="20">FIG. 20 is a diagram illustrating a first example of a configuration example on the receiver side to which the injection synchronization method is applied.</figref><figref num="21">FIG. 21 is a diagram illustrating a second example (No. 1) of the configuration example on the transmitter side to which the injection synchronization method is applied.</figref><figref num="22">FIG. 22 is a diagram illustrating a second example (No. 2) of the configuration example on the transmitter side to which the injection synchronization method is applied.</figref><figref num="23">FIG. 23 is a diagram illustrating a second example (No. 1) of the configuration example on the receiver side to which the injection synchronization method is applied.</figref><figref num="24">FIG. 24 is a diagram illustrating a second example (No. 2) of the configuration example on the receiver side to which the injection synchronization method is applied.</figref><figref num="25">FIG. 25 is a diagram showing the phase relationship of each signal in the injection synchronization.</figref><figref num="26">FIG. 26 is a diagram illustrating Example 7, and is a diagram showing a basic configuration of modulation / demodulation corresponding to injection synchronization.</figref><figref num="27">FIG. 27 is a diagram illustrating the seventh embodiment, and is an example of the relationship between the frequency difference between the modulated transport signal and the demodulated transport signal during self-propelling and the phase difference θ between the injection signal and the demodulated transport signal during injection lock. It is a figure which shows.</figref><figref num="28">28 (A) to 28 (C) are diagrams for explaining the seventh embodiment, showing an example of the relationship between the phase difference between the injection signal and the demodulation carrier signal at the time of injection lock and the DC component of the demodulation output. It is a figure.</figref><figref num="29">29 (A) to 29 (C) are diagrams for explaining the seventh embodiment, and are diagrams showing an example of the relationship between the reception level and the lock range.</figref><figref num="30">30 (A) to 30 (B) are diagrams for explaining the eighth embodiment, and are diagrams for explaining the phase difference between the received signal supplied to the frequency mixing unit and the demodulated carrier signal.</figref><figref num="31">31 (A) to 31 (C) are diagrams for explaining the eighth embodiment, in which the phase difference between the received signal supplied to the frequency mixing unit and the demodulated carrier signal and the DC component of the demodulated signal are shown. It is a figure explaining the relationship.</figref><figref num="32">32 (A) to 32 (B) are diagrams for explaining the eighth embodiment, and describes a method of suppressing the influence of the phase difference between the received signal supplied to the frequency mixing unit and the demodulated carrier signal. It is a figure.</figref><figref num="33">FIG. 33 is a diagram illustrating a communication device according to a ninth embodiment (diffusion code method).</figref><figref num="34">FIG. 34 is a diagram (first example) for explaining the overall operation of the communication device of the ninth embodiment.</figref><figref num="35">FIG. 35 is a diagram (second example) for explaining the overall operation of the communication device of the ninth embodiment.</figref><figref num="36">FIG. 36 is a diagram showing an overall outline of the wireless transmission device to which the tenth embodiment is applied.</figref><figref num="37">37 (A) to 37 (C) are diagrams showing an example of frequency amplitude characteristics for explaining the frequency deviation with respect to the carrier wave on the transmitting side and the receiving side.</figref><figref num="38">38 (A) to 38 (B) are diagrams illustrating a first example of the electronic device of the eleventh embodiment.</figref><figref num="39">FIG. 39 is a diagram illustrating a second example of the electronic device of the eleventh embodiment.</figref><figref num="40">FIG. 40 is a diagram illustrating a third example of the electronic device of the eleventh embodiment.</figref>

Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings. When distinguishing each functional element by form, describe it with an uppercase alphabetic reference such as A, B, C, ..., etc., and when explaining without distinguishing, this reference child Is omitted and described. The same applies to the drawings.

The explanation will be given in the following order. 1. Overview 2. Communication processing system: Basic configuration 1 3. Communication processing system: Basic configuration 2 4. Example 1: First example of the modulation function unit and the demodulation function unit 5. Example 2: Second example of the modulation function unit and the demodulation function unit 6. Example 3: Frequency characteristic correction processing 7. Example 4: Echo canceller technology during two-way communication 8. Example 5: Space division multiplexing (MIMO processing on the receiving side) 9. Example 6: Space division multiplexing (MIMO processing on the transmitting side) 10. Example 7: Third example of modulation function unit and demodulation function unit (injection lock method) 11. Example 8: Supports phase difference correction by injection lock method 12. Example 9: Diffusion coding method 13: Example 10: High-speed transmission data 14: Example 11: Application example to electronic equipment

&lt;Overview&gt; [Wireless transmission device, wireless transmission method] In the first configuration of the present embodiment corresponding to the first aspect and the fourth aspect of the present invention, the transmitting unit (for example, the transmission line coupling unit on the transmitting side) and the receiving unit (for example, the transmission line coupling unit) A wireless transmission device is configured by including at least one of them. The transmission unit transmits a signal that has been signal-processed with respect to the transmission target signal as a radio signal. The receiving unit receives the radio signal transmitted from the transmitting unit. Here, it is assumed that the transmission characteristics between the transmitting unit and the receiving unit are known. For example, even if the positions of the transmitter and receiver in one housing do not change (in the case of in-device communication), or if the transmitter and receiver are arranged in different housings, they are still in use. The transmission conditions between transmission and reception do not change substantially (that is, as in the case of wireless transmission between devices at a relatively short distance) when the arrangement positions of the transmission unit and the reception unit are in a predetermined state. Under a fixed environment, the transmission characteristics between the transmitting unit and the receiving unit can be known in advance. Then, at least one of the front stage of the transmission unit and the rear stage of the reception unit is further provided with a signal processing unit and a set value processing unit. The signal processing unit performs predetermined signal processing based on the set value. The set value processing unit inputs a predetermined set value for signal processing to the signal processing unit.

It is not limited to the set value corresponding to the transmission characteristic and the signal transmission in the device or between the devices, and includes, for example, the parameter setting for correcting the variation of the circuit element, but preferably, the set value processing unit is the transmission unit. It is preferable to input a predetermined set value for signal processing corresponding to the transmission characteristic between the signal processing unit and the receiving unit to the signal processing unit. In an environment where the transmission conditions between transmission and reception do not change substantially (that is, are fixed), even if the set value that defines the operation of the signal processing unit is treated as a fixed value, that is, even if the parameter setting is fixed, The signal processing unit can be operated without any inconvenience. By setting the signal processing setting value to a predetermined value (that is, a fixed value), it is not necessary to dynamically change the parameter setting, so that the parameter calculation circuit can be reduced and the power consumption can be reduced. .. Since the communication environment is fixed in wireless transmission within the device or between devices at a relatively short distance, various circuit parameters that depend on the communication environment can be determined in advance, and in an environment where the transmission conditions are fixed. Even if the set value that defines the operation of the signal processing unit is treated as a fixed value, that is, even if the parameter setting is fixed, the signal processing unit can be operated without any inconvenience. For example, by obtaining the optimum parameters at the time of shipment from the factory and holding the parameters inside the device, it is possible to reduce the parameter calculation circuit and the power consumption.

When determining various circuit parameters in advance, both the first method, which is automatically generated inside the device, and the second method, which uses the one generated outside the wireless transmission device (or electronic device), are both available. Can be taken. When the first method is adopted, the set value processing unit includes a set value determination unit that determines the set value, a storage unit that stores the set value determined by the set value determination unit, and a set value read from the storage unit. It is preferable to have an operation control unit that operates the signal processing unit based on the above. When the second method is adopted, the set value processing unit has a set value receiving unit that receives the set value from the outside, a storage unit that stores the set value received by the set value receiving unit, and a setting read from the storage unit. It is preferable to have an operation control unit that operates the signal processing unit based on the value.

There are various signal processing parameter settings. For example, there is a gain setting (signal amplitude setting) of a signal amplification circuit (amplitude adjustment unit). The signal amplifier circuit is used, for example, for transmission power setting, reception level setting input to the demodulation function unit, automatic gain control (AGC), and the like. In these cases, the signal processing unit shall have an amplitude adjusting unit that adjusts the magnitude of the input signal and performs signal processing to output the adjusted signal, and the set value processing unit adjusts the magnitude of the input signal. Input the set value for this to the amplitude adjustment unit.

Another example of signal processing parameter setting is the setting of the phase adjustment amount. For example, in a system in which a carrier signal or a clock is transmitted separately, the phase is adjusted according to the delay amount of the transmission signal. In these cases, the signal processing unit shall have a phase adjusting unit that adjusts the phase of the input signal and performs signal processing to output the adjusted signal, and the set value processing unit adjusts the phase of the input signal. Input the set value to the phase adjustment unit. The setting of the phase adjustment amount may be combined with the above-mentioned gain setting.

Another example of signal processing parameter setting is frequency characteristic setting. For example, this is a case where the amplitude of the low frequency component or the high frequency component is emphasized in advance on the transmitting side. In these cases, the signal processing unit shall have a frequency characteristic correction processing unit that corrects the frequency characteristics of the input signal and outputs the corrected signal, and the set value processing unit is for correcting the frequency characteristics of the input signal. Input the set value to the frequency characteristic correction processing unit.

Another example of signal processing parameter setting is setting the echo cancellation amount when bidirectional communication is performed. In this case, the signal processing unit shall have an echo suppressing unit that suppresses the echo component mixed in the input side of the signals output from the transmitting side, and the set value processing unit is set to suppress the echo component. Enter the value in the echo suppression section.

As another example of signal processing parameter setting, there is a setting of a crosstalk cancellation amount when the transmitting unit and the receiving unit each have a plurality of antennas and spatial multiplexing communication is performed between transmission and reception. In this case, the signal processing unit has a matrix operation processing unit that performs matrix operations based on a channel matrix whose elements are the transmission functions of each antenna pair between transmission and reception, and the set value processing unit performs matrix operations. Input the set value of to the matrix calculation processing unit.

As another example of signal processing parameter setting, a carrier signal for demodulation synchronized with a carrier signal for modulation (modulated carrier signal) generated by a carrier signal generator on the transmitting side by an injection synchronization method based on a received signal. There are settings such as the amplitude value (injection amount) and phase shift amount of the injection signal when generating (reconstruction transport signal), or the correction amount of the phase difference between the received signal and the demodulation transport signal input to the demodulation function unit. Set values related to injection synchronization, such as the amplitude value and phase shift amount of the injection signal, or the correction amount of the phase difference between the received signal and the demodulated transport signal, are referred to as "setting values for performing injection synchronization". In this case, the transmission signal processing unit has a frequency of a first carrier signal generator that generates a modulation carrier signal and a modulation carrier signal that generates a transmission target signal by the first carrier signal generator. It has a first frequency converter that converts and generates a modulated signal, and sends the modulated signal to the radio signal transmission line. The signal processing unit for reception generates a carrier signal for demodulation that is synchronized with the carrier signal for modulation generated by the first carrier signal generator by injecting the signal received via the wireless signal transmission path. It has a second carrier signal generator for frequency conversion and a second frequency converter for frequency-converting the modulated signal received via the wireless signal transmission line with the carrier signal for demodulation generated by the second carrier signal generator. It shall be. Then, the set value processing unit inputs the set value for performing injection synchronization to the signal processing unit for transmission and / or the signal processing unit for reception.

The magnitude of the DC component of the signal demodulated by the demodulation function unit (demodulation signal) is determined by the phase difference between the received signal input to the demodulation function unit and the demodulation carrier signal, but the phase difference is when the DC component is maximum. Since it becomes zero and there is no self-propelled frequency difference between the injection signal and the demodulated carrier signal generated by the injection lock, it is better to determine the "set value for injection synchronization" so that the DC component of the demodulated signal becomes large. .. However, since the lock range changes depending on the magnitude of the injection signal level (injection amount), the amount of change (step) that changes the self-propelled frequency of the demodulated carrier signal in order to quickly find the maximum value while maintaining the locked state. You need to choose the best. To deal with this, it is preferable to calculate the optimum step from the amplitude of the received signal input to the demodulation function unit in advance and store it in the storage unit, and use it when changing the self-propelled frequency of the demodulation carrier signal. Alternatively, it is preferable to obtain the optimum gain so that the injection amount becomes constant, store it in the storage unit, and use it for setting the injection amount. Since there is a path difference between the received signal input to the demodulation function unit and the demodulation carrier signal, the effect appears in the phase difference, and the way in which the DC component of the demodulation signal changes changes. Therefore, a phase adjustment unit (phase shifter) that corrects the phase difference is inserted into at least one of the paths of the injection signal, the demodulation transfer signal, and the reception signal, and the value of the phase adjustment amount (phase shift amount) is stored in advance. It is recommended to keep it in the unit and use it for setting the phase adjustment.

As a configuration for determining the "set value for performing injection synchronization", for example, an injection synchronization determination and an adjustment mechanism based on the determination result may be used. For example, the reception signal processing unit shall include an injection synchronization detection unit that detects information indicating the injection synchronization status in the second carrier signal generation unit, and may include a transmission signal processing unit and a reception signal processing unit. At least one of the above is based on the information indicating the state of injection synchronization detected by the injection synchronization detection unit, and the transfer signal for demodulation generated by the second transfer signal generation unit is generated by the first transfer signal generation unit. It is preferable to provide an injection synchronization adjustment unit that performs synchronization adjustment so as to synchronize with the carrier signal for modulation. The set value processing unit holds the set value adjusted by the injection synchronization adjustment unit in the storage unit, reads it out, and uses it for the operation setting of the signal processing unit.

The synchronization adjustment by the injection synchronization adjustment unit may be performed on the receiving side or on the transmitting side. For example, when performing on the receiving side, the injection synchronization adjustment unit determines the amplitude of the signal injected into the second carrier signal generator and / or the frequency of the output signal during self-propelled oscillation of the second carrier signal generator. It is better to adjust the synchronization by changing. When performed on the transmitting side, the injection synchronization adjustment unit changes the frequency of the modulation transport signal generated by the first transport signal generation unit and / or the amplitude of the signal transmitted to the radio signal transmission line. Perform synchronous adjustment with. It should be noted that it is whether the synchronization adjustment is performed on the receiving side or the transmitting side, and the control subject when the synchronization adjustment is performed on the transmitting side may be arranged on either the receiving side or the transmitting side.

When the demodulation carrier signal is generated by the injection synchronization method, it is preferable that the signal processing unit on the transmitting side has a modulation target signal processing unit that suppresses the DC neighborhood component of the transmitted transmission target information to be modulated, and the frequency on the transmitting side. The conversion unit may generate a transmission signal by frequency-converting the processed signal processed by the modulation target signal processing unit with the modulation transfer signal generated by the transfer signal generation unit on the transmitting side. In short, the direct current is cut in advance so that the injection can be easily synchronized. Preferably, the modulation target signal processing unit performs DC-free coding on the digital transmission target information.

Another example of signal processing parameter setting is setting the amount of clock phase correction when a clock signal synchronized with the spreading code string is transmitted due to the synchronization mechanism of the spreading code string in the wireless communication of the spreading code method. .. In this case, a reference signal output unit that outputs a reference signal and a clock signal for signal processing related to diffuse code type wireless communication processing are generated in synchronization with the reference signal based on the reference signal output from the reference signal output unit. It shall be further provided with a clock generation unit to be used. The clock generation unit shall have a phase correction unit that performs phase correction according to a set value, the signal processing unit performs signal processing based on the clock signal that has been phase-corrected by the phase correction unit, and the set value processing unit may perform signal processing. The set value for performing phase correction is input to the phase correction unit. The signal processing unit generates the spread code string in synchronization with the clock signal generated by the clock generation unit, and the transmission target data based on the spread code string generated by the spread code string generator. It is preferable to have a diffusion processing unit that performs the diffusion processing of the above as signal processing.

As another example of signal processing parameter setting, the amount of shift in the carrier frequency on the transmitting side and the receiving side when trying to speed up transmission data by utilizing the asymmetry of the transmission frequency characteristic between transmission and reception with respect to the carrier frequency. There is a setting of. In this case, the transmission signal is generated by frequency-converting the first carrier signal generation unit that generates the modulation carrier signal and the transmission target signal with the modulation carrier signal generated by the first carrier signal generation unit. The transmission side signal processing unit including the first frequency conversion unit, the second carrier signal generation section for generating the carrier signal for demodulation, and the received transmission signal are generated by the second carrier signal generation section. It shall be provided with a signal processing unit on the receiving side including a second frequency conversion unit for frequency conversion with a carrier signal for demodulation. Then, at least one of the carrier signal for modulation and the carrier signal for demodulation is set so as to deviate from the band center of the transmission characteristic between transmission and reception. For example, only one of the transmission system and the reception system needs to be frequency-shifted, and the band center and the reception system of the transmission system (which may include not only the signal processing unit and the modulation function unit on the transmission side but also the amplifier circuit on the transmission side). Only one of the band centers (which may include not only the signal processing unit and the demodulation function unit on the receiving side but also the amplifier circuit on the receiving side) may be set so as to deviate from the frequency of the carrier signal. Alternatively, both the transmitting system and the receiving system may be frequency-shifted in the same direction. In this case, both the band center of the transmission system and the band center of the reception system are set so as to be deviated in the same direction with respect to the frequency of the carrier signal.

Preferably, the demodulation is performed by synchronous detection, that is, the frequency conversion unit on the receiving side demodulates the transmission target signal by performing frequency conversion by the synchronous detection method. Preferably, the demodulation transfer signal is generated by the injection synchronization method. In this case, it is preferable to fix the "injection synchronization setting value" as described above, and as a configuration for determining the "injection synchronization setting value", for example, the injection synchronization determination and its determination. It is advisable to use a result-based adjustment mechanism. In the case of the injection synchronization method, it is preferable to perform DC cut (for example, DC-free coding) in advance on the transmitting side so that injection synchronization can be easily performed, as described above.

[Electronics] In the electronic device of the present embodiment corresponding to the second aspect of the present invention and the third aspect of the present invention, one electronic device may be formed by a device configuration in which each part is housed in one housing. It is possible, or a combination of a plurality of devices (electronic devices) may constitute an entire one electronic device. The wireless transmission device of the present embodiment is used in, for example, an electronic device such as a digital recording / playback device, a terrestrial television receiving device, a mobile phone device, a game device, and a computer.

The wireless transmission device of the present embodiment described below will be described as using a carrier frequency in the millimeter wave band (wavelength is 1 to 10 mm), but is not limited to the millimeter wave band and has a shorter wavelength, for example, a submillimeter wave. It is also applicable when a carrier frequency near the millimeter wave band such as a band is used.

When a wireless transmission device is configured, there are cases where the transmitting side is alone, cases where the receiving side is alone, and cases where both the transmitting side and the receiving side are provided. The transmitting side and the receiving side are coupled via a radio signal transmission line (for example, a millimeter wave signal transmission line) and are configured to perform signal transmission in the millimeter wave band. The signal to be transmitted is frequency-converted to a millimeter-wave band suitable for wideband transmission and transmitted. For example, the first communication unit (first millimeter wave transmission device) and the second communication unit (second millimeter wave transmission device) constitute a wireless transmission device. Then, between the first communication unit and the second communication unit arranged at a relatively short distance, the signal to be transmitted is converted into a millimeter wave signal, and then this millimeter wave signal is used in the millimeter wave signal transmission line. To transmit via. The "wireless transmission" of the present embodiment means that the signal to be transmitted is transmitted wirelessly (millimeter wave in this example) instead of general electrical wiring (simple wire wiring).

"Relatively short distance" means that the distance is shorter than the distance between outdoor (outdoor) communication devices used in broadcasting and general wireless communication, and as a space with a closed transmission range. It suffices as long as it can be substantially specified. "Closed space" means a space in which there is little leakage of radio waves from the inside of the space to the outside, and conversely, there is little arrival (intrusion) of radio waves from the outside to the inside of the space, and typically The entire space is surrounded by a housing that has a shielding effect against radio waves. For example, inter-board communication within the housing of one electronic device, inter-chip communication on the same substrate, or a state in which one electronic device is equipped with the other electronic device, the plurality of electronic devices are integrated. Corresponds to communication between devices in this state. A typical example of "integral" is a state in which both electronic devices are in complete contact with each other by mounting, but the "integral" may be such that the transmission range between the two electronic devices can be substantially specified as a closed space. This includes cases where both electronic devices are placed at a predetermined position at a relatively short distance, for example, within a few centimeters or within a dozen centimeters, and can be regarded as "substantially" one. In short, it suffices that there is little leakage of radio waves from the inside of the space where radio waves composed of both electronic devices can propagate to the outside, and conversely, there is little arrival (intrusion) of radio waves from the outside into the space.

In the following, signal transmission in the housing of one electronic device is referred to as signal transmission in the housing, and signal transmission in a state where a plurality of electronic devices are integrated (hereinafter, also includes "substantially integrated") is a device. It is called inter-signal transmission. In the case of signal transmission in a housing, the transmitting side communication device (communication unit: transmitting unit) and the receiving side communication device (communication unit: receiving unit) are housed in the same housing, and the communication unit (transmitting unit and receiving unit). A wireless transmission device in which a wireless signal transmission path is formed between them becomes an electronic device itself. On the other hand, in the case of inter-device signal transmission, the transmitting side communication device (communication unit: transmitting unit) and the receiving side communication device (communication unit: receiving unit) are housed in different electronic device housings, and both electronic devices are housed. When they are arranged at a predetermined position and integrated, a wireless signal transmission path is formed between the communication units (transmitting unit and receiving unit) in both electronic devices to construct a wireless transmission device.

In each communication device provided across a millimeter-wave signal transmission line, a transmission system and a reception system are arranged in pairs. Bidirectional communication is possible by coexisting the transmission system and the reception system in each communication device. When the transmission system and the reception system coexist in each communication device, the signal transmission between one communication device and the other communication device may be one-way (one-way) or two-way. For example, when the first communication unit is the transmitting side and the second communication unit is the receiving side, the transmitting unit is arranged in the first communication unit and the receiving unit is arranged in the second communication unit. When the second communication unit is the transmitting side and the first communication unit is the receiving side, the transmitting unit is arranged in the second communication unit and the receiving unit is arranged in the first communication unit.

The transmission unit is, for example, a signal generation unit on the transmitting side (a signal conversion unit that converts an electric signal to be transmitted into a millimeter wave signal) and a millimeter wave unit that processes a signal to be transmitted to generate a millimeter wave signal. It is assumed that the transmission line (millimeter wave signal transmission line) for transmitting the signal of the above is provided with a signal coupling section on the transmitting side for coupling the millimeter wave signal generated by the signal generating section on the transmitting side. Preferably, the signal generation unit on the transmission side is integrated with the functional unit that generates the signal to be transmitted.

For example, the signal generation unit on the transmission side has a modulation circuit, and the modulation circuit modulates the signal to be transmitted. The signal generator on the transmitting side frequency-converts the signal after being modulated by the modulation circuit to generate a millimeter-wave signal. In principle, the signal to be transmitted may be directly converted into a millimeter wave signal. The transmission side signal coupling unit supplies the millimeter wave signal generated by the transmission side signal generation unit to the millimeter wave signal transmission line.

The receiving unit is, for example, a signal coupling unit on the receiving side that receives a millimeter wave signal transmitted via a millimeter wave signal transmission path, and a millimeter wave signal (input signal) received by the signal coupling unit on the receiving side. ) Is signal-processed to generate a normal electric signal (signal to be transmitted), and a signal generation unit on the receiving side (a signal conversion unit that converts a millimeter-wave signal into an electric signal to be transmitted) is provided. Preferably, the signal generation unit on the receiving side is integrated with the functional unit that receives the signal to be transmitted. For example, the signal generation unit on the receiving side has a demodulation circuit, frequency-converts a millimeter-wave signal to generate an output signal, and then the demodulation circuit demodulates the output signal to generate a signal to be transmitted. In principle, a millimeter wave signal may be directly converted into a signal to be transmitted.

In other words, when adopting a signal interface, the signal to be transmitted is transmitted by a millimeter wave signal without contacts or cables (not transmission by electrical wiring). Preferably, at least signal transmission (particularly video signal requiring high-speed transmission or large-capacity transmission, high-speed clock signal, etc.) is transmitted by a millimeter-wave signal. In short, the signal transmission previously performed by electrical wiring is performed by millimeter wave signals in this embodiment. By performing signal transmission in the millimeter wave band, high-speed signal transmission on the order of Gbps can be realized, the range covered by the millimeter wave signal can be easily limited, and an effect due to this property can be obtained.

Here, each signal coupling unit may be such that the first communication unit and the second communication unit can transmit a millimeter wave signal via the millimeter wave signal transmission line. For example, it may be provided with an antenna structure (antenna coupling portion), or may be coupled without having an antenna structure. The "millimeter wave signal transmission line for transmitting a millimeter wave signal" may be air (so-called free space), but preferably, a structure for transmitting the millimeter wave signal while confining the millimeter wave signal in the transmission path (a structure in which the millimeter wave signal is transmitted. Those having a millimeter wave confinement structure or a radio signal confinement structure) are preferable. By positively using the millimeter wave confinement structure, it is possible to arbitrarily determine the routing of the millimeter wave signal transmission line as in the case of electrical wiring, for example. As such a millimeter wave confinement structure, for example, a so-called waveguide is typically applicable, but the present invention is not limited to this. For example, a material made of a dielectric material capable of transmitting millimeter-wave signals (referred to as a dielectric transmission line or a millimeter-wave dielectric transmission line), or a shield that constitutes a transmission line and suppresses external radiation of millimeter-wave signals. A hollow waveguide in which the material is provided so as to surround the transmission line and the inside of the shielding material is hollow is preferable. By giving flexibility to the dielectric material and the shielding material, it is possible to route the millimeter wave signal transmission line. In the case of air (so-called free space), each signal coupling portion has an antenna structure, and the antenna structure transmits signals in a short distance space. On the other hand, if it is made of a dielectric material, it may have an antenna structure, but that is not essential.

[Contrast between signal transmission by electrical wiring and wireless transmission] Signal transmission, in which signals are transmitted via electrical wiring, has the following problems. i) Large capacity and high speed of transmission data are required, but there is a limit to the transmission speed and capacity of electrical wiring. ii) In order to deal with the problem of high-speed transmission data, there is a method of increasing the number of wires and reducing the transmission speed per signal line by parallelizing the signals. However, this method leads to an increase in input / output terminals. As a result, complicated printed circuit boards and cable wiring, increase in physical size of connectors and electrical interfaces, etc. are required, their shapes become complicated, their reliability decreases, and costs increase. Occurs. iii) With the enormous amount of information such as movie images and computer images, the problem of EMC (electromagnetic environment compatibility) becomes more apparent as the band of the baseband signal becomes wider. For example, when electrical wiring is used, the wiring serves as an antenna, and signals corresponding to the tuning frequency of the antenna are interfered with. In addition, reflection or resonance due to impedance mismatch of wiring also causes unnecessary radiation. In order to deal with such a problem, the configuration of the electronic device becomes complicated. iv) In addition to EMC, if there is reflection, transmission errors due to interference between symbols on the receiving side and transmission errors due to diving of interference also become problems.

On the other hand, when signal transmission is performed wirelessly (for example, using a millimeter wave band) instead of electrical wiring, there is no need to worry about the wiring shape and the position of the connector, so there are not many restrictions on the layout. Wiring and terminals can be omitted for signals that have been replaced with millimeter-wave signal transmission, eliminating the problem of EMC. In general, since there is no other functional unit that uses a millimeter-wave band frequency inside the communication device, EMC countermeasures can be easily realized. Since wireless transmission is performed in a state where the communication device on the transmitting side and the communication device on the receiving side are close to each other and the signal is transmitted between fixed positions or in a known positional relationship, the following advantages can be obtained. 1) It is easy to properly design the propagation channel (waveguide structure) between the transmitting side and the receiving side. 2) Higher reliability than free space transmission by designing the dielectric structure of the transmission line coupling that seals the transmitting side and the receiving side together with the propagation channel (waveguide structure of the millimeter-wave signal transmission line). Good transmission is possible. 3) Since it is not necessary to control the controller that manages wireless transmission dynamically and adaptively frequently as in general wireless communication, the overhead of control can be reduced as compared with general wireless communication. As a result, the set value (so-called parameter) used in the control circuit, the arithmetic circuit, or the like can be set to a constant (so-called fixed value), which enables small size, low power consumption, and high speed. For example, if the wireless transmission characteristics are calibrated at the time of manufacturing or designing and individual variations are grasped, the data can be referred to, so the setting values that define the operation of the signal processing unit can be preset or statically controlled. .. Since the set value generally appropriately defines the operation of the signal processing unit, high-quality communication is possible while having a simple configuration and low power consumption.

For example, unlike field communication such as so-called cellular, in wireless transmission within or between devices, the state of the propagation path does not change, there is virtually no fluctuation in received power or timing (no or very little), and propagation occurs. Features include short distances and small multipath delay spreads. These are collectively referred to as the characteristics of "wireless transmission within or between devices". In "wireless transmission within or between devices", unlike outdoor wireless communication, it is not necessary to constantly check the condition of the propagation path, and it can be considered that a predetermined set value can be used. That is, "wireless transmission within or between devices" may be considered as wireless signal transmission in a static environment, and the communication environment characteristics may be considered to be substantially unchanged. This means that "the communication environment is immutable (fixed), so the parameter settings may be immutable (fixed)". Therefore, for example, a parameter indicating the communication environment characteristics may be determined at the time of product shipment, the parameter may be saved in the memory, and the operation setting of the signal processing unit may be performed based on this parameter at the time of operation. Since the operation is performed based on the set value, the adjustment mechanism itself exists, but since there is no need for a mechanism (control mechanism) that constantly monitors the communication environment characteristics and optimizes the set value based on the result, the circuit The scale can be reduced and the power consumption can be reduced.

Further, the following advantages can be obtained by using wireless communication in the millimeter wave band having a short wavelength. a) Millimeter-wave communication has a wide communication band, so it is easy to increase the data rate. b) The frequency used for transmission can be separated from the frequencies of other baseband signal processing, and interference between the millimeter wave and baseband signal frequencies is unlikely to occur. c) Since the millimeter wave band has a short wavelength, the antenna and waveguide structure that depend on the wavelength can be made smaller. In addition, the electromagnetic shield is easy to perform because the distance attenuation is large and the diffraction is small. d) In normal outdoor wireless communication, there are strict regulations on the stability of the carrier wave in order to prevent interference. In order to realize such a highly stable carrier wave, a highly stable external frequency reference component, a multiplication circuit, a PLL (phase-locked loop circuit), or the like is used, and the circuit scale becomes large. However, millimeter waves (especially when used in combination with signal transmission between fixed positions or in known positional relationships) can be easily shielded and prevented from leaking to the outside. In order to demodulate a signal transmitted on a carrier wave with loose stability on the receiving side with a small circuit, it is preferable to adopt an injection synchronization method (details will be described later).

For example, LVDS (Low Voltage Differential Signaling) is known as a method for realizing high-speed signal transmission between electronic devices arranged at a relatively short distance (for example, within 10 and several centimeters) or within the electronic device. However, with the recent increase in the capacity and speed of transmission data, problems such as an increase in power consumption, an increase in the influence of signal distortion due to reflection, an increase in unnecessary radiation (so-called EMI problem), and the like become problems. For example, LVDS has reached its limit when transmitting signals such as video signals (including imaging signals) and computer images at high speed (real time) within or between devices.

In order to support high-speed data transmission, the number of wires may be increased and the transmission speed per signal line may be reduced by parallelizing the signals. However, this measure leads to an increase in the number of input / output terminals. As a result, complicated printed circuit boards and cable wiring and an increase in the size of semiconductor chips are required. In addition, so-called electromagnetic field failure becomes a problem by routing high-speed and large-capacity data by wiring.

Problems with LVDS and methods of increasing the number of wires are all due to the transmission of signals via electrical wiring. Therefore, as a method for solving the problem caused by transmitting the signal by the electric wiring, a method of wirelessly transmitting the electric wiring may be adopted. As a method of wirelessly transmitting electrical wiring, for example, signal transmission inside the housing is performed wirelessly, and UWB (Ultra Wide Band) is used. ) A communication method may be applied (referred to as the first method), or a carrier frequency in the millimeter wave band with a short wavelength (1 to 10 mm) may be used (referred to as the second method). However, the UWB communication method of the first method has a low carrier frequency, is not suitable for high-speed communication such as transmitting a video signal, and has a size problem such as an large antenna. Further, since the frequency used for transmission is close to the frequency of other baseband signal processing, there is also a problem that interference is likely to occur between the radio signal and the baseband signal. Further, when the transport frequency is low, it is easily affected by the drive system noise in the device, and it is necessary to deal with it. On the other hand, if a carrier frequency in the millimeter wave band having a shorter wavelength is used as in the second method, problems of antenna size and interference can be solved.

Here, the case of communicating in the millimeter wave band has been described, but the applicable range is not limited to the case of communicating in the millimeter wave band. Communication in a frequency band below the millimeter wave band or conversely in a frequency band above the millimeter wave band may be applied. For example, a microwave band or a submillimeter wave band having a wavelength shorter than that of the millimeter wave band (0.1 to 1 mm) may be applied. However, in the signal transmission in the housing and the signal transmission between devices, it is effective to use the millimeter wave band whose wavelength is neither excessively long nor short.

Hereinafter, the wireless transmission device and the electronic device of this embodiment will be specifically described. As the most preferable example, many functional parts are formed in a semiconductor integrated circuit (chip), but this is not essential.

&lt;Communication processing system: Basic configuration 1&gt; 1 and 2 are a first basic configuration (basic configuration 1) for explaining the signal interface of the wireless transmission device (signal transmission device) of the present embodiment from the aspect of functional configuration.

[Functional configuration] As shown in FIGS. 1 and 2, in the signal transmission device 1, the first communication device 100, which is an example of the first wireless device, and the second communication device 200, which is an example of the second wireless device, transmit millimeter-wave signals. It is configured to be coupled via road 9 and perform signal transmission in the millimeter wave band. The figure shows a case where the transmission system is provided on the first communication device 100 side and the reception system is provided on the second communication device 200.

The first communication device 100 is provided with a semiconductor chip 103 that supports millimeter-wave band transmission, and the second communication device 200 is provided with a semiconductor chip 203 that supports millimeter-wave band reception.

In this embodiment, the signals to be communicated in the millimeter wave band are limited to signals that require high speed and large capacity, and other signals that are sufficient for low speed and small capacity and signals that can be regarded as direct current such as power supplies are used. Not subject to conversion to millimeter wave signals. For signals (including power supplies) that are not to be converted to millimeter-wave signals, the signals between the boards are connected by the same method as before. The original electrical signal to be transmitted before being converted to millimeter waves is collectively called a baseband signal.

[1st communication device] In the first communication device 100, a semiconductor chip 103 and a transmission line coupling portion 108 corresponding to millimeter wave band transmission are mounted on a substrate 102. The semiconductor chip 103 is an LSI (Large Scale Integrated Circuit) in which an LSI functional unit 104 and a signal generation unit 107 (millimeter wave signal generation unit) are integrated.

The semiconductor chip 103 is connected to the transmission line coupling portion 108. The transmission line coupling unit 108 is an example of a transmission unit, and for example, an antenna structure including an antenna coupling unit, an antenna terminal, a microstrip line, an antenna, or the like is applied.

The LSI functional unit 104 controls the main application of the first communication device 100, and includes, for example, a circuit that processes various signals to be transmitted to the other party.

The signal generation unit 107 (electric signal conversion unit) converts the signal from the LSI function unit 104 into a millimeter wave signal, and transmits a transmission side signal generation unit 110 for performing signal transmission control via the millimeter wave signal transmission line 9. Have. The transmission system (transmission unit: communication unit on the transmission side) is composed of the transmission side signal generation unit 110 and the transmission line coupling unit 108.

The transmitting side signal generation unit 110 uses the multiplexing processing unit 113, the parallel serial conversion unit 114, the modulation unit 115, the frequency conversion unit 116, and the amplification unit 117 in order to process the input signal and generate a millimeter wave signal. Have. The amplification unit 117 is an example of an amplitude adjustment unit that adjusts the magnitude of the input signal and outputs the signal. The modulation unit 115 and the frequency conversion unit 116 may be collectively referred to as a so-called direct conversion system.

The multiplexing processing unit 113 performs time division multiplexing, frequency division multiplexing, and code when there are a plurality of types (referred to as N1) of signals to be communicated in the millimeter wave band among the signals from the LSI function unit 104. By performing multiplexing processing such as division multiplexing, multiple types of signals are combined into one system of signals. For example, a plurality of types of signals that are required to have high speed and large capacity are combined into one system of signals to be transmitted in millimeter waves.

The parallel serial conversion unit 114 converts the parallel signal into a serial data signal and supplies it to the modulation unit 115. The modulation unit 115 modulates the transmission target signal and supplies it to the frequency conversion unit 116. The parallel serial conversion unit 114 is provided in the case of the parallel interface specification using a plurality of signals for parallel transmission when this embodiment is not applied, and is unnecessary in the case of the serial interface specification.

Basically, the modulation unit 115 may be any one that modulates at least one of the amplitude, frequency, and phase with the transmission target signal, and any combination of these methods can be adopted. For example, in the case of an analog modulation method, there are, for example, amplitude modulation (AM) and vector modulation. Vector modulation includes frequency modulation (FM) and phase modulation (PM). In the case of a digital modulation method, for example, amplitude transition modulation (ASK: Amplitude shift keying), frequency transition modulation (FSK: Frequency Shift Keying), phase transition modulation (PSK: Phase Shift Keying), amplitude phase that modulates amplitude and phase. There is modulation (APSK: Amplitude Phase Shift Keying). Quadrature Amplitude Modulation (QAM) is a typical example of amplitude phase modulation. In this embodiment, in particular, a method that can adopt a synchronous detection method on the receiving side is adopted.

The frequency conversion unit 116 frequency-converts the transmission target signal after being modulated by the modulation unit 115 to generate a millimeter-wave electric signal and supplies it to the amplification unit 117. A millimeter-wave electric signal is an electric signal having a frequency in the range of approximately 30 GHz to 300 GHz. The term "generally" is based on the fact that the frequency may be such that the effect of millimeter-wave communication can be obtained, the lower limit is not limited to 30 GHz, and the upper limit is not limited to 300 GHz.

The frequency conversion unit 116 may have various circuit configurations. For example, a configuration including a frequency mixing circuit (mixer circuit) and a local oscillation circuit may be adopted. The local oscillator circuit generates a carrier wave (carrier signal, reference carrier wave) used for modulation. Frequency mixing circuit, the carrier and multiplies the millimeter wave band local oscillation circuit generates a signal from the parallel-serial conversion unit 114 (modulation) to Mi supplied to the amplifier 117 to generate a transmission signal of the re-wave band.

The amplification unit 117 amplifies the millimeter-wave electric signal after frequency conversion and supplies it to the transmission line coupling unit 108. The amplification unit 117 is connected to the bidirectional transmission line coupling unit 108 via an antenna terminal (not shown).

The transmission line coupling unit 108 transmits the millimeter wave signal generated by the transmission side signal generation unit 110 to the millimeter wave signal transmission line 9. The transmission line coupling portion 108 is composed of an antenna coupling portion. The antenna coupling portion constitutes an example or a part of the transmission line coupling portion 108 (signal coupling portion). The antenna coupling portion is, in a narrow sense, a portion that couples an electronic circuit in a semiconductor chip with an antenna arranged inside or outside the chip, and in a broad sense, a semiconductor chip and a millimeter-wave signal transmission line 9. The part that combines signals. For example, the antenna coupling portion comprises at least an antenna structure. The antenna structure refers to a structure at a coupling portion with a millimeter wave signal transmission line 9, and may be a structure that couples an electric signal in the millimeter wave band to the millimeter wave signal transmission line 9, and does not mean only the antenna itself. ..

The millimeter wave signal transmission line 9, which is a millimeter wave propagation path, may be configured as a free space transmission line, for example, to propagate in the space inside the housing. Further, preferably, it is configured by a waveguide structure such as a waveguide, a transmission line, a dielectric line, or a dielectric, and has a structure in which electromagnetic waves in the millimeter wave band are confined in a transmission line and has a characteristic of being efficiently transmitted. It is desirable to do. For example, a dielectric transmission line 9A composed of a dielectric material having a relative permittivity in a certain range and a dielectric loss tangent in a certain range may be used. For example, by filling the entire inside of the housing with a dielectric material, a dielectric transmission line 9A is arranged between the transmission line coupling portion 108 and the transmission line coupling portion 208 instead of the free space transmission line. Further, the dielectric transmission line 9A is connected between the antenna of the transmission line coupling portion 108 and the antenna of the transmission line coupling portion 208 by a dielectric line which is a linear member having a certain wire diameter and is made of a dielectric material. May be configured. In addition to the dielectric transmission line 9A, the millimeter-wave signal transmission line 9 having a configuration in which the millimeter-wave signal is confined in the transmission line may be a hollow waveguide in which the periphery of the transmission line is surrounded by a shielding material and the inside is hollow. Good.

Further, the first communication device 100 of this embodiment has a first set value processing unit 7100 including a first set value determination unit 7110, a first set value storage unit 7130, and a first operation control unit 7150 as a substrate. Prepare on 102. The first set value determining unit 7110 determines set values (variables, parameters) for designating the operation of each functional unit of the semiconductor chip 103 (in other words, the overall operation of the first communication device 100). The process of determining the set value is performed, for example, when the product is shipped at the factory. The first set value storage unit 7130 stores the set value determined by the first set value determination unit 7110. The first operation control unit 7150 sets each functional unit (in this example, the modulation unit 115, the frequency conversion unit 116, the amplification unit 117, etc.) of the semiconductor chip 103 based on the set value read from the first set value storage unit 7130. Make it work.

In the example shown in FIG. 1, the first set value processing unit 7100 is provided on the substrate 102. However, as in the example shown in FIG. 2, the first set value processing unit 7100 is equipped with the semiconductor chip 103. It may be mounted on a board 7102 different from the board 102. Further, in the example shown in FIG. 1, the first set value processing unit 7100 is provided outside the semiconductor chip 103, but the first set value processing unit 7100 may be built in the semiconductor chip 103. In this case, the first set value processing unit 7100 shall be mounted on the same board 102 as the board 102 on which each function unit (modulation unit 115, frequency conversion unit 116, amplification unit 117, etc.) to be controlled is mounted. (The figure is omitted).

[Second communication device] In the second communication device 200, a semiconductor chip 203 corresponding to millimeter wave band reception and a transmission line coupling portion 208 are mounted on a substrate 202. The semiconductor chip 203 is an LSI in which an LSI function unit 204 and a signal generation unit 207 (millimeter wave signal generation unit) are integrated. Although not shown, the LSI functional unit 204 and the signal generation unit 207 may not be integrated, as in the first communication device 100.

The semiconductor chip 203 is connected to a transmission line coupling unit 208 similar to the transmission line coupling unit 108. The transmission line coupling unit 208 is an example of a receiving unit, and the same as the transmission line coupling unit 108 is adopted, and the millimeter wave signal is received from the millimeter wave signal transmission line 9 and output to the receiving side signal generation unit 220. ..

The signal generation unit 207 (electric signal conversion unit) has a reception side signal generation unit 220 for performing signal reception control via the millimeter wave signal transmission line 9. The receiving system (reception unit: communication unit on the receiving side) is composed of the receiving side signal generation unit 220 and the transmission line coupling unit 208.

The receiving side signal generation unit 220 signals the millimeter wave electric signal received by the transmission line coupling unit 208 to generate an output signal, so that the amplification unit 224, the frequency conversion unit 225, the demodulation unit 226, and the serial parallel conversion It has a unit 227 and a unification processing unit 228. The amplification unit 224 is an example of an amplitude adjustment unit that adjusts the magnitude of the input signal and outputs the signal. The frequency conversion unit 225 and the demodulation unit 226 may be collectively a so-called direct conversion system.

The receiving side signal generation unit 220 is connected to the transmission line coupling unit 208. The amplification unit 224 on the receiving side is connected to the transmission line coupling unit 208, amplifies the millimeter-wave electric signal after being received by the antenna, and supplies the electric signal to the frequency conversion unit 225. The frequency conversion unit 225 frequency-converts the amplified millimeter-wave electric signal and supplies the frequency-converted signal to the demodulation unit 226. The demodulation unit 226 demodulates the frequency-converted signal, acquires a baseband signal, and supplies the signal to the serial-parallel conversion unit 227.

The serial-parallel conversion unit 227 converts the serial reception data into parallel output data and supplies it to the unification processing unit 228. Similar to the parallel serial conversion unit 114, the serial-parallel conversion unit 227 is provided in the case of a parallel interface specification using a plurality of signals for parallel transmission when this embodiment is not applied. When the original signal transmission between the first communication device 100 and the second communication device 200 is in the serial format, it is not necessary to provide the parallel serial conversion unit 114 and the real parallel conversion unit 227.

When the original signal transmission between the first communication device 100 and the second communication device 200 is in parallel format, the input signal is converted into parallel serial and transmitted to the semiconductor chip 203 side, and also received from the semiconductor chip 203 side. By serial-parallel conversion of signals, the number of signals to be converted in millimeter waves is reduced.

The unification processing unit 228 corresponds to the multiplexing processing unit 113, and separates the signals grouped into one system into a plurality of types of signals _ @ (@ is 1 to N). For example, a plurality of data signals collected in one system of signals are separated from each other and supplied to the LSI functional unit 204.

The LSI functional unit 204 controls the main application of the second communication device 200, and includes, for example, a circuit that processes various signals received from the other party.

Further, the second communication device 200 of the present embodiment has a second set value processing unit 7200 including a second set value determination unit 7210, a second set value storage unit 7230, and a second operation control unit 7250 as a substrate. Prepare for 202. The second set value determining unit 7210 determines set values (variables, parameters) for designating the operation of each functional unit of the semiconductor chip 203 (in other words, the overall operation of the second communication device 200). The process of determining the set value is performed, for example, when the product is shipped at the factory. The second set value storage unit 7230 stores the set value determined by the second set value determination unit 7210. The second operation control unit 7250 sets each functional unit (in this example, the amplification unit 224, the frequency conversion unit 225, the demodulation unit 226, etc.) of the semiconductor chip 203 based on the set value read from the second set value storage unit 7230. Make it work.

In the first example shown in FIG. 1, the second set value processing unit 7200 is provided on the substrate 202, but as in the second example shown in FIG. 2, the second set value processing unit 7200 is a semiconductor chip. It may be mounted on a board 7202 different from the board 202 on which the 203 is mounted. Further, in the example shown in FIG. 1, the second set value processing unit 7200 is provided outside the semiconductor chip 203, but the second set value processing unit 7200 may be built in the semiconductor chip 203. In this case, the second set value processing unit 7200 will be mounted on the same board 202 as the board 202 on which each function unit (amplification unit 224, frequency conversion unit 225, demodulation unit 226) to be controlled is mounted. (The figure is omitted).

[Support for two-way communication] The signal generation unit 107 and the transmission line coupling unit 108 and the signal generation unit 207 and the transmission line coupling unit 208 can be configured to have bidirectional data so that bidirectional communication can be supported. For example, the signal generation unit 107 and the signal generation unit 207 are provided with a signal generation unit on the receiving side and a signal generation unit on the transmitting side, respectively. The transmission line coupling unit 108 and the transmission line coupling unit 208 may be provided separately on the transmitting side and the receiving side, but may also be used for transmission and reception.

In the "bidirectional communication" shown here, the millimeter wave signal transmission line 9 which is a millimeter wave transmission channel is a one-core bidirectional transmission of one system (one core). To achieve this, a half-duplex system that applies Time Division Duplex (TDD) and Frequency Division Duplex (FDD) are applied.

[Connection and operation] The method of frequency-converting an input signal and transmitting the signal is generally used in broadcasting and wireless communication. In these applications, it is possible to deal with problems such as how far communication can be performed (S / N problem with respect to thermal noise), how to deal with reflection and multipath, and how to suppress interference and interference with other channels. Such relatively complicated transmitters and receivers are used.

On the other hand, the signal generation unit 107 and the signal generation unit 207 used in this embodiment have higher frequencies than the frequencies used by complicated transmitters and receivers generally used in broadcasting and wireless communication. It is used in the millimeter-wave band of the band, and since the wavelength λ is short, it is easy to reuse the frequency, and the one suitable for communication between many devices arranged in the vicinity is used.

In this embodiment, unlike the conventional signal interface using electrical wiring, high speed and large capacity can be flexibly supported by transmitting signals in the millimeter wave band as described above. For example, only signals that require high speed and large capacity are targeted for communication in the millimeter wave band, and depending on the device configuration, the first communication device 100 and the second communication device 200 are for low-speed, small-capacity signals. It will be partially equipped with an interface (connection by terminals and connectors) by conventional electrical wiring for power supply and power supply.

The signal generation unit 107 is an example of a signal processing unit that performs predetermined signal processing based on a set value. In this example, the input signal input from the LSI function unit 104 is signal-processed to obtain a millimeter-wave signal. To generate. The signal generation unit 107 is connected to the transmission line coupling unit 108 by a transmission line such as a microstrip line, a strip line, a coplanar line, or a slot line, and the generated millimeter wave signal is transmitted via the transmission line coupling unit 108. It is supplied to the millimeter-wave signal transmission line 9.

The transmission line coupling unit 108 has an antenna structure, and has a function of converting a transmitted millimeter wave signal into an electromagnetic wave and transmitting the electromagnetic wave. The transmission line coupling unit 108 is coupled to the millimeter wave signal transmission line 9, and the electromagnetic wave converted by the transmission line coupling unit 108 is supplied to one end of the millimeter wave signal transmission line 9. A transmission line coupling portion 208 on the second communication device 200 side is coupled to the other end of the millimeter wave signal transmission line 9. By providing the millimeter-wave signal transmission line 9 between the transmission line coupling unit 108 on the first communication device 100 side and the transmission line coupling unit 208 on the second communication device 200 side, the millimeter-wave signal transmission line 9 has a millimeter-wave band. Electromagnetic waves propagate.

A transmission line coupling unit 208 on the second communication device 200 side is coupled to the millimeter wave signal transmission line 9. The transmission line coupling unit 208 receives the electromagnetic wave transmitted to the other end of the millimeter wave signal transmission line 9, converts it into a millimeter wave signal, and supplies it to the signal generation unit 207 (baseband signal generation unit). The signal generation unit 207 is an example of a signal processing unit that performs predetermined signal processing based on a set value. In this example, the converted millimeter wave signal is signal-processed to output a signal (baseband signal). Is generated and supplied to the LSI functional unit 204.

Up to this point, the case of signal transmission from the first communication device 100 to the second communication device 200 has been described, but by configuring both the first communication device 100 and the second communication device 200 to support bidirectional communication, When transmitting the signal from the LSI functional unit 204 of the second communication device 200 to the first communication device 100, the same can be considered, and the millimeter wave signal can be transmitted in both directions.

&lt;Communication processing system: Basic configuration 2&gt; 3 and 4 are a second basic configuration (basic configuration 2) for explaining the signal interface of the wireless transmission device (signal transmission device) of the present embodiment from the aspect of functional configuration. The first example shown in FIG. 3 is a modified example with respect to FIG. 1, and the second example shown with FIG. 4 is a modified example with respect to FIG.

The second basic configuration is characterized in that the set value determined outside the device is stored. In the following, the differences from the first basic configuration will be mainly described. The second basic configuration includes a first input / output interface unit 7170 in place of the first set value determination unit 7110, and a second input / output interface unit 7270 in place of the second set value determination unit 7210. Each of the first input / output interface unit 7170 and the second input / output interface unit 7270 is an example of a setting value receiving unit that receives a setting value from the outside.

The first input / output interface unit 7170 functions as an interface with the first set value storage unit 7130, stores the set value given from the outside in the first set value storage unit 7130, and stores the first set value. Reads the set value stored in unit 7130 and outputs it to the outside. The second input / output interface unit 7270 functions as an interface with the second set value storage unit 7230, stores the set value given from the outside in the second set value storage unit 7230, and also stores the second setting. The set value stored in the value storage unit 7230 is read out and output to the outside.

In the case of the second basic configuration, the set value is determined externally instead of being determined by the first set value processing unit 7100 or the second set value processing unit 7200. For example, the set value may be determined from the design parameters and the state of the actual machine, or the set value may be determined based on the actual operation test of the device. Further, in any case, the set value common to each device may be determined instead of determining the individual set value for each device. This case generally applies when determining the set value from the design parameters, and this case also applies when determining the set value based on an actual operation test with a standard device.

Next, a specific example of fixing the parameter setting, which is a feature of this embodiment, will be given. Although the present invention will be described with reference to Examples, the technical scope of the present invention is not limited to the scope described in Examples described later. Various changes or improvements can be made to the examples described below without departing from the gist of the invention, and the technical scope of the present invention also includes forms in which such changes or improvements are made. Further, the examples described later do not limit the invention according to the claim, and not all combinations of features described in the examples are essential for the means for solving the invention. .. The examples described below include inventions at various stages, and various inventions can be extracted by an appropriate combination of a plurality of disclosed constituent requirements. Each of the examples described later is not limited to being applied individually, but may be applied in any combination to the extent possible. Even if some constituents are deleted from all the constituents shown in the examples, a configuration in which some of these constituents are deleted can be extracted as an invention as long as the effect is obtained.

<p num="0101"> FIG. 5 is a diagram illustrating the first embodiment. Here, in particular, it will be described as a first example of the modulation function unit and the demodulation function unit.</p><p num="0102"> [Modulation function unit: 1st example] FIG. 5A shows the configuration of the modulation function unit 8300A of the first example provided on the transmitting side. The signal to be transmitted (baseband signal: for example, 12-bit image signal) is converted into a high-speed serial data series by the parallel serial conversion unit 8114 (PS: corresponding to the parallel serial conversion unit 114) and supplied to the modulation function unit 8300A. Will be done. The modulation function unit 8300A modulates the signal from the parallel serial conversion unit 8114 as a modulation signal into a millimeter-wave band signal according to a predetermined modulation method.</p><p num="0103"> The modulation function unit 8300A can adopt various circuit configurations depending on the modulation method. For example, in the case of the method of modulating the amplitude, the 2-input type frequency mixing unit 8302 (mixer circuit, multiplier) and the transmitting side A configuration including a local oscillator 8304 may be adopted.</p><p num="0104"> The local oscillator 8304 (first carrier signal generator) on the transmitting side generates a carrier signal (modulation carrier signal) used for modulation. The frequency mixing unit 8302 (first frequency conversion unit) multiplies (modulates) the signal from the parallel serial conversion unit 8114 with the carrier wave in the millimeter wave band generated by the local oscillator 8304 on the transmitting side to transmit the transmission signal in the millimeter wave band. (Modulated signal) is generated and supplied to the amplification unit 8117 (corresponding to the amplification unit 117). The transmitted signal is amplified by the amplification unit 8117 and radiated from the antenna 8136.</p><p num="0105"> [Demodulation function unit: 1st example] FIG. 5B shows the configuration of the demodulation function unit 8400A of the first example provided on the receiving side. The demodulation function unit 8400A can adopt various circuit configurations within a range according to the modulation method on the transmitting side, but here, a method in which the amplitude is modulated so as to correspond to the above description of the modulation function unit 8300A. Will be explained in the case of.</p><p num="0106"> The demodulation function unit 8400A of the first example includes a 2-input type frequency mixing unit 8402 (also referred to as a frequency conversion unit, a mixer circuit, a multiplier, etc.) and a carrier wave reproduction unit 8403, and demodulates by a so-called synchronous detection method. In the synchronous detection method, the carrier wave included in the received signal is reproduced by a carrier wave reproduction unit 8403 different from the frequency mixing unit 8402, and demodulation is performed using the reproduced carrier wave. Although not shown, not only the synchronous detection method but also the envelope detection and the square detection can be applied.</p><p num="0107"> The carrier wave reproduction unit 8403 can adopt various configurations, but here, a line spectrum matching the carrier frequency is generated and input to a resonance circuit or a phase locked loop (PLL) circuit to reproduce the carrier wave. Either the method of performing, the method of frequency multiplication, or the method of inverse modulation is adopted.</p><p num="0108"> The carrier wave reproduction unit 8403 extracts a carrier signal for demodulation (demodulation carrier signal: referred to as a reproduction carrier signal) whose frequency and phase are completely the same as those of the carrier on the transmitting side, that is, frequency-synchronized and phase-synchronized, and frequency mixing. Supply to unit 8402. The frequency mixing unit 8402 multiplies the reproduced carrier wave and the received signal. The multiplication output includes a modulation signal component (baseband signal) and a harmonic component (and a DC component in some cases), which are signal components to be transmitted.</p><p num="0109"> In the illustrated example, it corresponds to the filter processing unit 8410, the clock playback unit 8420 (CDR: Clock Data Recovery), and the serial parallel conversion unit 8227 (SP: serial parallel conversion unit 227) after the frequency mixing unit 8402. ) Is provided. The filter processing unit 8410 is provided with, for example, a low-pass filter (LPF) to remove harmonic components included in the multiplication output.</p><p num="0110"> The millimeter wave reception signal received by the antenna 8236 is input to the variable gain type and low noise type amplification unit 8224 (corresponding to the amplification unit 224: LNA), and after the amplitude adjustment is performed, it is supplied to the demodulation function unit 8400A. The amplitude-adjusted received signal is input to the frequency mixing unit 8402 and the carrier wave reproducing unit 8403, and as described above, the multiplication signal is generated by the frequency mixing unit 8402 by synchronous detection and supplied to the filter processing unit 8410. For the multiplication signal generated by the frequency mixing unit 8402, the waveform (baseband signal) of the input signal sent from the transmitting side is generated by removing the high-frequency component by the low-pass filter of the filtering unit 8410. , It is supplied to the clock reproduction unit 8420.</p><p num="0111"> The clock reproduction unit 8420 (CDR) reproduces a sampling clock based on this baseband signal, and generates a received data series by sampling the baseband signal with the reproduced sampling clock. The generated received data series is supplied to the serial-parallel converter 8227 (SP), and a parallel signal (for example, a 12-bit image signal) is reproduced. There are various clock recovery methods, and for example, the symbol synchronization method is adopted.</p><p num="0112"> [problem] Here, when the wireless transmission device is configured by the modulation function unit 8300A and the demodulation function unit 8400A of the first example, there are the following drawbacks. First, the oscillation circuit has the following drawbacks. For example, in outdoor (outdoor) communication, it is necessary to consider increasing the number of channels. In this case, since it is affected by the frequency fluctuation component of the carrier wave, the required specifications for the stability of the carrier wave on the transmitting side are strict. In in-housing signal transmission and inter-device signal transmission, when transmitting data in millimeter waves, if the transmitting side and the receiving side try to use the usual method used in outdoor wireless communication, the carrier wave is stable. A degree is required, and a highly stable millimeter-wave oscillator circuit with a frequency stability number on the order of ppm (parts per million) is required.</p><p num="0113"> In order to realize a carrier signal with high frequency stability, for example, a method of forming a highly stable millimeter-wave oscillation circuit on a silicon integrated circuit (CMOS) can be adopted. In the case of a typical LC oscillator circuit used in a normal CMOS process, the silicon substrate has low insulation, and the wiring that constitutes the inductor is thinner than that of discrete components. Therefore, it is not easy to form a tank circuit having a high Q value (Quality Factor), and it is not easy to realize it. For example, when an inductance is formed on a CMOS chip, its Q value is about 30 to 40.</p><p num="0114"> Therefore, in order to realize an oscillating circuit with high stability, for example, a tank circuit having a high Q value is provided outside the CMOS in which the main body of the oscillating circuit is configured by a crystal oscillator or the like, and the oscillator is oscillated at a low frequency. A method of multiplying the oscillation output and raising it to the millimeter wave band can be adopted. However, in order to realize a function of replacing signal transmission by wiring such as LVDS (Low Voltage Differential Signaling) with signal transmission by millimeter wave, it is not preferable to provide such an external tank on all chips.</p><p num="0115"> As another method for realizing a carrier signal having a high frequency stability number, a method using a frequency multiplication circuit or a PLL circuit with high stability can be adopted, but the circuit scale increases. A method for dealing with this problem will be described in Example 7 and the like described later.</p><p num="0116"> [Action and effect of Example 1] In the first embodiment, as shown in FIG. 5A, a first set value processing unit 7100A for controlling the level of the transmission signal output from the amplification unit 8117 is provided on the transmitting side. The first set value processing unit 7100A includes an output level DAC7152 that sets the output level of the amplification unit 8117 as the first operation control unit 7150. The first set value processing unit 7100A adopts the second basic configuration, but as in the first basic configuration, the first set value determination unit 7110 is used instead of the first input / output interface unit 7170. You may prepare. The output level DAC7152 reads the set value stored in the first set value storage unit 7130 and controls the amplification unit 8117 based on the set value so that the transmission output level becomes an appropriate value. .. The power consumption of the amplification unit 8117 is large when the transmission output level is high, but the power consumption can be reduced by lowering the transmission output level so that the reception level is not excessive or too small.</p><p num="0117"> In other words, a mechanism for managing the transmission power is provided, but the purpose is to prevent it from becoming an excessive level or an underlevel, or SNR (Signal Noise Ratio). The ratio, S / N) should not be too low. By appropriately managing the transmission output level based on the transmission characteristics (communication environment characteristics) such as the transmission distance and the state of the transmission line depending on the arrangement of the transmitter / receiver, the transmission level can be minimized and low power consumption communication (more preferable). Is a communication with less unnecessary radiation).</p><p num="0118"> As a mechanism for managing transmission power, various methods can be adopted from the viewpoint of fixed setting (so-called preset setting) or automatic control, and how to judge the setting level. In the first embodiment, at least a fixed setting method is adopted.</p><p num="0119"> For example, a method of presetting the transmission output level based on the transmission characteristics (communication environment) between transmission and reception is adopted. In that case, as a preferred embodiment, a transmission characteristic index detection unit for detecting the state of the transmission characteristic between the transmission chip which is the transmission device and the reception chip which is the reception device is provided, and the transmission characteristic index signal which is the detection result is used. Refer to it so that the transmission output level on the transmission chip side can be preset. For example, the first set value determination unit 7110 and the second set value determination unit 7210 function as the transmission characteristic index detection unit. For example, a transmission characteristic index detector is provided on the receiving chip side (or the transmission characteristic index detector does not have to be built in the receiving chip), the state of the received wireless signal is detected, and the state detection signal which is the detection result is detected. Refer to to preset the transmission output level on the transmission chip side (store the determined setting value in the first setting value storage unit 7130).</p><p num="0120"> If there is a certain correspondence between the reception level and the SNR, such as the SNR decreasing when the reception level is excessive or too small, using the reception level as a judgment index is equivalent to using the SNR as a judgment index. In the case of a device configuration in which there is no fixed correspondence between the reception level and the SNR, the level management focusing on the SNR may be performed by using, for example, an error rate or the like as a judgment index instead of the reception level. In other words, a detection mechanism (transmission characteristic index detector) that detects a judgment index that reflects the actual transmission characteristics such as reception level and SNR is provided on the receiving chip side, and the output level on the transmitting side is manually set by referring to the detection result. Set with. Alternatively, as shown in the figure, the set value determined externally is stored in the first set value storage unit 7130 via the first input / output interface unit 7170.</p><p num="0121"> The method of the first embodiment is not a method of automatic control by feedback, but is intended to refer to the reception level and SNR on the receiving side as a judgment index when presetting the transmission level. Since the reception level and SNR change according to the transmission characteristics such as the transmission distance and the state of the transmission line depending on the arrangement of the transmitter / receiver, the reception level reflects the actual transmission characteristics instead of directly judging the distance between transmissions and receptions. And SNR are used as judgment indicators to control the transmission level. That is, the transmission chip has a variable transmission output level, and the power consumption is reduced by lowering the transmission output level, depending on the transmission characteristics such as the transmission distance and the state of the transmission line depending on the arrangement of the transmitter / receiver. Set the transmission output level appropriately so that the reception status becomes appropriate by referring to the reception level and SNR that change. For example, when the reception level (that is, reception strength) is high, the transmission output level is lowered, and when the reception level is low, the transmission output level is raised so that the reception level is neither excessive nor too small. Set the output level. By minimizing the transmission output level, the output amplifier can be operated with low power consumption to realize low power consumption communication.</p><p num="0122"> By setting the output level of the transmitter to the minimum required level in consideration of the communication environment (communication range, transmission line characteristics, etc.), the output of the transmitter can be lowered to the minimum level for use. , The power consumption of the transmitter output amplifier can be reduced. Low power consumption communication can be realized by operating the transmission output amplifier with low power consumption. When the input level to the receiver becomes a constant level, the resistance to strong input can be relaxed and the power consumption of the receiver can be reduced. Since the transmission output is at the minimum required level, radiation to the outside of the device is also mitigated. Since it is not an automatic control method based on feedback, the circuit scale for controlling (setting) the output level can be smaller and the power consumption can be smaller than in the case of automatic control.</p><p num="0123"> In the first embodiment, since feedback control is not performed, it cannot be said that it can be managed to an appropriate level in conjunction with a change in the communication environment, but when the communication environment changes, the set value is manually changed. You can deal with it.</p><p num="0124"> Further, in the first embodiment, as shown in FIG. 5B, a second set value processing unit 7200A for controlling the level of the received signal output from the amplification unit 8224 is provided on the receiving side. The second set value processing unit 7200A includes an output level DAC7252 that sets the output level of the amplification unit 8224 as the second operation control unit 7250. The second set value processing unit 7200A adopts the second basic configuration, but as in the first basic configuration, the second set value determination unit 7210 is used instead of the second input / output interface unit 7270. You may prepare. The output level DAC7252 reads the set value stored in the second set value storage unit 7230 and controls the amplification unit 8224 based on the set value to control the output level of the amplification unit 8224 (in other words, the demodulation function). Make sure that the input level to part 8400) is an appropriate value. By doing so, the demodulation function unit 8400 can perform proper demodulation processing regardless of the reception level of the antenna 8236.</p><p num="0125"> In the configuration example shown in FIG. 5C, the receiving chip 8002 (receiving device) is provided with an amplification unit 8224, a demodulation function unit 8400, and a transmission environment index detection unit 8470. The transmission environment index detection unit 8470 detects the state of the transmission environment between the transmission chip 8001 (transmission device) and the reception chip 8002, and outputs a transmission environment index signal based on the detection result. In particular, in this example, it will be described as detecting the reception level. That is, the transmission environment index detection unit 8470 of this example forms a mechanism for detecting the reception level (input level), performs reception level detection, detects the input level, and outputs the level detection signal Vdet which is the detection result. Output. The transmission environment index detection unit 8470 may be supplied with the input signal of the demodulation function unit 8400 (that is, the received signal, specifically the output of the amplification unit 8224), or the baseband signal demodulated by the demodulation function unit 8400 (that is, the output of the amplification unit 8224). That is, the output signal of the demodulation function unit 8400) may be supplied. The transmission environment index detection unit 8470 detects the input level based on the input signals.</p><p num="0126"> Based on the input level of the receiver indicated by the level detection signal Vdet output from the transmission environment index detector 8470, the distance between the transmitter and receiver and the amount of attenuation due to the transmission line can be obtained, and the output level of the transmitter is set to the optimum value. can do. Feedback control of the transmission output level is performed based on the level detection signal Vdet, but in the case of signal transmission within or between devices, once the transmission output level is set to the optimum state, it is dynamically and adaptively frequently performed. It is not necessary to perform this, and the feedback control may be stopped and the set value stored as the optimum value may be used. Although it is different from feedback control, a detection mechanism (transmission characteristic index detection unit) that detects a judgment index that reflects the actual transmission characteristics is provided on the receiving chip 8002 side, and the level detection signal Vdet, which is the detection result, is referred to. The transmission output level of the transmission chip 8001 can be set to an appropriate level (neither too small nor too large). When the amount of attenuation is small, the output level can be lowered and communication can be performed with low power consumption. That is, low power consumption communication can be performed by the transmission chip 8001 (an example of a transmitter) having a variable gain amplification unit 8117 and the receiving chip 8002 (an example of a receiver) having a transmission environment index detection unit 8470.</p><p num="0127"> For example, although not shown, the information detected by the transmission environment index detection unit 8470 may be used by the first set value processing unit 7100A shown in FIG. 5 (A). In this case, for example, the detection information (level detection signal Vdet) acquired by the transmission environment index detection unit 8470 is referred to when the operator sets the transmission output level. Based on the detection result output from the transmission environment index detection unit 8470, the operator first inputs / outputs a set value that makes the transmission output level of the transmission chip 8001 an appropriate level (neither too small nor too large). It is stored in the first set value storage unit 7130 via the interface unit 7170.</p><p num="0128"> The information detected by the transmission environment index detection unit 8470 may be automatically used by the first set value processing unit 7100A shown in FIG. 5 (C). Structurally, it includes a gain control unit 8090 that executes feedback control. In the illustrated example, the gain control unit 8090 is provided outside the transmission chip 8001 and the reception chip 8002. Although not shown, the gain control unit 8090 may be built in either the transmission chip 8001 or the reception chip 8002. The transmission of the level detection signal Vdet between the transmission characteristic index detection unit 8470 and the gain control unit 8090 and the transmission of the signal Gcontt between the gain control unit 8090 and the first set value processing unit 7100A may be either wireless or wired. In the case of wireless communication, either optical or radio waves may be used, and the frequency band may be the same as or different from the wireless signal Sm.</p><p num="0129"> The gain control unit 8090 determines a set value at which the transmission output level of the transmission chip 8001 is an appropriate level (neither too small nor too large) based on the level detection signal Vdet output from the transmission characteristic index detection unit 8470. To do. The determined set value is stored in the first set value storage unit 7130 via the first input / output interface unit 7170. For example, at the beginning of operation, the transmission chip 8001 (amplification unit 8117) starts operation at the maximum output, the reception chip 8002 (transmission characteristic index detection unit 8470) detects the received signal level, and the gain control unit 8090 detects the level. Supply the signal Vdet. The gain control unit 8090 generates a gain control signal Gcont so that the transmission output level becomes an appropriate level based on the level detection signal Vdet, and controls the gain of the amplification unit 8117 of the transmission chip 8001. Feedback control may be performed at regular time intervals during communication processing so as to respond to changes in the communication environment. Although it will not be possible to support feedback control at regular time intervals, it is not essential to install the gain control unit 8090 in the product because the determined set value can be stored in the first set value storage unit 7130. For example, it may be connected at the time of shipment from the factory to make adjustments, and then disconnected.</p><p num="0130"> When the first embodiment is not applied, a constant baseband signal can be obtained by keeping the transmitter output constant at a large level, detecting the signal on the receiving side, and controlling the gain in the receiver. However, between transmission and reception with a short communication distance, communication is performed at an unnecessarily large level, and power consumption is also large. It consumes wasted power. Since the receiver needs to be able to receive even a strong input signal, a circuit with good linearity is required, and the power consumption of the receiver also increases. When the transmission output is large, there is also a problem that the radiation to the outside becomes large.</p><p num="0131"> On the other hand, according to the method of the first embodiment, the transmission output level is managed (set) to an appropriate level according to the transmission characteristics between transmissions and receptions, so that these problems can be solved. Further, on the receiving side, the amplification unit 8224 in the previous stage of the demodulation function unit 8400 adjusts the output level so that the output level becomes appropriate, so that even if the transmission output level is excessive, the demodulation function unit 8400 properly demodulates. Can perform processing. In particular, in signal transmission within or between devices, signal transmission is between fixed positions or known positional relationships in which transmission characteristics such as the distance between transmission and reception and the state of the transmission line are specified. It is easy to properly design the propagation channel of. Therefore, the control of the controller that manages wireless transmission (gain control unit in this example) does not need to be dynamically and adaptively frequently performed unlike general wireless communication, and the wireless transmission characteristics are controlled at the time of manufacturing or design. By calibrating and grasping individual variations, etc., the transmission output level can be preset and statically controlled, and the overall configuration can be made smaller and the power consumption can be reduced.</p>

<p num="0132"> FIG. 6 is a diagram illustrating the second embodiment. Here, in particular, as the second example of the modulation function unit and the demodulation function unit, the differences from the first example of the modulation function unit and the demodulation function unit will be mainly described. Although not shown, the output level of the amplification unit 8117 is set by the first set value processing unit 7100A, and the output level of the amplification unit 8224 is set by further applying the above-described first embodiment to the second embodiment. 2 It may be set by the set value processing unit 7200A. This also applies to other examples described later.</p><p num="0133"> The second embodiment is a system in which a carrier signal is transmitted separately from the transmission target signal (a system for transmission by carrier frequency), and is received from the transmitting side according to the delay amount of the transmission signal wirelessly transmitted from the antenna 8136 to the antenna 8236. When a mechanism for adjusting the phase of the carried signal is provided, the second set value processing unit 7200B is characterized in that the phase adjustment amount is set. Although not shown, the same idea is used in a system that transmits a clock for clock reproduction separately from the data to be transmitted (a system that transmits clocks separately), and the phase of the received clock according to the delay amount of the transmission data (transmission signal). It can also be applied when adjusting.</p><p num="0134"> For example, on the receiving side, the demodulation function unit 8400B is provided with a phase amplitude adjustment unit 8406 having a function of a phase adjustment circuit (phase shifter). A carrier signal is supplied to the phase amplitude adjusting unit 8406 from the transmitting side local oscillation unit 8304 on the transmitting side by wire or wirelessly. Further, on the receiving side, the second set value processing unit 7200B includes a phase shift amount DAC7253 for setting the phase shift amount of the phase amplitude adjusting unit 8406 (phase adjusting circuit) as the second operation control unit 7250. .. The second set value processing unit 7200B adopts the second basic configuration, but as in the first basic configuration, the second set value determination unit 7210 is used instead of the second input / output interface unit 7270. You may prepare.</p><p num="0135"> [Action and effect of Example 2] The second set value storage unit 7230 holds in advance a set value for setting the optimum value of the phase shift amount by the demodulation function unit 8400 (phase adjustment circuit). The phase shift amount DAC7253 reads the set value stored in the second set value storage unit 7230, and based on the set value, sets the demodulation function unit 8400 (the functional unit of the phase shifter of the phase amplitude adjustment unit 8406). By controlling, the phase shift amount of the carrier signal output from the phase amplitude adjusting unit 8406 is set to an appropriate value. By doing so, the demodulation function unit 8400 can perform proper demodulation processing regardless of the amount of signal transmission delay that depends on the transmission characteristics between transmission and reception. That is, proper demodulation processing can be performed by appropriately setting the phase of the carrier signal according to the delay amount of the transmission target signal.</p>

<p num="0136"> FIG. 7 is a diagram illustrating the third embodiment. In the third embodiment, when a function unit (frequency characteristic correction processing unit) for correcting a high frequency component or a low frequency component of the transmitted transmission target signal to be reproduced is provided, the operation setting of the frequency characteristic correction processing unit is set to the first set value. The feature is that it is performed by the processing unit 7100C or the second set value processing unit 7200C.</p><p num="0137"> For example, in the example shown in FIG. 7A, when the filter processing unit 8410 provided after the demodulation function unit 8400 has a waveform equalization function as the frequency characteristic correction processing unit, the operation setting of the equalizer is set. The second set value processing unit 7200C performs this. The filter processing unit 8410 has a low-pass filter 8412 and an equalizer 8414. The equalizer 8414 has an equalizer (that is, waveform equalization) filter that adds a reduced gain to the high frequency band of the received signal, for example, in order to reduce intersymbol interference. The baseband signal demodulated by the demodulation function unit 8400 has the high frequency component removed by the low-pass filter 8412, and the high frequency component is corrected by the equalizer 8414.</p><p num="0138"> [Action and effect of Example 3] The second set value processing unit 7200C of the third embodiment includes an equalizer DAC7254 that sets the operation of the equalizer 8414 (specifically, the tap coefficient is set) as the second operation control unit 7250. The second set value processing unit 7200C adopts the second basic configuration, but as in the first basic configuration, the second set value determination unit 7210 is used instead of the second input / output interface unit 7270. You may prepare. The second set value storage unit 7230 holds in advance the optimum set value (tap coefficient) for the equalizer 8414. The equalizer DAC7254 reads the set value stored in the second set value storage unit 7230 and adjusts the tap coefficient of the equalizer 8414 based on the set value.</p><p num="0139"> In the case of wireless transmission within or between devices using the millimeter wave band or wavelength bands before and after it, even if there is reflection, it is a fixed reflection, so the effect can be easily affected by a small equalizer on the receiving side. Can be removed with. The equalizer can be set by presetting or static control, which is easy to realize.</p><p num="0140"> In FIG. 7A, the case where the receiving side is provided with the waveform equalization function as the frequency characteristic correction processing unit has been described, but the transmitting side is provided with the pre-emphasis unit as the frequency characteristic correction processing unit. The operation of the emphasis unit may be controlled by the first set value processing unit 7100C. For example, as shown in FIG. 7B, a modulation target signal processing unit 8301 having a pre-emphasis unit function is provided in front of the modulation function unit 8300A (frequency mixing unit 8302). The modulation target signal processing unit 8301 (pre-emphasis unit) emphasizes the high frequency component of the transmission target signal in advance and supplies it to the modulation function unit 8300.</p><p num="0141"> In this case, the first set value processing unit 7100C of the third embodiment uses the pre-emphasis DAC7154 as the first operation control unit 7150 to set the operation of the modulation target signal processing unit 8301 (specifically, set the high frequency emphasis degree). I have. The first set value processing unit 7100C adopts the second basic configuration, but as in the first basic configuration, the first set value determination unit 7110 is used instead of the first input / output interface unit 7170. You may prepare. The first set value storage unit 7130 holds in advance the optimum set value (high frequency emphasis degree) for the pre-emphasis unit of the modulation target signal processing unit 8301. The pre-emphasis DAC7154 reads out the set value stored in the first set value storage unit 7130, and adjusts the emphasis degree of the high frequency component of the transmission target signal in the modulation target signal processing unit 8301 based on the set value. Further, although not shown, a high frequency enhancement processing unit as a frequency characteristic correction processing unit is provided on the transmitting side, and while this is controlled by the first set value processing unit 7100C, equalization as a frequency characteristic correction processing unit is performed on the receiving side. A device 8414 may be provided and this may be controlled by the second set value processing unit 7200C.</p>

<p num="0142"> FIG. 8 is a diagram illustrating the fourth embodiment. The fourth embodiment is characterized in that the echo canceller technique is applied in the case of a configuration in which two-way communication is performed. When the transmitted signal covers the received signal, the echo component is suppressed by using a known echo canceller technique. "Echo canceller technology" prevents the signal output from the transmitting side from being picked up by the input side and mixed with noise called echo or howling (hereinafter referred to as the echo component) (that is, the echo component). (Suppress) means technology. There are various methods for suppressing the echo component, but in the fourth embodiment, the method of subtracting the transmission signal whose amplitude and phase is adjusted from the received signal is adopted as the simplest method. "Amplitude phase adjustment" is to adjust both the amplitude and phase of the input signal so that the echo component of the processed signal is suppressed (cancelled) (optimally, the echo component becomes zero). Means to do. In Example 4, the echo component is suppressed by "amplitude phase adjustment", but the method is not necessarily limited to this, and any method may be adopted as long as the method can suppress the echo component.</p><p num="0143"> Each of the first communication device 100 and the second communication device 200 is provided with a function unit of a transmission system and a function unit of a reception system so as to perform bidirectional communication. For example, the first communication device 100 includes an amplification unit 8117_1 and an antenna 8136_1 as functional units of the transmission system, and includes an antenna 8236_1, an amplification unit 8224_1, and a demodulation function unit 8400_1 as functional units of the reception system. The second communication device 200 includes an amplification unit 8117_2 and an antenna 8136_2 as functional units of the transmission system, and also includes an antenna 8236_2, an amplification unit 8224_2, and a demodulation function unit 8400_2 as functional units of the reception system. Further, in order to apply the echo canceller technology, the first communication device 100 includes an echo canceling unit 8380_1 having a phase amplitude adjusting unit 8386_1 and an addition / subtraction unit 8388_1, and the second communication device 200 has a phase amplitude adjusting unit 8386_2 and an addition / subtraction unit 8388_2. It is equipped with an echo canceling unit 8380_2.</p><p num="0144"> The echo canceling unit 8380_1 and the echo canceling unit 8380_2 are examples of echo suppressing units that suppress echo components mixed in the input side of the signals output from the transmitting side. In this configuration, each phase amplitude adjusting unit 8386 is designed to output with phase inversion, and correspondingly, the addition / subtraction unit 8388 is an addition processing unit. When each phase amplitude adjusting unit 8386 outputs without phase inversion, the addition / subtraction unit 8388 may be a subtraction processing unit correspondingly. Each phase amplitude adjusting unit 8386 adjusts the phase and amplitude of the signal modulated by the modulation function unit 8300 and input to the amplification unit 8117, and supplies the adjusted signal to the addition / subtraction unit 8388. The addition / subtraction unit 8388 adds the transmission signal whose amplitude and phase have been adjusted by the phase amplitude adjustment unit 8386 and the reception signal output from the amplification unit 8224. As a matter of fact, the transmission signal whose amplitude and phase are adjusted is subtracted from the reception signal, and the component of the transmission signal on the reception signal is canceled.</p><p num="0145"> [Action and effect of Example 4] The first set value processing unit 7100D includes an echo cancel DAC 7156 that sets the phase shift amount and the amplitude adjustment amount of the phase amplitude adjustment unit 8386_1 of the echo cancel unit 8380_1 as the first operation control unit 7150. The second set value processing unit 7200D includes an echo cancel DAC 7256 that sets the phase shift amount and the amplitude adjustment amount of the phase amplitude adjustment unit 8386_2 of the echo cancel unit 8380_2 as the second operation control unit 7250. The first set value processing unit 7100D and the second set value processing unit 7200D adopt the second basic configuration, but instead of the first input / output interface unit 7170 as in the first basic configuration. The first set value determination unit 7110 may be provided, and the second set value determination unit 7210 may be provided in place of the second input / output interface unit 7270. The first set value storage unit 7130 and the second set value storage unit 7230 each have the optimum values of the phase shift amount and the amplitude adjustment amount by the phase amplitude adjustment unit 8386 so that the component of the transmission signal applied to the received signal can be canceled. The setting value for setting is retained in advance. Each echo cancel DAC 7156 reads out the set values stored in the first set value storage unit 7130 and the second set value storage unit 7230, and based on the set values, the phase of the signal output from the phase amplitude adjusting unit 8386 ( Shift amount) and amplitude level.</p>

<p num="0146"> FIG. 9 is a diagram illustrating the fifth embodiment. In the fifth embodiment, a plurality of pairs (sets) of the transmission line coupling unit 108 and the transmission line coupling unit 208 are provided, whereby a plurality of millimeter-wave signal transmission lines 9 are provided, in other words, a point of increasing the number of channels. It has the characteristics of. In Example 5 (also in Example 6 described later), it is assumed that the millimeter wave signal transmission line 9 is a free space transmission line 9B, but this is not essential. Further, in the fifth embodiment, MIMO (Multi-Input Multi-Output) processing is applied as a countermeasure against interference between channels, but as a difference from the sixth embodiment described later, signal processing for alleviating the degree of demand for interference countermeasures is applied. The feature is that it is performed on the receiving side. "Relaxing the degree of demand for interference countermeasures" means that the distance between channels can be shortened without using a radio signal shield, and that interference countermeasures can be reduced.</p><p num="0147"> It is assumed that the millimeter-wave signal transmission lines 9 of a plurality of systems are installed so as not to interfere spatially (there is no influence of interference), and communication can be performed at the same frequency and at the same time in the signal transmission of a plurality of systems. "No spatial interference" means that signals of a plurality of systems can be transmitted independently. Such a method is called "space division multiplexing". When increasing the number of transmission channels, if space division multiplexing is not applied, for example, it is necessary to apply frequency division multiplexing and use different transport frequencies for each channel, but if space division multiplexing is applied, Even when transport signals with the same transport frequency are used, transmission can be performed without being affected by interference. In the fifth embodiment (also the sixth embodiment described later), the transport frequencies of the respective channels are standardized, but this is not essential, and the transport frequencies of the respective channels may be at least synchronized.</p><p num="0148"> Here, in applying "spatial division multiplexing", it is sufficient that a plurality of millimeter-wave signal transmission lines 9 are formed in a three-dimensional space capable of transmitting millimeter-wave signals, and a plurality of systems are provided in the free space. It is not limited to configuring the millimeter-wave signal transmission line 9 of the above. For example, when a three-dimensional space capable of transmitting a millimeter wave signal (electromagnetic wave) is composed of a dielectric material (tangible object), a plurality of millimeter wave signal transmission lines 9 may be formed in the dielectric material. Good. Further, each of the plurality of millimeter-wave signal transmission lines 9 is not limited to the free space, and may take the form of a dielectric transmission line, a hollow waveguide, or the like.</p><p num="0149"> As a method for increasing the number of channels, there is a so-called frequency division multiplexing method in which a plurality of transmission / reception pairs use different transport frequencies. Full-duplex bidirectional communication can be easily realized by using different transport frequencies, and a situation in which a plurality of transmission / reception pairs communicate independently within the housing of an electronic device can also be realized. However, if frequency division multiplexing is used to increase the number of channels, it is necessary to considerably widen the entire bandwidth used in the millimeter-wave signal transmission line. A free space transmission line can meet this requirement, but it becomes a problem in a transmission line having a limited bandwidth such as a dielectric transmission line.</p><p num="0150"> On the other hand, in wireless transmission within or between devices, it is easy to define the arrangement positions of circuit members, antennas, and the like, so that the space division multiplexing method can be easily applied. In the case of space division multiplexing, basically, each channel (each of a plurality of transmission / reception pairs) can use the same transport frequency, which has an advantage of being freed from the limitation of transmission bandwidth. However, in space division multiplexing, it is necessary to take measures against interference between channels (so-called crosstalk). For example, in a free space transmission line, it is important to keep a sufficient distance between transmitting antennas (or receiving antennas). However, this means that the distance between channels is limited, which is a problem when a large number of antenna pairs (that is, transmission channels) need to be arranged in a narrow space.</p><p num="0151"> As another anti-interference method, for example, a structure that hinders radio wave propagation between transmitting antennas (or between receiving antennas) can be adopted. Further, a method of shortening the distance between channels can be adopted by adopting a structure such as a dielectric transmission line or a hollow waveguide that can confine a radio signal. However, these methods are more costly than free space transmission lines.</p><p num="0152"> On the other hand, a plurality of antennas (the number of antennas may be different between the transmitting side and the receiving side) are provided on the transmitting side and the receiving side, respectively, and a MIMO method using space division multiplexing is used by the plurality of antennas. A technique for expanding the transmission capacity is known. In MIMO system, the transmitting side encodes and multiplexes k transmission data, distributes them to, for example, M antennas and sends them to the transmission space (also called a channel), and the receiving side passes through the transmission space. The received signal received by m antennas (either M m or M = m) is decoded to obtain K received data. That is, in the MIMO method, transmission data is distributed to a plurality of antennas on the transmitting side and transmitted, and reception data is obtained by signal processing from signals received by the plurality of antennas on the receiving side, and the transmission characteristics of the transmission space are used. This is a communication method based on the spatial division multiplex method. In the MIMO method, multiple independent logical paths without crosstalk can be obtained at the same frequency and at the same time, and multiple data can be transmitted by wireless communication using the same frequency at the same time. It is possible to improve the transmission speed.</p><p num="0153"> There are various methods for configuring data transmission by MIMO method, such as singular value decomposition (SVD) of channel matrix and eigenmode transmission using eigenvalue decomposition, but the conventional method generally requires a large amount of calculation. Is big. For example, in order to perform eigenmode transmission, it is necessary to perform an operation on a channel matrix of m rows × M columns, where M is the number of antennas on the transmitting side and m is the number of antennas on the receiving side.</p><p num="0154"> In Example 5 (also in Example 6 described later), as a method for alleviating the problems in the space division multiplexing method using such MIMO method, signal processing for alleviating the degree of demand for interference countermeasures is performed on the receiving side. .. Basically, as shown in FIG. 9, a MIMO processing unit 604 is provided on the receiving side, and interference countermeasures are taken from the side of baseband signal processing so that the antenna interval can be narrowed. The MIMO processing unit 604 is an example of a matrix operation processing unit (transmission characteristic correction unit) that performs matrix operations based on a channel matrix whose elements are the transfer functions of each antenna pair between transmission and reception. Specifically, the MIMO processing unit 604 transmits millimeter-wave signals between the transmitting side antenna 136 and the receiving side antenna 236 for each of the plurality of antennas 136 and the corresponding plurality of transmission target signals. A correction calculation is performed based on the transmission characteristics of the road 9 (transmission space). The transmission characteristics are represented by a channel matrix, and as a correction operation, an inverse matrix operation is performed on the transmission target signal of each channel.</p><p num="0155"> The significance of the correction calculation (inverse matrix calculation) is that by correcting the transmission characteristic component for the demodulated signal, it is possible to acquire the transmission target signal excluding the influence of the transmission characteristic as the processed signal. is there. If the modulation scheme of each channel is the same, the demodulation component based on the unwanted wave received by the antenna 236 is completely canceled. When the modulation method of each channel is different, it cannot be said that the unnecessary wave components are completely canceled, but it can be prevented from being affected by the correspondence of the demodulation processing.</p><p num="0156"> Here, the MIMO processing in the MIMO processing unit 604 of the fifth embodiment is characterized in that it is a MIMO processing that targets only the direct wave between transmission and reception. This is because in MIMO processing in wireless transmission between devices and in a housing, which can be usually adopted, radio waves transmitted from the transmitting side are reflected and diffracted by parts and walls in the housing, and are placed in a multipath environment. As a multipath countermeasure that the same radio wave reaches the receiving side from the same path, one receiving antenna can receive multiple received signals that also target reflected waves that follow a different path from the direct wave emitted from the same transmitting antenna. It is very different from the signal processing to be handled. By using millimeter waves (or microwaves) with relatively short wavelengths in wireless signal transmission within or between devices, a millimeter wave signal transmission line 9 to which spatial division multiplexing is applied is formed. This is because the space can be free of obstacles that are substantially obstructive to wireless transmission, in which case there is little need to consider the effects of reflected waves.</p><p num="0157"> In a multipath environment, when radio waves from a plurality of routes are received on the receiving side, the time required for the radio waves from the transmitting side to reach the receiving side differs depending on the route because the distances of the plurality of routes are different. Therefore, a plurality of radio waves out of phase may be received on the receiving side, and as a result, the waveform of the received signal may be distorted and the signal may not be decoded. MIMO processing can be applied as a countermeasure. In this case, the idea of the channel matrix naturally fits the multipath countermeasure.</p><p num="0158"> On the other hand, the MIMO processing of Example 5 and Example 6 described later is different from the MIMO processing for such multipath countermeasures, and the concept of the channel matrix is also different from that for multipath countermeasures. However, in an environment with abundant reflected waves, the inverse matrix of the channel matrix is easy to solve, but in a real environment where only direct waves exist and no reflected waves exist, it is difficult to obtain the inverse matrix of the channel matrix. Is a concern. In the fifth and sixth embodiments, the antenna arrangement is restricted to prevent the inverse matrix of the channel matrix from becoming difficult to obtain.</p><p num="0159"> At that time, in the fifth embodiment, the antenna arrangement (the distance between each antenna on the transmitting side and the receiving side) was determined so that the number of multipliers (amplifier elements) and adders required for MIMO processing could be reduced. Set to the one, and perform MIMO processing on the receiving side accordingly. In other words, the antenna arrangement is decided so that the number of MIMO processing can be reduced, and the MIMO processing on the receiving side that targets only the direct wave according to it is performed. However, depending on these relationships, the necessity of orthogonal detection or synchronous detection in the demodulation function unit 8400 depends on the relationship. Envelope detection and square detection can be applied if orthogonal detection and synchronous detection are not required. By setting the distance between each antenna 136 on the transmitting side and each antenna 236 on the receiving side so that orthogonal detection and synchronous detection are unnecessary conditions, it is advisable to adopt a configuration in which envelope detection and square detection are applied. .. In any case, by applying MIMO processing to the receiving side, the request for interference countermeasures when the free space transmission line is used is alleviated. Preferably, MIMO processing is performed in the baseband on the receiving side by sharing the carrier frequency of each channel, and more preferably, the amount of MIMO processing (inverse matrix calculation amount) is reduced by restricting the antenna arrangement.</p><p num="0160"> It is preferable to make the carrier frequency of each channel common, but this is not essential. It suffices if the carrier frequencies of the channels are at least synchronized. The basic idea of space division multiplexing is that the frequencies of carrier signals are usually shared (same). If the frequency of the carrier signal on the transmitting side is made common, the influence of the carrier frequency is surely the same for each channel, so that MIMO processing in the baseband region can be performed reliably and efficiently. If the carrier frequency differs depending on the channel, it is necessary to take measures such as providing a demodulation circuit and a frequency selection filter corresponding to each carrier frequency on the receiving side for each channel, which increases the scale of the device. In these respects, the advantage of having the same carrier frequency for each channel is great.</p><p num="0161"> In the first example shown in FIG. 9A, the receiving side has a one-chip configuration with respect to the N system, and the transmitting side uses a semiconductor chip 103 accommodating the modulation function unit 8300 (MOD) for each system (a configuration in which the semiconductor chip 103 is used for each system. It is called an N-to-1 configuration). In the second example shown in FIG. 9B, the receiving side has a one-chip configuration, and the transmitting side also has a one-chip configuration, which is a one-to-one configuration. In the case of adopting the configuration of the second example, since the transmission side has a one-chip configuration, it is not essential that the modulation function unit 8300 in the transmission side signal generation unit 110 includes the transmission side local oscillation unit 8304 for each system. That is, it is preferable to provide only one system of the transmitting side local oscillator 8304, and to perform frequency conversion (modulation) of the remaining systems using the carrier signal itself generated by the transmitting side local oscillator 8304. In the third example shown in FIG. 9C, the transmitting side has a one-chip configuration, and the receiving side uses a chip for each system (referred to as a one-to-N configuration). In the fourth example shown in FIG. 9 (D), the transmitting side uses a chip for each system, and the receiving side also uses a chip for each system (N to N configuration). In the case of the third example and the fourth example, a MIMO processing unit 604 shared by all systems is provided between the demodulation function unit 8400 (DEMOD) of each system and the serial parallel conversion unit 8227.</p><p num="0162"> In each of the first to fourth examples, a second set value processing unit 7200E that controls the operation of the MIMO processing unit 604 is provided. The second set value processing unit 7200E of the fifth embodiment is used as the second operation control unit 7250 (not shown) to set the operation of the MIMO processing unit 604 (for details, the coefficients of the matrix calculation of MIMO processing (corresponding to the matrix elements)). It is equipped with a MIMO coefficient DAC7257 that performs (setting). The second set value processing unit 7200E adopts the second basic configuration, but as in the first basic configuration, the second set value determination unit 7210 is used instead of the second input / output interface unit 7270. You may prepare. The optimum MIMO processing parameters (values of each matrix element described later) that can suitably cancel crosstalk are investigated in advance, and the values (examples of set values) are set in advance as the second set value of the second set value processing unit 7200E. It is stored in the storage unit 7230. The second operation control unit 7250 reads the set value (value of each matrix element) stored in the second set value storage unit 7230 and sets it in the MIMO processing unit 604.</p><p num="0163"> Hereinafter, a specific description will be given focusing on MIMO processing on the receiving side. In the following, unless otherwise specified, for the sake of simplicity, one-way communication from the first communication device 100 to the second communication device 200 will be described. Further, as the chip configuration of the transmission system, as an optimum form, a case where the transmission side signal generation unit 110 (accommodating the modulation function unit 8300) for the M system is housed in one semiconductor chip 103 is shown. As for the receiving system, as an optimum form, the case where all the receiving side signal generation units 220 (accommodating the demodulation function unit 8400) for the M system are housed in one semiconductor chip 203 is shown. That is, from the first communication device 100 equipped with one semiconductor chip 103 accommodating the transmission side signal generation unit 110 for the M system, one semiconductor chip accommodating the reception side signal generation unit 220 for the M system. One-way communication to the second communication device 200 equipped with 203 will be described.</p><p num="0164"> [Overview of MIMO processing applied to the receiving side] 10 to 11 are diagrams illustrating an outline of MIMO processing applied to the receiving side. Here, FIG. 10 is a diagram illustrating an operation of MIMO processing applied to the receiving side. FIG. 11 is a diagram illustrating the basics of the operation method of MIMO processing applied to the receiving side.</p><p num="0165"> In FIG. 10, the antenna 136 and the antenna 236 are each set to M so that the number of transmission channels in space division multiplexing is M. A millimeter-wave signal is transmitted from each of the transmitting antennas 136 to the receiving antennas 236 arranged opposite to each other. In FIG. 10, the solid line shows the desired wave directly transmitted from the antenna 136_a (a is any of 1 to M) to the antenna 236_a arranged opposite to the antenna 136_a. The dotted line indicates that the antenna 136_a is directly transmitted from the antenna 136_a to another antenna 236_b (b is any of 1 to M and b a) that is not arranged to face the antenna 136_a. It is an unnecessary wave (interference wave). Both the desired wave and the unwanted wave are direct waves transmitted directly from the antenna 136_a to the antenna 236_a and the antenna 236_b.</p><p num="0166"> Here, the channel matrix H applied to the MIMO processing operation is expressed by Eq. (1-1). In the M-by-M channel matrix H, the matrix element h_{i, j}Of, the element of i = j is the element related to the desired wave, and the element of i j is the element related to the unnecessary wave. The received signal r at this time is expressed by Eq. (1-2). Note that s is a transmission signal and v is noise.</p><p num="0167"><maths num="1"><img id="000002" he="95" wi="156" file="JP5779850B2_D0001.tif" img-format="tif" img-content="drawing" /></maths></p><p num="0168"> As shown in FIG. 10B, in the MIMO processing on the receiving side in the MIMO processing unit 604, the inverse matrix H of the channel matrix H^-1Is multiplied by the received signal r. As a result, on the receiving side, the signal to be transmitted s (more specifically, the noise component H^-1 V) is obtained. The transmission target signal s is a baseband signal before modulation. That is, the MIMO processing in the MIMO processing unit 604 is the matrix element h._{i, j}It becomes a matrix operation using the value of. For details, the inverse matrix H^-1The inverse matrix calculation in the MIMO processing unit 604 based on is demodulation of the received signal in which the desired wave and the unnecessary wave are mixed so that the component based on the unnecessary wave received by the antenna 236 on the receiving side is canceled. It is a process of superimposing a component based on an unnecessary wave and a component opposite to the component based on an unnecessary wave on the output in the baseband region. If MIMO processing is applied in the baseband region after demodulation on the receiving side, the transmission target signal s that is not affected by the interference wave can be acquired. As a result, when multiplex transmission is realized by time division multiplexing, even if the millimeter-wave signal transmission line 9 is set to the free space transmission line 9B, the degree of demand for interference countermeasures can be relaxed, and interference countermeasures become unnecessary or become unnecessary. Interference measures can be reduced. In FIG. 10B, for convenience of illustration, the second set value processing unit 7200E is shown outside the semiconductor chip 203.</p><p num="0169"> FIG. 11 shows the relationship between MIMO processing applied to the receiving side and the carrier frequency. The first communication device 100 includes a frequency mixing unit 8302 for each channel as a modulation function unit 8300. In this example, the frequency mixing section 8302 of each channel (system) is a method of modulating the amplitude and does not adopt quadrature modulation. The modulation function unit 8300 has one transmitter local oscillation unit 8304 that is shared by all channels. The frequency mixing unit 8302 of each channel modulates the carrier signal itself generated by the local oscillator 8304 on the transmitting side. This configuration is convenient because the semiconductor chip 103 on the transmitting side has a one-chip configuration.</p><p num="0170"> The second communication device 200 includes an amplitude detection circuit 8403 for each channel as a demodulation function unit 8400. The amplitude detection circuit 8403 does not employ orthogonal detection or synchronous detection, but simply demodulates the amplitude component of the amplitude-modulated wave. For example, an envelope detection circuit or a self-mounted detection circuit is adopted.</p><p num="0171"> If one transmitting side local oscillator 8304 shared by all channels is provided and the carrier signal itself generated by the transmitting side local oscillator 8304 is used by the frequency mixing unit 8302 of each channel to perform modulation, each system The effect of the carrier frequency is the same. By sharing the carrier frequency of all systems in order to take advantage of the basic advantages of time division multiplexing, the influence of the carrier frequency is the same for each system, so MIMO processing can be performed in the baseband region on the receiving side.</p><p num="0172"> [Relationship between antenna placement restrictions and MIMO processing amount] FIG. 12 shows the relationship between the restrictions on antenna arrangement and the amount of MIMO processing (inverse matrix calculation amount). FIG. 12 shows the simplest configuration with two channels (two antenna pairs). As shown in FIG. 12 (A), the semiconductor chip 103 on the transmitting side is provided with the antenna 136_1 and the antenna 136_2, and the semiconductor chip 203 is provided with the antenna 236_1 so as to face the antenna 136_1 and is positive with the antenna 136_2. Antenna 236_2 is provided so as to face it. The antenna 136 is equivalent to the antenna 8136, and the antenna 236 is equivalent to the antenna 8236. Hereinafter, this point is the same in other descriptions.</p><p num="0173"> By "face-to-face" is meant that the antenna pairs are arranged so that the antennas do not have directivity-dependent phase characteristics. In other words, it means that the angle of radiation of the desired wave from the antenna 136 and the angle of incidence on the corresponding antenna 236 are zero. If the "face-to-face" relationship is broken, correction may be performed based on the phase characteristics depending on the directivity of the antenna. In the following, unless otherwise specified, the antenna pairs are arranged in a face-to-face state.</p><p num="0174"> The distance between the antennas related to the desired wave is d1. That is, the facing distance between the antenna 136_1 of the semiconductor chip 103 and the antenna 236_1 of the semiconductor chip 203 is d1, and similarly, the facing distance between the antenna 136_2 of the semiconductor chip 103 and the antenna 236_2 of the semiconductor chip 203 is also It is d1. On the other hand, the distance between the antennas related to the unwanted wave is d2. That is, the distance between the antenna 136_1 of the semiconductor chip 103 and the antenna 236_2 of the semiconductor chip 203 is d2, and similarly, the distance between the antenna 136_2 of the semiconductor chip 103 and the antenna 236_1 of the semiconductor chip 203 is also d2. The desired wave transmitted from the antenna 136_1 is directly received by the antenna 236_1. The desired wave transmitted from the antenna 136_2 is directly received by the antenna 236_2. The unwanted wave transmitted from the antenna 136_1 is directly received by the antenna 236_2. The unwanted wave transmitted from the antenna 136_2 is directly received by the antenna 236_1. Since "distance d1 &lt;distance d2", even if the transmission levels of the antenna 136_1 and the antenna 136_2 are the same, the reception level of the desired wave received by the antenna 236_1 (or the antenna 236_2) is higher than that of the antenna due to the distance attenuation. It is higher than the reception level of unwanted waves received by 236_2 (or antenna 236_1). This is also a factor in the existence of the inverse matrix of the channel matrix.</p><p num="0175"> MIMO processing generally requires complex number operations (or equivalent processing), which increases the circuit scale. On the other hand, the amount of MIMO processing (inverse matrix calculation amount) can be reduced by restricting the antenna arrangement by focusing on the point that only the direct wave is targeted and performing the signal processing according to it. For example, in the case of two channels, the distance difference (also referred to as the path difference) between the antenna-to-antenna distance d1 of the desired wave and the antenna-to-antenna distance d2 of the unnecessary wave is Δd (= d2-d1), and the distance attenuation element is α. In the M-by-M channel matrix H, the matrix element h_{i, j}Is represented by a complex number, each is represented by a combination of a real number term (cos term) and an imaginary number acquisition term (sin term). In this case, if a certain condition is set for the path difference Δd, each matrix element h of the channel matrix H_{i, j}Is only a real number term (cos term) or an imaginary number acquisition term (sin term). Also, due to the presence of the distance attenuation element α, the inverse matrix H of the channel matrix H^-1Is always required, and the inverse matrix H^-1Each element of is also only a real number term (cos term) or an imaginary number term (sin term). For example, when normalizing the channel matrix H in the case of 2 channels, the elements of the desired wave (each element of 1 row 1 column and 2 rows 2 columns) are real terms (Re ==) regardless of the path difference Δd. 1) and the inverse matrix H^-1Each element of is also a real term (Re'). On the other hand, the elements of unnecessary waves (each element of 1 row 2 columns and 2 rows 1 column) are either real number term only, imaginary number term only, or "real number term + imaginary number term" depending on the path difference Δd.</p><p num="0176"> For example, as shown in FIG. 12 (B), when "Δd = (n / 2 + 1/4) λc (n is 0 or a positive integer greater than or equal to 1)" is satisfied (referred to as path condition 1), the path is passed. The difference Δd is an odd multiple of π / 2 in terms of phase, and since the real number term is zero, only the imaginary number term (Im) is available, and the inverse matrix H^-1Each element of is also an imaginary term (Im') only (Fig. 12 (B-1)). If it deviates from the relationship of path condition 1, it becomes "real number term + imaginary number term", but when it is close to the relationship of path condition 1, the real number term component is much smaller than the imaginary number term component, and it is treated as practically only the imaginary number term. May be good. That is, it is optimal to completely satisfy Δd = (n / 2 + 1/4) λc, but this relationship may deviate slightly. In the present specification, "only the imaginary number term" includes the case where there is such a slight deviation. Here, in detail, when n is 0 or even, the imaginary term becomes "+1", so that the unnecessary wave rotates by π / 2 with the path difference with respect to the desired wave. At this time, when the time difference corresponding to the path difference Δd is Δt and D = exp (-jωΔt), detH = 1- (α · D)).²= 1- (α -j)²&gt; 1 , so the inverse matrix H of the channel matrix H^-1Can exist. In MIMO processing, -α D = -j α is obtained, so that the unnecessary component is topologically -π / 2 with respect to the desired component. On the other hand, when n is an odd number, the imaginary term becomes "-1", so that the unnecessary wave turns by -π / 2 due to the path difference with respect to the desired wave. At this time, "detH = 1- (α D)²= 1- (α j)²&gt; 1 , so the inverse matrix H of the channel matrix H^-1Can exist. In MIMO processing, -α D = j α is obtained, so that the unnecessary component is topologically π / 2 with respect to the desired component.</p><p num="0177"> In any case, the element of the desired wave of 1 row 1 column and 2 rows 2 columns is only the real number term, and the element of the unnecessary wave of 1 row 2 columns and 2 rows 1 column is only the imaginary term term. Therefore, the amount of MIMO processing can be reduced. Since the imaginary term Im'(orthogonal component) exists, even if the modulation method when this configuration example is not applied is originally a modulation method that does not involve an orthogonal component, such as the ASK method or the BPSK method. As the demodulation function unit 8400, a demodulation circuit having an orthogonal component (that is, an orthogonal detection circuit) is required. For example, Fig. 12 (B-2) shows the state of the received signal of each channel when path condition 1 is applied and MIMO processing is performed on the receiving side, as opposed to the case where the modulation method is the BPSK method. ing. As shown in the figure, the components of the first channel ch1 are the I-axis component (Ch1_I) of the originally desired wave (for the desired signal) and the Q-axis component (Ch2_Q') of the unnecessary wave for the unnecessary signal by the second channel ch2. Antenna 236_1 will receive as a composite. The component of the 2nd channel ch2 is the combination of the I-axis component (Ch2_I) of the originally desired wave (for the desired signal) and the Q-axis component (Ch1_Q') of the unnecessary wave for the unnecessary signal by the 1st channel ch1. Will be received. As can be seen from the figure, since the desired wave and the unnecessary wave are orthogonal to each other, the demodulation function unit 8400 requires an orthogonal detection circuit. In MIMO processing on the receiving side, the component of the unnecessary wave that appears as an orthogonal component with respect to the desired signal is canceled, so that the demodulation function unit 8400 requires an orthogonal detection circuit.</p><p num="0178"> As shown in Fig. 12 (C), when "Δd = (n / 2) λc (n is a positive integer of 1 or more)" is satisfied (referred to as path condition 2), the path difference Δd is π in phase. Since the relationship is an integral multiple of, and the imaginary term is zero, only the real term (Re ) is available, and the inverse matrix H^-1Each element of is also only a real number term (Re ') (Fig. 12 (C-1)). If it deviates from the relationship of path condition 2, it becomes real number term + imaginary term term , but it is close to the relationship of this path condition. Occasionally, the imaginary term component is much smaller than the real term component and may be treated as substantially only the real term. That is, it is optimal to completely satisfy Δd = (n / 2) λc, but this relationship may deviate slightly. In the present specification, "only the real number term" includes the case where there is such a slight deviation. Here, in detail, when n is an even number, the real number term is "+1", so that the unnecessary wave has a phase difference of 2π with respect to the desired wave (that is, it has the same phase and polarity). ). At this time, "detH = 1- (α D)²= 1- (α 1)²&gt; 1 , so the inverse matrix H of the channel matrix H^-1Can exist. In MIMO processing, "-α · D = -α" is obtained, so that the unnecessary component is topologically "-π" (that is, in-phase / reverse polarity) with respect to the desired component. On the other hand, when n is an odd number, the real number term is "-1", so the unnecessary wave has a phase difference of π with respect to the desired wave (that is, it has in-phase and opposite polarity). At this time, "detH = 1- (α D)²= 1- (α -1)²&gt; 1 , so the inverse matrix H of the channel matrix H^-1Can exist. In MIMO processing, -α · D = α is obtained, so that the unnecessary component is topologically 2π (that is, in-phase / same polarity) with respect to the desired component.</p><p num="0179"> In any case, the elements of the desired wave of 1 row 1 column and 2 rows 2 columns are real number terms, and the elements of unnecessary waves of 1 row 2 columns and 2 rows 1 column are only real number terms. Therefore, the amount of MIMO processing can be reduced. In this case, since the imaginary term (orthogonal component) does not exist, if the modulation method when this configuration example is not applied is a modulation method that originally does not involve an orthogonal component, such as the ASK method, the demodulation function unit. The 8400 eliminates the need for an orthogonal component demodulation circuit (that is, an orthogonal detection circuit). For example, Fig. 12 (C-2) shows each channel when path condition 2 is applied and MIMO processing is performed on the receiving side, as opposed to the case where the modulation method is the ASK method when this configuration example is not applied. The state of the transmitted signal of is shown. As shown in the figure, the components of the first channel ch1 are the I-axis component (Ch1_I) of the originally desired wave (for the desired signal) and the I-axis component (Ch2_I') of the unnecessary wave for the unnecessary signal by the second channel ch2. Antenna 236_1 will receive as a composite. The component of the second channel ch2 is the combination of the I-axis component (Ch2_I) of the originally desired wave (for the desired signal) and the I-axis component (Ch1_I') of the unnecessary wave for the unnecessary signal by the first channel ch1. Will be received. As can be seen from the figure, in the MIMO processing on the receiving side, it is sufficient to cancel the component of the unnecessary signal that appears as an in-phase component with respect to the desired wave, and the demodulation function unit 8400 does not require an orthogonal detection circuit.</p><p num="0180"> The difference between the desired wave antenna-to-antenna distance d1 and the unwanted wave antenna-to-antenna distance d2 between the transmitting side antenna 136 and the receiving side antenna 236 is the transmission characteristic of the transmission space (free space transmission line 9B in this example). Channel matrix H (or its inverse matrix H)^-1It suffices that each element of the unnecessary wave (also) is set so that it can be represented by only a real number term or only an imaginary number term. Focusing on the characteristics based on the set value of the path difference Δd, the antenna arrangement satisfies the above-mentioned path condition 1 or path condition 2, so that the unnecessary wave element of the channel matrix is an imaginary term only or a real number. Only terms can be used, and the inverse matrix operation processing in the MIMO processing unit 604 can be simplified. In particular, by satisfying the path condition 2 which is only a real number term, the demodulation function unit 8400 can be configured without using an orthogonal detection circuit, and the configuration can be made extremely simple.</p><p num="0181"> [Action and effect of Example 5] Where each matrix element h_{i, j}The value of depends on the transmission characteristics of the transmission space (millimeter wave signal transmission line 9) between the antenna 136 and the antenna 236, but in the case of "wireless transmission within or between devices", the communication environment characteristics are generally the same. Fixed values can be used because they can be considered invariant. Therefore, each optimal matrix element h that can preferably cancel crosstalk._{i, j}The value of is checked in advance, and the matrix element of the inverse matrix based on the value (an example of the set value) is stored in advance in the second set value storage unit 7230 of the second set value processing unit 7200E. That is, in this case, the matrix element of the inverse matrix of the channel matrix corresponds to the setting value for performing the matrix operation based on the channel matrix having the transfer function of each antenna pair between transmission and reception as an element. The MIMO processing unit 604 is a set value (each matrix element h) stored in the second set value storage unit 7230._{i, j}(Value of) is read, and MIMO processing is performed based on the set value. By doing so, the MIMO processing unit 604 on the receiving side can suitably cancel the crosstalk.</p>

<p num="0182"> FIG. 13 is a diagram illustrating the sixth embodiment. Example 6 is similar to Example 5 in that MIMO processing is applied as a countermeasure against interference between channels when trying to increase the number of channels, but signal processing for alleviating the degree of demand for interference countermeasures is performed on the transmitting side. The point to be performed is different from that of the fifth embodiment. Basically, as shown in FIG. 13, a MIMO processing unit 601 is provided on the transmitting side, and interference countermeasures are taken from the side of baseband signal processing so that the antenna interval can be narrowed.</p><p num="0183"> The MIMO processing unit 601 is an example of a matrix operation processing unit (transmission characteristic correction unit) in which the MIMO processing unit 604 performs matrix operations based on a channel matrix whose elements are the transfer functions of each antenna pair between transmission and reception. Specifically, the MIMO processing unit 601 transmits millimeter-wave signals between the transmitting side antenna 136 and the receiving side antenna 236 for each of the plurality of antennas 136 and the corresponding plurality of transmission target signals. A correction calculation is performed based on the transmission characteristics of the road 9 (transmission space). The transmission characteristics are represented by a channel matrix, and as a correction operation, an inverse matrix operation is performed on the transmission target signal of each channel. The MIMO processing in the MIMO processing unit 601 is characterized in that it is the MIMO processing that targets only the direct wave between transmission and reception in each antenna. These points are the same as in the case of the MIMO processing unit 604 provided on the receiving side. However, the essential significance of the correction calculation (inverse matrix calculation) of the MIMO processing unit 601 is that the transmission characteristic is corrected in advance and transmitted, so that the receiving side receives the transmission target signal without being affected by the transmission characteristic. To be able to do it. The components of the unnecessary signal received by the antenna 236 are completely canceled, and only the components based on the desired signals are input to the demodulation function unit 8400.</p><p num="0184"> Also in the sixth embodiment, preferably, by restricting the antenna arrangement, it is possible to prevent the inverse matrix of the channel matrix from becoming difficult to obtain. In that case, set the antenna arrangement (sending side and receiving side antenna spacing) to a fixed one so that the number of multipliers (amplifier elements) and adders required for MIMO processing can be reduced. MIMO processing on the transmitting side is performed accordingly. In other words, the antenna arrangement is determined so that the number of MIMO processing can be reduced, and MIMO processing is performed on the transmitting side that targets only the direct wave that matches it. Depending on these relationships, the necessity of quadrature modulation in the modulation function unit, the demodulation method (whether to use the injection synchronization method, the envelope detection, or the self-square detection), etc. are affected. In any case, by applying MIMO processing to the transmitting side, the request for interference countermeasures when the free space transmission line 9B is used is alleviated, and by sharing the carrier frequency of each channel, the transmitting side is based. MIMO processing is performed in a band, and the amount of MIMO processing (inverse matrix calculation amount) is reduced by restricting the antenna arrangement.</p><p num="0185"> In the first example shown in FIG. 13 (A), the transmitting side has a one-chip configuration for the N system, and the receiving side uses a semiconductor chip 203 containing the demodulation function unit 8400 (DEMOD) for each system (a configuration in which the semiconductor chip 203 is used for each system. 1 to N configuration). When adopting the configuration of the first example, it is advisable to provide only one system of the transmitting side local oscillator 8304, and to perform frequency conversion (modulation) of the remaining systems using the carrier signal itself generated by the transmitting side local oscillator 8304. In the second example shown in FIG. 13B, the transmitting side has a one-chip configuration, and the receiving side also has a one-chip configuration, which is a one-to-one configuration. In the case of adopting the configuration of the second example, since the receiving side has a one-chip configuration, it is not essential that the demodulation function unit 8400 in the receiving side signal generation unit 220 is provided with the receiving side local oscillation unit 8404 for each system. Only one system of the side local oscillator 8404 may be provided, and the remaining system may demodulate the received signal by synchronous detection using the reproduction carrier signal itself generated by the receiving side local oscillator 8404. In the third example shown in FIG. 13C, the receiving side has a one-chip configuration, and the transmitting side uses a chip for each system (N to 1 configuration). In the fourth example shown in FIG. 13 (D), the transmitting side uses a chip for each system, and the receiving side also uses a chip for each system (N to N configuration). In the case of the third example and the fourth example, a MIMO processing unit 601 shared by all systems is provided between the modulation function unit 8300 (MOD) of each system and the parallel serial conversion unit 8114.</p><p num="0186"> In each of the first to fourth examples, the first set value processing unit 7100F for controlling the operation of the MIMO processing unit 601 is provided. The first set value processing unit 7100F of the sixth embodiment serves as the first operation control unit 7150 (not shown) and sets the operation of the MIMO processing unit 601 (for details, the coefficients of the matrix calculation of the MIMO processing (corresponding to the matrix elements)). It is equipped with a MIMO coefficient DAC7157 that performs (setting). The first set value processing unit 7100F adopts the second basic configuration, but as in the first basic configuration, the first set value determination unit 7110 is used instead of the first input / output interface unit 7170. You may prepare. The optimum MIMO processing parameters (values of each matrix element described later) that can suitably cancel crosstalk are investigated in advance, and the values (examples of set values) are set in advance as the first set value of the first set value processing unit 7100F. It is stored in the storage unit 7130. The first operation control unit 7150 reads the set value (value of each matrix element) stored in the first set value storage unit 7130 and sets it in the MIMO processing unit 601.</p><p num="0187"> Hereinafter, a specific description will be given focusing on MIMO processing on the transmitting side. In the following, unless otherwise specified, for the sake of simplicity, one-way communication from the first communication device 100 to the second communication device 200 will be described. Further, as the chip configuration of the transmission system, as an optimum form, a case where the transmission side signal generation unit 110 (accommodating the modulation function unit 8300) for the M system is housed in one semiconductor chip 103 is shown. Regarding the receiving system, the case where the receiving side signal generation unit 220 (accommodating the demodulation function unit 8400) for the M system is housed in each separate semiconductor chip 203 is shown. That is, from the first communication device 100 equipped with one semiconductor chip 103 accommodating the transmitting side signal generating unit 110 for M systems, M semiconductor chips accommodating the receiving side signal generating unit 220 for one system. One-way communication to the second communication device 200 equipped with 203 will be described.</p><p num="0188"> [Overview of MIMO processing applied to the sender] 14 to 15 are diagrams illustrating an outline of MIMO processing applied to the transmitting side. Here, FIG. 14 is a diagram illustrating an operation of MIMO processing applied to the transmitting side. FIG. 15 is a diagram illustrating the basics of the operation method of MIMO processing applied to the transmitting side.</p><p num="0189"> In FIG. 14, the antenna 136 and the antenna 236 are each set to M so that the number of transmission channels in space division multiplexing is M. A millimeter-wave signal is transmitted from each of the transmitting antennas 136 to the receiving antennas 236 arranged opposite to each other. In FIG. 14, the solid line shows the desired wave directly transmitted from the antenna 136_a (a is any of 1 to M) to the antenna 236_a arranged opposite to the antenna 136_a. The dotted line indicates that the antenna 136_a is directly transmitted from the antenna 136_a to another antenna 236_b (b is any of 1 to M and b a) that is not arranged to face the antenna 136_a. It is an unnecessary wave (interference wave). Both the desired wave and the unnecessary wave are direct waves transmitted directly from the antenna 136_a to the antenna 236_a and the antenna 236_b.</p><p num="0190"> As inferred from the comparison between FIG. 10 (A) and FIG. 14 (A), the channel matrix H applied to the MIMO processing operation is represented by the equation (1-1) as in the fifth embodiment. However, in the sixth embodiment, since the MIMO processing operation is performed on the transmitting side, as shown in FIG. 14B, in the MIMO processing on the transmitting side in the MIMO processing unit 601, the inverse matrix H of the channel matrix H is performed.^-1Is multiplied by the transmission target signal s ^ (s hat). As a result, on the receiving side, the transmission target signal s ^ (more specifically, noise v) is obtained. The transmission target signal s ^ is a signal input to the MIMO processing unit 601. As you can see, if MIMO processing is applied to the transmitting side, it is possible to acquire the transmission target signal s ^ that is not affected by the interference wave. As a result, in the case of realizing multiplex transmission by spatial division multiplexing, even if the millimeter-wave signal transmission line 9 is set to the free space transmission line 9B, the degree of requirement for interference countermeasures can be relaxed, and interference countermeasures become unnecessary or. Interference measures can be reduced.</p><p num="0191"> Inverse matrix H^-1The inverse matrix calculation in the MIMO processing unit 601 based on the above is the transmission target of another channel received together with the desired wave based on the transmission target signal (desired signal) of the own channel by the antenna 236 on the receiving side when the sixth embodiment is not applied. This is a process for canceling the components of unnecessary waves based on the signal (unnecessary signal). More specifically, it is a process in which a component opposite to the component of the unwanted wave based on the unwanted signal is superimposed in advance so that the desired wave can be transmitted.</p><p num="0192"> FIG. 15 shows the relationship between MIMO processing applied to the transmitting side and the carrier frequency. The first communication device 100 includes a frequency mixing unit 8302 for each channel as a modulation function unit 8300 after the MIMO processing unit 601. In this example, the frequency mixing section 8302 is shown to perform quadrature modulation, but this is not essential. The modulation function unit 8300 has one transmitter local oscillation unit 8304 that is shared by all channels. The frequency mixing unit 8302 of each channel modulates the carrier signal itself generated by the local oscillator 8304 on the transmitting side. This configuration is convenient because the semiconductor chip 103 on the transmitting side has a one-chip configuration. The second communication device 200 includes a modulation function unit 8300 having a frequency mixing unit 8402 and a receiving side local oscillation unit 8404 for each channel. In this example, the frequency mixing unit 8402 is shown to perform quadrature detection so as to correspond to quadrature modulation on the transmitting side. If the transmitting side is not quadrature modulation, the frequency mixing unit 8402 does not have to perform quadrature detection. In this way, one transmitting side local oscillator 8304 shared by all channels is provided, and the carrier signal itself generated by the transmitting side local oscillator 8304 is used by the frequency mixing unit 8302 of each channel to perform modulation. Then, the influence of the transport frequency becomes the same in each system. By sharing the carrier frequency of all systems in order to take advantage of the basic advantages of time division multiplexing, MIMO processing can be performed in the baseband because the effect of the carrier frequency is the same for each system.</p><p num="0193"> [Action and effect of Example 6] As in Example 5, each matrix element h_{i, j}The value of depends on the transmission characteristics of the millimeter-wave signal transmission line 9 between the antenna 136 and the antenna 236, but in the case of "wireless transmission within or between devices", the communication environment characteristics are generally unchanged. You can think of it, so you can use a fixed value. Therefore, each optimal matrix element h that can preferably cancel crosstalk._{i, j}The value of is checked in advance, and the matrix element (an example of the set value) of the inverse matrix based on the value is stored in the first set value storage unit 7130 in advance. That is, in this case, the matrix element of the inverse matrix of the channel matrix corresponds to the setting value for performing the matrix operation based on the channel matrix having the transfer function of each antenna pair between transmission and reception as an element. The MIMO processing unit 601 is a set value (each matrix element h) stored in the first set value storage unit 7130._{i, j}(Value of) is read, and MIMO processing is performed based on the set value. By doing so, the baseband signal can be corrected in advance by the MIMO processing unit 601 on the transmitting side so that the crosstalk can be suitably canceled on the receiving side.</p><p num="0194"> [Modified Examples of Example 5 and Example 6] When the antenna pair has a phase characteristic φa depending on the directivity, it is necessary to consider the influence of this phase characteristic φa in addition to the path difference Δd. Basically, the influence of the phase characteristic φa may be corrected for consideration. In that case, for example, the influence of the phase characteristic φa may be converted into a distance and expressed, and the pass condition 1 and the pass condition 2 may be recalculated after considering the influence.</p><p num="0195"> Even when there are 3 channels (3 transmission / reception antenna pairs) or more, the concept of antenna placement constraints can be applied as in the case of 2 channels. For example, even when there are three or more antenna pairs, by satisfying the path condition Δd for the path difference Δd, the channel matrix and its inverse matrix can be the real term Re, as in the case of two antenna pairs. Or it is a component of only the imaginary term Im. That is, the element of the desired wave of i = j is the real number term Re, and the element of the unnecessary wave of i j is the imaginary number term Im. Also, even when there are three or more antenna pairs, the channel matrix and its inverse matrix are only the real number Re, as in the case of two antenna pairs by satisfying the path condition 2 for the path difference Δd. It becomes a component of. That is, the element of the desired wave of i = j is the real term Re, and the element of the unnecessary wave of i j is also the real term Re.</p><p num="0196"> Generally, when it comes to M channel, as inferred from the channel matrix, both path condition 1 and path condition 2 can be multiplied by real numbers by 2 M in 2-axis modulation such as QPSK.²This is required, and M is required for 1-axis modulation such as ASK method and BPSK method.²You will need one. This means that when there are three or more antenna pairs, simply applying the same idea as when there are two antenna pairs increases the amount of calculation of real multiplication by the square of the antenna logarithm. .. Therefore, in the case of 3 channels or more, the real number multiplication number is not the square of the number of channels (so as to suppress the increase of the real number multiplication number) based on the characteristics of the antenna arrangement. Specifically, we pay attention to the fact that the influence of the interference waves from the adjacent antennas is the largest and that the interference waves from the other antennas are relatively small. As a result, the antenna spacing is determined in consideration of unnecessary waves (interference waves) from adjacent antennas, and this is also applied to other antennas. As a result, the amount of real number multiplication as a whole is reduced.</p><p num="0197"> For example, when the path condition 1 is applied, only the real term for the desired wave antenna 136 and the imaginary term for the unwanted wave antenna 136 on both sides of the inner channel except both ends need to be considered. That is, when focusing on the i-th channel, the desired wave from the i-th antenna 136_i to the antenna 236_i, the unnecessary wave from the i-1st antenna 136_i-1 to the antenna 236_i, and the i + 1th antenna 136_i + We only need to think about unwanted waves from 1 to antenna 236_i. Therefore, in the channel matrix and its inverse matrix, in row i, the element of the desired wave in column i is a real term, the element of the unwanted wave in columns i-1 and i + 1 is an imaginary term, and other unnecessary. The wave element is zero.</p><p num="0198"> When the path condition 2 is applied, only the real number term for the desired wave antenna 136 and the real number term for the unwanted wave antenna 136 on both sides of the inner channel except both ends need to be considered. That is, when focusing on the i-th channel, the desired wave from the i-th antenna 136_i to the antenna 236_i, the unnecessary wave from the i-1st antenna 136_i-1 to the antenna 236_i, and the i + 1th antenna 136_i + We only need to think about unwanted waves from 1 to antenna 236_i. Therefore, in the channel matrix and its inverse matrix, in row i, the desired wave element in column i is a real number term, the unnecessary wave elements in columns i-1 and i + 1 are also real number terms, and other unnecessary items are unnecessary. The wave element is zero.</p><p num="0199"> In both path condition 1 and path condition 2, the number of real multiplications in the channels at both ends is two, and the number of real multiplications in the inner channel excluding the channels at both ends is three, which is higher than when this method is not applied. The amount of MIMO processing can be reduced. In other words, in the case of M channel (M is an integer of 3 or more), in both path condition 1 and path condition 2, real number multiplication is 2 {2 2 + (M-2) in 2-axis modulation such as QPSK. ) 3}, and {2.2+ (M-2) 3} for 1-axis modulation such as ASK and BPSK. This means that when there are three or more antenna pairs, the amount of calculation of real number multiplication can be reduced compared to the case where the same idea as in the case of two is simply applied as it is.</p><p num="0200"> The matters described in Example 5 and Example 6 were application examples in the case where the transmitting side antenna 136 and the receiving side antenna 236 are arranged in a two-dimensional manner. However, the methods of Example 5 and Example 6 can be applied not only to the case where the transmitting and receiving antennas are arranged two-dimensionally, but also to the case where the transmitting and receiving antennas are arranged three-dimensionally. The desired wave between the semiconductor chip 103 on the transmitting side and the antennas arranged opposite to each other on the receiving side and the unnecessary wave between the antennas not arranged facing each other in three-dimensional space are the same as in the case of the above-mentioned two-dimensional arrangement. Think about it. Even in the case of the three-dimensional arrangement, by setting the path difference Δd between the desired wave and the unnecessary wave to be the above-mentioned path condition 1 or the above-mentioned path condition 2, the same effects as described above can be obtained.</p><p num="0201"> In the fifth and sixth embodiments, as a preferred embodiment, it is premised that signal processing for alleviating the degree of demand for interference countermeasures in the space division multiplexing method by the MIMO method is performed on the receiving side or the transmitting side, and further, a channel matrix is used. Matrix element h_{i, j}It was explained that the value of is treated as a fixed value and the inverse matrix operation of MIMO processing is performed, but the present invention is not limited to this. A technique for treating a parameter as a fixed value can be similarly applied to any of the methods for adjusting (correcting) the amount of crosstalk cancellation in the space division multiplexing method based on the MIMO method. For example, Japanese Patent Application Laid-Open No. 2009-272823, Japanese Patent Application Laid-Open No. 2009-272822, Japanese Patent Application Laid-Open No. 2008-124533 and the like disclose a method for calculating an antenna weighting coefficient matrix. The value of the matrix element may be treated as a fixed value, and a weight matrix operation (weighting process based on a weighting coefficient matrix) may be performed. In this case, the matrix element of the antenna weighting coefficient matrix corresponds to the setting value for performing the matrix operation based on the channel matrix having the transfer function of each antenna pair between transmission and reception as an element.</p>

<p num="0202"> 16 to 17 are diagrams for explaining the seventh embodiment. Here, in particular, a third example of the modulation function unit and the demodulation function unit will be described. Here, FIG. 16 shows a transmission side signal generation unit 8110 (transmission side communication unit) composed of a modulation function unit 8300C (modulation unit 115 and frequency conversion unit 116) of the third example provided on the transmission side and peripheral circuits thereof. ) Is a diagram for explaining a basic configuration example. FIG. 17 shows the basics of the reception side signal generation unit 8220 (reception side communication unit) composed of the demodulation function unit 8400C (frequency conversion unit 225 and demodulation unit 226) of the third example provided on the reception side and its peripheral circuits. It is a figure explaining the configuration example.</p><p num="0203"> Example 7 (third example of the modulation function unit and the demodulation function unit) is characterized in that an injection lock (injection synchronization) method is applied. In particular, the difference from the eighth embodiment described later is that the second set value processing unit 7200A appropriately sets the self-propelled frequency of the receiving side local oscillation unit 8404 and the injection amount for injection lock.</p><p num="0204"> The injection lock method is applied for the following reasons. That is, in the case of wireless transmission to which the millimeter wave band is applied, if a wireless method (wireless communication method) as used in general outdoors (outdoors) is applied, high stability is required for the carrier frequency. .. This means that a complicated oscillation circuit having a circuit configuration with high frequency stability is required, and it means that the device configuration as a whole becomes complicated. For example, in order to realize a frequency carrier signal with high stability on the order of ppm (parts per million), the circuit scale becomes large when an external reference component, a frequency multiplication circuit, a PLL circuit, or the like is used. Also, when trying to realize the entire oscillation circuit including the tank circuit (resonator circuit consisting of an inductor and a capacitor) with a silicon integrated circuit, it is actually difficult to form a tank circuit with a high Q value, and the Q value There is no choice but to place a high tank circuit outside the integrated circuit.</p><p num="0205"> However, when considering the realization of high-speed wireless signal transmission between electronic devices arranged at relatively short distances or within electronic devices in a frequency band with a shorter wavelength (for example, millimeter wave band), the carrier frequency is set. It seems unwise to seek high stability. Rather, it is better to consider using an oscillation circuit with a simple circuit configuration by relaxing the stability of the carrier frequency, and also simplifying the device configuration as a whole. However, if the stability of the transport frequency is simply relaxed, frequency fluctuation (difference between the transport frequency used in the transmission circuit and the transport frequency used in the reception circuit) becomes a problem, depending on the modulation / demodulation method, and an appropriate signal is used. There is a concern that transmission cannot be performed (proper demodulation cannot be performed).</p><p num="0206"> On the other hand, if the injection lock method is applied, even if the frequency stability of the carrier signal for modulation is relaxed when wireless signal transmission is performed between devices or within the device (housing), the receiving side The signal to be transmitted can be demodulated appropriately. Since the frequency stability of the carrier signal may be relaxed, an oscillation circuit having a simple circuit configuration can be used, and the device configuration as a whole can be simplified. Since the frequency stability of the carrier signal may be relaxed, the entire oscillation circuit (and the frequency conversion unit) including the tank circuit can be formed on the same semiconductor substrate. A 1-chip oscillator circuit (semiconductor integrated circuit) with a built-in tank circuit and a 1-chip communication circuit (semiconductor integrated circuit) with a built-in tank circuit are realized. This will be described in detail below.</p><p num="0207"> As a countermeasure to the problem in the first embodiment (the first example of the modulation function unit and the demodulation function unit), the demodulation function unit 8400C of the third example adopts the injection synchronization (injection lock) method. By using the injection synchronization method as the carrier wave synchronization means, a simple and low power consumption circuit can be configured. In the case of using the injection synchronization method, it is preferable to perform appropriate correction processing in advance on the modulation target signal so that injection synchronization on the receiving side can be facilitated. Typically, the signal to be modulated is modulated after suppressing the direct current near component, that is, the low frequency component near DC (direct current) is suppressed (cut) and then modulated, so that the carrier frequency is near fc. The modulation signal component of the above should be as small as possible so that injection synchronization on the receiving side can be facilitated. In the case of the digital method, for example, DC-free coding is performed in order to eliminate the generation of DC components due to the continuation of the same code.</p><p num="0208"> Further, in order to use it as a reference for injection synchronization on the receiving side, the reference carrier frequency corresponding to the carrier signal used for modulation is transmitted in addition to the transmission signal (modulated signal) modulated in the millimeter wave band. Is desirable. The reference carrier signal is a signal in which the frequency and phase (more preferably, the amplitude) corresponding to the carrier signal used for modulation output from the transmitting side local oscillating unit 8304 are always constant (invariant), and is typically modulated. It is the carrier signal itself used for, but it is not limited to this as long as it is at least synchronized with the carrier signal. For example, a signal having a different frequency synchronized with the carrier signal used for modulation (for example, a harmonic signal) or a signal having the same frequency but having a different phase (for example, an orthogonal carrier signal orthogonal to the carrier signal used for modulation) may be used.</p><p num="0209"> Depending on the modulation method and modulation circuit, when the output signal of the modulation circuit itself contains a carrier signal (for example, standard amplitude modulation or ASK) or when the carrier wave is suppressed (carrier suppression method amplitude modulation or ASK or PSK). Etc.). Therefore, the circuit configuration for transmitting the reference carrier signal together with the signal modulated in the millimeter wave band from the transmitting side is the type of the reference carrier signal (whether or not the carrier signal itself used for modulation is used as the reference carrier signal). The circuit configuration will be adopted according to the modulation method and the modulation circuit.</p><p num="0210"> [Modulation function unit: 3rd example] FIG. 16 shows a configuration example of a third example of the modulation function unit 8300C and its peripheral circuits. A modulation target signal processing unit 8301 is provided in front of the modulation function unit 8300C (frequency mixing unit 8302). Each example shown in FIG. 16 is a configuration example corresponding to the case of the digital method, and the modulation target signal processing unit 8301 has a DC component generated by the continuation of the same code with respect to the data supplied from the parallel serial conversion unit 8114. In order to eliminate the possibility of occurrence, DC-free coding such as 8-9 conversion coding (8B / 9B coding), 8-10 conversion coding (8B / 10B coding), and scramble processing is performed. Although not shown, in the analog modulation method, it is preferable to perform high-pass filter processing (or band-pass filter processing) on the signal to be modulated.</p><p num="0211"> Here, in the basic configuration 1 shown in FIG. 16 (A), the reference transfer signal processing unit 8306 and the signal synthesis unit 8308 are provided, and the output signal (transmission signal) and the reference transfer of the modulation circuit (first frequency conversion unit) are provided. The operation of synthesizing (mixing) signals is performed. It is a versatile method that is not affected by the type of reference carrier signal, modulation method, or modulation circuit. However, depending on the phase of the reference carrier signal, the combined reference carrier signal may be detected as a DC offset component during demodulation on the receiving side, which may affect the reproducibility of the baseband signal. In that case, the receiving side should take measures to suppress the DC component. In other words, it is preferable to use a reference carrier signal having a phase relationship in which the DC offset component does not have to be removed at the time of demodulation.</p><p num="0212"> The reference carrier signal processing unit 8306 adjusts the phase and amplitude of the modulated carrier signal supplied from the transmitting side local oscillator 8304 as necessary, and supplies the output signal to the signal synthesis section 8308 as a reference carrier signal. .. For example, in the case of a method in which the output signal itself of the frequency mixing unit 8302 does not essentially include a carrier signal whose frequency and phase are always constant (a method of modulating the frequency and phase), or a harmonic of the carrier signal used for modulation. This basic configuration 1 is adopted when a wave signal or an orthogonal carrier signal is used as a reference carrier signal.</p><p num="0213"> In this case, the harmonic signal or orthogonal carrier signal of the carrier signal used for modulation can be used as the reference carrier signal, and the amplitude and phase of the transmission signal and the reference carrier signal can be adjusted separately. That is, the amplification unit 8117 adjusts the gain focusing on the amplitude of the transmission signal, and at the same time, the amplitude of the reference transfer signal is also adjusted, but the reference transfer signal processing unit adjusts the amplitude to be preferable in relation to the injection synchronization. Only the amplitude of the reference carrier signal can be adjusted with the 8306.</p><p num="0214"> In the basic configuration 1, the signal synthesizer 8308 is provided to synthesize the transmission signal and the reference carrier signal, but this is not essential. As shown in the basic configuration 2 shown in FIG. 16 (B), the transmission signal and the reference carrier signal are received by the respective antennas 8136_1 and 8136_2, preferably by the respective millimeter wave signal transmission lines 9 so as not to cause interference. You may send it to the side. In the basic configuration 2, a reference carrier signal having a constant amplitude can be sent to the receiving side, which is the optimum method from the viewpoint of ease of injection synchronization.</p><p num="0215"> In the case of the basic configuration 1 and the basic configuration 2, there is an advantage that the amplitude and phase of the carrier signal used for modulation (in other words, the transmission signal transmitted) and the reference carrier signal can be adjusted separately. Therefore, it is suitable to set the modulation axis on which the transmission target information is carried and the axis of the reference transfer signal used for injection synchronization (reference transfer axis) to different phases instead of the same phase so that a DC offset does not occur in the demodulated output. Configuration.</p><p num="0216"> When the output signal of the frequency mixing unit 8302 itself can contain a carrier signal having a constant frequency and phase, the basic configuration 3 shown in FIG. 16 (C) does not include the reference carrier signal processing section 8306 and the signal synthesizer 8308. Can be adopted. Only the transmission signal modulated in the millimeter wave band by the frequency mixing unit 8302 may be transmitted to the receiving side, and the transport signal included in the transmission signal may be treated as the reference transport signal, and the output signal of the frequency mixing unit 8302 may be used as another reference. It is not necessary to add a carrier signal and send it to the receiving side. For example, in the case of a method of modulating the amplitude (for example, the ASK method), the basic configuration 3 can be adopted. In this case, preferably, DC-free processing is performed.</p><p num="0217"> However, even in amplitude modulation and ASK, the frequency mixing unit 8302 is positively made into a carrier suppression type circuit (for example, a balanced modulation circuit or a double balanced modulation circuit), and its output is as shown in the basic configuration 1 and the basic configuration 2. A reference carrier signal may be sent together with the signal (transmission signal).</p><p num="0218"> In each of the basic configurations 1 to 3, information based on the injection synchronization detection result on the receiving side is received from the receiving side, and the frequency and millimeter wave of the modulated carrier signal (particularly those used for the injection signal on the receiving side: for example. It is possible to adopt a method of adjusting the phase of the reference carrier signal (reference carrier signal or transmission signal) or the reference carrier signal. It is not essential to transmit information from the receiving side to the transmitting side in millimeter waves, and any method may be used regardless of whether it is wired or wireless. Since the receiving side notifies the optimum information for optimally realizing the injection lock, for example, the first setting value determining unit 7110 of the first setting value processing unit 7100G takes in it and the optimum setting value based on this information. Is determined, and the determined value is stored in the first set value storage unit 7130 in advance. The first operation control unit 7150 reads out the set value stored in the first set value storage unit 7130, and based on the set value, the transmitting side local oscillator unit 8304, the reference carrier signal processing unit 8306, the amplification unit 8117, etc. To control. By doing so, the carrier signal level and the like can be adjusted to an appropriate level on the transmitting side so that the injection lock can be suitably realized on the receiving side. A configuration in which the second set value processing unit 7200G on the receiving side directly controls each functional unit on the transmitting side (a part or all of the functional units to be controlled) without providing the first set value processing unit 7100G. It may be.</p><p num="0219"> In all of the basic configurations 1 to 3, the frequency of the modulated carrier signal (or the reference carrier signal) is adjusted by controlling the local oscillator 8304 on the transmitting side. In the basic configuration 1 and the basic configuration 2, the amplitude and phase of the reference transport signal are adjusted by controlling the reference transport signal processing unit 8306 and the amplification unit 8117. In the basic configuration 1, the amplitude of the reference carrier signal may be adjusted by the amplification unit 8117 that adjusts the transmission power, but in that case, there is a drawback that the amplitude of the transmission signal is also adjusted.</p><p num="0220"> In the basic configuration 3 suitable for the method of modulating the amplitude (analog amplitude modulation or digital ASK), the DC component with respect to the signal to be modulated is adjusted or the degree of modulation (modulation rate) is controlled in the transmitted signal. The carrier frequency component (corresponding to the amplitude of the reference carrier signal) is adjusted. For example, consider the case of modulating a signal in which a DC component is added to a signal to be transmitted. In this case, when the degree of modulation is kept constant, the amplitude of the reference carrier signal is adjusted by controlling the DC component. Further, when the DC component is kept constant, the amplitude of the reference carrier signal is adjusted by controlling the degree of modulation.</p><p num="0221"> However, in this case, it is not necessary to use the signal synthesizer 8308, and only the transmission signal output from the frequency mixing section 8302 is sent to the receiving side, and the carrier signal is automatically modulated by the transmission target signal. And the carrier signal used for modulation are mixed and transmitted. Inevitably, the reference carrier signal is placed on the same axis (in phase with the modulation axis) as the modulation axis on which the transmission target signal of the transmission signal is placed. On the receiving side, the carrier frequency component in the transmission signal is used as the reference carrier signal for injection synchronization. When considered in terms of the phase plane, the modulation axis on which the transmission target information is placed and the axis of the carrier frequency component (reference carrier signal) used for injection synchronization are in phase, and the demodulated output uses the carrier frequency component (reference carrier signal). The resulting DC offset occurs.</p><p num="0222"> Although not shown, in the case of a method of modulating the phase or frequency, only the modulation signal modulated (frequency conversion) in the millimeter wave band by the modulation function unit 8300 (for example, using orthogonal modulation) may be transmitted. However, whether or not injection synchronization can be achieved on the receiving side depends on the injection level (amplitude level of the reference carrier signal input to the oscillation circuit of the injection synchronization method), modulation method, data rate, transfer frequency, etc., and is applicable. Is limited.</p><p num="0223"> [Demodulation function: 3rd example] FIG. 17 shows a configuration example of a third example of the demodulation function unit 8400C and its peripheral circuits. The demodulation function unit 8400C of the third example is provided with the receiving side local oscillation unit 8404, and by supplying the injection signal to the receiving side local oscillation unit 8404, the output signal corresponding to the carrier signal used for modulation on the transmitting side is acquired. To do. Typically, the oscillation output signal synchronized with the carrier signal used on the transmitting side is acquired. Then, the synchronous detection signal is acquired by multiplying (synchronically detecting) the received millimeter wave transmission signal and the carrier signal for demodulation (reproduction carrier signal) based on the output signal of the receiving side local oscillation unit 8404 by the frequency mixing unit 8402 (synchronous detection). To do. As for this synchronous detection signal, the waveform (baseband signal) of the input signal sent from the transmitting side is obtained by removing the high frequency component by the filter processing unit 8410. Hereinafter, the same as in the first example.</p><p num="0224"> The frequency mixing unit 8402 has advantages such as excellent bit error rate characteristics by performing frequency conversion (down-conversion / demodulation) by synchronous detection, and phase modulation and frequency modulation can be applied by developing it into orthogonal detection. Be done.</p><p num="0225"> When supplying the reproduction carrier signal based on the output signal of the local oscillator 8404 on the receiving side to the frequency mixing unit 8402 for demodulation, it is necessary to consider the phase shift, and it is important to provide a phase adjustment circuit in the synchronous detection system. Become. For example, there is a phase difference between the received transmission signal and the oscillation output signal output by the injection synchronization by the local oscillation unit 8404 on the receiving side.</p><p num="0226"> In this example, the demodulation function unit 8400C is provided with a phase amplitude adjustment unit 8430 having not only the function unit (phase adjustment unit) of the phase adjustment circuit but also the function unit (amplitude adjustment unit) for adjusting the injection amplitude. The phase adjusting unit may be provided for either the injection signal to the receiving side local oscillation unit 8404 or the output signal of the receiving side local oscillation unit 8404, or may be applied to both of them. Carrier reproduction functioning as a demodulation side (second) carrier signal generator that generates a demodulation carrier signal synchronized with the modulation carrier signal and supplies it to the frequency mixing section 8402 by the local oscillation section 8404 on the receiving side and the phase amplitude adjustment section 8430. Part 8403 is composed.</p><p num="0227"> As shown by the broken line in the figure, the latter stage of the frequency mixing section 8402 is synchronously detected according to the phase of the reference carrier signal synthesized in the transmission signal (specifically, when the modulated signal and the reference carrier signal are in phase). A DC component suppression unit 8407 that removes the DC offset component that may be included in the signal is provided. The DC component suppression unit 8407 suppresses unnecessary DC components (DC offset components) included in the synchronous detection signal output from the frequency mixing unit 8402. For example, when the reference carrier signal is transmitted from the transmitting side to the receiving side together with the modulated signal, a large DC offset component may be generated in the synchronous detection signal depending on the phase relationship between the modulated signal and the reference carrier signal. The DC component suppression unit 8407 functions to remove the DC offset component.</p><p num="0228"> In supplying the injection signal to the receiving side local oscillator 8404, the received millimeter wave signal may be supplied to the receiving side local oscillator 8404 as an injection signal as shown in the basic configuration 1 shown in FIG. 17 (A). .. Basic configuration 1 if the low frequency component is suppressed (DC-free coding, etc.) in advance on the transmission side and then modulated so that the modulated signal component does not exist in the vicinity of the carrier frequency. But it doesn't matter.</p><p num="0229"> As shown in the basic configuration 2 shown in FIG. 17 (B), a frequency separation unit 8401 is provided, the transmission signal and the reference carrier signal are frequency-separated from the received millimeter wave signal, and the separated reference carrier signal component is used as an injection signal on the receiving side. It may be supplied to the local oscillator 8404. Since the frequency component unnecessary for injection synchronization is suppressed in advance and then supplied, it becomes easy to take injection synchronization.</p><p num="0230"> The basic configuration 3 shown in FIG. 17 (C) corresponds to the case where the transmitting side adopts the basic configuration 2 shown in FIG. 16 (B). In this method, the transmission signal and the reference carrier signal are received by different antennas 8236_1 and 8236_2, preferably by different millimeter-wave signal transmission lines 9 so as not to cause interference. In the basic configuration 3 on the receiving side, a reference carrier signal having a constant amplitude can be supplied to the local oscillator 8404 on the receiving side, which is the optimum method from the viewpoint of ease of injection synchronization.</p><p num="0231"> The millimeter-wave signal received by the antenna 8236 is supplied to the frequency mixing section 8402 and the receiving side local oscillator section 8404 by a distributor (branch filter) omitted from the figure. The local oscillator 8404 on the receiving side outputs a reproduction carrier signal synchronized with the carrier signal used for modulation on the transmitting side by the function of injection synchronization.</p><p num="0232">Whether or not injection synchronization can be achieved on the receiving side (reproduction carrier signal synchronized with the carrier signal used for modulation can be obtained on the transmitting side) depends on the injection level (amplitude of the reference carrier signal input to the oscillation circuit of the injection synchronization method ) . Level), modulation method, data rate, carrier frequency, etc. are also relevant. In addition, it is important to reduce the components in the band that can be injected and synchronized in the transmission signal. For that purpose, DC-free coding is performed on the transmission side to obtain the center (average) frequency of the transmission signal. Should be approximately equal to the carrier frequency and the center (average) phase should be approximately equal to zero (origin on the phase plane).</p><p num="0233"> Although not shown, in the case of a method in which the transmitting side modulates the phase or frequency, the same configuration as in the basic configuration 1 can be adopted. However, the configuration of the demodulation function unit 8400 is actually a demodulation circuit corresponding to phase modulation such as an orthogonal detection circuit and frequency modulation.</p><p num="0234"> In any of the basic configurations 1 to 3, the lock range is controlled by controlling the injection voltage Vi and the self-propelled oscillation frequency fo, in other words, the injection voltage Vi and the self-propelled oscillation frequency so that injection synchronization can be obtained. It is important to adjust fo. For example, an injection synchronization control unit 8440 that performs processing based on the signal in the subsequent stage of the frequency mixing unit 8402 (the signal in the previous stage of the DC component suppression unit 8407 in the example of the figure) is provided. The injection synchronization control unit 8440 has a function of an injection synchronization detection unit that detects information indicating the injection synchronization state of the carrier wave reproduction unit 8403 (reception side local oscillation unit 8404). In this embodiment, the injection synchronization control unit 8440 may be configured by the second set value processing unit 7200G, if necessary. This point will be explained in detail later.</p><p num="0235"> The injection synchronization control unit 8440 determines the injection synchronization status based on the synchronous detection signal (baseband signal) acquired by the frequency mixing unit 8402, and the adjustment target is adjusted so that the injection synchronization can be obtained based on the determination result. Control each part. In that case, the method of dealing with it on the receiving side and the information that contributes to control (not only the control information but also the detection signal that is the source of the control information, etc.) are supplied to the transmitting side as shown by the broken line in the figure. Either one of the methods to be dealt with on the transmitting side or a combination thereof can be adopted. In either case, the injection synchronization adjustment unit that synchronizes the demodulation carrier signal generated by the receiving side local oscillator 8404 with the modulation carrier signal generated by the transmission side local oscillator 8304. Is provided. For example, the reference carrier signal processing unit 8306 and the injection synchronization control unit 8440 are in charge of the functions of the injection synchronization adjustment unit. The method to deal with on the receiving side is that the injection synchronization cannot be achieved on the receiving side unless the millimeter wave signal (especially the reference carrier signal component) is transmitted with a certain intensity, so power consumption and interference resistance are considered. However, there is an advantage that it can be dealt with only by the receiving side. On the other hand, the method to deal with on the transmitting side requires transmission of information from the receiving side to the transmitting side, but the millimeter wave signal can be transmitted with the minimum power that can be injected and synchronized on the receiving side, and the power consumption is reduced. There are advantages such as reduction and improvement of interference resistance.</p><p num="0236"> By applying the injection synchronization method to the signal transmission in the housing (equipment) and the signal transmission between devices, the following advantages can be obtained. The transmitting side local oscillator 8304 on the transmitting side can relax the required specifications for the frequency stability of the carrier signal used for modulation. The local oscillator 8404 on the receiving side that synchronizes the injection needs to have a low Q value that can follow the frequency fluctuation on the transmitting side. Although detailed explanation is omitted, in the injection synchronization method, the Q value affects the lock range, and the lower the Q value, the wider the lock range. This is convenient when the entire receiving side local oscillator 8404 including the tank circuit (inductance component and capacitance component) is formed on CMOS. On the receiving side, the receiving side local oscillator 8404 may have a low Q value, but this point is the same for the transmitting side local oscillator 8304, and the transmitting side local oscillator 8304 has low frequency stability. It may be the one with a low Q value.</p><p num="0237"> CMOS will be further miniaturized in the future, and its operating frequency will be further increased. In order to realize a smaller transmission device with a wider band, it is desired to use a high carrier frequency. In the injection synchronization method of this example, the required specifications for oscillation frequency stability can be relaxed, so that a higher frequency carrier signal can be easily used. The fact that the frequency may be high but the frequency stability may be low (in other words, the Q value may be low) means that the frequency multiplication circuit with high stability is required to realize a carrier signal with high frequency and high stability. It is not necessary to use a PLL circuit or the like for carrier synchronization, and even at a higher carrier frequency, a communication function can be simply realized on a small circuit scale. The local oscillator 8404 on the receiving side acquires the reproduction carrier signal synchronized with the carrier signal used on the transmitting side and supplies it to the frequency mixing section 8402 for synchronous detection. Therefore, a bandpass filter for wavelength selection is performed before the frequency mixing section 8402. It is not necessary to provide. In the reception frequency selection operation, it is practically sufficient to perform control that completely synchronizes the transmission / reception local oscillation circuit (makes injection synchronization possible), and the reception frequency can be easily selected. In the millimeter wave band, the time required for injection synchronization is shorter than that of low frequencies, and the reception frequency selection operation can be completed in a short time.</p><p num="0238"> Since the local oscillation circuit of transmission and reception is completely synchronized, the fluctuation component of the carrier frequency on the transmission side is canceled. The frequency shift method of this embodiment, which will be described later, is vulnerable to a phase shift, but the problem can be solved by applying the injection synchronization method. If injection synchronization is applied, multiple channels can be used in combination with synchronous detection, such as when performing multi-channel or full-duplex bidirectional without using a bandpass filter for wavelength selection on the receiving side. Even if the transmission / reception pairs of the above transmit and receive independently at the same time, they are less susceptible to the problem of interference.</p><p num="0239"> FIG. 18 is a diagram showing a configuration example of the phase amplitude adjusting unit 8406. Here, it is assumed that the transmission information and the reference carrier signal are in an orthogonal relationship. The phase amplitude adjusting unit 8406 has a configuration in which only the phase adjustment is performed as in the first example shown in FIG. 18 (A) and a configuration in which both the phase and the amplitude are adjusted as in the second example shown in FIG. 18 (B). Any of these can be taken. When adjusting both the phase and the amplitude, either the case where the adjustment is performed on the injection side of the local oscillation unit 8404 on the receiving side or the case where the adjustment is performed on the oscillation output side can be adopted. In order to adjust whether or not the injection synchronization functions properly as in the third example shown in FIG. 18C, the injection amplitude may be adjusted on the injection side of the receiving side local oscillator 8404.</p><p num="0240"> FIG. 19 is a diagram illustrating a first example of a configuration example on the transmitter side to which the injection synchronization method is applied. FIG. 20 is a diagram illustrating a first example of a configuration example on the receiver side to which the injection synchronization method is applied. The first example is an embodiment in which a method of controlling so that injection synchronization can be achieved on the receiving side is applied.</p><p num="0241"> FIG. 19 shows the configuration of the transmitting side signal generation unit 8110 (corresponding to the transmitting side signal generation unit 110) of the first example. The transmitting side signal generation unit 8110 includes an encoding unit 8322, a multiplexer unit 8324, and a waveform shaping unit 8326 between the parallel serial conversion unit 8114 and the modulation function unit 8300 (not shown). It is not essential to have all of these functional parts, and they may be provided when those functions are required.</p><p num="0242"> The transmitting side signal generation unit 8110 includes an injection synchronization control unit 8340 that controls each functional unit. The injection synchronization control unit 8340 of this configuration adopts the configuration of the first set value processing unit 7100G, and the first set value determination unit 7110 determines the set value suitable for the injection lock in advance and the first set value storage unit. Store in 7130. The controller unit 8346, which is an example of the first operation control unit 7150, sets encoding and multiplex, waveform shaping, and modulation mode based on the setting values stored in the first setting value storage unit 7130. The oscillation frequency is set, the phase and amplitude of the reference carrier signal are set, the gain and frequency characteristics of the amplification unit 8117 are set, and the antenna characteristics are set. Each setting information is supplied to the corresponding functional unit. The injection synchronization control unit 8340 adopts the first basic configuration as the first set value processing unit 7100G, but like the second basic configuration, the first set value determination unit 7110 is replaced with the first. An input / output interface unit 7170 may be provided.</p><p num="0243"> The encoding unit 8322 performs coding processing such as error correction on the data serialized by the parallel serial conversion unit 8114 (not shown) based on the setting information of the encoding (Encode) pattern from the controller unit 8346. At this time, the encoding unit 8322 applies DC-free coding such as an 8-9 conversion code or an 8-10 conversion code as a function of the modulation target signal processing unit 8301, and the modulated signal component does not exist in the vicinity of the carrier frequency. In order to facilitate injection synchronization on the receiving side.</p><p num="0244"> The multiplexer section 8324 packetizes the data. When the injection synchronization detection unit on the receiver side detects injection synchronization with the correlation of a known pattern, the multiplexer unit 8324 has a known signal waveform based on the setting information of the synchronization detection packet from the controller unit 8346. And known data patterns (for example, pseudo-random signal: PN signal) are inserted regularly.</p><p num="0245"> The waveform shaping unit 8326 performs waveform shaping processing such as frequency characteristic correction, pre-emphasis, and band limitation based on the waveform shaping setting information from the controller unit 8346.</p><p num="0246"> The transmission side signal generation unit 8110 includes a modulation function unit 8300 having a frequency mixing unit 8302 (modulation circuit) and a transmission side local oscillation unit 8304 (transmission side oscillation unit). Further, the transmission side signal generation unit 8110A includes a reference carrier signal processing unit 8306 having a phase amplitude adjustment circuit 8307 and a signal synthesis unit 8308 in addition to the modulation function unit 8300. In this example, the reference carrier signal processing unit 8306 uses the carrier signal itself output from the transmission side local oscillator 8304 as a reference carrier signal, and adjusts the amplitude and phase of the reference carrier signal by the phase amplitude adjustment circuit 8307 to signal. It is supplied to the synthesis unit 8308.</p><p num="0247"> Here, in the configuration shown in FIG. 19, the transmitting side local oscillator 8304 uses a tank circuit on the CMOS chip to generate a carrier signal used for modulation on the CMOS chip. Although not shown, if the first communication device 100 has a clock signal that can be used as a reference, the modulation function unit 8300 may include a frequency multiplication unit 8303 in front of the transmission side local oscillation unit 8304. The frequency multiplication unit 8303 multiplies a "clock signal that can be used as a reference" supplied from a clock signal generation unit (not shown), and supplies the multiplied signal to the local oscillator 8304 on the transmitting side. In this case, the local oscillator 8304 on the transmitting side functions as a synchronous oscillator circuit and generates a carrier signal used for modulation in synchronization with the multiplied signal.</p><p num="0248"> The frequency mixing unit 8302 modulates the carrier signal generated by the transmitting side local oscillator unit 8304 with the processed input signal from the waveform shaping unit 8326 and supplies it to the signal synthesis unit 8308. The phase amplitude adjusting circuit 8307 sets the phase and amplitude of the reference carrier signal to be transmitted based on the phase / amplitude setting information from the controller unit 8346.</p><p num="0249"> The signal synthesis unit 8308 is provided to send the reference carrier signal to the receiving side together with the modulated signal modulated in the millimeter wave band when the antenna 8136 and the antenna 8236 are each one. The signal synthesis unit 8308 is not required when the modulation signal generated by the frequency mixing unit 8302 and the reference carrier signal generated by the reference carrier signal processing section 8306 are transmitted by different antennas.</p><p num="0250"> When the signal synthesizer 8308 sends the reference carrier signal to the receiving side together with the signal modulated in the millimeter wave band, the modulated signal modulated in the millimeter wave band by the frequency mixing unit 8302 and the phase amplitude adjusting circuit 8307 After combining the reference transport signals of the above, it is passed to the amplification unit 8117. When only the modulated signal modulated in the millimeter wave band by the frequency mixing unit 8302 is transmitted to the receiving side, the signal combining unit 8308 is modulated in the millimeter wave band by the frequency mixing unit 8302 without performing the synthesis processing. Only the modulated signal is passed to the amplification unit 8117. The amplification unit 8117 adjusts the amplitude and frequency characteristics of the transmission output of the millimeter-wave signal received from the signal synthesis unit 8308 as necessary, and supplies the signal to the antenna 8136.</p><p num="0251"> As can be understood from the above explanation, when the reference carrier signal is also transmitted to the receiving side together with the signal modulated in the millimeter wave band, whether or not the signal synthesizer 8308 functions is determined by the modulation method and the frequency mixing unit. It is also related to the circuit configuration of 8302. Depending on the modulation method and the circuit configuration of the frequency mixing unit 8302, it is possible to send the reference carrier signal to the receiving side together with the signal modulated in the millimeter wave band without operating the signal combining unit 8308.</p><p num="0252"> In amplitude modulation or ASK, the frequency mixing unit 8302 may be positively used as a carrier wave suppression type modulation circuit, and the reference carrier signal generated by the transmitting side local oscillator 8304 may be transmitted together with the output. In this case, the harmonics of the carrier signal used for modulation can be used as the reference carrier signal, and the amplitudes of the modulated signal and the reference carrier signal can be adjusted separately. That is, the amplification unit 8117 adjusts the gain focusing on the amplitude of the modulated signal, and at the same time, the amplitude of the reference carrier signal is also adjusted. It is possible to adjust only the amplitude of the reference carrier signal with.</p><p num="0253"> FIG. 20 shows the configuration of the receiving side signal generation unit 8220 (corresponding to the receiving side signal generation unit 220). The demodulation function unit 8400, DC component suppression unit 8407, filter processing unit 8410, and clock recovery unit 8420 are the same as those already described. The explanation will be focused on.</p><p num="0254"> The receiving side signal generation unit 8220 includes a controller unit 8446 (an example of the second operation control unit 7250) that controls each functional unit. Further, the receiving side signal generation unit 8220 has a DC component suppression unit 8407, an injection synchronization detection unit 8442 (an example of the second set value determination unit 7210), and a second set value storage unit 7230 in the subsequent stage of the demodulation function unit 8400. Be prepared. The controller 8446 sets the gain and frequency characteristics of the amplification unit 8224, sets the phase and amplitude of the received reference carrier signal, sets the oscillation frequency, sets the modulation mode, sets the filter and equalization, and sets the coding and multiplex. It has functions such as settings. Each setting information is supplied to the corresponding functional unit.</p><p num="0255"> A circuit (bandpass filter circuit, etc.) that extracts only the reference carrier signal component may be arranged on the injection signal side to the local oscillator 8404 on the receiving side (for example, in front of the phase amplitude adjusting unit 8406). In this case, the modulated signal component and the reference carrier signal component are separated from the received millimeter wave signal, and only the reference carrier signal component is supplied to the receiving side local oscillator 8404, which facilitates injection synchronization.</p><p num="0256"> The phase amplitude adjusting unit 8406 sets the phase and amplitude of the received reference carrier signal based on the phase / amplitude setting information from the controller unit 8446. In the figure, the phase amplitude adjusting unit 8406 is arranged on the input end side of the injection signal to the receiving side local oscillator 8404, but the phase amplitude is on the signal path of the receiving side local oscillator 8404 and the frequency mixing unit 8402. The adjustment unit 8406 may be arranged, or both of them may be used in combination.</p><p num="0257"> The controller unit 8446 performs synchronization adjustment so that the demodulation transfer signal generated by the receiving side local oscillation unit 8404 is synchronized with the modulation transfer signal based on the information indicating the injection synchronization state detected by the injection synchronization detection unit 8442. It has a functional part of the injection synchronization adjustment part. The injection synchronization control unit 8440 is composed of the injection synchronization detection unit 8442 and the functional unit (injection synchronization adjustment unit) related to the injection synchronization adjustment of the controller unit 8446.</p><p num="0258"> Here, the injection synchronization control unit 8440 of this configuration adopts the configuration of the second set value processing unit 7200G, and the injection synchronization detection unit 8442, which is an example of the second setting value determination unit 7210, detects the injection synchronization. The information indicating the state (detection result) and the set value based on this information (detection result) are stored in the second set value storage unit 7230. The controller unit 8446, which is an example of the second operation control unit 7250, has each functional unit to be controlled based on the set value read from the second set value storage unit 7230 (in this example, the amplification unit 224, the frequency conversion unit 225, Operate the demodulation unit 226, etc.). That is, the injection synchronization detection unit 8442 determines the injection synchronization state based on the baseband signal acquired by the frequency mixing unit 8402, and the determination result is notified to the controller unit 8446 via the second set value storage unit 7230. To. The injection synchronization state is whether or not the output signal (oscillation circuit output) output from the local oscillation unit 8404 on the receiving side is synchronized with the reference carrier signal on the transmitting side. The synchronization of the oscillator circuit output and the reference carrier signal on the transmitting side is also referred to as "injection synchronization".</p><p num="0259"> The receiving side signal generation unit 8220 determines the self-propelled oscillation frequency of the transmitting side local oscillation unit 8304, the amplitude (injection amplitude) and the phase (injection phase) of the injection signal to the receiving side local oscillation unit 8404 so that injection synchronization can be achieved. Control at least one. Which one to control depends on the device configuration, and it is not always necessary to control all the elements. For example, the controller unit 8446 controls the self-propelled oscillation frequency of the receiving side local oscillation unit 8404 in conjunction with the detection result of the injection synchronization detection unit 8442 so that the injection synchronization can be obtained, and the phase amplitude adjustment unit 8406 is used. Controls the injection amplitude and injection phase to the local oscillator 8404 on the receiving side.</p><p num="0260"> For example, first, the millimeter wave signal (modulated signal or reference carrier signal) transmitted from the transmitting side via the millimeter wave signal transmission line 9 is amplified by the amplification unit 8224 via the antenna 8236. A part of the amplified millimeter-wave signal is injected into the receiving side local oscillation unit 8404 after the amplitude and phase are adjusted by the phase amplitude adjustment unit 8406. In the frequency mixing unit 8402, the millimeter wave signal from the amplification unit 8224 is frequency-converted into a baseband signal by the output signal (reproduction reference carrier signal) from the receiving side local oscillation unit 8404. A part of the converted baseband signal is input to the injection synchronization detection unit 8442, and the information for determining whether or not the receiving side local oscillation unit 8404 is synchronized with the transmission side reference carrier signal is input to the injection synchronization detection unit 8442. Is acquired by and notified to the controller unit 8446.</p><p num="0261"> The controller unit 8446 determines whether or not synchronization has been performed based on the "injection synchronization status" information (referred to as injection synchronization determination information) from the injection synchronization detection unit 8442, for example, one of the following two methods. Or use them in combination.</p><p num="0262"> 1) The injection synchronization detection unit 8442 correlates the restored waveform with a known signal waveform or a known data pattern, and uses the correlation result as injection synchronization determination information. The controller unit 8446 determines that synchronization is achieved when a strong correlation is obtained.</p><p num="0263"> 2) The injection synchronization detection unit 8442 monitors (monitors) the DC component of the demodulated baseband signal, and uses the monitoring result as injection synchronization determination information. When the DC component becomes stable, the controller unit 8446 determines that it is synchronized.</p><p num="0264"> Various methods can be adopted for the mechanisms 1) and 2) above, but the details are omitted here. In addition to 1) and 2) shown here, other methods for determining whether or not synchronization is possible can be considered, and these can also be adopted in this embodiment.</p><p num="0265"> When the controller unit 8446 determines that the injection synchronization is not achieved, the carrier signal used for modulation on the transmitting side and the signal output from the local oscillating unit 8404 on the receiving side (oscillation circuit output) follow a predetermined procedure. The oscillation frequency setting information to the receiving side local oscillator 8404 and the amplitude and phase setting information to the phase amplitude adjustment unit 8406 are changed so that the above can be synchronized (injection synchronization can be achieved). After that, the controller unit 8446 repeats the procedure of determining the injection synchronization state again until good synchronization is obtained.</p><p num="0266"> The baseband signal after the injection synchronization of the local oscillation unit 8404 on the receiving side is correctly performed and the frequency conversion (synchronous detection) by the frequency mixing unit 8402 is supplied to the filter processing unit 8410. The filter processing unit 8410 is provided with an equalizer 8414 in addition to the low-pass filter 8412. The equalizer 8414 has an equalizer (that is, waveform equalization) filter that adds a reduced gain to the high frequency band of the received signal, for example, in order to reduce intersymbol interference. The high-frequency component of the baseband signal is removed by the low-pass filter 8412, and the high-frequency component is corrected by the equalizer 8414. After symbol synchronization, the clock reproduction unit 8420 restores the original input signal based on the coding pattern setting information and the multiplex setting from the controller unit 8446.</p><p num="0267"> CMOS will be further miniaturized in the future, and its operating frequency will be further increased. In order to realize a smaller transmission device with a higher band, it is desirable to use a high carrier frequency. In the injection synchronization method of this example, the required specifications for oscillation frequency stability can be relaxed, so that a higher carrier frequency can be easily used. The local oscillator 8404 on the receiving side that oscillates in the injection synchronization needs to have a low Q that can follow the frequency fluctuation on the transmitting side. This is convenient when the entire receiving side local oscillator 8404 including the tank circuit is formed on CMOS. Of course, an oscillation circuit having the same circuit configuration as the receiving side local oscillator 8404 may be used as the transmitting side local oscillator 8304, and the entire transmitting side local oscillator 8304 including the tank circuit can be formed on CMOS. it can.</p><p num="0268"> 21 to 22 are diagrams illustrating a second example of a configuration example on the transmitter side to which the injection synchronization method is applied. 23 to 24 are diagrams illustrating a second example of the configuration example on the receiver side to which the injection synchronization method is applied.</p><p num="0269"> The second example is a mode in which a method of adjusting a functional unit on the transmitting side to control injection synchronization is applied. Various configurations are used depending on what information is sent from the receiving side to the transmitting side and whether the controlling entity is placed on the transmitting side or the receiving side when adjusting the functional parts on the transmitting side and controlling so that injection synchronization can be achieved. Can be taken. In the following, only the differences between the two typical methods and the first example will be explained.</p><p num="0270"> The second example (No. 1) of FIGS. 21 and 23 is a mode in which the injection synchronization determination information is sent to the transmitting side and the control subject is placed on the transmitting side. Specifically, the controller unit 8446 of the receiving side signal generation unit 8220B_1 sends the injection synchronization determination information acquired by the injection synchronization detection unit 8442 to the injection synchronization control unit 8340 of the transmitting side signal generation unit 8110B_1. The controller unit 8446 only intervenes in the transmission of the injection synchronization determination information to the transmitting side, and does not actually become the control entity. The injection synchronization detection unit 8442 may be configured to send the injection synchronization determination information to the injection synchronization control unit 8340 of the transmission side signal generation unit 8110B_1 without the intervention of the controller unit 8446.</p><p num="0271"> Here, the injection synchronization control unit 8340 of this configuration adopts the configuration of the first set value processing unit 7100G, and the first input / output interface unit 7170 receives the injection synchronization determination information from the receiving side, and the first It is stored in the set value storage unit 7130. In the controller unit 8346, which is an example of the first operation control unit 7150, the demodulation transfer signal generated by the local oscillation unit 8404 on the receiving side is generated based on the information indicating the injection synchronization status detected by the injection synchronization detection unit 8442 on the receiving side. , It is equipped with a functional unit of the injection synchronization adjustment unit that performs synchronization adjustment so as to synchronize with the modulation carrier signal. An injection synchronization control unit similar to the injection synchronization control unit 8440 is configured by the injection synchronization detection unit 8442 and the functional unit (injection synchronization adjustment unit) related to the injection synchronization adjustment of the controller unit 8346. The controller unit 8346 controls the self-propelled oscillation frequency of the local oscillator 8304 on the transmitting side and the transmission amplitude (transmission power) of the millimeter-wave signal so that injection synchronization can be achieved. The method for determining whether or not synchronization may be the same as in the case of the controller unit 8446. The controller unit 8346 operates each function unit to be controlled based on the set value read from the first set value storage unit 7130, as in the first example.</p><p num="0272"> When the controller unit 8346 determines that the injection synchronization is not achieved, the oscillator unit 8346 sets the oscillation frequency to the transmitting side local oscillator 8304 and sets the amplitude and phase to the phase amplitude adjusting circuit 8307 according to a predetermined procedure. The information is changed, and the gain setting information for the amplification unit 8117 is changed. When the amplitude modulation or the ASK method is adopted, the amplitude of the unmodulated component of the carrier signal included in the millimeter wave signal may be adjusted by controlling the degree of modulation. After that, the controller unit 8346 repeats the procedure of determining the injection synchronization state again until good synchronization is obtained.</p><p num="0273"> On the other hand, the second example (No. 2) of FIGS. 22 and 24 has a configuration in which a control subject is placed on the receiving side and a control command is sent to the transmitting side to control the transmitting side from the receiving side. Specifically, the controller unit 8446 determines whether or not the injection synchronization is synchronized based on the injection synchronization determination information acquired by the injection synchronization detection unit 8442, and if it is determined that the injection synchronization is not achieved, the modulation function is used. A control command for controlling the unit 8300 and the amplification unit 8117 is sent to the transmitting side. That is, the controller unit 8446 directly controls the modulation function unit 8300 and the amplification unit 8117. In other words, the controller unit 8346 initializes the oscillation frequency and the phase and amplitude of the reference carrier signal for the modulation function unit 8300, and also initializes the gain for the amplification unit 8117. The change control of the setting information related to synchronization is not performed.</p><p num="0274"> When the controller unit 8446 determines that the injection synchronization is not achieved, the setting information and the phase of the oscillation frequency to the transmitting side local oscillation unit 8304 are performed according to a predetermined procedure as in the controller unit 8346 of the first example. The amplitude and phase setting information for the amplitude adjustment circuit 8307 is changed, and the gain setting information for the amplification unit 8117 is changed. When the amplitude modulation or the ASK method is adopted, the amplitude of the unmodulated component of the carrier signal included in the millimeter wave signal may be adjusted by controlling the degree of modulation. After that, the controller unit 8446 repeats the procedure of determining the injection synchronization state again until good synchronization is obtained.</p><p num="0275"> Here, in "wireless transmission within or between devices", since the communication environment is immutable (fixed), the parameter setting related to the injection lock may be immutable (fixed). For example, if the value to be stored in the first set value storage unit 7130 or the second set value storage unit 7230 is determined so that the injection synchronization state is optimized at the time of product shipment, the first set value storage unit 7130 is used during the subsequent operation. And the injection lock control may be executed based on the value saved in the second set value storage unit 7230. It can be said that it is not necessary to constantly monitor by the first set value storage unit 7130 or the second set value storage unit 7230 and control based on the result. Therefore, the control by the controller unit 8346 and the controller unit 8446 does not need to be performed dynamically and adaptively frequently as in general wireless communication, so that the overhead due to control can be reduced as compared with general wireless communication. It enables small size, low power consumption, and high speed.</p><p num="0276"> [Relationship between injection signal and oscillation output signal] FIG. 25 shows the phase relationship of each signal in the injection synchronization. Here, as a basic example, the case where the phase of the injection signal (here, the reference transport signal) is in phase with the phase of the transport signal used for modulation is shown.</p><p num="0277"> There are two possible operations of the local oscillator 8404 on the receiving side: injection synchronization mode and amplifier mode. In adopting the injection synchronization method, the basic operation is to use the injection synchronization mode and use the amplifier mode in a special case. A special case is when the reference carrier signal is used as the injection signal and the carrier signal used for modulation and the reference carrier signal are out of phase (typically orthogonal). The phase difference between the output signal Vout (demodulation carrier signal) of the receiving side local oscillator 8404 and the self-propelled output Vo of the receiving side local oscillator 8404 when the injection is synchronized is ψ, and the injection into the receiving side local oscillator 8404 The phase difference between the signal Sinj and the self-propelled output Vo of the local oscillator 8404 on the receiving side is θ + ψ.</p><p num="0278"> When the receiving side local oscillation unit 8404 operates in the injection synchronization mode, as shown in the figure, there is a phase difference between the received reference transfer signal and the oscillation output signal output from the reception side local oscillation unit 8404 by injection synchronization. In order to perform orthogonal detection with the frequency mixing unit 8402, it is necessary to correct this phase difference. As can be seen from the figure, the phase shift amount for which the phase amplitude adjusting unit 8406 adjusts the phase of the output signal of the receiving side local oscillation unit 8404 so as to substantially match the phase of the modulated signal is θ in the figure. .. In other words, when the phase amplitude adjusting unit 8406 injects and synchronizes the phase of the output signal Vout when the receiving side local oscillator 8404 is operating in the injection synchronization mode with the injection signal Sinj to the receiving side local oscillator 8404. The phase may be shifted so as to cancel the phase difference θ with the output signal Vout of. However, although the details will be described in Example 8, in reality, there is a path difference between the received signal input to the frequency mixing unit 8402 and the carrier signal input to the frequency mixing unit 8402 via the injection lock function. Therefore, it is appropriate to make a correction that takes that amount into consideration.</p><p num="0279"> [Injection amount and self-propelled frequency setting] 26 to 29 are diagrams illustrating a method of appropriately setting the injection amount of the signal for injection synchronization (injection lock) in the seventh embodiment. Here, FIG. 26 is a diagram showing a basic configuration of modulation / demodulation corresponding to injection synchronization. FIG. 27 shows the relationship between the frequency difference between the carrier signal f1 used for modulation and the demodulated carrier signal output from the local oscillator 8404 on the receiving side during self-propelling, and the phase difference θ between the injection signal and the carrier signal during injection lock. It is a figure which shows an example. FIG. 28 is a diagram showing an example of the relationship between the phase difference θ between the injection signal and the demodulation carrier signal at the time of injection lock and the DC component of the demodulation output s2. FIG. 29 is a diagram showing an example of the relationship between the reception level (in other words, the input level to the frequency mixing unit 8402) and the lock range.</p><p num="0280"> As shown in FIG. 26, the phase amplitude adjusting unit 8406 adjusts the magnitude of the received signal (that is, the demodulation target signal m2 input to the frequency mixing unit 8402) based on the amplification factor (gain A), and has adjusted the magnitude. It has an amplitude adjusting unit 8434 that supplies the signal as an injection signal to the local oscillating unit 8404 on the receiving side. The injection synchronization detection unit 8442 of the injection synchronization control unit 8440 detects the DC (direct current) component of the demodulated signal s2, and stores the detection result and the set value based on the detection result in the second set value storage unit 7230. Details of the set value based on the detection result of the injection synchronous detection unit 8442 will be described later. The controller unit 8446, which is an example of the second operation control unit 7250, has a function of a frequency control unit that controls the self-propelled frequency of the receiving side local oscillation unit 8404 based on the set value read from the second set value storage unit 7230. ..</p><p num="0281"> As can be understood from the above description, the frequency (self-propelled frequency f) of the self-propelled transport signal f2 (self-propelled transport signal Vo) output from the receiving side local oscillator 8404₂) Is the frequency of the modulation carrier signal f1 (modulation frequency f) output from the local oscillator 8304 on the transmission side used for modulation on the transmission side.₁The closer it is to), the easier it is to lock the injection. When there is an environmental change such as a temperature change, the frequency f of the modulation carrier signal f1₁And the self-propelled frequency f of the self-propelled transport signal f2 (= self-propelled transport signal Vo)₂And the reception level (in other words, the injection amount to the local oscillator 8404 on the receiving side) fluctuate, but the self-propelled frequency f of the carrier signal f2 during self-propelling₂Modulate frequency f₁The lock can be stabilized by controlling it so that it is close to.</p><p num="0282"> Here, as shown in FIG. 27, the frequency f of the modulation carrier signal f1 (in other words, the demodulation target signal m2 input to the frequency mixing unit 8402).₁And the self-propelled frequency f of the self-propelled carrier signal f2 output from the local oscillator 8404 on the receiving side.₂The difference in the phase difference θ between the carrier signal f2 (= injection synchronous output Vout) after the injection lock and the demodulation target signal m2 is determined. In other words, the phase offset of the carrier signal f2 with respect to the demodulation target signal m2 after injection lock is the phase difference θ, and from Reference A, the lock range f._LOCKIs expressed by Eq. (2-1), and the phase difference θ is expressed by Eq. (2-2). In Eq. (2) (Equation (2-1) and Eq. (2-2)), I_injIs the injection signal level (A | m2 |) and I_oscIs the oscillation level (| f2 |) of the receiving side local oscillator 8404 as an injection lock oscillator, and Q is the Q value of the receiving side local oscillator 8404. References A: Narasimha Lanka, et al, University of Minneapolis, Understanding the Transient Behavior of Injection Lock LC Oscillators, IEEE2007 Custom Integrated Circuits Conference (CICC)</p><p num="0283"><maths num="2"><img id="000003" he="86" wi="155" file="JP5779850B2_D0001.tif" img-format="tif" img-content="drawing" /></maths></p><p num="0284"> [Action and effect of Example 7] As shown in FIG. 28, in the demodulation processing in the demodulation function unit 8400, the magnitude of the DC (direct current) component of the demodulation signal s2 is determined by the phase difference θ. From this, when the DC component of the demodulated signal s2 is maximum, the phase difference θ becomes 0, and the frequency difference between the modulated carrier signal f1 and the self-propelled carrier signal f2 output from the receiving side local oscillator 8404 disappears. You can see that. Therefore, it is preferable to control the frequency of the carrier signal f2 during self-propelled operation so that the DC component of the demodulated output s2 becomes large.</p><p num="0285"> However, as shown in FIG. 29, the lock range changes depending on the reception level (that is, the magnitude of the demodulation target signal m2 input to the frequency mixing unit 8402). Specifically, when the level of the demodulation target signal m2 is small, the change in the phase difference θ with respect to the frequency difference of the self-propelled transport signal f2 with respect to the modulation transport signal f1 is large, and when the level of the demodulation target signal m2 is large, the change is large. The change in the phase difference θ with respect to the frequency difference of the carrier signal f2 during self-propelling with respect to the modulated carrier signal f1 is small. Therefore, in order to quickly find the maximum value of the DC component of the demodulated signal s2 while maintaining the locked state, it is preferable to optimally select the amount of change (step) that changes the frequency of the carrier signal f2 during self-propelled operation.</p><p num="0286"> Considering the above, the controller unit 8446 (frequency control unit) and the amplitude adjustment unit 8434 may function as follows as an example of the second operation control unit 7250. For example, the optimum step is calculated in advance from | m2 | and stored in the second set value storage unit 7230, and the frequency control unit of the controller unit 8446 bases the self-propelled frequency f of the carrier signal f2 based on the stored information.₂Should be adjusted. Alternatively, the optimum value for gain adjustment by the phase amplitude adjusting unit 8430 (amplitude adjusting unit 8434) is obtained and stored in the second set value storage unit 7230 so that the injection amount becomes constant, and the amplitude adjusting unit 8434 stores it. , It is advisable to adjust the gain based on the stored information to optimize the injection amount.</p>

<p num="0287"> 30 to 32 are diagrams for explaining the eighth embodiment. Here, FIG. 30 illustrates the phase difference between the received signal supplied to the frequency mixing unit 8402 (that is, the demodulation target signal m2 input to the frequency mixing unit 8402) and the demodulation carrier signal supplied to the frequency mixing unit 8402. It is a figure to do. FIG. 31 is a diagram illustrating the relationship between the phase difference between the received signal supplied to the frequency mixing unit and the demodulated carrier signal and the DC component of the demodulated signal. FIG. 32 is a diagram illustrating a method of suppressing the influence of the phase difference between the received signal supplied to the frequency mixing unit and the demodulated carrier signal.</p><p num="0288"> The eighth embodiment is characterized in that the injection lock is applied as in the seventh embodiment, but the difference from the seventh embodiment is that the second set value processing unit 7200H properly adjusts the phase difference of the injection lock. The feature is that it is set. In the following, for the sake of simplicity, the embodiment 7 is not applied, but the eighth embodiment may be further applied to the embodiment in which the seventh embodiment is adopted.</p><p num="0289"> As described in the seventh embodiment, as shown in FIG. 30, the path of the received signal (demodulation target signal m2) input to the frequency mixing unit 8402 and the carrier signal input to the frequency mixing unit 8402 via the injection lock function. Since there is a difference, the influence of the phase difference φ corresponding to the path difference actually appears. Therefore, it is appropriate to make a correction in consideration of the phase difference φ.</p><p num="0290"> Here, as shown in FIG. 31, the way in which the DC component of the demodulated output s2 changes changes depending on the phase difference φ. For example, an example is shown in FIG. 31 (C). When the phase difference φ is zero, the change in the DC component with respect to the frequency difference of the self-propelled transport signal f2 with respect to the modulated transport signal f1 is the frequency difference. It has symmetry around zero. On the other hand, as the phase difference φ increases in the positive direction, the peak position becomes the self-propelled frequency f.₂Shifts to the low frequency side of, and conversely, the peak position becomes the self-propelled frequency f as the phase difference φ increases in the negative direction.₂It shifts to the high frequency side of, and all become non-symmetrical and broken characteristics.</p><p num="0291"> Therefore, for example, as shown in FIG. 32 (A), as the phase amplitude adjusting unit 8406, a phase adjusting unit 8432 for correcting the influence of the phase difference φ is provided on at least one of the path of the injection signal Sinj and the path of the carrier signal f2. (Fig. 32 (A) shows the case where it is provided in the path of the carrier signal f2). Then, in order to optimize the phase correction amount by the phase adjustment unit 8432, the phase correction amount is stored in advance in the second set value storage unit 7230 of the second set value processing unit 7200H, and the phase adjustment unit 8432 stores the phase correction amount. It is advisable to perform phase correction based on the stored information. In both the injection signal path and the carrier signal f2 path, the phase adjuster 8432 has the frequency f of the carrier signal f2.₂Anything corresponding to the band of. As shown in FIG. 32 (B), the phase adjustment unit 8432 may be provided in the system of the signal m2 to be demodulated to the frequency mixing unit 8402. However, in this case, the phase adjustment unit 8432 has the frequency f of the carrier signal f2.₂Bandwidth is required that corresponds not only to the band of the above but also to the band of the entire demodulation target signal m2.</p>

<p num="0292"> FIG. 33 is a diagram illustrating the communication device of the ninth embodiment. Example 9 is an example in which the reference signal transmission device 3I is applied to the signal transmission device 1I to configure the communication device 8I.</p><p num="0293"> In the ninth embodiment, the fixed parameter setting is applied to the wireless communication of the diffusion code system. The communication device 8I of the ninth embodiment includes a signal transmission device 1I including a plurality of communication devices 2I for wirelessly transmitting a transmission target signal, and a reference signal transmission device 3I. The communication device 2I on the transmitting side is referred to as a transmitter (transmitter), the communication device 2I on the receiving side is referred to as a receiver (receiver), and the transmitter and receiver are collectively referred to as a transmitter / receiver.</p><p num="0294"> The signal transmission device 1I performs communication by adopting the diffusion code method. The transmission band shall be the millimeter wave band. Instead of the millimeter wave band, a submillimeter wave band having a shorter wavelength (0.1 to 1 mm) may be used. Reference B may be referred to as a reference material for the code multiplexing method. Reference B: Proakis, Digital Communications, especially Chapter 13 (Spread Spectrum Signals for Digital Communication), McGraw Hill Education</p><p num="0295"> The communication device 2I has a communication chip 8000. The communication chip 8000 may be either one or both of the transmission chip 8001 (TX) and the reception chip 8002 (RX) described later, or has the functions of both the transmission chip 8001 and the reception chip 8002 in one chip and is bidirectional. It may be one that supports communication. A preferred embodiment is a case where the communication chip 8000 and the reference signal receiving device 7I are incorporated in the communication device 2I as shown in the drawing, but the present invention is not limited to this. In the example of the figure, the communication chip 8000 and the reference signal receiving device 7I are shown as separate functional units, but the communication chip 8000 may be configured to include the functional unit of the reference signal receiving device 7I.</p><p num="0296"> The reference signal transmission device 3I of the ninth embodiment wirelessly transmits a reference signal used by the communication device 2I (in this example, a signal that serves as a reference for a timing signal such as a diffusion code string), and is a reference signal transmission device 5I (reference signal output). It is equipped with an example of the device) and a reference signal receiving device 7I provided for each communication device 2I. In the example of the figure, five communication devices 2I_1 to communication device 2I_5, one reference signal transmitter 5I, and four reference signal receivers 7I_1 to reference signal receiver 7I_4 are in one electronic device housing. Although shown in the example housed in, the number of communication devices 2I and reference signal receiving device 7I installed is not limited to this example, and it is not essential that they are housed in the housing of one electronic device.</p><p num="0297"> The diffusion code string (diffusion code period signal) is a reference clock of the symbol period Tsym, and is also referred to as a symbol period signal Sig1. The diffusion rate for the symbol period signal Sig1 is SF, and the diffusion code rate is Tchip / sec (chip / s). In performing communication using the diffusion code method, the reference signal transmitting device 5I transmits a reference signal (hereinafter, also referred to as a reference clock) having the same frequency as the symbol period signal Sig1.</p><p num="0298"> At this time, in the example of the figure, since the radio frequencies of the transmission target signal between the communication devices 2I and the reference signal between each communication device 2I and the reference signal transmission device 5I are different, the communication device 2I has the radio signal and the reference signal of the transmission target signal. I try to use different antennas (antenna 5400, antenna 7100, antenna 8080) for each of the radio signals, but this is not essential. For example, one antenna may be shared by paying attention to the transmission and reception of synchronized signals by each communication device 2I, the reference signal transmitting device 5I, and the reference signal receiving device 7I.</p><p num="0299"> In the signal transmission device 1I, first, the reference signal transmission device 5I wirelessly transmits a reference clock (reference signal) having a spread code period, and the reference clock is received by the communication device 2I (transmitter and receiver). That is, a reference clock synchronized with the spread code string (reference clock of symbol period Tsym: symbol period signal Sig1) is generated by the reference signal transmitter 5I, and is provided separately from the transmission signal in correspondence with each communication device 2I. Send to the reference signal receiver 7I.</p><p num="0300"> The reference signal receiver 7I provided for each communication device 2I generates a symbol cycle signal Sig1 synchronized with the reference clock of the received symbol cycle Tsym and a clock with a spread code rate Tchip / sec. Then, in the communication device 2I, a diffusion code string is generated in synchronization with the reference clock transmitted from the reference signal transmitter 5I (clock transmitter), and diffusion processing and reverse reverse diffusion processing are performed based on this diffusion code string. Do.</p><p num="0301"> In communication to which the diffusion code method is applied, it is necessary to synchronize the code timings of the transmitting side and the receiving side. When wireless communication is performed by adopting the diffusion code method, in a form in which the communication environment is fixed to some extent (for example, in-device communication or relatively short-distance device-to-device communication), an event different from normal outdoor communication is considered. It is preferable to do so.</p><p num="0302"> For example, unlike field communication such as so-called cellular, 1) the condition of the propagation path does not change, 2) there is virtually no fluctuation in received power or timing (no or very little), 3) the propagation distance is short, 4 ) The delay spread of multipath is small, and 5) the need to use a pseudo-random series for the spreading code is low. 1) to 5) are summarized as the characteristics of "wireless transmission within or between devices". In "wireless transmission within or between devices", unlike ordinary code division multiple access, it is not always necessary to check the state of the propagation path, and a predetermined diffusion code string can be used.</p><p num="0303"> Therefore, the reference clock is transmitted from the reference signal transmitting device 5I to each reference signal receiving device 7I, the reference clock is received by each reference signal receiving device 7I, and the reference clock received by the reference signal receiving device 7I in each communication device 2I. It is possible to generate a timing signal for code division multiplexing processing based on the above. Then, in the communication device 2I, the above-mentioned code timing synchronization can be obtained by performing timing correction based on the propagation delay and other communication environment characteristics investigated in advance. Since it is not necessary to use a complicated method such as a matched filter, the circuit scale and power consumption of the communication device 2I can be reduced.</p><p num="0304"> Further, in "wireless transmission within or between devices", it may be regarded as wireless signal transmission in a static environment, and the communication environment characteristics may be regarded as substantially unchanged. This means that "the communication environment is immutable (fixed), so the parameter settings may be immutable (fixed)". Therefore, for example, a parameter indicating the communication environment characteristics may be determined at the time of product shipment, the parameter may be stored in a storage device such as a memory, and phase correction may be executed based on this parameter during operation. In the case of this example, a phase correction mechanism is installed, but since a mechanism that constantly monitors the communication environment characteristics and corrects the phase based on the result is unnecessary, the circuit scale can be reduced and the power consumption can be reduced. Can be made smaller.</p><p num="0305"> [Operation of communication device] 34 and 35 are diagrams illustrating the overall operation of the communication device 8I of the ninth embodiment. Here, the first example shown in FIG. 34 is a mode in which both the transmitting side and the receiving side are provided with a clock generator using the reference signal receiving device 7I on the communication chip 8000, and the second example shown in FIG. 35. Is a mode in which both the transmitting side and the receiving side are provided with a clock generator using the reference signal receiving device 7I separately from the communication chip 8000. Although not shown, one of the transmitting side and the receiving side has a clock generator using the reference signal receiving device 7I in the communication chip 8000, and the other of the transmitting side and the receiving side has a clock using the reference signal receiving device 7I. The generation unit may be provided separately from the communication chip 8000. BPSK shall be adopted as the modulation method. Since the only difference is whether or not the clock generator is built in the communication chip, the first example in which the clock generator is built in the communication chip 8000 will be described below.</p><p num="0306"> When applied to signal transmission in the device (inside the housing), each part (preferably also the reference signal transmitting device 5I) such as the transmitting chip 8001 and the receiving chip 8002 is housed in the same housing. Then, in the housing, wireless transmission is enabled between the code spreading processing unit 8200, which is an example of the first signal processing unit, and the code despreading processing unit 8500, which is an example of the second signal processing unit. Form a radio signal transmission line. Further, in the case of application to signal transmission between devices, the transmitting chip 8001 is housed in the housing of the first electronic device, and the receiving chip 8002 is housed in the housing of the second electronic device. Preferably, the reference signal transmitter 5I is housed in the housing of either the first electronic device and the second electronic device. Then, when the first electronic device and the second electronic device are arranged at predetermined positions, they are an example of the code diffusion processing unit 8200 and the second signal processing unit, which are examples of the first signal processing unit. A radio signal transmission line that enables wireless transmission is formed with the code demultiplexing processing unit 8500.</p><p num="0307"> The transmission chip 8001 (TX) and the reception chip 8002 (RX), which require the reference signal REFCLK, and the data interface unit 8100 and the data interface unit 8600 provided before and after the transmission chip 8001 (TX) form the basis of the signal transmission device 1I. The transmission chip 8001 is provided with a code diffusion processing unit 8200 and a modulation function unit 8300. The receiving chip 8002 is provided with a demodulation function unit 8400 and a code reverse diffusion processing unit 8500. The symbol period signal Sig1 and the spread code rate signal Sig2 are supplied as reference signals REFCLK to the code spreading processing unit 8200 and the code despreading processing unit 8500, respectively, from the clock generation unit described later. In this configuration, as will be described later, the reference signal receiver 7I is used as the clock generator.</p><p num="0308"> [Data interface: sender] The data interface unit 8100 on the transmitting side receives the supply of the first data string x1 and the second data string x2, and passes each of them to the transmitting chip 8001 (particularly the code spreading processing unit 8200). For example, 1.25 gigabits per second (Gbps) of data is supplied to the code spreading processing unit 8200 via the data interface unit 8100.</p><p num="0309"> [Code diffusion processing unit] The code spreading processing unit 8200 on the transmitting side uses the symbol period signal Sig1 and the spreading code rate signal Sig2 supplied from the reference signal receiving device 7I (not shown), and makes two spreading code strings orthogonal to each other into two data strings x1. And multiply the data string x2, add them, and pass them to the modulation function unit 8300.</p><p num="0310"> [Modulation function unit] The signal to be transmitted (baseband signal: for example, a 12-bit image signal) is converted into a high-speed serial data series by a signal generator (not shown) and supplied to the modulation function unit 8300. The modulation function unit 8300 is an example of a signal processing unit that performs signal processing based on the multiplication reference signal CLK2 (low frequency reference signal), and uses a signal from the parallel serial conversion unit as a modulation signal according to a predetermined modulation method. Modulates to a millimeter-wave band signal.</p><p num="0311"> The modulation function unit 8300 can adopt various circuit configurations depending on the modulation method. For example, a 2-input type frequency mixing unit 8302 (also referred to as a frequency conversion unit, a mixer circuit, a multiplier, etc.) and a local oscillation on the transmitting side A configuration including a unit 8304 (first carrier signal generation unit) may be adopted. The frequency mixing unit 8302 modulates the signal output from the code spreading processing unit 8200 with the carrier signal Lo_TX generated by the transmitting side local oscillator unit 8304.</p><p num="0312"> The local oscillator 8304 on the transmitting side generates a carrier signal Lo_TX (modulation carrier signal) used for modulation. The local oscillator 8304 on the transmitting side generates a second high-frequency reference signal output unit that generates a higher-frequency carrier signal (an example of a second high-frequency reference signal) synchronized with the multiplication reference signal CLK2 generated by the reference signal reproduction unit. This is an example. The local oscillator 8304 on the transmitting side may have various circuit configurations as long as it generates a carrier signal Lo_TX based on the multiplication reference signal CLK2_TX, but it is preferably configured with a PLL, a DLL, or the like, for example. ..</p><p num="0313"> The frequency mixing unit 8302 generates a millimeter-wave band transmission signal (modulated signal) by multiplying (modulating) the millimeter-wave band carrier signal Lo_TX generated by the transmitting side local oscillator 8304 with the signal from the parallel serial conversion unit. It supplies to the amplification unit 8360. The transmission signal is amplified by the amplification unit 8360 and radiated from the transmission antenna 8380 as a millimeter-wave band radio signal Sm.</p><p num="0314"> [Demodulation function unit] The demodulation function unit 8400 can adopt various circuit configurations within a range according to the modulation method on the transmitting side, but at least the one corresponding to the modulation method of the modulation function unit 8300 is adopted. The demodulation function unit 8400 is an example of a signal processing unit that performs signal processing based on the multiplication reference signal CLK2 (low frequency reference signal). The demodulation function unit 8400 includes, for example, a 2-input type frequency mixing unit 8402 and a receiving side local oscillation unit 8404 (second carrier signal generation unit), and signals from the received signal received by the antenna 8236 by a so-called synchronous detection method. Perform demodulation.</p><p num="0315"> The frequency mixing unit 8402 demodulates the signal output from the amplification unit 8460 with the carrier signal Lo_RX generated by the receiving side local oscillator unit 8404. Although not shown, it is preferable to provide, for example, a low-pass filter (LPF) after the frequency mixing unit 8402 to remove harmonic components included in the multiplication output. In the synchronous detection method, the carrier wave is reproduced by the receiving side local oscillation unit 8404 different from the frequency mixing unit 8402, and demodulation is performed using the reproduced carrier wave. In communication using synchronous detection, the transmitted and received carrier signals need to be frequency-synchronized and phase-synchronized.</p><p num="0316"> The local oscillator 8404 on the receiving side generates a second high-frequency reference signal output unit that generates a higher-frequency carrier signal (an example of a second high-frequency reference signal) synchronized with the multiplication reference signal CLK2 generated by the reference signal reproduction unit. This is an example. The local oscillator 8404 on the receiving side may have various circuit configurations as long as it generates a carrier signal based on the multiplication reference signal CLK2_RX, but it is preferably composed of, for example, a PLL or a DLL.</p><p num="0317"> [Sign reverse diffusion processing unit] The code reverse diffusion processing unit 8500 on the receiving side uses the symbol period signal Sig1 and the diffusion code rate signal Sig2 supplied from the reference signal receiver 7I (not shown), knows the diffusion code string, and demolishes it with the demodulation function unit 8400. The timing of the spread code string in the received received signal (baseband signal) is detected, and the received signal is multiplied by the spread code string and integrated to perform despreading and pass it to the data interface unit 8600. Therefore, the diffusion code method requires a code synchronization mechanism.</p><p num="0318"> [Data interface: receiving side] The data interface unit 8600 on the receiving side receives the supply of the first data string D1 and the second data string D2 from the receiving chip 8002 (sign reverse diffusion processing unit 8500), and passes each of them to the subsequent circuit. For example, 1.25 gigabits per second (Gbps) of data supplied from the code spreading processing unit 8500 is passed to the subsequent stage via the data interface unit 8600.</p><p num="0319"> [Sender] In the transmission chip 8001, the code spreading processing unit 8200 has a spreading code string generating unit 8212 and a spreading processing unit 8214 corresponding to the data string x1, and the spreading code string generating unit 8222 and the spreading processing corresponding to the data string x2. It has a part 8224 and further has an adder part 8230. Further, the transmission chip 8001 includes a clock generation unit 7002 (an example of a first clock generation unit) using the reference signal receiving device 7I. The clock generation unit 7002 has an amplification unit 7202 (corresponding to the amplification unit 7200), a Schmitt trigger 7402 (an example of a reference signal reproduction unit), and a clock generation unit 7502 (corresponding to an example of a multiplication reference signal output unit).</p><p num="0320"> The Schmitt trigger 7402 has a function of a binarization unit that acquires a reference clock (symbol period signal Sig1) as binary data. Specifically, the Schmitt trigger 7402 waveform-shapes the reference signal CLK0 (based on the reference signal J1) amplified by the amplification unit 7202 to acquire the symbol period signal Sig1 of the period Tsym, and obtains the symbol period signal Sig1. Is supplied to the data interface unit 8100, the diffusion code string generation unit 8212, and the diffusion code sequence generation unit 8222.</p><p num="0321"> The clock generation unit 7502 generates a reference clock (diffusion code rate signal Sig2) of the period Tchip synchronized with the symbol period signal Sig1 supplied from the Schmitt trigger 7402, and spreads the diffusion code rate signal Sig2 with the diffusion processing unit 8214. Supply to section 8224. The frequency relationship between the symbol period signal Sig1 and the diffusion code rate signal Sig2 is Tsym = SF × Tchip. The symbol period signal Sig1 and the spreading code rate signal Sig2 generated on the clock generation unit 7002 side are examples of the first reference clock for the first signal processing (code spreading processing) related to the wireless communication processing of the spreading code method. ..</p><p num="0322"> The data interface unit 8100 synchronizes the data string x1 and the data string x2 with the symbol period signal Sig1 and outputs the data string x1 to the code spreading processing unit 8200.</p><p num="0323"> The diffusion code string generation unit 8212 outputs the diffusion code F1 having the same clock period and code string period to the diffusion processing unit 8214 based on the symbol period signal Sig1 and the diffusion code rate signal Sig2 supplied from the clock generation unit 7002. The spreading processing unit 8214 performs code spreading by multiplying the data string x1 supplied synchronously with the symbol period signal Sig1 via the data interface unit 8100 and the spreading code F1 supplied from the spreading code string generating unit 8212. The completed data is supplied to the addition unit 8230. Similarly, the diffusion code string generation unit 8222 outputs the diffusion code F2 having the same clock period and code string period to the diffusion processing unit 8224 based on the symbol period signal Sig1 and the diffusion code rate signal Sig2 supplied from the clock generation unit 7002. To do. The spreading processing unit 8224 performs code spreading by multiplying the data string x2 supplied synchronously with the symbol period signal Sig1 via the data interface unit 8100 and the spreading code F2 supplied from the spreading code string generating unit 8222. The completed data is supplied to the addition unit 8230.</p><p num="0324"> [Receiver] In the receiving chip 8002, the code despreading processing unit 8500 has a spreading code string generating unit 8512 and a despreading processing unit 8514 corresponding to the data string D1 to be reproduced, and diffuses corresponding to the data string D2 to be reproduced. It has a code string generation unit 8522 and a back diffusion processing unit 8524. The receiving chip 8002 includes a clock generation unit 7004 (an example of a second clock generation unit) using the reference signal receiving device 7I. The clock generation unit 7004 includes an amplification unit 7204 (corresponding to the amplification unit 7200), a phase shift unit 7404 (an example of a reference signal reproduction unit) that functions as a phase correction circuit, and a clock generation unit 7504 (an example of a multiplication reference signal output unit). ).</p><p num="0325"> The clock generation unit 7504 generates a reference clock (diffusion code rate signal Sig2) of the period Tchip synchronized with the symbol period signal Sig1 supplied from the phase shift unit 7404, and reverses the diffusion code rate signal Sig2 to the reverse diffusion processing unit 8514. It is supplied to the diffusion processing unit 8524. The frequency relationship between the symbol period signal Sig1 and the diffusion code rate signal Sig2 is Tsym = SF × Tchip. The symbol period signal Sig1 and the spreading code rate signal Sig2 generated on the clock generation unit 7004 side are examples of a second reference clock for the second signal processing (code despreading processing) related to the wireless communication processing of the spreading code method. is there.</p><p num="0326"> The diffusion code string generation unit 8512 outputs the diffusion code F3 having the same clock period and code string period to the reverse diffusion processing unit 8514 based on the symbol period signal Sig1 and the diffusion code rate signal Sig2 supplied from the clock generation unit 7004. To do. The despread processing unit 8514 performs code despreading by multiplying the baseband demodulated by the demodulation function unit 8400 and the diffusion code F3 supplied from the diffusion code string generation unit 8512, and supplies the processed data to the data interface unit 8600. To do. Similarly, the diffusion code string generation unit 8522 reverse-spreads the diffusion code F4 having the same clock period and code string period based on the symbol period signal Sig1 and the diffusion code rate signal Sig2 supplied from the clock generation unit 7004. Output to. The despread processing unit 8524 performs code despreading by multiplying the baseband demodulated by the demodulation function unit 8400 and the diffusion code F4 supplied from the diffusion code string generator 8522, and transfers the processed data to the data interface unit 8600. Supply.</p><p num="0327"> The data interface unit 8600 outputs the back-diffusion processed data supplied from the back-diffusion processing unit 8514 and the back-diffusion processing unit 8524 as data string D1 and data string D2, respectively, in synchronization with the symbol period signal Sig1.</p><p num="0328"> Although not shown, the diffusion code string generation unit 8212, the diffusion code string generation unit 8222, the diffusion code string generation unit 8512, and the diffusion code string generation unit 8522 are the diffusion code string a {a {a.₀, a₁, a₂, ... a_N-1} Each value a_iIt is preferable to have a configuration having a plurality of registers storing the above, a multiplication unit for frequency-multiplying the reference clock (here, the symbol period signal Sig1) with a predetermined value (here, SF), and a selection unit (selector). Diffuse code string a {a {a from the register at each input end of the selection section₀, a₁, a₂, ... a_N-1} Each value a_iIs entered. The output signal of the multiplication unit is supplied to the control input end of the selection unit as an output switching signal. For example, the multiplication unit multiplies the symbol period signal Sig1 of 1.25 GHz (GHz) by 4, generates an output switching signal of 5 GHz, and supplies it to the control input terminal of the selection unit 8806. The selection unit uses the spread code string a {a from the register based on the output switching signal from the multiplication unit.₀, a₁, a₂, ... a_N-1} Each value a_iBy selecting and outputting any one of them in order, the diffusion code F @ (@ is 1,2,3,4) having the same clock period (symbol period Tsym) and code string period is output.</p><p num="0329"> In the signal transmission device 1I, for example, the diffusion rate SF = 4, the chip rate is 5 gigachip / sec (Gchip / s), and the modulation method is BPSK. Therefore, the transmission speed of the data to be transmitted is 1.25 Gbit / sec. The reference signal transmitter 5 transmits the same 1.25 GHz reference signal CLK0 (corresponding to the reference signal J1) as the symbol period signal Sig1. Each of the data interface unit 8100, the transmission chip 8001, the reception chip 8002, and the data interface unit 8600 operates in synchronization with the reference signal CLK0 transmitted from the reference signal transmission device 5.</p><p num="0330"> For example, on the transmitting side, the reference signal CLK0 is received, amplified by the amplification unit 7202, and then waveform-shaped by the Schmitt trigger 7402 to obtain the symbol periodic signal Sig1 of the periodic Tsym. Further, in synchronization with this, the clock generator 7502 generates the spread code rate signal Sig2 of the periodic Tchip. The receiving side also receives the reference clock (symbol period signal Sig1 and diffusion code rate signal Sig2) in the same manner, but its phase can be adjusted by the phase shift unit 7404.</p><p num="0331"> The data interface unit 8100 outputs a data string x1 and a data string x2 in synchronization with the symbol period signal Sig1. The diffusion processing unit 8214 and the diffusion processing unit 8224 synchronously output the diffusion code F1 and the diffusion code F2 having the same clock period and code string period. The diffusion processing unit 8214 and the diffusion processing unit 8224 spread by multiplying the data string D1 and the data string D2 by the corresponding spreading code F1 or spreading code F2, respectively. After that, the modulation function unit 8300 converts the frequency to a predetermined frequency (for example, 60 GHz) and sends it out.</p><p num="0332"> The receiving chip 8002 receives the radio signal transmitted from the transmitting chip 8001, converts it into a baseband by the demodulation function unit 8400, and converts it into a baseband by the code despreading processing unit 8500 (the despreading processing unit 8514 and the despreading processing unit 8524). Back-diffuse. Since the timing of the diffusion code string at this time is determined by the propagation delay of the signal from the reference signal transmission device 5 to the transmission chip 8001 and the reception chip 8002, the phase shift unit 7404 corrects this.</p><p num="0333"> [Action and effect of Example 9] When performing signal transmission using a wireless signal, a plurality of signals may be multiplexed and transmitted. As an example, for example, code division multiplex in which code strings orthogonal to each other are multiplied by a data string to be added and multiplexed and transmitted is known. The code division multiple access method is characterized in that a plurality of data strings can be multiplexed on a single carrier wave. For example, high-speed data transmission can be realized by applying a code division multiple access to realize a wireless transmission device using millimeter waves. In particular, when such a device is used for communication within the device (between chips, between boards, between modules, etc.), a transmission line using conductors is not required, which improves the degree of freedom in arranging boards, reduces mounting costs, LVDS, etc. Can also reduce noticeable EMI problems. The reliability of the connector part of the flexible board is a problem, but the reliability can be improved by replacing it with wireless transmission.</p><p num="0334"> A plurality of signals having different transmission rates and data widths are transmitted between communication circuits within or between devices. There are roughly four methods for multiplexing these methods: frequency division multiplexing, time division multiplexing, spatial division multiplexing, and code division multiplexing. Here, in the transmission device in the device or between devices, one or a plurality of these four multiplex methods may be used in combination.</p><p num="0335"> Frequency division multiplexing is a method of transmitting a plurality of data by changing the carrier frequency, and it is necessary to prepare a plurality of transmitters and receivers having different carrier frequencies. Time division multiplexing is a method of transmitting a plurality of data by changing the transmission timing, and a mechanism for defining the transmission timing of each data is required for both the transmitter and the receiver. Space division multiplexing is a method of transmitting a plurality of data through a plurality of isolation paths, and examples thereof include preparing a plurality of transmission lines and using the directivity of an antenna. As described above, code division multiplexing is a method in which code strings orthogonal to each other are multiplied by a data string to be added, multiplexed, and transmitted. Data strings having different transmission rates can also be multiplexed, but synchronization of diffusion codes is possible. A mechanism is needed. In the conventional spread code type receiver which does not adopt the ninth embodiment, a matched filter or the like is used, but the receiver becomes complicated, and there are drawbacks in terms of power consumption and circuit scale.</p><p num="0336"> On the other hand, in the signal transmission device 1I of the ninth embodiment, the reference signal transmission device 3I including the reference signal transmission device 5I and the reference signal receiving device 7I is added to the communication device 8I composed of the transmitter / receiver to construct the entire device. ing. The reference clock transmitted from the reference signal transmission device 5I is supplied to the transmission chip 8001 as a transmitter, and is input to the diffusion code string generation unit 8212 and the diffusion code sequence generation unit 8222 of the code diffusion processing unit 8200. The same applies to the receiving side, and the reference clock that serves as the reference for the symbol period signal Sig1 and the spreading code rate signal Sig2 transmitted from the reference signal transmitting device 5I is supplied to the receiving chip 8002 as a receiver, and the code despreading processing unit 8500 It is input to the diffusion code string generator 8512 and the diffusion code sequence generator 8522.</p><p num="0337"> As a result, the spreading code handled by the transmitter / receiver is synchronized with one cycle of the symbol cycle signal Sig1. Therefore, the receiver does not need a code timing detection circuit for backdiffusion such as a matched filter. That is, the reference clock that serves as the reference for the symbol period signal Sig1 and the spread code rate signal Sig2 is transmitted from the reference signal transmitter 5 of the reference signal transmission device 3, and is received by the transmitter and the receiver to synchronize the spread code string. This simplifies the receiver synchronization mechanism. As a result, power consumption and circuit size can be suppressed. For example, since the code division multiple access method can be used for intra-device transmission, there is an advantage that a plurality of data strings having different data rates can be multiplexed.</p><p num="0338"> Further, the signal transmission device 1I of the ninth embodiment includes a second set value processing unit 7200I. The second set value processing unit 7200I has a second input / output interface unit 7270, a second set value storage unit 7230, and a second operation control unit 7250. A preset value of correction amount defined based on communication environment characteristics such as signal propagation delay from the reference signal transmitter 5I to the transmitter (particularly the transmitting chip 8001) and the receiver (particularly the receiving chip 8002) is set. , It is stored in the second set value storage unit 7230 in advance via the second input / output interface unit 7270. The second operation control unit 7250 notifies (sets) the set value of the stored correction amount to the phase shift unit 7404.</p><p num="0339"> The phase shift unit 7404 has a function of a binarization unit that acquires a reference clock (symbol period signal Sig1) as binary data and a function of a phase correction unit that corrects the phase of the acquired symbol period signal Sig1. .. Specifically, the binarization unit of the phase shift unit 7404 waveform-shapes the reference signal CLK0 amplified by the amplification unit 7204, acquires the symbol period signal Sig1 of the period Tsym, and obtains the symbol period signal Sig1 as the diffusion code. It is supplied to the column generation unit 8512, the diffusion code sequence generation unit 8522, and the data interface unit 8600. At this time, the phase correction unit of the phase shift unit 7404 performs phase correction according to the correction amount notified from the second operation control unit 7250. That is, the phase shift unit 7404 is predetermined based on the communication environment characteristics such as the propagation delay of the signal from the reference signal transmitter 5I to the transmitter (particularly the transmission chip 8001) and the receiver (particularly the reception chip 8002). Phase correction is performed according to the corrected amount. Since it is not a mechanism that constantly monitors the communication environment characteristics and corrects the phase based on the result, the circuit scale can be reduced and the power consumption can be reduced.</p><p num="0340"> [Modification of Example 9] As a modification, although not shown, for example, a reference clock may be supplied instead of the second data string x2 and supplied to the transmission chip 8001. The communication device 8I (signal transmission device 1I, reference signal transmission device 3I) is provided with a reference signal transmission device 5I on either the transmission side or the reception side communication device 2I, and the oscillator (reference) used in the communication device 2I. The signal generated by the oscillator, local oscillator circuit, etc.) is used as a reference reference clock (corresponding to the reference signal J1) to be sent to another communication device 2I. This is a suitable example when applied to a signal transmission device that transmits a clock together with data (a signal to be transmitted). In this case, the reference signal transmitting device 5I does not have to have a function of generating the reference signal J1 in particular, and simply functions as a reference signal output unit that outputs the reference signal. A device simpler than that of the ninth embodiment can be realized.</p><p num="0341"> For example, the data string to be transmitted and the reference clock (synchronous clock) synchronized with the data string to be transmitted are input to the transmission chip 8001 of the communication device 2I on the transmission side. In this case, the input synchronous clock is transmitted to the reference signal transmission device 5I as it is, and the reference signal transmission device 5I transmits the synchronous clock. In comparison with the above-mentioned Example 9, the transmitting chip 8001 includes a part other than the clock generation unit 7002, and the receiving chip 8002 includes a part other than the clock generation unit 7004. It is assumed that the reference signal receiver 7I has the same configuration as the clock generator 7004. In this case, the transmission chip 8001 synchronizes the spread code string using the synchronization clock, and wirelessly transmits the synchronization clock from the reference signal transmission device 5I. The communication device 2I on the receiving side receives the synchronous clock transmitted from the reference signal transmitting device 5I, and the receiving chip 8002 includes the demodulation function unit 8400 and the code despreading processing unit 8500 of the ninth embodiment, and is provided with the reference signal receiving device. Despread processing is performed based on the synchronous clock generated by 7I. The data interface unit 8600 is supplied with the signal from the code despreading processing unit 8500 and the clock from the reference signal receiving device 7I.</p><p num="0342"> As another modification, based on the above-mentioned Example 9, a local oscillator circuit (transmitter local oscillator 8304, receiver local oscillator) of at least one (either one or both, preferably both) of the transmitting side and the receiving side (either one or both, preferably both) is used. The carrier signal generated by the oscillator 8404) is also configured to be synchronized with the reference signal J1 transmitted from the reference signal transmitter 5I. That is, it is a method of synchronizing the local oscillator with the reference signal J1 transmitted from the reference signal transmitter 5I. At the time of this synchronization processing, it is preferable to apply the injection synchronization method.</p><p num="0343"> In the above-mentioned Example 9, the timing synchronization with the chip rate of the diffusion code string has been described, but in the code division multiplexing method, it is preferable to take the carrier frequency synchronization. In the ninth embodiment, the description is made on the premise that the carrier signal is synchronized by a general method on the receiving side, but in this modified example, the synchronization process is performed based on the reference signal J1 transmitted from the reference signal transmitting device 5I. Do it. In this example, in the communication device 2I on both the transmitting side and the receiving side, the local oscillator is synchronized with the reference signal J1 transmitted from the reference signal transmitting device 5I. The symbol period signal Sig1 is generated by the clock generation unit 7002 (Schmitt trigger 7402) on the transmitting side and the clock generation unit 7004 (phase shifting unit 7404) on the receiving side based on the reference signal J1 transmitted from the reference signal transmitting device 5I. However, this is used as a reference clock for each local oscillator circuit (for example, one with a PLL configuration or an injection synchronous configuration).</p>

<p num="0344"> 36 and 37 are diagrams illustrating the tenth embodiment. Here, FIG. 36 is a diagram showing an overall outline of the signal transmission device 1J to which the tenth embodiment is applied. FIG. 37 is a diagram showing an example of frequency amplitude characteristics for explaining the frequency deviation of the transmitting side Tx and the receiving side Rx with respect to the carrier wave. Specifically, FIG. 37 (A) is a diagram for explaining a comparative example to which Example 10 is not applied, and FIG. 37 (B) is a diagram for explaining a first basic example of Example 10, FIG. 37 (C). Is a diagram illustrating a second basic example of the tenth embodiment.</p><p num="0345"> In the tenth embodiment, the fixed parameter setting is applied when the transmission data is speeded up. First, for each of the transmission system and the reception system, when wideband transmission is possible without widening the actual transmission band, the operation settings for speeding up the transmission data are set to the first set value processing unit 7100J and the first. 2 Set value processing unit 7200J. In order to increase the speed of transmission data, it is limited in terms of device configuration to widen the bandwidth of the transmission system and the reception system or to set the bandwidth used for the carrier frequency to a shorter wavelength band. There is a need for a method to increase the speed of transmission data without expanding the bandwidth of the transmission system or reception system or changing the bandwidth used for the carrier frequency, but that demand has not been met. As a matter of fact, Example 10 provides a countermeasure method.</p><p num="0346"> The method of Example 10 is to shift the carrier frequency (carrier frequency) with respect to the center of the band in the transmission characteristics (comprehensive communication characteristics) between transmission and reception having the same bandwidth as in the case where Example 10 is not applied. , Achieve high-speed transmission. In other words, it supports wideband transmission by utilizing the asymmetry of the transmission frequency characteristic between transmission and reception with respect to the carrier frequency. As a method of shifting the carrier frequency with respect to the band center of the transmission frequency characteristic between transmission and reception, the first frequency shift method of shifting only one of the Tx (transmission) band and the Rx (reception) band with respect to the carrier frequency There is also a second frequency shift method that shifts both the Tx band and the Rx band in the same direction with respect to the carrier frequency. In any case, wideband transmission is possible by shifting the frequency characteristics of the Tx system and the Rx system with respect to the carrier wave. A wider signal band can be obtained and high-speed transmission is possible as compared with the combination of the transmitting unit and the receiving unit having the same bandwidth as in the case where the tenth embodiment is not applied. It can be said that it is an extremely effective method as a method for achieving a high data rate in a limited band. Hereinafter, such a method of Example 10 is also simply referred to as a frequency shift method.</p><p num="0347"> As shown in FIG. 36, on the transmitting side, the operation of the modulation function unit 8300 (for example, the modulation function unit 8300A), which is a function unit that defines the transfer frequency during the modulation process (particularly, the transfer signal of the transmission side local oscillation unit 8304). It is equipped with the first set value processing unit 7100J that controls the output operation). The modulation function unit 8300A is an example of a signal processing unit, the transmitting side local oscillation unit 8304 is an example of a first transport signal generation unit that generates a transport signal for modulation, and the frequency mixing unit 8302 sets the signal to be transmitted to the first. This is an example of a first frequency conversion unit that generates a transmission signal by frequency conversion with a modulation transfer signal generated by the transfer signal generation unit (transmission side local oscillation unit 8304) of 1. The first set value processing unit 7100J sets the set value for defining the amount of frequency deviation of the carrier signal with respect to the band center of the transmission characteristic as an example of the signal processing unit, the modulation function unit 8300 (specifically, the transmitting side local unit). Input to the oscillator 8304). The first set value processing unit 7100J adopts the second basic configuration, but as in the first basic configuration, the first set value determination unit 7110 is used instead of the first input / output interface unit 7170. You may prepare.</p><p num="0348"> On the receiving side, the operation of the demodulation function unit 8400 (for example, the demodulation function unit 8400A), which is a function unit that defines the transport frequency during demodulation processing (particularly the output operation of the transport signal of the receiving side local oscillation unit 8404), is controlled. 2 Equipped with a set value processing unit 7200J. The demodulation function unit 8400A is an example of a signal processing unit, the carrier wave reproduction unit 8403 is an example of a second carrier signal generation unit that generates a carrier signal for demodulation, and the frequency mixing unit 8402 uses the received transmission signal as the first. This is an example of a second frequency conversion unit that performs frequency conversion with the carrier signal for demodulation generated by the carrier signal generation unit (carrier wave reproduction unit 8403) of 2. The second set value processing unit 7200J sets the set value for defining the amount of frequency deviation of the carrier signal with respect to the band center of the transmission characteristic as an example of the signal processing unit, the demodulation function unit 8400 (specifically, the carrier wave reproduction unit). Enter in 8403). The second set value processing unit 7200J adopts the second basic configuration, but as in the first basic configuration, the second set value determination unit 7210 is used instead of the second input / output interface unit 7270. You may prepare. In the tenth embodiment, the receiving side (that is, the demodulation function unit 8400A) adopts the synchronous detection method. Any method may be based on the synchronous detection method, including those using injection synchronization.</p><p num="0349"> In this example, both the modulation transfer signal and the demodulation transfer signal can be set so as to be offset from the band center of the transmission characteristic between transmission and reception (that is, the second frequency shift method can be applied). (As described above), setting value processing units are provided on both the transmitting side and the receiving side, but this is not essential. At least one of the carrier signal for modulation and the carrier signal for demodulation may be set so as to be offset from the band center of the transmission characteristic between transmission and reception, and when the first frequency shift method is applied, it may be set. It is sufficient to match the center of either the Tx band or the Rx band with the carrier frequency and shift only the other of the Tx band and the Rx band with respect to the carrier frequency. For example, when shifting only the Tx band with respect to the transport frequency, only the first set value processing unit 7100J needs to be provided, and when shifting only the Rx band with respect to the transport frequency, only the second set value processing unit 7200J is provided. Just do it.</p><p num="0350"> In the case of wireless transmission within or between devices using the millimeter wave band or the wavelength band before and after it, for example, even if there is reflection, it is a fixed reflection, so the reception band (demodulation frequency characteristic band) and transmission band. The overall transmission characteristics including (band of modulation frequency characteristics), transmission characteristics of amplifiers on the transmitting side and receiving side, and transmission characteristics of the transmission space may be treated as fixed. Therefore, in the transmission characteristics between transmission and reception having the same bandwidth as in the case where Example 10 is not applied, when the transport frequency is shifted with respect to the center of the band according to the transmission characteristics, the shift amount (an example of the set value) is set. It can be fixed in advance.</p><p num="0351"> When setting (determining) the shift amount of the carrier frequency, for example, it is preferable to refer to the simulation analysis result. In the simulation, first, the frequency characteristics of each of the transmitting chip (semiconductor chip 103 on the transmitting side) and the receiving chip (semiconductor chip 203 on the receiving side) are obtained from the measurement data of the amplitude characteristics. For example, the modulation frequency characteristic is measured as the frequency characteristic of the transmission chip.</p><p num="0352"> Specifically, in order to ignore the influence of the millimeter-wave signal transmission line 9, that is, to grasp the characteristics of the transmission chip alone, the measurement point is set as the output end of the amplification unit 8117, and the modulated signal is generated by a carrier wave having a unique carrier frequency. Modulate and measure the frequency characteristics of the ratio of the output signal to the carrier (conversion gain = output signal / carrier [dB]). The modulated signal (transmission target signal) may be supplied from the previous stage of the parallel serial conversion unit 8114 (for example, the LSI functional unit 104 shown in FIG. 1 or the like).</p><p num="0353"> As the frequency characteristic of the receiving chip, the frequency characteristic of the conversion gain is measured. Specifically, in order to ignore the influence of the millimeter wave signal transmission path 9, that is, to grasp the characteristics of the receiving chip alone, the input point of the millimeter wave signal (unmodulated wave = RF input) is set to the input end of the amplification unit 8224. Then, the millimeter-wave signal is demodulated with a reproduction carrier wave having a unique carrier frequency, and the frequency characteristic of the ratio of the demodulated output to the RF input (conversion gain = demodulated output / RF input [dB]) is measured. The measurement point may be the output end of the filter processing unit 8410 or the like in order to easily eliminate the influence of the DC component and the harmonic component included in the demodulated output.</p><p num="0354"> Then, the total frequency characteristics are obtained by approximating and extrapolating (extrapolation) the data points obtained by combining the frequency characteristics of both chips (Tx value / Rx value) using a quadratic function or a cubic function. To find (approximate). Assuming that the frequency characteristics of the millimeter-wave signal transmission line 9 are flat and lossless within the transmission band range, the obtained total frequency characteristics are obtained from the signal input end (LSI function unit 104) of the receiving system to the signal output end of the transmitting system. It can be considered as a comprehensive frequency specification up to (LSI functional unit 204). After that, the approximated total frequency characteristic is shifted (shifted) to the baseband side by the amount of the carrier frequency. In this state, the impulse response of the I-axis component (in-phase component) and the Q-axis component (orthogonal component) is simulated, and the data transmission capability is considered from the result. Further, from the relationship between the asymmetry of the frequency characteristics and the impulse response, the frequency shift amount may be determined by considering the conditions for speeding up the transmission data. A wide band is required for high-speed communication, but it may be difficult to obtain a wide band. Even in such a case, the frequency shift of the tenth embodiment is highly effective because it does not substantially widen the bandwidth. The total frequency characteristic in this case is "Tx". Although the transmission characteristics of the millimeter-wave signal transmission line 9 are not taken into consideration, which is indicated by "value / Rx value", the characteristics are also affected, so the transmission characteristics of the millimeter-wave signal transmission line 9 are taken as the TRx value. In that case, the synthesis of the overall frequency characteristics may be "Tx value / Rx value / TRx value".</p><p num="0355"> For example, as shown in FIG. 37 (A), in the comparative example, the reception band (the band of the demodulation frequency characteristic) and the transmission are similar to the case of modulating the normal amplitude (see, for example, Japanese Patent Application Laid-Open No. 2005-513866). This is an example of setting the carrier frequency at the center with respect to the band (band of modulation frequency characteristics). In this case, a wide frequency band is required for high-speed communication. However, there is a limit to widening each frequency band of the transmission system, the transmission line (corresponding to the millimeter wave signal transmission line 9), and the reception system. Even if you try to increase the speed of transmission data by setting the band used for the carrier frequency to a band shorter than the wavelength, such as using the submillimeter wave band instead of the millimeter wave band, it is not possible to support infinitely. There is a limit in the composition.</p><p num="0356"> On the other hand, in the first basic example of Example 10 shown in FIG. 37 (B), the first frequency shift method is applied, the center of the Rx band is matched with the carrier frequency ωc, and only the Tx band is the carrier frequency ωc. It shows the case of shifting upward with respect to. Although not shown, the center of the Rx band may be aligned with the transport frequency ωc, and only the Tx band may be shifted downward with respect to the transport frequency ωc. Further, although not shown, the center of the Tx band may be matched with the transport frequency ωc, and only the Rx band may be shifted to the upper side or the lower side with respect to the transport frequency ωc. The actual setting of the frequency arrangement is realized by shifting the setting of the carrier frequency used by the local oscillator 8304 on the transmitting side with respect to the center of the transmission band (band of the modulation frequency characteristic) obtained by measurement or the like.</p><p num="0357"> The second basic example of Example 10 shown in FIG. 37 (C) applies the second frequency shift method, and shows a case where both the Tx band and the Rx band are shifted upward with respect to the carrier frequency ωc. ing. Although not shown, both the Tx band and the Rx band may be shifted downward with respect to the carrier frequency ωc. It is necessary that the shift directions of the Tx band and the Rx band with respect to the carrier frequency ωc are the same, and shifting in opposite directions has (almost) no effect. In setting the actual frequency arrangement, the frequency of the reproduction carrier wave used by the receiving side local oscillator 8404 (that is, the transmitting side local oscillator 8304) with respect to the center of the reception band (band of the demodulation frequency characteristic) obtained by measurement or the like. This is achieved by shifting the setting of the carrier frequency used by.</p><p num="0358"> [Action and effect of Example 10] By applying the first frequency shift method and the second frequency shift method of Example 10 and shifting the Tx band and the Rx band with respect to the center of the carrier frequency, wideband transmission becomes possible as follows. Derived from. When the frequency shift of Example 10 is applied, the imaginary axis component is largely demodulated due to the asymmetry, but if the baseband is formed by synchronous detection, the influence of this imaginary axis component can be suppressed. Explaining in terms of the frequency axis, the so-called folding back does not expand the actual transmission band of each of the transmission system Tx and the reception system Rx, but the total frequency band by combining the two is apparently expanded. Explaining in relation to impulse responses, impulse responses of imaginary axis components (Impulse Responses at Different) Phases) has a narrower pulse width, so faster transmission is possible. By shifting the frequency characteristics of the transmission system Tx and the reception system Rx with respect to the carrier wave, wideband transmission is possible for each of the transmission system Tx and the reception system Rx without widening the actual transmission band. However, the imaginary axis component with respect to the carrier frequency (local oscillation frequency) for synchronous detection is large. In other words, if the oscillator is used with asymmetric frequency characteristics as in the first basic example shown in Fig. 37 (B) and the second basic example shown in Fig. 37 (C), the impulse width will be narrower and high-speed data can be sent. , It becomes sensitive to the phase shift of the regenerated carrier wave (so-called local oscillation wave, local oscillator) output from the local oscillator for synchronous detection (carrier wave reproduction unit 8403).</p><p num="0359"> [Comparison with reference example] In the field of wireless communication, achieving both high-speed signal transmission and (reduction of) the occupied frequency band for that purpose is a necessary condition for efficient equipment construction. For example, in the frequency spectrum of amplitude modulation, the spectrum of the signal to be transmitted is stored in both sidebands around the carrier frequency. DSB (Double Side Band-Suppressed Carrier) transmission is a method of transmitting both sides of the band as it is while suppressing the carrier wave component, and is a method of transmitting only one of the upper wave band and the lower wave band. Is SSB (Single Side Band-Suppressed Carrier) : Single sideband) transmission. DSB transmission suppresses the carrier wave and transmits it, and the power efficiency is good. However, DSB transmission requires an ideal band-passing filter for suppressing the carrier wave, which makes it difficult to transmit signals of DC components and low-frequency components in the vicinity of DC. Normal AM modulation can handle this, but requires a wide occupied frequency band. In addition, DSB transmission requires twice the bandwidth of the signal to be transmitted, as in the case of ordinary AM modulation. Similar to DSB transmission, SSB transmission suppresses carrier waves and transmits, and has good power efficiency. Further, the SSB transmission may have the same bandwidth as the bandwidth of the signal to be transmitted, but an ideal passband filter is required to limit the bandwidth to only one sideband.</p><p num="0360"> On the other hand, there is VSB (Vestigial Side Band) transmission as a method corresponding to the middle between DSB transmission and SSB transmission. In VSB transmission, the cutoff frequency characteristics of the filter required for SSB transmission are relaxed, and the spectrum of the sideband band to be erased in the AM-modulated high-frequency signal through a filter with gentle cutoff characteristics near the carrier frequency is slightly reduced. The remaining VSB signal is transmitted. On the receiving side, a VSB filter that exhibits a point-symmetrical cutoff characteristic at the carrier frequency is used for reception. Demodulation is performed in the same way as the SSB method, but if the phase characteristic of the VSB filter is straight, the components on the left side of the carrier wave are folded back to the right and overlap, so the demodulated signal has flat characteristics and is the correct signal from the received signal. Can be restored. VSB transmission can be said to be a method that achieves both transmission of DC components and a relatively narrow occupied frequency band.</p><p num="0361"> Here, at first glance, the frequency arrangement in the frequency shift method of the tenth embodiment is similar to the frequency arrangement in VSB transmission. However, VSB transmission requires specific filters on both the transmitting side and the receiving side, whereas the frequency shift method of Example 10 is different in that the equivalent of these filters is not used. In the tenth embodiment, the processing equivalent to the filter processing in transmission / reception in VSB transmission is performed by setting the band used (frequency shift) of the amplification unit 8117 on the transmission side and the amplification unit 8224 on the reception side. Based on. In addition, VSB transmission has the purpose of ensuring the transmission of information near DC while improving the frequency utilization efficiency, and is the entire sideband on one side of the carrier wave and a part of the sideband on the other side (carrier wave). Side) is used. On the other hand, the frequency shift method of the tenth embodiment enables high-speed transmission by shifting the carrier frequency with respect to the center of the band (specifically, the transmission band between transmission and reception: the band of the total frequency characteristic in the previous example). There is also a difference in action and effect. VSB transmission and the frequency shift method of Example 10 only seem to have the same frequency arrangement, and VSB transmission has an embodiment of "shifting the carrier frequency with respect to the center of the transmission band between transmission and reception". There is no technical idea adopted by the 10 frequency shift method.</p>

<p num="0362"> The eleventh embodiment is an example in which the immobilization of the parameter settings of each of the above-described embodiments is applied to an electronic device. Three typical cases are shown below.</p><p num="0363"> [Example 1] FIG. 38 is a diagram illustrating a first example of the electronic device of the eleventh embodiment. The first example is an application example in which a signal is transmitted wirelessly within the housing of one electronic device. As an electronic device, an example of application to an image pickup device equipped with a solid-state image pickup device is shown. This type of imaging device is distributed on the market as, for example, a digital camera, a video camera (camcorder), a camera of a computer device (web camera), or the like.</p><p num="0364"> The first communication device (corresponding to communication device 2) is mounted on the main board on which the control circuit, image processing circuit, etc. are mounted, and the second communication device (corresponding to communication device 2) is mounted on the image pickup board (camera) on which the solid-state imaging device is mounted. It has a device configuration mounted on the board).</p><p num="0365"> The image pickup board 502 and the main board 602 are arranged in the housing 590 of the image pickup apparatus 500. A solid-state image sensor 505 is mounted on the image pickup board 502. For example, the solid-state image sensor 505 is a CCD (Charge Coupled Device), which is applicable when the drive unit (horizontal driver or vertical driver) is mounted on the image sensor 502 or when it is a CMOS (Complementary Metal-oxide Semiconductor) sensor. To do.</p><p num="0366"> The semiconductor chip 103 that functions as the first communication device is mounted on the main board 602, and the semiconductor chip 203 that functions as the second communication device is mounted on the image pickup board 502. Although not shown, the image pickup board 502 is equipped with peripheral circuits such as an image pickup drive unit in addition to the solid-state image sensor 505, and the main board 602 is equipped with an image processing engine, an operation unit, various sensors, and the like.</p><p num="0367"> Each of the semiconductor chip 103 and the semiconductor chip 203 incorporates the function of the reference signal transmitting device 5 and also incorporates the function of the reference signal receiving device 7. Further, each of the semiconductor chip 103 and the semiconductor chip 203 incorporates functions equivalent to those of the transmitting chip 8001 and the receiving chip 8002. By incorporating both the functions of the transmitting chip 8001 and the receiving chip 8002, it is possible to deal with bidirectional communication. These points are the same in other application cases described later.</p><p num="0368"> The solid-state image sensor 505 and the image pickup drive unit correspond to the application function unit of the LSI function unit on the first communication device side. A signal generation unit on the transmission side is connected to the LSI functional unit, and further connected to the antenna 236 via a transmission line coupling unit. The signal generation unit and the transmission line coupling unit are housed in a semiconductor chip 203 separate from the solid-state image sensor 505 and mounted on the image sensor 502.</p><p num="0369"> The image processing engine, the operation unit, various sensors, and the like correspond to the application function unit of the LSI function unit on the second communication device side, and accommodate the image processing unit that processes the image pickup signal obtained by the solid-state image sensor 505. A signal generation unit on the receiving side is connected to the LSI functional unit, and further connected to the antenna 136 via a transmission line coupling unit. The signal generation unit and the transmission line coupling unit are housed in a semiconductor chip 103 separate from the image processing engine and mounted on the main board 602.</p><p num="0370"> The signal generation unit on the transmitting side includes, for example, a multiplexing processing unit, a parallel serial conversion unit, a modulation unit, a frequency conversion unit, an amplification unit, and the signal generation unit on the receiving side is, for example, an amplification unit, a frequency conversion unit, and a demodulation unit. It is provided with a unit, a serial-parallel conversion unit, a unification processing unit, and the like. These points are the same in other application cases described later.</p><p num="0371"> By performing wireless communication between the antenna 136 and the antenna 236, the image signal acquired by the solid-state imaging device 505 is transmitted to the main board 602 via the wireless signal transmission line 9 between the antennas. It may be configured to support bidirectional communication. In this case, for example, the reference clock and various control signals for controlling the solid-state image sensor 505 are transmitted to the image pickup board 502 via the radio signal transmission line 9 between the antennas. Is transmitted to.</p><p num="0372"> Both FIGS. 38 (A) and 38 (B) are provided with two millimeter-wave signal transmission lines 9. Similar to the second example described later, the millimeter wave signal transmission line 9 may be one system. In FIG. 38 (A), the free space transmission line 9B is used, but in FIG. 38 (B), the hollow waveguide line 9L is used. The hollow waveguide 9L may have a structure in which the periphery is surrounded by a shielding material and the inside is hollow. For example, the structure is made hollow by being surrounded by a conductor MZ, which is an example of a shielding material. For example, a conductor MZ enclosure is mounted on the main board 602 so as to surround the antenna 136. The moving center of the antenna 236 on the image pickup board 502 side is arranged at a position facing the antenna 136. Since the inside of the conductor MZ is hollow, it is not necessary to use a dielectric material, and the millimeter wave signal transmission line 9 can be easily configured at low cost.</p><p num="0373"> In the first example, the semiconductor chip 103 and the semiconductor chip 203 are arranged in one housing, and in-device communication in which the arrangement positions of the transmitting unit and the receiving unit do not change is executed. Since the environment is such that the transmission conditions between transmission and reception do not change substantially (that is, are fixed), the transmission characteristics between the transmission unit and the reception unit can be known in advance. Based on the transmission characteristics, for example, the parameter setting that defines the transmission / reception operation such as the amplitude adjustment of the first embodiment is fixed (preset).</p><p num="0374"> [2nd example] FIG. 39 is a diagram illustrating a second example of the electronic device of the eleventh embodiment. The second example is an application example in which a signal is transmitted wirelessly between electronic devices in a state where a plurality of electronic devices are integrated. In particular, it is applied to signal transmission between both electronic devices when one electronic device is attached to the other electronic device.</p><p num="0375"> For example, a card-type information processing device typified by a so-called IC card or memory card with a built-in central processing unit (CPU) or non-volatile storage device (for example, flash memory) is attached to the electronic device on the main unit side. Some are made possible (detachable). On the other hand, the card-type information processing device, which is an example of the (first) electronic device, is also referred to as a "card-type device" below. The other (second) electronic device on the main body side is also simply referred to as an electronic device below.</p><p num="0376"> A structural example of the memory card 201B (planar perspective and cross-sectional perspective) is shown in FIG. 39 (A). A structural example (planar perspective and cross-sectional perspective) of the electronic device 101B is shown in FIG. 39 (B). FIG. 39 (C) shows a structural example (cross-sectional perspective) when the memory card 201B is inserted into the slot structure 4 (particularly the opening 192) of the electronic device 101B.</p><p num="0377"> The slot structure 4 has a configuration in which the memory card 201B (its housing 290) can be inserted and removed from the opening 192 and fixed to the housing 190 of the electronic device 101B. A connector 180 on the receiving side is provided at a contact position with the terminal of the memory card 201B of the slot structure 4. A connector terminal (connector pin) is not required for the signal replaced by wireless transmission.</p><p num="0378"> As shown in FIG. 39 (A), the housing 290 of the memory card 201B is provided with a cylindrical concave configuration 298 (recess), and as shown in FIG. 39 (B), the housing 190 of the electronic device 101B is provided with a cylindrical convex. A shape configuration 198 (protrusion) is provided. The memory card 201B has a semiconductor chip 203 on one surface of the substrate 202, and an antenna 236 is formed on one surface of the substrate 202. The housing 290 has a concave structure 298 formed on the same surface as the antenna 236, and the portion of the concave structure 298 is made of a dielectric resin containing a dielectric material capable of transmitting wireless signals.</p><p num="0379"> On one side of the board 202, a connection terminal 280 for connecting to the electronic device 101B is provided at a predetermined position of the housing 290. The memory card 201B is partially provided with a conventional terminal structure for low-speed / small-capacity signals and power supply. Those that can be the target of signal transmission in millimeter waves have their terminals removed, as shown by the broken lines in the figure.</p><p num="0380"> As shown in FIG. 39 (B), the electronic device 101B has the semiconductor chip 103 on the surface of the substrate 102 on the opening 192 side, and the antenna 136 is formed on one surface of the substrate 102. The housing 190 is formed with an opening 192 into which the memory card 201B is inserted and removed as the slot structure 4. When the memory card 201B is inserted into the opening 192, the housing 190 is formed with a convex configuration 198 having a millimeter wave confinement structure (widden channel structure) at a portion corresponding to the position of the concave configuration 298. It is configured to be a body transmission line 9A.</p><p num="0381"> As shown in FIG. 39 (C), in the housing 190 of the slot structure 4, the convex configuration 198 (dielectric transmission line 9A) and the concave configuration 298 are concave and convex with respect to the insertion of the memory card 201B from the opening 192. It has a mechanical structure that makes contact. When the concave-convex structure is fitted, the antenna 136 and the antenna 236 face each other, and the dielectric transmission line 9A is arranged as the radio signal transmission line 9 between them. The memory card 201B has a housing 290 sandwiched between the dielectric transmission line 9A and the antenna 236, but since the material of the concave configuration 298 is a dielectric material, it has a great influence on wireless transmission in the millimeter wave band. It's not a thing.</p><p num="0382"> In the second example, the semiconductor chip 103 and the semiconductor chip 203 are arranged in separate housings, but even in that case, when the memory card 201B is installed in the slot structure 4, the transmission is performed. Wireless communication is executed in a state in which the arrangement positions of the unit and the receiving unit are predetermined. Similar to the first example, since the environment is such that the transmission conditions between transmission and reception do not substantially change (that is, are fixed), the transmission characteristics between the transmission unit and the reception unit can be known in advance. Based on the transmission characteristics, for example, the parameter setting that defines the transmission / reception operation such as the amplitude adjustment of the first embodiment is fixed (preset).</p><p num="0383"> [3rd example] FIG. 40 is a diagram illustrating a third example of the electronic device of the eleventh embodiment. The signal transmission device 1 includes a portable image reproduction device 201K as an example of the first electronic device, and an image acquisition device 101K as an example of the second (main body side) electronic device on which the image reproduction device 201K is mounted. I have. The image acquisition device 101K is provided with a mounting table 5K on which the image reproduction device 201K is mounted in a part of the housing 190. Instead of the mounting table 5K, the slot structure 4 may be used as in the second example. It is the same as the second example in that a signal is transmitted wirelessly between both electronic devices when one electronic device is attached to the other electronic device. In the following, we will focus on the differences from the second example.</p><p num="0384"> The image acquisition device 101K is generally in the shape of a rectangular parallelepiped (box shape) and can no longer be said to be a card type. The image acquisition device 101K may be, for example, one that acquires moving image data, and corresponds to, for example, a digital recording / playback device or a terrestrial television receiver. The image reproduction device 201K has a storage device for storing moving image data transmitted from the image acquisition device 101K side as an application function unit, and a display unit (for example, a liquid crystal display device or an organic EL display) for reading moving image data from the storage device. A functional unit for playing a moving image is provided in the device). Structurally, it can be considered that the memory card 201B is replaced with the image reproduction device 201K and the electronic device 101B is replaced with the image acquisition device 101K.</p><p num="0385"> A semiconductor chip 103 is housed in the housing 190 at the lower part of the mounting table 5K, as in the second example (FIG. 39), and an antenna 136 is provided at a certain position. A dielectric transmission line 9A is formed of a dielectric material as a wireless signal transmission line 9 in a portion of the housing 190 facing the antenna 136. A semiconductor chip 203 is housed in the housing 290 of the image reproduction device 201K mounted on the mounting table 5K, as in the second example (FIG. 39), and an antenna 236 is provided at a certain position. .. The portion of the housing 290 facing the antenna 236 is configured such that a wireless signal transmission line 9 (dielectric transmission line 9A) is formed of a dielectric material. These points are the same as in the second example described above.</p><p num="0386"> In the third example, the wall abutting method is adopted instead of the idea of a fitting structure, so that the antenna 136 and the antenna 236 face each other when the image acquisition device 101K is placed so as to abut against the corner 101a of the mounting table 5K. Therefore, the influence of misalignment can be reliably eliminated. With such a configuration, when the image reproduction device 201K is mounted (mounted) on the mounting table 5K, the image reproduction device 201K can be aligned with respect to the wireless signal transmission. The housing 190 and the housing 290 are sandwiched between the antenna 136 and the antenna 236, but since they are made of a dielectric material, they do not significantly affect wireless transmission in the millimeter wave band.</p><p num="0387"> In the third example, as in the second example, the semiconductor chip 103 and the semiconductor chip 203 are arranged in separate housings, but even in that case, the image acquisition device 101K is mounted on the mounting table 5K. In the used state, wireless communication is executed in a state in which the arrangement positions of the transmitting unit and the receiving unit are predetermined. As in the first and second examples, the transmission conditions between transmission and reception are substantially unchanged (that is, fixed), so that the transmission characteristics between the transmitter and receiver can be known in advance. .. Based on the transmission characteristics, for example, the parameter setting that defines the transmission / reception operation such as the amplitude adjustment of the first embodiment is fixed (preset).</p>

1 ... wireless transmission device, 2 ... communication device, 3 ... reference signal transmission device, 5 ... reference signal transmission device, 7 ... reference signal receiver, 8 ... communication device, 7100 ... 1st set value processing unit, 7110 ... 1st set value determination unit, 7130 ... 1st set value storage unit, 7150 ... 1st operation control unit, 7170 ... 1st input / output Interface unit, 7200 ... 2nd set value processing unit, 7120 ... 2nd set value determination unit, 7230 ... 2nd set value storage unit, 7250 ... 2nd operation control unit, 7270 ... 2nd input / output interface section, 8000,800 1,8002 ... communication chip, 8300 ... modulation function section, 8302 ... frequency mixing section, 8304 ... transmitting side local oscillation section, 8400 ... demodulation function Part, 8402 ... Frequency mixing part, 8404 ... Receiving side local oscillation part