Transmission and reception method and apparatus

(Reference regarding related applications) Claims included in Japanese patent application 2011-093540 filed on April 9, 2011 and Japanese patent application 2011-140749 filed on June 24, 2011. , Specifications, drawings and abstracts are all incorporated herein by reference.

The present invention particularly relates to a signal generation method and a signal generation device for performing communication using a multi-antenna.

Conventionally, as a communication method using a multi-antenna, for example, there is a communication method called MIMO (Multiple-Input Multiple-Output). In multi-antenna communication represented by MIMO, the communication speed of data is increased by modulating each of a plurality of series of transmission data and transmitting each modulation signal from different antennas at the same time.

FIG. 23 shows an example of the configuration of the transmission / reception device when the number of transmitting antennas is 2, the number of receiving antennas is 2, and the number of transmission modulation signals (transmission streams) is 2. In the transmitting device, the encoded data is interleaved, the interleaved data is modulated, frequency conversion or the like is performed to generate a transmission signal, and the transmission signal is transmitted from the antenna. At this time, the spatial multiplex MIMO method is a method in which different modulated signals are transmitted from the transmitting antenna to the same frequency at the same time.

At this time, Patent Document 1 proposes a transmitting device having a different interleaving pattern for each transmitting antenna. That is, in the transmitter of FIG. 23, the two interleaves (πa, πb) have different interleave patterns. Then, in the receiving device, as shown in Non-Patent Document 1 and Non-Patent Document 2, the reception quality is improved by repeatedly performing the detection method using the soft value (MIMO detector in FIG. 23). Will be done.

By the way, as a model of the actual propagation environment in wireless communication, there are an NLOS (non-line of sight) environment represented by a Rayleigh fading environment and an LOS (line of sight) environment represented by a rice fading environment. When transmitting a single modulated signal in the transmitting device, performing maximum ratio synthesis on the signal received by multiple antennas in the receiving device, and demodulating and decoding the signal after maximum ratio synthesis, the LOS environment, In particular, in an environment where the rice factor indicating the magnitude of the received power of the direct wave with respect to the received power of the scattered wave is large, good reception quality can be obtained. However, depending on the transmission method (for example, spatial multiplex MIMO transmission method), there arises a problem that the reception quality deteriorates as the rice factor increases. (Refer to Non-Patent Document 3) FIGS. 24 (A) and 24 (B) are LDPC (low-density parity-check) encoding in a ray-fading environment and a rice fading environment with a rice factor K = 3, 10, 16 dB. BER (Bit Error) when 2 × 2 (2 antenna transmission, 2 antenna reception) spatial parity MIMO transmission is performed An example of the simulation result of the rate) characteristic (vertical axis: BER, horizontal axis: SNR (signal-to-noise power ratio)) is shown. FIG. 24 (A) shows the BER characteristics of Max-log-APP (see Non-Patent Document 1 and Non-Patent Document 2) (APP: a posterior probability) without repeated detection, and FIG. 24 (B) shows the repeat. The BER characteristics of the detected Max-log-APP (see Non-Patent Document 1 and Non-Patent Document 2) (number of repetitions 5 times) are shown. As can be seen from FIGS. 24 (A) and 24 (B), it can be confirmed that the reception quality deteriorates as the rice factor increases in the spatial multiplex MIMO system regardless of whether or not repeated detection is performed. From this, it is possible to have a problem peculiar to the spatial multiplex MIMO system, which is not found in the conventional single modulated signal transmission system, that "in the spatial multiplex MIMO system, the reception quality deteriorates when the propagation environment becomes stable". Recognize.

Broadcasting and multicast communication are services that must support various propagation environments, and it is naturally possible that the radio wave propagation environment between the receiver and the broadcasting station owned by the user is the LOS environment. When a spatial multiplex MIMO system having the above-mentioned problems is used for broadcasting or multicast communication, a phenomenon occurs in the receiver that the received electric wave strength of radio waves is high, but the service cannot be received due to deterioration of reception quality. there is a possibility. In other words, in order to use a spatial multiplex MIMO system for broadcasting and multicast communication, it is desirable to develop a MIMO transmission method that can obtain a certain level of reception quality in both the NLOS environment and the LOS environment.

Non-Patent Document 8 describes a method of selecting a codebook (precoding matrix (also referred to as precoding weight matrix)) to be used for precoding from feedback information from a communication partner. There is no description about how to perform precoding in a situation where feedback information from the communication partner cannot be obtained, such as multicast communication.

On the other hand, Non-Patent Document 4 describes a method of switching the precoding matrix over time, which can be applied even when there is no feedback information. In this document, it is described that the unitary matrix is used as the matrix used for precoding and that the unitary matrix is randomly switched. However, the application method for the deterioration of the reception quality in the LOS environment shown above is described. It is not mentioned at all, only the random switching is mentioned. As a matter of course, there is no description about the precoding method for improving the deterioration of the reception quality of the LOS environment and the method of constructing the precoding matrix.

<p><patcit num="1"><text>International Publication No. 2005/050885</text></patcit></p>

<p><nplcit><text>"Achieving near-capacity on a multiple-antenna channel" IEEE Transaction on communications, vol.51, no.3, pp.389-399, March 2003.</text></nplcit><nplcit><text>"Performance analysis and design optimization of LDPC-coded MIMO OFDM systems" IEEE Trans. Signal Processing., Vol.52, no.2, pp.348-361, Feb. 2004.</text></nplcit><nplcit><text>"BER performance evaluation in 2x2 MIMO spatial multiplexing systems under Rician fading channels," IEICE Trans. Fundamentals, vol.E91-A, no.10, pp.2798-2807, Oct. 2008.</text></nplcit><nplcit><text>"Turbo space-time codes with time varying linear transformations," IEEE Trans. Wireless communications, vol.6, no.2, pp.486-493, Feb. 2007.</text></nplcit><nplcit><text>"Likelihood function for QR-MLD suitable for soft-decision turbo decoding and its performance," IEICE Trans. Commun., Vol.E88-B, no.1, pp.47-57, Jan. 2004.</text></nplcit><nplcit><text>"Signpost to the Shannon Limits:" Parallel concatenated (Turbo) coding "," Turbo (iterative) decoding "and its surroundings" Institute of Electronics, Information and Communication Engineers, IT98-51</text></nplcit><nplcit><text>"Advanced signal processing for PLCs: Wavelet-OFDM," Proc. Of IEEE International symposium on ISPLC 2008, pp.187-192, 2008.</text></nplcit><nplcit><text>DJ Love, and RW heath, Jr., "Limited feedback unitary precoding for spatial multiplexing systems," IEEE Trans. Inf. Theory, vol.51, no.8, pp.2967-2976, Aug. 2005.</text></nplcit><nplcit><text>DVB Document A122, Framing structure, channel coding and modulation for a second generation digital terrestrial television broadcasting syste, m (DVB-T2), June 2008.</text></nplcit><nplcit><text>L. Vangelista, N. Benvenuto, and S. Tomasin, "Key technologies for next-generation terrestrial digital television standard DVB-T2," IEEE Commun. Magazine, vo.47, no.10, pp.146-153, Oct. 2009.</text></nplcit><nplcit><text>T. Ohgane, T. Nishimura, and Y. Ogawa, "Application of space division multiplexing and those performance in a MIMO channel," IEICE Trans. Commun., vo.88-B, no.5, pp.1843-1851, May 2005.</text></nplcit><nplcit><text>RG Gallager, "Low-density parity-check codes," IRE Trans. Inform. Theory, IT-8, pp-21-28, 1962.</text></nplcit><nplcit><text>DJC Mackay, "Good error-correcting codes based on very sparse matrices," IEEE Trans. Inform. Theory, vol.45, no.2, pp399-431, March 1999.</text></nplcit><nplcit><text>ETSI EN 302 307, "Second generation framing structure, channel coding and modulation systems for broadcasting, interactive services, news gathering and other broadband satellite applications," v.1.1.2, June 2006.</text></nplcit><nplcit><text>Y.-L. Ueng, and C.-C. Cheng, "a fast-convergence decoding method and memory-efficient VLSI decoder architecture for irregular LDPC codes in the IEEE 802.16e standards," IEEE VTC-2007 Fall, pp.1255 -1259.</text></nplcit><nplcit><text>SMAlamouti, "A simple transmit diversity technique for wireless communications," IEEE J. Select. Areas Commun., Vol.16, no.8, pp.1451-1458, Oct 1998.</text></nplcit><nplcit><text>V. Tarokh, H. Jafrkhani, and ARCalderbank, "Space-time block coding for wireless communications: Performance results," IEEE J. Select. Areas Commun., Vol.17, no.3, no.3, pp.451 460, March 1999.</text></nplcit></p>

<p>An object of the present invention is to provide a MIMO system capable of improving reception quality in an LOS environment.</p>

<p>The signal generation method according to the present invention is a signal generation method for generating a plurality of signals transmitted from a plurality of baseband signals in the same frequency band and at the same time, and is a first modulation from the first plurality of bits. Phase change is performed on both the first baseband signal s1 generated according to the method and the second baseband signal s2 generated according to the second modulation method from the second plurality of bits, and after the phase change. The first baseband signal s1'and the second baseband signal s2'after the phase change are generated, the first baseband signal s1'after the phase change is multiplied by u, and the first after the phase change. The baseband signal s2'of 2 is multiplied by v, and u and v are real numbers different from each other, and the signal obtained by multiplying the first baseband signal s1'after the phase change by u and the second after the phase change. The baseband signal s2'of The first weighted composite signal z1 and the second weighted composite signal z2, which are generated as a plurality of signals transmitted at the same time, are (z1, z2).^T= F (u × s1', v × s2')^TThe first modulation method is different from the second modulation method.</p><p>Further, the signal generation device according to the present invention is a signal generation device that generates a plurality of signals transmitted from a plurality of baseband signals in the same frequency band and at the same time, and is a signal generation device from the first plurality of bits to the first. Phase change is performed on both the first baseband signal s1 generated according to the modulation method of and the second baseband signal s2 generated according to the second modulation method from the second plurality of bits to change the phase. The phase change unit that generates the first baseband signal s1'after the first baseband signal s1'and the second baseband signal s2'after the phase change and the first baseband signal s1'after the phase change are multiplied by u. The second baseband signal s2'after the phase change was multiplied by v, and the power change unit, which is a real number different from u and v, and the first baseband signal s1'after the phase change were multiplied by u. The signal and the signal obtained by multiplying the second baseband signal s2'after the phase change by v are weighted and synthesized according to a predetermined matrix F, and the first weighted composite signal z1 and the second weighting are performed. The first weighted composite signal z1 and the second weighted composite signal z2 include a weighted composite unit that generates the composite signal z2 as a plurality of signals transmitted in the same frequency band and at the same time. (z1, z2)^T= F (u × s1', v × s2')^TThe first modulation method is different from the second modulation method.</p>

<p>As described above, according to the present invention, since it is possible to provide a signal generation method and a signal generation device for improving the deterioration of reception quality in the LOS environment, the quality is high for users who are in line of sight in broadcasting and multicast communication. Can provide services.</p>

<figref num="1">Example of configuration of transmitter / receiver in spatial multiplex MIMO transmission system</figref><figref num="2">An example of frame configuration</figref><figref num="3">Example of transmitter configuration when phase change method is applied</figref><figref num="4">Example of transmitter configuration when phase change method is applied</figref><figref num="5">Example of frame configuration</figref><figref num="6">Example of phase change method</figref><figref num="7">Configuration example of receiver</figref><figref num="8">Configuration example of the signal processing unit of the receiving device</figref><figref num="9">Configuration example of the signal processing unit of the receiving device</figref><figref num="10">Decryption processing method</figref><figref num="11">Example of reception status</figref><figref num="12">Example of transmitter configuration when phase change method is applied</figref><figref num="13">Example of transmitter configuration when phase change method is applied</figref><figref num="14">Example of frame configuration</figref><figref num="15">Example of frame configuration</figref><figref num="16">Example of frame configuration</figref><figref num="17">Example of frame configuration</figref><figref num="18">Example of frame configuration</figref><figref num="19">An example of mapping method</figref><figref num="20">An example of mapping method</figref><figref num="21">Example of configuration of weighted composite unit</figref><figref num="22">An example of how to rearrange symbols</figref><figref num="23">Example of configuration of transmitter / receiver in spatial multiplex MIMO transmission system</figref><figref num="24">BER characteristic example</figref><figref num="25">Example of phase change method</figref><figref num="26">Example of phase change method</figref><figref num="27">Example of phase change method</figref><figref num="28">Example of phase change method</figref><figref num="29">Example of phase change method</figref><figref num="30">Example of symbol arrangement of modulated signal that can obtain high reception quality</figref><figref num="31">Example of frame configuration of modulated signal that can obtain high reception quality</figref><figref num="32">Example of symbol arrangement of modulated signal that can obtain high reception quality</figref><figref num="33">Example of symbol arrangement of modulated signal that can obtain high reception quality</figref><figref num="34">Example of change in the number of symbols and the number of slots required for one coded block when using a block code</figref><figref num="35">Example of change in the number of symbols and the number of slots required for the two coded blocks when using the block code</figref><figref num="36">Overall configuration diagram of the digital broadcasting system</figref><figref num="37">Block diagram showing a configuration example of a receiver</figref><figref num="38">Diagram showing the structure of multiplexed data</figref><figref num="39">A diagram schematically showing how each stream is multiplexed in the multiplexed data.</figref><figref num="40">Detailed diagram showing how the video stream is stored in the PES packet string</figref><figref num="41">Diagram showing the structure of TS packets and source packets in multiplexed data</figref><figref num="42">Diagram showing the data structure of PMT</figref><figref num="43">Diagram showing the internal structure of multiplexed data information</figref><figref num="44">Diagram showing the internal structure of stream attribute information</figref><figref num="45">Configuration diagram of video display and audio output device</figref><figref num="46">An example of a communication system configuration</figref><figref num="47">Example of symbol arrangement of modulated signal that can obtain high reception quality</figref><figref num="48">Example of symbol arrangement of modulated signal that can obtain high reception quality</figref><figref num="49">Example of symbol arrangement of modulated signal that can obtain high reception quality</figref><figref num="50">Example of symbol arrangement of modulated signal that can obtain high reception quality</figref><figref num="51">Example of transmitter configuration</figref><figref num="52">Example of transmitter configuration</figref><figref num="53">Example of transmitter configuration</figref><figref num="54">Example of transmitter configuration</figref><figref num="55">The figure which shows the baseband signal exchange part</figref><figref num="56">Example of transmitter configuration</figref><figref num="57">An example of the operation of the distributor</figref><figref num="58">Another example of the operation of the distributor</figref><figref num="59">An example of a communication system showing the relationship between a base station and a terminal</figref><figref num="60">An example of frequency allocation for transmitted signals</figref><figref num="61">An example of frequency allocation for transmitted signals</figref><figref num="62">An example of a communication system showing the relationship between a base station, a repeater, and a terminal</figref><figref num="63">An example of frequency allocation of a transmission signal from a base station</figref><figref num="64">An example of frequency allocation of a transmission signal from a repeater</figref><figref num="65">An example of the configuration of the receiver and transmitter of a repeater</figref><figref num="66">An example of the data format of the signal transmitted by the base station</figref><figref num="67">Example of transmitter configuration</figref><figref num="68">The figure which shows the baseband signal exchange part</figref><figref num="69">An example of weighting, baseband signal replacement, and phase change method</figref><figref num="70">Example of configuration of transmitter using OFDM method</figref><figref num="71">Example of frame configuration</figref><figref num="72">Example of the number of slots and phase change value according to the modulation method</figref><figref num="73">Example of the number of slots and phase change value according to the modulation method</figref><figref num="74">Outline of the frame configuration of the signal transmitted by the broadcasting station in the DVB-T2 standard</figref><figref num="75">An example where two or more types of signals exist at the same time</figref><figref num="76">Example of transmitter configuration</figref><figref num="77">Example of frame configuration</figref><figref num="78">Example of frame configuration</figref><figref num="79">Example of frame configuration</figref><figref num="80">Example of frame configuration</figref><figref num="81">Example of frame configuration</figref><figref num="82">Example of frame configuration</figref><figref num="83">Example of frame configuration</figref><figref num="84">An example where two or more types of signals exist at the same time</figref><figref num="85">Example of transmitter configuration</figref><figref num="86">Example of receiver configuration</figref><figref num="87">Example of receiver configuration</figref><figref num="88">Example of receiver configuration</figref><figref num="89">Example of frame configuration</figref><figref num="90">Example of frame configuration</figref><figref num="91">Example of frame configuration</figref><figref num="92">Example of frame configuration</figref><figref num="93">Example of frame configuration</figref><figref num="94">Example of frame configuration when using spatiotemporal block code</figref><figref num="95">Example of signal point arrangement for 16QAM in IQ plane</figref><figref num="96">Example of signal point arrangement for QPSK in IQ plane</figref><figref num="97">An example schematically showing the absolute value of the log-likelihood ratio obtained by the receiving device</figref><figref num="98">A good example of the absolute value of the log-likelihood ratio obtained by the receiver</figref><figref num="99">Example of configuration of signal processing unit related to weighting synthesis unit</figref><figref num="100">Example of configuration of signal processing unit related to weighting synthesis unit</figref><figref num="101">Example of signal point arrangement for 64QAM in IQ plane</figref><figref num="102">Example of signal point arrangement for 16QAM in IQ plane</figref><figref num="103">Example of configuration of signal generator when applying cyclic Q delay</figref><figref num="104">First example of how to generate s1 (t) and s2 (t) when using cyclic Q delay</figref><figref num="105">Example of configuration of signal generator when applying cyclic Q delay</figref><figref num="106">Example of configuration of signal generator when applying cyclic Q delay</figref><figref num="107">Second example of how to generate s1 (t) and s2 (t) when using cyclic Q delay</figref><figref num="108">Example of configuration of signal generator when applying cyclic Q delay</figref><figref num="109">Example of configuration of signal generator when applying cyclic Q delay</figref>

Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.

(Embodiment 1) The transmission method, transmission device, reception method, and reception device of this embodiment will be described in detail.

Before giving this description, the outline of the transmission method and the decoding method in the spatial multiplex MIMO transmission system which is a conventional system will be described.

N_txN_rFigure 1 shows the configuration of a spatial multiplex MIMO system. The information vector z is coded and interleaved. Then, as the output of the interleave, the vector of the coded bits u = (u).₁, ..., u_Nt) Is obtained. However, u_i= (u_i1, ..., u_iM) (M: Number of transmission bits per symbol). Transmission vector s = (s₁, ..., s_Nt)^TThen, the transmission signal s from the transmission antenna #i_i= map (u_i), And normalizing the transmission energy, E {| s_i|²} = Es / Nt (E)_s: Total energy per channel). And the receive vector is y = (y₁, ..., y_Nr)^TThen, it is expressed as in equation (1).

<math num="1"><img file="JP2022017567A_D0001.tif" /></math>

At this time, H_NtNrIs the channel matrix, n = (n₁, ..., n_Nr)^TIs a noise vector and n_iIs mean 0, variance σ²The iid complex Gaussian noise. From the relationship between the transmission symbol and the reception symbol introduced in the receiver, the probability regarding the reception vector can be given by a multidimensional Gaussian distribution as shown in Eq. (2).

<math num="2"><img file="JP2022017567A_D0002.tif" /></math>

Here, consider a receiver consisting of an outer soft-in / soft-out decoder and MIMO detection, which performs iterative decoding as shown in Fig. 1. The vector (L-value) of the log-likelihood ratio in FIG. 1 is expressed by Eqs. (3)-(5).

<math num="3"><img file="JP2022017567A_D0003.tif" /></math>

<math num="4"><img file="JP2022017567A_D0004.tif" /></math>

<math num="5"><img file="JP2022017567A_D0005.tif" /></math>

&lt;Repeat detection method&gt; Here, N_txN_rIterative detection of MIMO signals in a spatial multiplex MIMO system will be described.

u_mnThe log-likelihood ratio of is defined as in Eq. (6).

<math num="6"><img file="JP2022017567A_D0006.tif" /></math>

From Bayes' theorem, equation (6) can be expressed as equation (7).

<math num="7"><img file="JP2022017567A_D0007.tif" /></math>

However, U_{mn, ± 1}= {u | u_mn= ± 1}. And lnΣa_j~ maxln a_jWhen approximated by, Eq. (7) can be approximated as Eq. (8). The symbol "~" above means an approximation.

<math num="8"><img file="JP2022017567A_D0008.tif" /></math>

P (u | u in equation (8)_mn) And ln P (u | u_mn) Is expressed as follows.

<math num="9"><img file="JP2022017567A_D0009.tif" /></math>

<math num="10"><img file="JP2022017567A_D0010.tif" /></math>

<math num="11"><img file="JP2022017567A_D0011.tif" /></math>

By the way, the logarithmic probability of the equation defined in equation (2) is expressed as in equation (12).

<math num="12"><img file="JP2022017567A_D0012.tif" /></math>

Therefore, from equations (7) and (13), the posterior L-value is expressed as follows in MAP or APP (a posteriori probability).

<math num="13"><img file="JP2022017567A_D0013.tif" /></math>

Hereinafter, it is referred to as iterative APP decryption. Further, from the equations (8) and (12), in the log-likelihood ratio (Max-Log APP) based on the Max-Log approximation, the subsequent L-value is expressed as follows.

<math num="14"><img file="JP2022017567A_D0014.tif" /></math>

<math num="15"><img file="JP2022017567A_D0015.tif" /></math>

Hereafter, it is called iterative Max-log APP decryption. The external information required by the iterative decoding system can be obtained by subtracting the pre-input from Eq. (13) or (14).

&lt;System model&gt; Figure 23 shows the basic configuration of the system that leads to the following explanation. Here, it is a 2 × 2 spatial parity MIMO system, each of stream A and B has an outer encoder, and the two outer encoders are the same LDPC code encoder (here, the LDPC code encoder is used as the outer encoder. However, the error correction code used by the outer encoder is not limited to the LDPC code, and other error correction codes such as a turbo code, a convolutional code, and an LDPC convolutional code can be used in the same manner. Further, the outer encoder is configured to be provided for each transmitting antenna, but the present invention is not limited to this, and a plurality of transmitting antennas may be used, or one outer encoder may be provided, and transmission may be performed. It may have more outer encoders than the number of antennas). And in streams A and B, interleaver (π) is used for each._a, π_{b b}). Here, the modulation method is 2^h-QAM (h bits will be transmitted with one symbol).

The receiver shall perform iterative detection (repeated APP (or Max-log APP) decoding) of the above-mentioned MIMO signal. Then, as the decoding of the LDPC code, for example, sum-product decoding is performed.

Figure 2 shows the frame configuration and describes the order of the symbols after interleaving. At this time, as shown in the following formula (i)_a, j_a), (i_{b b}, j_{b b}).

<math num="16"><img file="JP2022017567A_D0016.tif" /></math>

<math num="17"><img file="JP2022017567A_D0017.tif" /></math>

At this time, i_a, i_{b b}: Symbol order after interleaving, j_a, j_{b b}: Bit position in modulation method (j_a, j_{b b}= 1, . . ., h), π_a, π_{b b}: Streams A and B interleavers, Ω^a_{ia, ja}, Ω^{b b}_{ib, jb}: Indicates the order of data before interleaving of streams A and B. However, in Figure 2, i_a= i_{b b}The frame configuration at the time of is shown.

&lt;Repeated Decoding&gt; Here, the sum-product decoding and the iterative detection algorithm of the MIMO signal used for decoding the LDPC code in the receiver will be described in detail.

sum-product Decoding 2 source MxN matrix H = {H_mn} Is the inspection matrix of the LDPC code to be decoded. The subsets A (m) and B (n) of the set [1, N] = {1,2, ..., N} are defined as follows.

<math num="18"><img file="JP2022017567A_D0018.tif" /></math>

<math num="19"><img file="JP2022017567A_D0019.tif" /></math>

At this time, A (m) means a set of column indexes that are 1 in the mth row of the check matrix H, and B (n) is a set of row indexes that are 1 in the nth row of the check matrix H. .. The algorithm for sum-product decoding is as follows.

Step A . 1 (Initialization): H_mnPrevalued logarithmic ratio β for all pairs (m, n) that satisfy = 1._mnSet to = 0. Loop variable (number of iterations) l_sumSet = 1 and set the maximum number of loops to l_{sum, max}And set.

Step A . 2 (row processing): H in the order of m = 1,2, ..., M_mnFor all pairs (m, n) that satisfy = 1, the external value logarithmic ratio α is used using the following update equation._mnTo update.

<math num="20"><img file="JP2022017567A_D0020.tif" /></math>

<math num="21"><img file="JP2022017567A_D0021.tif" /></math>

<math num="22"><img file="JP2022017567A_D0022.tif" /></math>

At this time, f is a function of Gallager. And λ_nThe method of obtaining the above will be explained in detail below.

Step A . 3 (column processing): H in the order of n = 1,2, ..., N_mnExternal value logarithmic ratio β for all pairs (m, n) that satisfy = 1 using the following update equation_mnTo update.

<math num="23"><img file="JP2022017567A_D0023.tif" /></math>

Step A . 4 (Calculation of log-likelihood ratio): Log-likelihood ratio L for n [1, N]_nIs calculated as follows.

<math num="24"><img file="JP2022017567A_D0024.tif" /></math>

Step A . 5 (counting the number of repetitions): If l_sum&lt;l_{sum, max}Then l_sumIs incremented and returns to step A . 2. l_sum= l_{sum, max}In the case of, the sum-product decryption of this time is completed.

The above is the operation of one sum-product decryption. After that, repeated detection of the MIMO signal is performed. Variables m, n, α used in the above description of sum-product decoding operation_mn, β_mn, λ_n, L_nIn, the variable in stream A is m_a, n_a, α^a_mana, β^a_mana, λ_na, L_na, Variables in stream B_{b b}, n_{b b}, α^{b b}_mbnb, β^{b b}_mbnb, λ_nb, L_nbIt shall be represented by.

&lt;Repeated detection of MIMO signal&gt; Here, λ in the repeated detection of MIMO signal_nI will explain in detail how to find.

From equation (1), the following equation holds.

<math num="25"><img file="JP2022017567A_D0025.tif" /></math>

From the frame configuration of FIG. 2, the following relational expression is established from equations (16) and (17).

<math num="26"><img file="JP2022017567A_D0026.tif" /></math>

<math num="27"><img file="JP2022017567A_D0027.tif" /></math>

At this time, n_a, n_{b b} [1, N]. In the following, λ when the number of iterations of the iteration detection of the MIMO signal k_na, L_na, λ_nb, L_nbΛ respectively_{k, na}, L_{k, na}, λ_{k, nb}, L_{k, nb}It shall be expressed as.

Step B . 1 (Initial detection; k = 0): At the time of initial detection, λ_{0, na}, λ_{0, nb}Is calculated as follows.

For iterative APP decryption:

<math num="28"><img file="JP2022017567A_D0028.tif" /></math>

For iterative Max-log APP decryption:

<math num="29"><img file="JP2022017567A_D0029.tif" /></math>

<math num="30"><img file="JP2022017567A_D0030.tif" /></math>

However, let X = a and b. Then, the number of iterations of the repeated detection of the MIMO signal is calculated._mimoSet = 0 and set the maximum number of iterations to l_{mimo, max}And set.

Step B . 2 (Repeat detection; Number of repetitions k): λ when the number of repetitions k_{k, na}, λ_{k, nb}Is expressed as Eqs. (11) (13)-(15) (16) (17) to Eqs. (31)-(34). However, (X, Y) = (a, b) (b, a).

For iterative APP decryption:

<math num="31"><img file="JP2022017567A_D0031.tif" /></math>

<math num="32"><img file="JP2022017567A_D0032.tif" /></math>

For iterative Max-log APP decryption:

<math num="33"><img file="JP2022017567A_D0033.tif" /></math>

<math num="34"><img file="JP2022017567A_D0034.tif" /></math>

Step B . 3 (counting the number of iterations, estimating codewords): If l_mimo&lt;l_{mimo, max}Then l_mimoIs incremented and returns to step B . 2. l_mimo= l_{mimo, max}In the case of, the estimated codeword is determined as follows.

<math num="35"><img file="JP2022017567A_D0035.tif" /></math>

However, let X = a and b.

FIG. 3 is an example of the configuration of the transmission device 300 in the present embodiment. The coding unit 302A receives information (data) 301A and a frame configuration signal 313 as inputs, and the frame configuration signal 313 (error correction method used by the coding unit 302A for error correction coding of data, coding rate, block length, etc.) The information is included, and the method specified by the frame configuration signal 313 will be used. The error correction method may be switched.) For example, a convolution code, an LDPC code, a turbo code, etc. Error correction coding is performed, and the encoded data 303A is output.

The interleaver 304A receives the encoded data 303A and the frame configuration signal 313 as inputs, performs interleaving, that is, rearranges the order, and outputs the interleaved data 305A. (The interleaving method may be switched based on the frame configuration signal 313.) The mapping unit 306A inputs the interleaved data 305A and the frame configuration signal 313, and QPSK (Quadrature Phase Shift Keying) and 16QAM (16 Quadrature). Amplitude Modulation), 64QAM (64 Quadrature Amplitude) Modulation) or the like is applied, and the baseband signal 307A is output. (The modulation method may be switched based on the frame configuration signal 313.) FIG. 19 is an example of a mapping method in the IQ plane of the in-phase component I and the orthogonal component Q constituting the baseband signal in QPSK modulation. For example, as shown in Fig. 19 (A), when the input data is "00", I = 1.0 and Q = 1.0 are output, and similarly, when the input data is "01", I = 1.0 and Q. = 1.0 is output, ..., is output. FIG. 19 (B) is an example of a mapping method in the IQ plane of QPSK modulation different from that of FIG. 19 (A), and the difference between FIG. 19 (B) and FIG. 19 (A) is in FIG. 19 (A). The signal point shown in FIG. 19 (B) can be obtained by rotating the signal point around the origin. The method of rotating such a constellation is shown in Non-Patent Document 9 and Non-Patent Document 10, and Cyclic Q shown in Non-Patent Document 9 and Non-Patent Document 10. Delay may be applied. As another example from FIG. 19, FIG. 20 shows the signal point arrangement in the IQ plane at 16QAM, and the example corresponding to FIG. 19 (A) is FIG. 20 (A) and FIG. 19 (B). An example corresponding to is shown in FIG. 20 (B).

The coding unit 302B receives information (data) 301B and a frame configuration signal 313 as inputs, and includes information such as a frame configuration signal 313 (error correction method to be used, a coding rate, a block length, etc.), and the frame configuration signal 313. The method specified by is used. Further, the error correction method may be switched.) For example, error correction coding such as a convolution code, LDPC code, turbo code, etc. is performed, and the data after encoding is performed. Output 303B.

The interleaver 304B receives the coded data 303B and the frame configuration signal 313 as inputs, performs interleaving, that is, rearranges the order, and outputs the interleaved data 305B. (The interleaving method may be switched based on the frame configuration signal 313.) The mapping unit 306B inputs the interleaved data 305B and the frame configuration signal 313, and QPSK (Quadrature Phase Shift Keying) and 16QAM (16 Quadrature). Modulation such as Amplitude Modulation) and 64QAM (64 Quadrature Amplitude Modulation) is applied, and the baseband signal 307B is output. (The modulation method may be switched based on the frame configuration signal 313.) The signal processing method information generation unit 314 takes the frame configuration signal 313 as an input and outputs information 315 regarding the signal processing method based on the frame configuration signal 313. do. The information 315 regarding the signal processing method includes information for specifying which precoding matrix is used fixedly and information for a phase change pattern for changing the phase.

The weighted synthesis unit 308A inputs the baseband signal 307A, the baseband signal 307B, and the information 315 regarding the signal processing method, and weights and synthesizes the baseband signal 307A and the baseband signal 307B based on the information 315 regarding the signal processing method. The signal 309A after weighted synthesis is output. The details of the weighted composition method will be described in detail later.

The radio unit 310A receives the signal 309A after weighted synthesis as an input, performs processing such as quadrature modulation, band limitation, frequency conversion, and amplification, outputs the transmission signal 311A, and the transmission signal 311A is output as a radio wave from the antenna 312A. To.

The weighted synthesis unit 308B inputs the baseband signal 307A, the baseband signal 307B, and the information 315 regarding the signal processing method, and weights and synthesizes the baseband signal 307A and the baseband signal 307B based on the information 315 regarding the signal processing method. The signal 316B after weighting synthesis is output.

FIG. 21 shows the configuration of the weighted composition unit (308A, 308B). The area surrounded by the dotted line in FIG. 21 is the weighted composition unit. The baseband signal 307A is multiplied by w11 to generate w11 · s1 (t) and multiplied by w21 to generate w21 · s1 (t). Similarly, the baseband signal 307B multiplies w12 to generate w12 · s2 (t) and multiplies w22 to generate w22 · s2 (t). Next, we obtain z1 (t) = w11 · s1 (t) + w12 · s2 (t) and z2 (t) = w21 · s1 (t) + w22 · s2 (t). At this time, s1 (t) and s2 (t) are BPSK (Binary Phase Shift Keying), QPSK, 8PSK (8 Phase Shift Keying), 16QAM, 32QAM (32 Quadrature Amplitude Modulation), 64QAM, as can be seen from the above explanation. , 256QAM, 16APSK (16 Amplitude Phase Shift Keying), etc., which is the baseband signal of the modulation method.

Here, both weighting and synthesizing units shall execute weighting using a fixed precoding matrix, and as an example of the precoding matrix, an equation (37) or an equation (38) below is used as an example. There is a method using (36). However, this is an example, and the value of α is not limited to the equations (37) and (38), and another value, for example, α may be 1.

The precoding matrix is

<math num="36"><img file="JP2022017567A_D0036.tif" /></math>

However, in the above equation (36), α is

<math num="37"><img file="JP2022017567A_D0037.tif" /></math>

Is.

Alternatively, in the above equation (36), α is

<math num="38"><img file="JP2022017567A_D0038.tif" /></math>

Is.

The precoding matrix is not limited to the equation (36), and the one shown in the equation (39) may be used.

<math num="39"><img file="JP2022017567A_D0039.tif" /></math>

In this equation (39), a = Ae^jδ11, B = Be^jδ12, C = Ce^jδ21, D = De^jδ22It should be represented by. Further, any one of a, b, c, and d may be "zero". For example, (1) a is zero, b, c, d are non-zero, (2) b is zero, a, c, d are non-zero, (3) c is zero, a, b. , D may be non-zero, (4) d may be zero, and a, b, and c may be non-zero.

When any one of the modulation method, the error correction code, and the coding rate thereof is changed, the precoding matrix to be used may be set or changed, and the precoding matrix may be used fixedly.

The phase changing unit 317B receives the signal 316B after weighting synthesis and the information 315 regarding the signal processing method as inputs, and periodically changes the phase of the signal 316B and outputs the signal 316B. To change regularly means to change the phase in a predetermined period (for example, every n symbols (n is an integer of 1 or more) or every predetermined time) according to a predetermined phase change pattern. .. The details of the phase change pattern will be described in the fourth embodiment below.

The radio unit 310B receives the phase-changed signal 309B as an input, performs processing such as quadrature modulation, band limitation, frequency conversion, and amplification, outputs the transmission signal 311B, and the transmission signal 311B is output as a radio wave from the antenna 312B. To.

FIG. 4 shows a configuration example of the transmitter 400 different from that of FIG. In FIG. 4, a part different from FIG. 3 will be described.

The coding unit 402 receives the information (data) 401 and the frame configuration signal 313 as inputs, performs error correction coding based on the frame configuration signal 313, and outputs the encoded data 402.

The distribution unit 404 takes the coded data 403 as an input, distributes the data, and outputs the data 405A and the data 405B. Note that FIG. 4 describes the case where there is only one coding unit, but the present invention is not limited to this, and the coding unit is m (m is an integer of 1 or more), and the code created by each coding unit is used. The present invention can be similarly carried out in the case where the distribution unit outputs the conversion data by dividing it into two systems of data.

FIG. 5 shows an example of a frame configuration on the time axis of the transmitter according to the present embodiment. Symbol 500_1 is a symbol for notifying the receiving device of the transmission method, for example, an error correction method used for transmitting a data symbol, information on its coding rate, and a modulation method used for transmitting the data symbol. Information etc. is transmitted.

Symbol 501_1 is a symbol for estimating the channel variation of the modulated signal z1 (t) {where t is time} transmitted by the transmitter. Symbol 502_1 is a data symbol transmitted by the modulation signal z1 (t) to symbol number u (on the time axis), and symbol 503_1 is a data symbol transmitted by modulation signal z1 (t) to symbol number u + 1.

Symbol 501_2 is a symbol for estimating the channel variation of the modulated signal z2 (t) {where t is time} transmitted by the transmitter. Symbol 502_2 is a data symbol transmitted by the modulation signal z2 (t) to the symbol number u, and symbol 503_2 is a data symbol transmitted by the modulation signal z2 (t) to the symbol number u + 1.

At this time, in the symbol at z1 (t) and the symbol at z2 (t), the symbols at the same time (same time) are transmitted from the transmitting antenna using the same (common) frequency.

The relationship between the modulated signal z1 (t) and the modulated signal z2 (t) transmitted by the transmitting device and the received signals r1 (t) and r2 (t) in the receiving device will be described.

In FIG. 5, 504 # 1 and 504 # 2 indicate the transmitting antenna in the transmitting device, 505 # 1 and 505 # 2 indicate the receiving antenna in the receiving device, and the transmitting device transmits the modulated signal z1 (t) to the transmitting antenna 504. # 1, the modulation signal z2 (t) is transmitted from the transmission antenna 504 # 2. At this time, it is assumed that the modulated signal z1 (t) and the modulated signal z2 (t) occupy the same (common) frequency (band). The channel fluctuations of each transmitting antenna of the transmitting device and each antenna of the receiving device are set to h11 (t), h12 (t), h21 (t), and h22 (t), respectively, and the reception received by the receiving antenna 505 # 1 of the receiving device. Assuming that the signal is r1 (t) and the received signal received by the receiving antenna 505 # 2 of the receiving device is r2 (t), the following relational expression is established.

<math num="40"><img file="JP2022017567A_D0040.tif" /></math>

FIG. 6 is a diagram related to the weighting method (precoding method) and the phase changing method in the present embodiment, and the weighting synthesis unit 600 integrates both the weighting synthesis units 308A and 308B of FIG. It is a weighted composition unit. As shown in FIG. 6, streams s1 (t) and streams s2 (t) correspond to the baseband signals 307A and 307B in FIG. 3, that is, the base according to the mapping of modulation schemes such as QPSK, 16QAM, 64QAM. It becomes the common mode I component and the quadrature Q component of the band signal. Then, as in the frame configuration of FIG. 6, the stream s1 (t) represents the signal of the symbol number u as s1 (u), the signal of the symbol number u + 1 as s1 (u + 1), and so on. Similarly, the stream s2 (t) represents the signal with the symbol number u as s2 (u), the signal with the symbol number u + 1 as s2 (u + 1), and so on. Then, the weighting / combining unit 600 inputs the baseband signals 307A (s1 (t)) and 307B (s2 (t)) in FIG. 3 and the information 315 regarding the signal processing method, and weights according to the information 315 regarding the signal processing method. Is applied, and the signals 309A (z1 (t)) and 316B (z2'(t)) after the weighted synthesis shown in FIG. 3 are output. The phase change unit 317B changes the phase of the weighted signal 316B (z2'(t)) and outputs the phase-changed signal 309B (z2 (t)).

At this time, z1 (t) can be expressed by the following equation (41), where W1 = (w11, w12) is the vector of the first row in the fixed precoding matrix F.

<math num="41"><img file="JP2022017567A_D0041.tif" /></math>

On the other hand, in z2 (t), if the vector of the second row in the fixed precoding matrix F is W2 = (w21, w22) and the phase change equation by the phase change part is y (t), the following equation (42) ) Can be expressed.

<math num="42"><img file="JP2022017567A_D0042.tif" /></math>

Here, y (t) is an equation for changing the phase according to a predetermined method. For example, assuming that the period is 4, the phase changing equation at time u is expressed by, for example, equation (43). be able to.

<math num="43"><img file="JP2022017567A_D0043.tif" /></math>

Similarly, the phase change equation at time u + 1 can be expressed by, for example, equation (44).

<math num="44"><img file="JP2022017567A_D0044.tif" /></math>

That is, the phase change equation at time u + k can be expressed by equation (45).

<math num="45"><img file="JP2022017567A_D0045.tif" /></math>

The regular phase change examples shown in Eqs. (43) to (45) are only examples.

The period of regular phase change is not limited to 4. The larger the number of cycles, the more it may be possible to promote the improvement of the reception performance (more accurately, error correction performance) of the receiving device (although it is not necessary to have a large cycle, 2). It is likely that you should avoid small values such as).

Further, in the phase change example shown in the above equations (43) to (45), a configuration in which the phase is sequentially rotated by a predetermined phase (in the above equation, by π / 2) is shown, but the same phase amount is rotated. Instead, the phase may be changed randomly. For example, the phase of y (t) to be multiplied in the order shown in Eqs. (46) and (47) may be changed according to a predetermined period. What is important in the regular change of phase is that the phase of the modulated signal is changed regularly, and the degree of the changed phase is as uniform as possible, for example, from -π radian to π radian. On the other hand, although it is desirable to have a uniform distribution, it may be random.

<math num="46"><img file="JP2022017567A_D0046.tif" /></math>

<math num="47"><img file="JP2022017567A_D0047.tif" /></math>

As described above, the weighted synthesis unit 600 of FIG. 6 executes precoding using a predetermined fixed precoding weight, and the phase changing unit 317B regulates the phase of the input signal and the degree of the change. Change while changing the target.

In the LOS environment, the reception quality may be greatly improved by using a special precoding matrix, but depending on the direct wave situation, the special precoding matrix depends on the phase and amplitude component of the direct wave when it is received. different. However, there is a certain rule in the LOS environment, and if the phase of the transmitted signal is changed regularly according to this rule, the data reception quality is greatly improved. The present invention proposes a signal processing method for improving the LOS environment.

FIG. 7 shows an example of the configuration of the receiving device 700 according to the present embodiment. The radio unit 703_X receives the received signal 702_X received by the antenna 701_X as an input, performs processing such as frequency conversion and orthogonal demodulation, and outputs the baseband signal 704_X.

The channel variation estimation unit 705_1 in the modulated signal z1 transmitted by the transmitter takes the baseband signal 704_X as an input, extracts the reference symbol 501_1 for channel estimation in FIG. 5, and obtains the value corresponding to h11 in the equation (40). Estimate and output the channel estimation signal 706_1.

The channel variation estimation unit 705_2 in the modulated signal z2 transmitted by the transmitter takes the baseband signal 704_X as an input, extracts the reference symbol 501_2 for channel estimation in FIG. 5, and obtains the value corresponding to h12 in the equation (40). Estimate and output the channel estimation signal 706_2.

The radio unit 703_Y receives the received signal 702_Y received by the antenna 701_Y as an input, performs processing such as frequency conversion and orthogonal demodulation, and outputs the baseband signal 704_Y.

The channel variation estimation unit 707_1 in the modulated signal z1 transmitted by the transmitter takes the baseband signal 704_Y as an input, extracts the reference symbol 501_1 for channel estimation in FIG. 5, and obtains the value corresponding to h21 in the equation (40). Estimate and output the channel estimation signal 708_1.

The channel variation estimation unit 707_2 in the modulated signal z2 transmitted by the transmitter takes the baseband signal 704_Y as an input, extracts the reference symbol 501_2 for channel estimation in FIG. 5, and obtains the value corresponding to h22 in the equation (40). Estimate and output the channel estimation signal 708_2.

The control information decoding unit 709 inputs the baseband signals 704_X and 704_Y, detects the symbol 500_1 for notifying the transmission method of FIG. 5, and outputs the signal 710 regarding the transmission method information notified by the transmission device.

The signal processing unit 711 receives the baseband signals 704_X, 704_Y, the channel estimation signals 706_1, 706_2, 708_1, 708_2, and the signal 710 related to the transmission method information notified by the transmission device as inputs, detects and decodes them, and receives the received data. Output 712_1 and 712_2.

Next, the operation of the signal processing unit 711 of FIG. 7 will be described in detail. FIG. 8 shows an example of the configuration of the signal processing unit 711 according to the present embodiment. FIG. 8 mainly consists of an INNER MIMO detection unit, a soft-in / soft-out decoder, and a coefficient generation unit. The method of iterative decoding in this configuration is described in detail in Non-Patent Document 2 and Non-Patent Document 3, but the MIMO transmission method described in Non-Patent Document 2 and Non-Patent Document 3 is spatial multiplex MIMO transmission. Although it is a method, the transmission method in the present embodiment is a MIMO transmission method in which the phase of the signal is regularly changed with time and a precoding matrix is used. This is different from Patent Document 3. The (channel) matrix in Eq. (36) is H (t), the precoding weight matrix in FIG. 6 is F (where the precoding matrix is fixed in the received signal of 1), and FIG. The matrix of the phase change equation by the phase change part is Y (t) (where Y (t) changes with t), and the receive vector is R (t) = (r1 (t), r2 (t)).^T, Stream vector S (t) = (s1 (t), s2 (t))^TThen, the following relational expression holds.

<math num="48"><img file="JP2022017567A_D0048.tif" /></math>

At this time, the receiving device can apply the decoding methods of Non-Patent Document 2 and Non-Patent Document 3 to the reception vector R (t) by obtaining H (t) × Y (t) × F. ..

Therefore, the coefficient generation unit 819 in FIG. 8 is a signal 818 regarding the transmission method information (information for specifying the fixed precoding matrix used and the phase change pattern when the phase is changed) notified by the transmission device. It takes (corresponding to 710 in Fig. 7) as an input and outputs a signal 820 related to information on the signal processing method.

The INNER MIMO detection unit 803 takes the signal 820 related to the information of the signal processing method as an input, and by using this signal and using the relationship of the equation (48), iterative detection / decoding will be performed, but its operation. Will be explained.

In the signal processing unit having the configuration shown in FIG. 8, it is necessary to perform the processing method as shown in FIG. 10 in order to perform iterative decoding (repeated detection). First, one codeword (or one frame) of the modulated signal (stream) s1 and one codeword (or one frame) of the modulated signal (stream) s2 are decoded. As a result, from the soft-in / soft-out decoder, one codeword (or one frame) of the modulated signal (stream) s1 and one codeword (or one frame) of the modulated signal (stream) s2 are each. The log-likelihood ratio (LLR) of the bit is obtained. Then, the detection / decoding is performed again using the LLR. This operation is performed multiple times (this operation is called iterative decoding (repeated detection)). In the following, the method of creating the log-likelihood ratio (LLR) of a symbol at a specific time in one frame will be mainly described.

In FIG. 8, the storage unit 815 includes a baseband signal 801X (corresponding to the baseband signal 704_X in FIG. 7), a channel estimation signal group 802X (corresponding to the channel estimation signals 706_1 and 706_2 in FIG. 7), and a baseband. To realize iterative decoding (repeated detection) by inputting the signal 801Y (corresponding to the baseband signal 704_Y in FIG. 7) and the channel estimation signal group 802Y (corresponding to the channel estimation signals 708_1 and 708_2 in FIG. 7). In addition, H (t) × Y (t) × F in Eq. (48) is executed (calculated), and the calculated matrix is stored as a modified channel signal group. Then, the storage unit 815 outputs the above signals as a baseband signal 816X, a modified channel estimation signal group 817X, a baseband signal 816Y, and a modified channel estimation signal group 817Y when necessary.

Subsequent operations will be described separately for the case of initial detection and the case of iterative decoding (repeated detection).

&lt;In the case of initial detection&gt; The INNER MIMO detection unit 803 inputs the baseband signal 801X, the channel estimation signal group 802X, the baseband signal 801Y, and the channel estimation signal group 802Y. Here, the modulation method of the modulated signal (stream) s1 and the modulated signal (stream) s2 will be described as 16QAM.

The INNER MIMO detection unit 803 first executes H (t) × Y (t) × F from the channel estimation signal group 802X and the channel estimation signal group 802Y, and obtains a candidate signal point corresponding to the baseband signal 801X. The situation at that time is shown in FIG. In FIG. 11, (black circle) is a candidate signal point in the IQ plane, and since the modulation method is 16QAM, there are 256 candidate signal points. (However, since FIG. 11 shows an image diagram, not all 256 candidate signal points are shown.) Here, the 4 bits transmitted by the modulated signal s1 are b0, b1, b2, b3, and the modulated signal s2. Assuming that the 4 bits transmitted in 1 are b4, b5, b6, and b7, there are candidate signal points corresponding to (b0, b1, b2, b3, b4, b5, b6, b7) in FIG. Then, the square Euclidean distance between the received signal point 1101 (corresponding to the baseband signal 801X) and each candidate signal point is obtained. Then, each squared Euclidean distance is the noise variance σ²Divide by. Therefore, the value obtained by dividing the candidate signal point corresponding to (b0, b1, b2, b3, b4, b5, b6, b7) and the Euclidean distance squared to the received signal point by the noise variance is E._X(b0, b1, b2, b3, b4, b5, b6, b7) will be obtained. The baseband signals, modulation signals s1 and s2 are complex signals.

Similarly, execute H (t) × Y (t) × F from the channel estimation signal group 802X and the channel estimation signal group 802Y to find the candidate signal point corresponding to the baseband signal 801Y, and receive the reception signal point (baseband signal). Find the squared Euclidean distance with (corresponding to 801Y.), And use this squared Euclidean distance as the signal dispersion σ.²Divide by. Therefore, the value obtained by dividing the candidate signal point corresponding to (b0, b1, b2, b3, b4, b5, b6, b7) and the Euclidean distance squared to the received signal point by the noise variance is E._Y(b0, b1, b2, b3, b4, b5, b6, b7) will be obtained.

And E_X(b0, b1, b2, b3, b4, b5, b6, b7) + E_YFind (b0, b1, b2, b3, b4, b5, b6, b7) = E (b0, b1, b2, b3, b4, b5, b6, b7).

The INNER MIMO detector 803 outputs E (b0, b1, b2, b3, b4, b5, b6, b7) as a signal 804.

The log-likelihood calculation unit 805A takes the signal 804 as an input, calculates the log-likelihood of the bits b0 and b1 and b2 and b3, and outputs the log-likelihood signal 806A. However, in the calculation of the log-likelihood, the log-likelihood when it is "1" and the log-likelihood when it is "0" are calculated. The calculation method is as shown in the formula (28), the formula (29), and the formula (30), and the details are shown in Non-Patent Document 2 and Non-Patent Document 3.

Similarly, the log-likelihood calculation unit 805B takes the signal 804 as an input, calculates the log-likelihood of the bits b4 and b5 and b6 and b7, and outputs the log-likelihood signal 806B.

The deinterleaver (807A) takes the log-likelihood signal 806A as an input, performs deinterleave corresponding to the interleaver (interleaver (304A) in FIG. 3), and outputs the log-likelihood signal 808A after deinterleave.

Similarly, the deinterleaver (807B) takes the log-likelihood signal 806B as an input, performs deinterleave corresponding to the interleaver (interleaver (304B) in FIG. 3), and outputs the log-likelihood signal 808B after deinterleave.

The log-likelihood ratio calculation unit 809A takes the deinterleaved log-likelihood signal 808A as an input and calculates the log-likelihood ratio (LLR: Log-Likelihood Ratio) of the bits encoded by the encoder 302A in FIG. Then, the log-likelihood ratio signal 810A is output.

Similarly, the log-likelihood ratio calculation unit 809B takes the deinterleaved log-likelihood signal 808B as an input, and the log-likelihood ratio (LLR: Log-Likelihood Ratio) of the bits encoded by the encoder 302B in FIG. ) Is calculated, and the log-likelihood ratio signal 810B is output.

The Soft-in / soft-out decoder 811A takes a log-likelihood ratio signal 810A as an input, performs decoding, and outputs a log-likelihood ratio 812A after decoding.

Similarly, the Soft-in / soft-out decoder 811B takes the log-likelihood ratio signal 810B as an input, performs decoding, and outputs the log-likelihood ratio 812B after decoding.

&lt;In the case of iterative decoding (repetitive detection), the number of iterations k&gt; The interleaver (813A) takes the log-likelihood ratio 812A after decoding obtained by the k-1th soft-in / soft-out decoding as an input and interleaves. Is performed, and the log-likelihood ratio 814A after interleaving is output. At this time, the interleave pattern of the interleave (813A) is the same as the interleave pattern of the interleaver (304A) in FIG.

The interleaver (813B) inputs the log-likelihood ratio 812B after decoding obtained by the k-1st soft-in / soft-out decoding, performs interleaving, and outputs the log-likelihood ratio 814B after interleaving. .. At this time, the interleave pattern of the interleave (813B) is the same as the interleave pattern of the interleaver (304B) of FIG.

The INNER MIMO detector 803 inputs the baseband signal 816X, the modified channel estimation signal group 817X, the baseband signal 816Y, the modified channel estimation signal group 817Y, the log-likelihood ratio 814A after interleaving, and the log-likelihood ratio 814B after interleaving. And. Here, instead of the baseband signal 801X, the channel estimation signal group 802X, the baseband signal 801Y, and the channel estimation signal group 802Y, the baseband signal 816X, the modified channel estimation signal group 817X, the baseband signal 816Y, and the modified channel estimation signal group 817Y Is used because there is a delay time due to repeated decoding.

The difference between the operation during repeated decoding of the INNER MIMO detector 803 and the operation during initial detection is that the log-likelihood ratio 814A after interleaving and the log-likelihood ratio 814B after interleaving are used for signal processing. Is. The INNER MIMO detection unit 803 first obtains E (b0, b1, b2, b3, b4, b5, b6, b7) as in the case of initial detection. In addition, the coefficients corresponding to equations (11) and (32) are obtained from the log-likelihood ratio 814A after interleaving and the log-likelihood ratio 814B after interleaving. Then, the value of E (b0, b1, b2, b3, b4, b5, b6, b7) is corrected using this obtained coefficient, and the value is corrected by E'(b0, b1, b2, b3, b4, b5). , B6, b7) and output as signal 804.

The log-likelihood calculation unit 805A takes the signal 804 as an input, calculates the log-likelihood of the bits b0 and b1 and b2 and b3, and outputs the log-likelihood signal 806A. However, in the calculation of the log-likelihood, the log-likelihood when it is "1" and the log-likelihood when it is "0" are calculated. The calculation method is as shown in the equation (31), the equation (32), the equation (33), the equation (34), and the equation (35), and is shown in Non-Patent Document 2 and Non-Patent Document 3. ..

Similarly, the log-likelihood calculation unit 805B takes the signal 804 as an input, calculates the log-likelihood of the bits b4 and b5 and b6 and b7, and outputs the log-likelihood signal 806B. The operation after the demodulator is the same as the initial detection.

Note that FIG. 8 shows the configuration of the signal processing unit when performing repeated detection, but repeated detection is not necessarily an essential configuration for obtaining good reception quality, and is a configuration part required only for repeated detection. , The configuration may not have interleavers 813A and 813B. At this time, the INNER MIMO detection unit 803 does not perform repetitive detection.

Then, an important part in this embodiment is to perform an operation of H (t) × Y (t) × F. As shown in Non-Patent Document 5 and the like, initial detection and repeated detection may be performed using QR decomposition.

Further, as shown in Non-Patent Document 11, based on H (t) × Y (t) × F, linear operations of MMSE (Minimum Mean Square Error) and ZF (Zero Forcing) are performed to perform initial detection. You may go.

FIG. 9 has a configuration of a signal processing unit different from that of FIG. 8, and is a signal processing unit for a modulated signal transmitted by the transmitting device of FIG. The difference from FIG. 8 is the number of soft-in / soft-out decoders. The soft-in / soft-out decoder 901 receives log-likelihood ratio signals 810A and 810B as inputs, performs decoding, and after decoding. The log-likelihood ratio 902 is output. The distribution unit 903 receives the log-likelihood ratio 902 after decoding as an input and distributes. For the other parts, the operation is the same as in FIG.

As described above, as in the present embodiment, when the transmitting device of the MIMO transmission system transmits a plurality of modulated signals from a plurality of antennas, the precoding matrix is multiplied and the phase is changed with time, and the phase is changed. By making the changes regularly, it is possible to obtain the effect of improving the data reception quality in the receiving device as compared with the case of using the conventional spatial multiplex MIMO transmission in the LOS environment where the direct wave is dominant.

In the present embodiment, in particular, regarding the configuration of the receiving device, the operation is described by limiting the number of antennas, but the same can be performed even if the number of antennas increases. That is, the number of antennas in the receiving device does not affect the operation and effect of the present embodiment.

Further, in the present embodiment, the LDPC code has been described as an example, but the present invention is not limited to this, and the decoding method is also limited to sum-product decoding as a soft-in / soft-out decoder. There are other soft-in / soft-out decoding methods, such as BCJR algorithm, SOVA algorithm, Max-log-MAP algorithm, etc. Details are shown in Non-Patent Document 6.

Further, in the present embodiment, the single carrier method has been described as an example, but the present invention is not limited to this, and the same can be performed even when multi-carrier transmission is performed. Therefore, for example, spectrum diffusion communication method, OFDM (Orthogonal Frequency-Division Multiplexing) method, SC-FDMA (Single Carrier Frequency Division Multiple Access), SC-OFDM (Single Carrier Orthogonal Frequency-Division Multiplexing) method, Non-Patent Document 7, etc. The same can be performed when the wavelet OFDM method or the like shown in is used. Further, in the present embodiment, symbols other than the data symbols, for example, pilot symbols (preambles, unique words, etc.), symbols for transmitting control information, and the like may be arranged in the frame.

Hereinafter, as an example of the multi-carrier method, an example when the OFDM method is used will be described.

FIG. 12 shows the configuration of the transmitter when the OFDM method is used. In FIG. 12, the same reference numerals are given to those operating in the same manner as in FIG.

The OFDM system-related processing unit 1201A receives the weighted signal 309A as an input, performs OFDM system-related processing, and outputs a transmission signal 1202A. Similarly, the OFDM method-related processing unit 1201B takes the phase-changed signal 309B as an input and outputs the transmission signal 1202B.

FIG. 13 shows an example of the configuration of the OFDM method-related processing units 1201A and 1201B and later in FIG. 12, and the parts related to 1201A to 312A in FIG. 12 are 1301A to 1310A and the parts related to 1201B to 312B. Is from 1301B to 1310B.

The serial-parallel conversion unit 1302A performs serial-parallel conversion of the weighted signal 1301A (corresponding to the weighted signal 309A in FIG. 12), and outputs a parallel signal 1303A.

The rearrangement unit 1304A receives the parallel signal 1303A as an input, performs rearrangement, and outputs the rearranged signal 1305A. The rearrangement will be described in detail later.

The inverse fast Fourier transform unit 1306A takes the rearranged signal 1305A as an input, performs an inverse fast Fourier transform, and outputs the signal 1307A after the inverse Fourier transform.

The radio unit 1308A receives the signal 1307A after the inverse Fourier transform as an input, performs processing such as frequency conversion and amplification, outputs the modulated signal 1309A, and the modulated signal 1309A is output as a radio wave from the antenna 1310A.

The serial-parallel conversion unit 1302B performs serial-parallel conversion on the weighted and phase-changed signal 1301B (corresponding to the phase-changed signal 309B in FIG. 12), and outputs the parallel signal 1303B.

The rearrangement unit 1304B receives the parallel signal 1303B as an input, performs rearrangement, and outputs the rearranged signal 1305B. The rearrangement will be described in detail later.

The inverse fast Fourier transform unit 1306B takes the rearranged signal 1305B as an input, performs an inverse fast Fourier transform, and outputs the signal 1307B after the inverse Fourier transform.

The radio unit 1308B receives the signal 1307B after the inverse Fourier transform as an input, performs processing such as frequency conversion and amplification, outputs the modulated signal 1309B, and the modulated signal 1309B is output as a radio wave from the antenna 1310B.

Since the transmission device of FIG. 3 is not a transmission method using a multi-carrier, the phase is changed so as to have four cycles as shown in FIG. 6, and the phase-changed symbols are arranged in the time axis direction. When using a multi-carrier transmission method such as the OFDM method shown in FIG. 12, naturally, the symbols after precoding and changing the phase are arranged in the time axis direction as shown in Fig. 3, and each of them is arranged. A method of performing for each (sub) carrier can be considered, but in the case of the multi-carrier transmission method, a method of arranging in the frequency axis direction or using both the frequency axis and the time axis can be considered. Hereinafter, this point will be described.

FIG. 14 shows an example of a method of rearranging symbols in the rearrangement portions 1301A and 1301B of FIG. 13 on the horizontal axis frequency and the vertical axis time, and the frequency axis is from (sub) carrier 0 to (sub) carrier 9. The modulated signals z1 and z2 use the same frequency band at the same time (time), and FIG. 14 (A) shows the method of rearranging the symbols of the modulated signal z1 and FIG. 14 (B). Shows how to rearrange the symbols of the modulated signal z2. The symbols of the weighted signal 1301A input by the serial-parallel converter 1302A are numbered in order as # 0, # 1, # 2, # 3, .... Here, since the case of cycle 4 is considered, # 0, # 1, # 2, and # 3 are for one cycle. Considering the same, # 4n, # 4n + 1, # 4n + 2, and # 4n + 3 (n is an integer of 0 or more) are for one cycle.

At this time, as shown in FIG. 14 (a), symbols # 0, # 1, # 2, # 3, ... Are arranged in order from carrier 0, and symbols # 0 to # 9 are arranged at time $ 1. After that, symbols # 10 to # 19 shall be arranged regularly, such as at time $ 2. The modulated signals z1 and z2 are complex signals.

Similarly, the symbols of the weighted and phase-changed signal 1301B input by the serial-parallel converter 1302B are numbered in order as # 0, # 1, # 2, # 3, .... .. Here, since the case of period 4 is considered, # 0, # 1, # 2, and # 3 have different phase changes, and # 0, # 1, # 2, and # 3 are one. It is for the cycle. Thinking in the same way, # 4n, # 4n + 1, # 4n + 2, and # 4n + 3 (n is an integer greater than or equal to 0) have different phase changes, and # 4n and # 4n + 1 , # 4n + 2 and # 4n + 3 are for one cycle.

At this time, as shown in FIG. 14 (b), symbols # 0, # 1, # 2, # 3, ... Are arranged in order from carrier 0, and symbols # 0 to # 9 are arranged at time $ 1. After that, symbols # 10 to # 19 shall be arranged regularly, such as at time $ 2.

The symbol group 1402 shown in FIG. 14 (B) is a symbol for one cycle when the phase changing method shown in FIG. 6 is used, and symbol # 0 is a symbol when the phase at time u in FIG. 6 is used. Symbol # 1 is a symbol when the phase of time u + 1 in FIG. 6 is used, symbol # 2 is a symbol when the phase of time u + 2 in FIG. 6 is used, and symbol # 2. 3 is a symbol when the phase of time u + 3 in Fig. 6 is used. Therefore, in symbol #x, when x mod 4 is 0 (the remainder when x is divided by 4, so mod: modulo), symbol #x is the symbol when using the phase of time u in FIG. Yes, when x mod 4 is 1, symbol # x is the symbol when the phase of time u + 1 in Fig. 6 is used, and when x mod 4 is 2, symbol # x is the time u + 2 in Fig. 6. It is a symbol when the phase of is used, and when x mod 4 is 3, the symbol #x is the symbol when the phase of time u + 3 in Fig. 6 is used.

In the present embodiment, the phase of the modulated signal z1 shown in FIG. 14A is not changed.

As described above, when a multi-carrier transmission method such as the OFDM method is used, the symbols can be arranged in the frequency axis direction, unlike the case of single-carrier transmission. The arrangement of symbols is not limited to the arrangement as shown in FIG. Other examples will be described with reference to FIGS. 15 and 16.

FIG. 15 shows an example of the symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 14, and FIG. 15 (A) shows the modulation signal z1. The method of rearranging the symbols of the above, FIG. 15 (B) shows the method of rearranging the symbols of the modulated signal z2. The difference between FIGS. 15 (A) and 15 (B) is that the method of rearranging the symbols of the modulated signal z1 and the method of rearranging the symbols of the modulated signal z2 are different. Place 0 to # 5 on carriers 4 to 9, symbols # 6 to # 9 on carriers 0 to 3, and then place symbols # 10 to # 19 on each carrier according to the same rules. At this time, similarly to FIG. 14 (B), the symbol group 1502 shown in FIG. 15 (B) is a symbol for one cycle when the phase changing method shown in FIG. 6 is used.

FIG. 16 shows an example of the symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 14, and FIG. 16 (A) shows the modulation signal z1. The method of rearranging the symbols, FIG. 16 (B) shows the method of rearranging the symbols of the modulated signal z2. The difference between FIGS. 16 (A) and 16 (B) is that the symbols are arranged in order on the carrier in FIG. 14, whereas the symbols are not arranged in order on the carrier in FIG. It is a point. As a matter of course, in FIG. 16, as in FIG. 15, the method of rearranging the symbols of the modulated signal z1 and the method of rearranging the modulated signal z2 may be different.

FIG. 17 shows an example of the symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIGS. 14 to 16, and FIG. 17 (A) shows modulation. The method of rearranging the symbols of the signal z1 and FIG. 17B show the method of rearranging the symbols of the modulated signal z2. In FIGS. 14 to 16, the symbols are arranged in the frequency axis direction, but in FIG. 17, the symbols are arranged using both the frequency and the time axis.

In FIG. 6, an example of switching the phase change in 4 slots has been described, but here, a case of switching in 8 slots will be described as an example. The symbol group 1702 shown in FIG. 17 is a symbol for one cycle (hence, 8 symbols) when the phase change method is used, and symbol # 0 is a symbol when the phase at time u is used, and the symbol # 1 is a symbol when the phase of time u + 1 is used, symbol # 2 is a symbol when the phase of time u + 2 is used, and symbol # 3 is a symbol when the phase of time u + 3 is used. Symbol # 4 is a symbol when the phase of time u + 4, symbol # 5 is a symbol when the phase of time u + 5 is used, and symbol # 6 is time u +. It is a symbol when the phase of 6 is used, and symbol # 7 is a symbol when the phase of time u + 7 is used. Therefore, in symbol #x, when x mod 8 is 0, symbol #x is the symbol when the phase of time u is used, and when x mod 8 is 1, symbol # x is the phase of time u + 1. When x mod 8 is 2, the symbol #x is the symbol when the phase of time u + 2 is used, and x When mod 8 is 3, the symbol #x is the symbol when the phase at time u + 3 is used, and when x mod 8 is 4, the symbol #x is the symbol when the phase at time u + 4 is used. So, when x mod 8 is 5, the symbol #x is the symbol when using the phase at time u + 5, and when x mod 8 is 6, the symbol #x uses the phase at time u + 6. The symbol when I was there, x mod When 8 is 7, symbol #x is the symbol when the phase of time u + 7 is used. In the symbol arrangement in FIG. 17, symbols for one cycle are arranged using a total of 4 × 2 = 8 slots, 4 slots in the time axis direction and 2 slots in the frequency axis direction. At this time, one cycle is arranged. The number of minute symbols is m × n symbols (that is, there are m × n types of phases to be multiplied.) The frequency axis slot (number of carriers) used to place symbols for one cycle is n, and the time axis. If the slot used in the direction is m, then m&gt; n. This is because the phase of the direct wave, the fluctuation in the time axis direction is gradual as compared with the fluctuation in the frequency axis direction. Therefore, since the regular phase change of the present embodiment is performed in order to reduce the influence of the steady direct wave, it is desired to reduce the fluctuation of the direct wave in the period of performing the phase change. Therefore, m&gt; n should be set. In consideration of the above points, it is better to rearrange the symbols using both the frequency axis and the time axis as shown in FIG. 17 rather than rearranging the symbols only in the frequency axis direction or only in the time axis direction. Is likely to be stationary, and the effect of the present invention can be easily obtained. However, when arranging in the direction of the frequency axis, the fluctuation of the frequency axis is steep, so there is a possibility that diversity gain can be obtained. It is not always the method.

FIG. 18 shows an example of a symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 17, and FIG. 18 (A) shows the modulation signal z1. The method of rearranging the symbols of the above, FIG. 18 (B) shows the method of rearranging the symbols of the modulated signal z2. In FIG. 18, the symbols are arranged using both the frequency and the time axis as in FIG. 17, but the difference from FIG. 17 is that in FIG. 17, the frequency direction is prioritized and then in the time axis direction. Whereas the symbols are arranged, in FIG. 18, the time axis direction is prioritized, and then the symbols are arranged in the frequency axis direction. In FIG. 18, the symbol group 1802 is a symbol for one cycle when the phase change method is used.

In addition, in FIGS. 17 and 18, similarly to FIG. 15, even if the symbol arrangement method of the modulation signal z1 and the symbol arrangement method of the modulation signal z2 are arranged differently, it can be carried out in the same manner, and it is expensive. The effect of being able to obtain reception quality can be obtained. Further, in FIGS. 17 and 18, even if the symbols are not arranged in order as in FIG. 16, the same can be performed, and the effect that high reception quality can be obtained can be obtained. can.

FIG. 22 shows an example of a symbol rearrangement method in the rearrangement portions 1301A and 130B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from the above. Consider the case where the phase is changed regularly using 4 slots such as time u ~ u + 3 in Fig. 6. The characteristic point in FIG. 22 is that the symbols are arranged in order in the frequency axis direction, but when the symbols are advanced in the time axis direction, the symbols are cyclically shifted by n (n = 1 in the example of FIG. 22). Is. In the four symbols shown in the symbol group 2210 in the frequency axis direction in FIG. 22, the phase of time u to u + 3 in FIG. 6 shall be changed.

At this time, the symbol of # 0 changes the phase using the phase of time u, # 1 changes the phase using the phase of time u + 1, and # 2 changes the phase using the phase of time u + 2, time u. It is assumed that the phase is changed using the phase of +3.

Similarly for the symbol group 2220 in the frequency axis direction, the phase change using the phase of time u in the symbol of # 4, the phase change using the phase of time u + 1 in # 5, and the phase change of time u + 2 in # 6. It is assumed that the phase is changed using the phase, and in # 7, the phase is changed using the phase at time u + 3.

The phase was changed as described above for the symbol of time $ 1, but since it is cyclically shifted in the time axis direction, the phase of the symbols 2201, 2202, 2203, and 2204 is changed as follows. Will do.

In the symbol group 2201 in the time axis direction, the # 0 symbol uses the phase change at time u, the # 9 uses the phase change at time u + 1, and the # 18 uses the phase at time u + 2. It is assumed that the phase is changed using the phase at time u + 3 in # 27.

In the symbol group 2202 in the time axis direction, the phase of the symbol of # 28 uses the phase change of time u, the phase change of # 1 uses the phase of time u + 1, and the phase of # 10 uses the phase of time u + 2. It is assumed that the phase change that was performed, and in # 19, the phase change using the phase at time u + 3 is performed.

In the symbol group 2203 in the time axis direction, the phase of the symbol of # 20 uses the phase change of time u, the phase change of # 29 uses the phase of time u + 1, and the phase of # 2 uses the phase of time u + 2. It is assumed that the phase is changed using the phase at time u + 3 in # 11.

In the symbol group 2204 in the time axis direction, the # 12 symbol uses the phase change at time u, the # 21 uses the phase change at time u + 1, and the # 30 uses the phase at time u + 2. It is assumed that the phase change was performed, and in # 3, the phase is changed using the phase at time u + 3.

The feature in FIG. 22 is that, for example, when focusing on the symbol of # 11, the symbols (# 10 and # 12) on both sides in the frequency axis direction at the same time both change the phase using a phase different from that of # 11. At the same time, the symbols (# 2 and # 20) on both sides of the same carrier of the symbol of # 11 in the time axis direction change the phase using a phase different from that of # 11. And this is not limited to the symbol of # 11, and all the symbols having symbols on both sides in the frequency axis direction and the time axis direction have the same characteristics as the symbol of # 11. As a result, the phase is effectively changed, and it is less likely to be affected by the constant condition of the direct wave, so that the data reception quality is likely to be improved.

In FIG. 22, the explanation is made with n = 1, but the present invention is not limited to this, and the same can be performed with n = 3. Further, in FIG. 22, the above characteristics are realized by arranging the symbols on the frequency axis and cyclically shifting the order of the arrangement of the symbols when the time advances in the axial direction, but the symbols are random. There is also a method to realize the above characteristics by arranging them (which may be regular).

(Embodiment 2) In the first embodiment, the phase of the weighted composite signal z (t) (precoded by a fixed precoding matrix) is changed. Here, various embodiments of the phase changing method that can obtain the same effect as that of the first embodiment will be disclosed.

In the above embodiment, as shown in FIGS. 3 and 6, the phase changing unit 317B is configured to execute the phase change only for one output from the weighting combining unit 600.

However, the timing for executing the phase change may be executed before the precoding by the weighting / combining unit 600, and the transmitting device replaces the configuration shown in FIG. 6 with the configuration shown in FIG. 6, as shown in FIG. 25. The phase changing unit 317B may be provided in front of the weighting / combining unit 600.

In this case, the phase change unit 317B performs regular phase change to the baseband signal s2 (t) according to the mapping of the selected modulation method, and s2'(t) = s2 (t) y. (t) (where y (t) is changed by t) is output, and the weighted synthesizer 600 performs precoding on s2'(t) and z2 (t) (= W2s2'). (t)) (Refer to Eq. (42)) may be output and transmitted.

Further, the phase change may be performed for both the modulated signals s1 (t) and s2 (t), and the transmitter is as shown in FIG. 26 instead of the configuration shown in FIG. , A phase changing unit may be provided for both outputs of the weighting / combining unit 600.

The phase changing unit 317A regularly changes the phase of the input signal in the same manner as the phase changing unit 317B, and changes the phase of the precoded signal z1'(t) from the weighting synthesis unit. The phase-changed signal z1 (t) is output to the transmitter.

However, the phase changing unit 317A and the phase changing unit 317B change the phase as shown in FIG. 26 at the same timing to change the phase of each other. (However, the following is an example, and the phase change method is not limited to this.) At time u, the phase change unit 317A in FIG. 26 has z1 (t) = y.₁(t) z1'(t), and the phase change unit 317B is z2 (t) = y₂(t) Change the phase so that it becomes z2'(t). For example, as shown in FIG. 26, at time u, y₁(u) = e^j0, Y₂(u) = e^{-jπ / 2}, At time u + 1, y₁(u + 1) = e^{jπ / 4}, Y₂(u + 1) = e^{-j3π / 4}, ..., at time u + k, y₁(u + k) = e^{jkπ / 4}, Y₂(u + k) = e^{j (-kπ / 4-π / 2)}, And change the phase. The period for regularly changing the phase may be the same or different between the phase changing unit 317A and the phase changing unit 317B.

Further, as described above, the timing of changing the phase may be before the execution of precoding by the weighting / synthesizing unit, and the transmission device may have the configuration shown in FIG. 27 instead of the configuration shown in FIG. 26.

When the phases of both modulated signals are changed regularly, it is assumed that each transmitted signal includes information on each phase change pattern as, for example, control information, and the receiving device obtains this control information. Then, the transmitting device can know the phase changing method, that is, the phase changing pattern, which is regularly switched, and thereby, it becomes possible to perform correct demodulation (detection).

Next, a modified example of the configuration of FIGS. 6 and 25 will be described with reference to FIGS. 28 and 29. The difference between FIG. 28 and FIG. 6 is that the information 2800 regarding the phase change ON / OFF exists, and the phase change is performed to either z1'(t) or z2'(t) (at the same time). , Or, at the same frequency, the phase is changed to either z1'(t) or z2'(t).) Point. Therefore, since the phase change is performed to either z1'(t) or z2'(t), the phase change unit 317A and the phase change unit 317B in FIG. 28 perform the phase change (ON). In some cases, the phase is not changed (OFF). The control information related to this ON / OFF becomes the information 2800 related to the phase change ON / OFF. The information 2800 regarding the phase change ON / OFF is output from the signal processing method information generation unit 314 shown in FIG.

The phase change section 317A in FIG. 28 has z1 (t) = y.₁(t) z1'(t), and the phase change unit 317B is z2 (t) = y₂The phase will be changed so that (t) z2'(t).

At this time, for example, z1'(t) is assumed to change the phase in period 4. (At this time, z2'(t) does not change the phase.) Therefore, at time u, y₁(u) = e^j0, Y₂(u) = 1, at time u + 1, y₁(u + 1) = e^{jπ / 2}, Y₂At (u + 1) = 1, time u + 2, y₁(u + 2) = e^jπ, Y₂At (u + 2) = 1, time u + 3, y₁(u + 3) = e^{j3π / 2}, Y₂It is assumed that (u + 3) = 1.

Next, for example, z2'(t) is assumed to change the phase in period 4. (At this time, z1'(t) does not change the phase.) Therefore, at time u + 4, y₁(u + 4) = 1, y₂(u + 4) = e^j0, At time u + 5, y₁(u + 5) = 1, y₂(u + 5) = e^{jπ / 2}, At time u + 6, y₁(u + 6) = 1, y₂(u + 6) = e^jπ, At time u + 7, y₁(u + 7) = 1, y₂(u + 7) = e^{j3π / 2}It shall be assumed.

Therefore, in the above example, at time 8k, y₁(8k) = e^j0, Y₂When (8k) = 1, time 8k + 1, y₁(8k + 1) = e^{jπ / 2}, Y₂When (8k + 1) = 1, time 8k + 2, y₁(8k + 2) = e^jπ, Y₂When (8k + 2) = 1, time 8k + 3, y₁(8k + 3) = e^{j3π / 2}, Y₂When (8k + 3) = 1, time 8k + 4, y₁(8k + 4) = 1, y₂(8k + 4) = e^j0, When the time is 8k + 5, y₁(8k + 5) = 1, y₂(8k + 5) = e^{jπ / 2}, When the time is 8k + 6, y₁(8k + 6) = 1, y₂(8k + 6) = e^jπ, When the time is 8k + 7, y₁(8k + 7) = 1, y₂(8k + 7) = e^{j3π / 2}Will be.

As described above, there is a time for changing the phase only for z1'(t) and a time for changing the phase only for z2'(t). Further, the phase change cycle is composed of the time for changing the phase only for z1'(t) and the time for changing the phase only for z2'(t). In the above, the period when the phase is changed only for z1'(t) and the period when the phase is changed only for z2'(t) are the same, but the period is not limited to this, and z1'(. The period when only t) is changed in phase and the period when only z2'(t) is changed in phase may be different. Further, in the above example, it is explained that the phase of z1'(t) is changed in 4 cycles and then the phase of z2'(t) is changed in 4 cycles, but the present invention is not limited to this. , The order of the phase change of z1'(t) and the phase change of z2'(t) may be arbitrary (for example, the phase change of z1'(t) and the phase change of z2'(t) are alternated. It may be performed, the order may be according to a certain rule, or the order may be random.) The phase change unit 317A in FIG. 29 has s1'(t) = y.₁(t) s1 (t), and the phase change unit 317B has s2'(t) = y₂The phase will be changed so that (t) s2 (t).

At this time, for example, s1 (t) is assumed to change the phase in period 4. (At this time, s2 (t) does not change the phase.) Therefore, at time u, y₁(u) = e^j0, Y₂(u) = 1, at time u + 1, y₁(u + 1) = e^{jπ / 2}, Y₂At (u + 1) = 1, time u + 2, y₁(u + 2) = e^jπ, Y₂At (u + 2) = 1, time u + 3, y₁(u + 3) = e^{j3π / 2}, Y₂It is assumed that (u + 3) = 1.

Next, for example, it is assumed that s2 (t) changes the phase in period 4. (At this time, s1 (t) does not change the phase.) Therefore, at time u + 4, y₁(u + 4) = 1, y₂(u + 4) = e^j0, At time u + 5, y₁(u + 5) = 1, y₂(u + 5) = e^{jπ / 2}, At time u + 6, y₁(u + 6) = 1, y₂(u + 6) = e^jπ, At time u + 7, y₁(u + 7) = 1, y₂(u + 7) = e^{j3π / 2}It shall be assumed.

Therefore, in the above example, at time 8k, y₁(8k) = e^j0, Y₂When (8k) = 1, time 8k + 1, y₁(8k + 1) = e^{jπ / 2}, Y₂When (8k + 1) = 1, time 8k + 2, y₁(8k + 2) = e^jπ, Y₂When (8k + 2) = 1, time 8k + 3, y₁(8k + 3) = e^{j3π / 2}, Y₂When (8k + 3) = 1, time 8k + 4, y₁(8k + 4) = 1, y₂(8k + 4) = e^j0, When the time is 8k + 5, y₁(8k + 5) = 1, y₂(8k + 5) = e^{jπ / 2}, When the time is 8k + 6, y₁(8k + 6) = 1, y₂(8k + 6) = e^jπ, When the time is 8k + 7, y₁(8k + 7) = 1, y₂(8k + 7) = e^{j3π / 2}Will be.

As described above, there is a time for changing the phase only for s1 (t) and a time for changing the phase only for s2 (t). Further, the phase change cycle is composed of the time for changing the phase only for s1 (t) and the time for changing the phase only for s2 (t). In the above, the period when the phase is changed only for s1 (t) and the period when the phase is changed only for s2 (t) are the same, but the period is not limited to this, and only s1 (t) is used. The period for changing the phase and the period for changing the phase only for s2 (t) may be different. Further, in the above example, it is explained that the phase of s1 (t) is changed in 4 cycles and then the phase of s2 (t) is changed in 4 cycles. The order of the phase change of (t) and the phase change of s2 (t) may be arbitrary (for example, the phase change of s1 (t) and the phase change of s2 (t) may be alternately performed. The order may be according to a certain rule, or the order may be random.) Thereby, the reception states when the transmission signals z1 (t) and z2 (t) are received on the receiving device side are equalized. In addition, the phase of each of the received signals z1 (t) and z2 (t) can be periodically switched to improve the error correction capability after error correction and decoding, so that the LOS environment can be used. It is possible to improve the reception quality in.

As described above, even with the configuration shown in the second embodiment, the same effect as that of the first embodiment can be obtained.

In the present embodiment, the case where the single carrier method is used as an example, that is, the case where the phase change is performed with respect to the time axis has been described, but the present invention is not limited to this, and the same method may be used even when multi-carrier transmission is performed. Can be done. Therefore, for example, spectrum diffusion communication method, OFDM (Orthogonal Frequency-Division Multiplexing) method, SC-FDMA (Single Carrier Frequency Division Multiple Access), SC-OFDM (Single Carrier Orthogonal Frequency-Division) The same can be applied to the case where the Multiplexing) method, the wavelet OFDM method shown in Non-Patent Document 7 and the like are used. As described above, in the present embodiment, the case of performing the phase change in the time t-axis direction has been described as an explanation for performing the phase change, but the phase change is performed in the frequency axis direction as in the first embodiment. That is, in the present embodiment, in the description of the phase change in the t direction, t is replaced with f (f: frequency ((sub) carrier)), and the phase change method described in the present embodiment is considered. Can be applied to phase change in the frequency direction. Further, the phase change method of the present embodiment can be applied to the phase change in the time-frequency direction as in the description of the first embodiment.

Therefore, although FIGS. 6, 25, 26, and 27 show the case where the phase is changed in the time axis direction, in FIGS. 6, 25, 26, and 27, the time t is replaced with the carrier f. By thinking, it is equivalent to changing the phase in the frequency direction, and by substituting time t for time t and frequency f, that is, (t) for (t, f), phase change in the time frequency block. Is equivalent to doing.

Then, in the present embodiment, symbols other than the data symbols, for example, pilot symbols (preambles, unique words, etc.), symbols for transmitting control information, and the like may be arranged in the frame.

(Embodiment 3) In the above-described first and second embodiments, the phase is changed regularly. In the third embodiment, in the receiving devices that are scattered in various places when viewed from the transmitting device, the receiving devices can obtain good data reception quality regardless of where the receiving devices are arranged. The method will be disclosed.

In the third embodiment, the symbol arrangement of the signal obtained by changing the phase will be described.

FIG. 31 shows an example of the frame configuration of some symbols of the signal on the time-frequency axis when a multi-carrier method such as the OFDM method is used in the transmission method in which the phase is regularly changed.

First, of the two precoded baseband signals described in the first embodiment, a case where one of the baseband signals (see FIG. 6) is phase-changed will be described.

(Note that FIG. 6 shows the case where the phase is changed in the time axis direction, but in FIG. 6, it is equivalent to performing the phase change in the frequency direction by replacing the time t with the carrier f. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) FIG. 31 is shown in FIG. It shows the frame configuration of the modulation signal z2'which is the input of the phase change unit 317B, and one square is a symbol (however, since it is precoded, it usually contains both signals of s1 and s2. However, depending on the configuration of the precoding matrix, it may be only one signal of s1 and s2.).

Here, we focus on the symbol 3100 of carrier 2 and time $ 2 in Fig. 31. Although it is described as a carrier here, it may also be referred to as a subcarrier.

In carrier 2, the symbols closest to time $ 2, that is, the symbol 3103 at time $ 1 of carrier 2 and the symbol 3101 at time $ 3, are the channel states of carrier 2, the symbol 3100 at time $ 2, and so on. Very high correlation.

Similarly, at time $ 2, the channel states of the frequency symbol closest to carrier 2 in the frequency axis direction, namely carrier 1, time $ 2 symbol 3104 and time $ 2, carrier 3 symbol 3104, are both carriers. 2. Very high correlation with the channel state of symbol 3100 at time $ 2.

As mentioned above, the channel states of symbols 3101, 3102, 3103, and 3104 are highly correlated with the channel states of symbol 3100.

In the present specification, it is assumed that N kinds of phases (where N is an integer of 2 or more) are prepared as the phases to be multiplied in the transmission method in which the phases are regularly changed. The symbols shown in FIG. 31 include, for example, "e".^j0This is for the signal z2'in FIG. 6 in this symbol, which is "e".^j0"Is multiplied to mean that the phase has been changed. That is, the values described in each symbol in FIG. 31 are y (t) in the equation (42) and z2 (t) = y described in the second embodiment.₂(t) y in z2'(t)₂It becomes the value of (t).

In the present embodiment, high data reception quality is obtained on the receiving device side by utilizing the high correlation between the channel states of the symbols adjacent to each other in the frequency axis direction and / or the symbols adjacent to each other in the time axis direction. Discloses the symbol arrangement of the phase-changed symbols obtained.

&lt;Condition # 1&gt; and &lt;Condition # 2&gt; can be considered as conditions for obtaining high data reception quality on the receiving side.

&lt;Condition # 1&gt; As shown in Fig. 6, when a multi-carrier transmission method such as OFDM is used in the transmission method that regularly changes the phase of the precoded baseband signal z2', the time X -Carrier Y is a symbol for data transmission (hereinafter referred to as data symbol), and adjacent symbols in the time axis direction, that is, time X-1 · carrier Y and time X + 1 · carrier Y are all data. Precoding of the precoded baseband signal z2'corresponding to these three data symbols, namely time X · carrier Y, time X-1 · carrier Y and time X + 1 · carrier Y, respectively. In the later baseband signal z2', different phase changes are made.

&lt;Condition # 2&gt; As shown in Fig. 6, when a multi-carrier transmission method such as OFDM is used in the transmission method that regularly changes the phase of the precoded baseband signal z2', the time X -Carrier Y is a symbol for data transmission (hereinafter referred to as data symbol), and adjacent symbols in the frequency axis direction, that is, time X · carrier Y-1 and time X · carrier Y + 1 are both data. If it is a symbol, the pre-coded baseband signal z2'corresponding to these three data symbols, that is, the pre-codes in time X-carrier Y, time X-carrier Y-1, and time X-carrier Y + 1, respectively. In the baseband signal z2'after coding, different phase changes are performed in each case.

Then, it is preferable that there is a data symbol that satisfies &lt;condition # 1&gt;. Similarly, it is desirable that there is a data symbol that satisfies &lt;Condition 2&gt;.

The reason why this &lt;condition # 1&gt; and &lt;condition # 2&gt; are derived is as follows.

There is a certain symbol (hereinafter referred to as symbol A) in the transmission signal, and the channel state of each symbol temporally adjacent to the symbol A has a high correlation with the channel state of the symbol A as described above.

Therefore, if different phases are used for three symbols that are adjacent in time, the symbol A has poor reception quality (although the reception quality is high for SNR, the phase relationship of the direct wave is poor) in the LOS environment. Even if the reception quality is poor due to the poor situation), it is very likely that good reception quality can be obtained with the two symbols adjacent to the remaining symbol A, and as a result, after error correction and decoding. Can obtain good reception quality.

Similarly, there is a symbol (hereinafter referred to as symbol A) in the transmission signal, and the channel state of each symbol frequency-adjacent to this symbol A has a high correlation with the channel state of symbol A as described above. ..

Therefore, if different phases are used for the three symbols that are adjacent in frequency, the symbol A has poor reception quality (although the reception quality is high for SNR, the phase relationship of the direct wave is poor) in the LOS environment. Even if the reception quality is poor due to the poor situation), it is very likely that good reception quality can be obtained with the two symbols adjacent to the remaining symbol A, and as a result, after error correction and decoding. Can obtain good reception quality.

Further, by combining &lt;Condition # 1&gt; and &lt;Condition # 2&gt;, there is a possibility that the reception quality of data can be further improved in the receiving device. Therefore, the following &lt;condition # 3&gt; can be derived.

&lt;Condition # 3&gt; As shown in Fig. 6, when a multi-carrier transmission method such as OFDM is used in the transmission method that regularly changes the phase of the precoded baseband signal z2', the time X -Carrier Y is a symbol for data transmission (hereinafter referred to as data symbol), and adjacent symbols in the time axis direction, that is, time X-1 · carrier Y and time X + 1 · carrier Y are all data. Precoding corresponding to these five data symbols when they are symbols and adjacent symbols in the frequency axis direction, that is, time X carrier Y-1 and time X carrier Y + 1 are both data symbols. Later baseband signals z2', i.e. time X carrier Y and time X-1 carrier Y and time X + 1 carrier Y and time X carrier Y-1 and time X carrier Y + 1, respectively. The precoded baseband signal z2'has different phase changes.

Here, a supplement is given regarding "different phase changes". The phase change will be defined from 0 radians to 2π radians. For example, at time X and carrier Y, the phase change applied to the baseband signal z2'after precoding in FIG. 6 is performed.^{jθX, Y}, At time X-1 and carrier Y, change the phase of the baseband signal z2'after precoding in Fig. 6 e.^{jθX-1, Y}, At time X + 1 and carrier Y, e change the phase applied to the baseband signal z2'after precoding in Fig. 6.^{jθX + 1, Y}Then 0 radians θ_{X, Y}&lt;2π, 0 radians θ_{X-1, Y}&lt;2π, 0 radians θ_{X + 1, Y}&lt;2π. Therefore, in &lt;condition # 1&gt;, θ_{X, Y} θ_{X-1, Y}And θ_{X, Y} θ_{X + 1, Y}And θ_{X +}_{1, Y} θ_{X-1, Y}Will be established. Considering the same, in &lt;Condition # 2&gt;, θ_{X, Y} θ_{X, Y-1}And θ_{X, Y} θ_{X, Y + 1}And θ_{X, Y-1} θ_{X-1, Y + 1}Will be satisfied, and in &lt;condition # 3&gt;, θ_{X, Y} θ_{X-1, Y}And θ_{X, Y} θ_{X + 1, Y}And θ_{X, Y} θ_{X, Y-1}And θ_{X, Y} θ_{X, Y + 1}And θ_{X-1, Y} θ_{X + 1, Y}And θ_{X-1, Y} θ_{X, Y-1}And θ_{X-1, Y} θ_{X, Y + 1}And θ_{X + 1, Y} θ_{X, Y-1}And θ_{X + 1, Y} θ_{X, Y + 1}And θ_{X, Y-1} θ_{X, Y + 1}Will be established.

Then, it is preferable that there is a data symbol that satisfies &lt;condition # 3&gt;.

FIG. 31 is an example of &lt;condition # 3&gt;, in which the phase multiplied by the precoded baseband signal z2'in FIG. 6 corresponding to the symbol 3100 corresponding to the symbol A and the symbol 3100 are temporally. Symbols that are frequency-adjacent to the phase multiplied by the precoded baseband signal z2'in FIG. 6 corresponding to the adjacent symbol 3101 and the precoded baseband signal z2' in FIG. 6 corresponding to 3103. The phases multiplied by the precoded baseband signal z2'in FIG. 6 corresponding to 3102 and the precoded baseband signal z2' in FIG. 6 corresponding to 3104 are arranged so as to be different from each other. Therefore, even if the reception quality of the symbol 3100 is poor on the receiving side, the reception quality of the adjacent symbol is very high, so that high reception quality after error correction and decoding can be ensured.

Figure 32 shows an example of the arrangement of symbols obtained by changing the phase under this condition.

As can be seen from FIG. 32, in any data symbol, the degree of phase change for the symbols whose phases are adjacent to each other in both the frequency axis direction and the time axis direction is different from each other. ing. By doing so, the error correction capability of the receiving device can be further improved.

That is, in FIG. 32, when data symbols exist in adjacent symbols in the time axis direction, &lt;condition # 1&gt; is satisfied for all X and all Y.

Similarly, in FIG. 32, when a data symbol exists in an adjacent symbol in the frequency direction, &lt;condition # 2&gt; is satisfied for all X and all Y.

Similarly, in FIG. 32, if the data symbol exists in the adjacent symbol in the frequency direction and the data symbol exists in the adjacent symbol in the time axis direction, &lt;condition # 3&gt; is all X, all. It is established by Y of.

Next, the case where the phase of the two precoded baseband signals described in the second embodiment is changed (see FIG. 26) will be described.

As shown in FIG. 26, when giving a phase change to both the precoded baseband signal z1'and the precoded baseband signal z2', there are several methods for changing the phase. This point will be explained in detail.

As method 1, the phase change of the baseband signal z2'after precoding is performed as shown in FIG. 32 as described above. In FIG. 32, the phase change of the baseband signal z2'after precoding has a period of 10. However, as mentioned above, in order to satisfy &lt;Condition # 1&gt; &lt;Condition # 2&gt; &lt;Condition # 3&gt;, (sub) carrier 1 applies to the precoded baseband signal z2'. The phase change is changing over time. (Although such a change is made in FIG. 32, a period of 10 may be used and another phase change method may be used.) Then, the phase change of the baseband signal z1'after precoding is shown in FIG. 33. As described above, in the phase change of the baseband signal z2'after precoding, the phase change value for one cycle of cycle 10 is constant. In FIG. 33, at time $ 1 including one cycle (of the phase change of the precoded baseband signal z2'), the value of the phase change of the precoded baseband signal z1'is e.^j0At time $ 2, which includes one cycle (of the phase change of the baseband signal z2'after precoding), the value of the phase change of the baseband signal z1'after precoding is e.^{jπ / 9}And ...

The symbols shown in FIG. 33 include, for example, "e".^j0Is added, which means "e" for the signal z1'in FIG. 26 in this symbol.^j0"Is multiplied to mean that the phase has been changed. That is, the values described in each symbol in FIG. 33 are z1 (t) = y described in the second embodiment.₁(t) y in z1'(t)₁It becomes the value of (t).

As shown in Fig. 33, the phase change of the baseband signal z1'after precoding is performed by changing the phase of the baseband signal z2' after precoding by setting the phase change value for one cycle of cycle 10 to be constant. The value should be changed along with the number for one cycle. (As mentioned above, in FIG. 33, in the first cycle, e^j0And in the second cycle, e^{jπ / 9}, ... ) By doing the above, the phase change of the baseband signal z2'after precoding has a period of 10, but the phase change of the baseband signal z1'after precoding and the baseband signal z2' after precoding It is possible to obtain the effect that the period can be made larger than 10 when both of the phase changes of are taken into consideration. This may improve the reception quality of the data of the receiving device.

As method 2, the phase change of the baseband signal z2'after precoding is performed as shown in FIG. 32 as described above. In FIG. 32, the phase change of the baseband signal z2'after precoding has a period of 10. However, as mentioned above, in order to satisfy &lt;Condition # 1&gt; &lt;Condition # 2&gt; &lt;Condition # 3&gt;, (sub) carrier 1 applies to the precoded baseband signal z2'. The phase change is changing over time. (Although such a change is made in FIG. 32, a period of 10 may be used and another phase change method may be used.) And the phase change of the baseband signal z1'after precoding is shown in FIG. As shown, the phase change of the baseband signal z2'after precoding performs the phase change in the period 3 different from the period 10.

The symbols shown in FIG. 30 include, for example, "e".^j0Is added, which means "e" for the signal z1'in FIG. 26 in this symbol.^j0"Is multiplied to mean that the phase has been changed. That is, the values described in each symbol in FIG. 30 are z1 (t) = y described in the second embodiment.₁(t) y in z1'(t)₁It becomes the value of (t).

By doing so, the phase change of the baseband signal z2'after precoding has a period of 10, but the phase change of the baseband signal z1'after precoding and the phase change of the baseband signal z2' after precoding The period when both phase changes are taken into consideration is 30, and the period when both the phase change of the baseband signal z1'after precoding and the phase change of the baseband signal z2' after precoding are taken into consideration is larger than 10. You can get the effect that you can. This may improve the reception quality of the data of the receiving device. One effective method of method 2 is especially when the phase change cycle of the baseband signal z1'after precoding is N and the phase change cycle of the baseband signal z2' after precoding is M. If N and M are in an elementary relationship with each other, the period when both the phase change of the baseband signal z1'after precoding and the phase change of the baseband signal z2' after precoding are taken into consideration is N × M. It has the advantage that it can be easily set to a large period, but it is possible to increase the period even if N and M are in a prime relationship with each other.

Note that the phase changing method of the third embodiment is an example and is not limited to this, and as described in the first and second embodiments, the phase can be changed in the frequency axis direction or the time can be changed. Even if the phase is changed in the axial direction or the phase is changed in the time-frequency block, the reception quality of the data in the receiving device can be improved in the same manner.

In addition to the frame configuration described above, it is conceivable that a pilot symbol (SP (Scattered Pilot)) or a symbol for transmitting control information may be inserted between the data symbols. The phase change in this case will be described in detail.

FIG. 47 shows the frame configuration on the time-frequency axis of the modulated signal (baseband signal after precoding) z1 or z1'and the modulated signal (baseband signal after precoding) z2', FIG. 47 (a). ) Is the time of the modulated signal (baseband signal after precoding) z1 or z1'-frame configuration on the frequency axis, FIG. 47 (b) is the time of the modulated signal (baseband signal after precoding) z2'- It is a frame configuration on the frequency axis. In FIG. 47, 4701 is a pilot symbol, 4702 is a data symbol, and the data symbol 4702 is a precoded or precoded and phase-changed symbol.

FIG. 47 shows the symbol arrangement when the phase is changed for the precoded baseband signal z2'as shown in FIG. 6 (the phase is not changed for the precoded baseband signal z1). ). (Note that FIG. 6 shows the case where the phase is changed in the time axis direction, but in FIG. 6, it is equivalent to performing the phase change in the frequency direction by replacing the time t with the carrier f. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, after precoding in FIG. 47. The numerical value described in the symbol of the baseband signal z2'indicates the phase change value. Since the phase of the symbol of the baseband signal z1'(z1) after precoding in FIG. 47 is not changed in phase, the numerical value is not described.

The important point in FIG. 47 is that the phase change for the baseband signal z2'after precoding is applied to the data symbol, that is, the precoded symbol. (Here, it is described as a symbol, but since the symbol described here is precoded, it includes both the s1 symbol and the s2 symbol.) Therefore. , The phase change will not be applied to the pilot symbol inserted in z2'.

FIG. 48 shows the frame configuration of the modulated signal (precoded baseband signal) z1 or z1'and the modulated signal (precoded baseband signal) z2' on the time-frequency axis, FIG. 48 (a). ) Is the time of the modulated signal (baseband signal after precoding) z1 or z1'-frame configuration on the frequency axis, and Fig. 48 (b) is the time of the modulated signal (baseband signal after precoding) z2'-. It is a frame configuration on the frequency axis. In FIG. 48, 4701 indicates a pilot symbol, 4702 indicates a data symbol, and the data symbol 4702 is a symbol that has undergone precoding and phase change.

FIG. 48 shows the symbol arrangement when the phase is changed for the precoded baseband signal z1'and the precoded baseband signal z2', as shown in FIG. 26. (Note that FIG. 26 shows the case where the phase is changed in the time axis direction, but in FIG. 26, by substituting the time t with the carrier f, it is equivalent to performing the phase change in the frequency direction. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, after precoding in FIG. 48. The numerical values shown in the symbols of the baseband signal z1'and the precoded baseband signal z2' indicate the phase change value.

The important point in FIG. 48 is that the phase change for the precoded baseband signal z1'is applied to the data symbol, that is, the precoded symbol, and the precoded baseband signal z2. The phase change for'is the point applied to the data symbol, that is, the precoded symbol. (Here, it is described as a symbol, but since the symbol described here is precoded, it includes both the s1 symbol and the s2 symbol.) Therefore. , The phase change is not applied to the pilot symbol inserted in z1', and the phase change is not applied to the pilot symbol inserted in z2'.

FIG. 49 shows the frame configuration on the time-frequency axis of the modulated signal (baseband signal after precoding) z1 or z1'and the modulated signal (baseband signal after precoding) z2', FIG. 49 (a). ) Is the modulated signal (baseband signal after precoding) z1 or z1' Time-frame configuration on the frequency axis, FIG. 49 (b) shows the frame configuration on the time-frequency axis of the modulated signal (baseband signal after precoding) z2'. In FIG. 49, 4701 is a pilot symbol, 4702 is a data symbol, 4901 is a null symbol, the in-phase component I = 0 of the baseband signal, and the orthogonal component Q = 0. At this time, the data symbol 4702 becomes a precoding or a symbol that has undergone phase change with precoding. The difference between FIGS. 49 and 47 is the method of constructing symbols other than the data symbol, where the modulated signal z2'is a null symbol at the time and carrier when the pilot symbol is inserted in the modulated signal z1', and vice versa. In addition, the modulation signal z1'is a null symbol at the time and carrier when the pilot symbol is inserted in the modulation signal z2'.

FIG. 49 shows the symbol arrangement when the phase is changed for the precoded baseband signal z2'as shown in FIG. 6 (the phase is not changed for the precoded baseband signal z1). ). (Note that FIG. 6 shows the case where the phase is changed in the time axis direction, but in FIG. 6, it is equivalent to performing the phase change in the frequency direction by replacing the time t with the carrier f. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, after precoding in FIG. 49. The numerical value described in the symbol of the baseband signal z2'indicates the phase change value. Since the phase of the symbol of the baseband signal z1'(z1) after precoding in FIG. 49 is not changed, the numerical value is not described.

The important point in FIG. 49 is that the phase change for the baseband signal z2'after precoding is applied to the data symbol, that is, the precoded symbol. (Here, it is described as a symbol, but since the symbol described here is precoded, it includes both the s1 symbol and the s2 symbol.) Therefore. , The phase change will not be applied to the pilot symbol inserted in z2'.

FIG. 50 shows the frame configuration on the time-frequency axis of the modulated signal (baseband signal after precoding) z1 or z1'and the modulated signal (baseband signal after precoding) z2', FIG. 50 (a). ) Is the modulated signal (baseband signal after precoding) z1 or z1' Time-frame configuration on the frequency axis, FIG. 50 (b) shows the frame configuration on the time-frequency axis of the modulated signal (baseband signal after precoding) z2'. In FIG. 50, 4701 is a pilot symbol, 4702 is a data symbol, 4901 is a null symbol, the in-phase component I = 0 of the baseband signal, and the orthogonal component Q = 0. At this time, the data symbol 4702 becomes a precoding or a symbol that has undergone phase change with precoding. The difference between FIGS. 50 and 48 is the method of constructing symbols other than the data symbol, where the modulated signal z2'is a null symbol at the time and carrier when the pilot symbol is inserted in the modulated signal z1', and vice versa. In addition, the modulation signal z1'is a null symbol at the time and carrier when the pilot symbol is inserted in the modulation signal z2'.

FIG. 50 shows the symbol arrangement when the phase is changed for the precoded baseband signal z1'and the precoded baseband signal z2', as shown in FIG. 26. (Note that FIG. 26 shows the case where the phase is changed in the time axis direction, but in FIG. 26, by substituting the time t with the carrier f, it is equivalent to performing the phase change in the frequency direction. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, after precoding in FIG. 50. The numerical values shown in the symbols of the baseband signal z1'and the precoded baseband signal z2' indicate the phase change value.

The important point in FIG. 50 is that the phase change for the precoded baseband signal z1'is applied to the data symbol, that is, the precoded symbol, and the precoded baseband signal z2. The phase change for'is the point applied to the data symbol, that is, the precoded symbol. (Here, it is described as a symbol, but since the symbol described here is precoded, it includes both the s1 symbol and the s2 symbol.) Therefore. , The phase change is not applied to the pilot symbol inserted in z1', and the phase change is not applied to the pilot symbol inserted in z2'.

FIG. 51 shows an example of the configuration of a transmission device that generates and transmits a modulated signal having the frame configuration of FIGS. 47 and 49, and the same reference numerals are given to those that operate in the same manner as in FIG. ..

In FIG. 51, the weighting synthesis units 308A and 308B and the phase change unit 317B operate only when the frame configuration signal 313 indicates the timing of the data symbol.

When the pilot symbol (which also serves as null symbol generation) generation unit 5101 of FIG. 51 indicates that the frame configuration signal 313 is a pilot symbol (and a null symbol), the baseband signal 5102A of the pilot symbol and Output 5102B.

Although not shown in the frame configurations of FIGS. 47 to 50, no precoding (and no phase rotation) is applied, for example, a method of transmitting a modulated signal from one antenna (in this case, the other antenna). When the control information symbol is transmitted using a transmission method using a spatiotemporal code (particularly a spatiotemporal block code), the control information symbol 5104 is a control information 5103, a frame. When the configuration signal 313 is input and the frame configuration signal 313 indicates that it is a control information symbol, the baseband signals 5102A and 5102B of the control information symbol are output.

The radio units 310A and 310B of FIG. 51 select a desired baseband signal from the plurality of baseband signals based on the frame configuration signal 313 among the plurality of input baseband signals. Then, the OFDM-related signal processing is performed, and the modulated signals 311A and 311B according to the frame configuration are output, respectively.

FIG. 52 shows an example of the configuration of the transmission device that generates and transmits the modulated signal having the frame configuration of FIGS. 48 and 50, and the same reference numerals are given to those that operate in the same manner as those of FIGS. 4 and 51. is doing. The phase change unit 317A added to FIG. 51 operates only when the frame configuration signal 313 indicates the timing of the data symbol. Others are the same as in FIG. 51.

FIG. 53 shows a transmission device configuration method different from that of FIG. 51. The differences will be described below. As shown in FIG. 53, the phase changing unit 317B inputs a plurality of baseband signals. When the frame configuration signal 313 indicates that it is a data symbol, the phase changing unit 317B performs a phase change on the precoded baseband signal 316B. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase change unit 317B stops the phase change operation and the baseband signal of each symbol. Is output as it is. (Interpretation is "e^j0It can be considered that the phase rotation corresponding to "" is forcibly performed. ) The selection unit 5301 takes a plurality of baseband signals as inputs, selects and outputs the baseband signal of the symbol indicated by the frame configuration signal 313.

FIG. 54 is a method of configuring a transmitter different from that of FIG. 52. The differences will be described below. As shown in FIG. 54, the phase changing unit 317B inputs a plurality of baseband signals. When the frame configuration signal 313 indicates that it is a data symbol, the phase changing unit 317B performs a phase change on the precoded baseband signal 316B. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase change unit 317B stops the phase change operation and the baseband signal of each symbol. Is output as it is. (Interpretation is "e^j0It can be considered that the phase rotation corresponding to "" is forcibly performed. ) Similarly, the phase changing unit 5201 inputs a plurality of baseband signals as shown in FIG. 54. When the frame configuration signal 313 indicates that it is a data symbol, the phase changing unit 5201 performs a phase change on the precoded baseband signal 309A. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase change unit 5201 stops the phase change operation and the baseband signal of each symbol. Is output as it is. (Interpretation is "e^j0It can be considered that the phase rotation corresponding to "" is forcibly performed. ) In the above explanation, the pilot symbol, the control symbol, and the data symbol have been described as an example, but the present invention is not limited to this, and a transmission method different from the precoding, for example, one antenna transmission and a spatiotemporal block code is used. Similarly, if the symbol is transmitted using a transmission method, etc., it is important not to change the phase. On the contrary, the precoded symbol is changed in phase. That is important in the present invention.

Therefore, it is a feature of the present invention that the phase change is not performed on all the symbols in the frame configuration on the time-frequency axis, and the phase change is given only to the precoded signal.

(Embodiment 4) In the first and second embodiments described above, it is disclosed that the phase is changed regularly, and in the third embodiment, the degree of the phase change of adjacent symbols is changed.

In the fourth embodiment, it is shown that the phase changing method may be different depending on the modulation method used by the transmission device and the coding rate of the error correction code.

Table 1 below shows an example of the phase change method set according to various setting parameters set by the transmitter.

<tables><img file="JP2022017567A_D0049.tif" /></tables>

In Table 1, # 1 is the modulation signal s1 of the above embodiment 1 (baseband signal s1 of the modulation method set by the transmitter), and # 2 is the modulation signal s2 (baseband signal s2 of the modulation method set by the transmitter). Means. The code rate column in Table 1 shows the code rate set by the error correction code for the modulation methods of # 1 and # 2. The columns of the phase change patterns in Table 1 are the phase change methods applied to the precoded baseband signals z1 (z1') and z2 (z2') as described in the first to third embodiments. The phase change pattern is defined as A, B, C, D, E, ..., but this is actually information indicating the degree of change in the degree of phase change. For example, it is assumed that a change pattern as shown in the above equations (46) and (47) is shown. In the example of the phase change pattern in Table 1, "-" is described, which means that the phase change is not performed.

The combinations of modulation methods and coding rates shown in Table 1 are examples, and modulation methods other than the modulation methods shown in Table 1 (for example, 128QAM, 256QAM, etc.) and coding rates (for example, 7/8) are examples. Etc.) may be included. Further, as shown in the first embodiment, the error correction code may be set separately for s1 and s2 (in the case of Table 1, as shown in FIG. 4, one error correction code is coded. It is assumed that the above is applied.). Further, a plurality of different phase change patterns may be associated with the same modulation method and coding rate. The transmitting device transmits information indicating each phase change pattern to the receiving device, and the receiving device identifies the phase change pattern by referring to the information and Table 1, and performs demodulation and decoding. Become. When the phase change pattern is uniquely determined for the modulation method and the error correction method, the transmitting device transmits the information of the modulation method and the error correction method to the receiving device, and the receiving device receives the information. In this case, the information on the phase change pattern is not always necessary because the phase change pattern can be known by obtaining the information.

In the first to third embodiments, the case where the phase is changed for the baseband signal after precoding has been described, but not only the phase but also the amplitude is regularly changed with a period like the phase change. It is also possible. Therefore, Table 1 may also correspond to an amplitude change pattern that regularly changes the amplitude of the modulated signal. In this case, the transmitting device may be provided with an amplitude changing unit for changing the amplitude after the weighted combining unit 308A in FIGS. 3 and 4, and an amplitude changing unit for changing the amplitude after the weighted combining unit 308B. It should be noted that the amplitude of one of the precoded baseband signals z1 (t) and z2 (t) may be changed (in this case, the amplitude changing part is added after either the weighting synthesis part 308A or 308B. It may be provided.) However, the amplitude may be changed for both.

Further, although not shown in Table 1 above, the mapping method may be changed regularly by the mapping unit instead of changing the phase regularly.

That is, the mapping method of the modulated signal s1 (t) is 16QAM, the mapping method of the modulated signal s2 (t) is 16QAM, for example, the mapping method to apply to the modulated signal s2 (t) is regularly 16QAM. 16APSK (16 Amplitude Phase Shift Keying) 1st mapping method with different signal point arrangement from 16QAM and 16APSK on IQ plane 2nd mapping method with different signal point arrangement from 16QAM and 16APSK on IQ plane By making such a change, it is possible to obtain the effect of improving the data reception quality in the receiving device, as in the case of regularly changing the phase as described above.

Further, the present invention may be a combination of any of a method of regularly changing the phase, a method of regularly changing the mapping method, and a method of changing the amplitude, and all of them are taken into consideration. It may be configured to transmit a transmission signal.

In this embodiment, it can be carried out in either case of the single carrier method or the multi-carrier transmission. Therefore, for example, spectrum diffusion communication method, OFDM (Orthogonal Frequency-Division Multiplexing) method, SC-FDMA (Single Carrier Frequency Division Multiple Access), SC-OFDM (Single Carrier Orthogonal Frequency-Division) It can also be carried out when the Multiplexing) method, the wavelet OFDM method shown in Non-Patent Document 7 and the like are used. As described above, in the present embodiment, as the explanation for performing the phase change, the amplitude change, and the mapping change, the case where the phase change, the amplitude change, and the mapping change are performed in the time t-axis direction has been described. Similarly, as in the case of performing the phase change in the frequency axis direction, that is, in the present embodiment, in the description of the phase change, the amplitude change, and the mapping change in the t direction, t is f (f: frequency ((sub). By substituting () carrier)), the phase change, amplitude change, and mapping change described in the present embodiment can be applied to the phase change, amplitude change, and mapping change in the frequency direction. Further, the phase change, amplitude change, and mapping change method of the present embodiment can be applied to the phase change, amplitude change, and mapping change in the time-frequency direction as in the description of the first embodiment. Is.

Then, in the present embodiment, symbols other than the data symbols, for example, pilot symbols (preambles, unique words, etc.), symbols for transmitting control information, and the like may be arranged in the frame.

(Embodiment A1) In the present embodiment, as shown in Non-Patent Documents 12 to 15, QC (Quasi Cyclic) LDPC (Low-Density Parity-Check) code (not QC-LDPC code). , LDPC code), LDPC code and BCH code (Bose-Chaudhuri-Hocquenghem code) concatenation code, turbo code using tail biting, or block code such as Duo-Binary Turbo Code. The method of changing the phase regularly will be described in detail. Here, as an example, a case where two streams of s1 and s2 are transmitted will be described as an example. However, when coding is performed using the block code, when control information or the like is not required, the number of bits constituting the coded block is the number of bits constituting the block code (however, among these, the following It may contain control information and the like as described.) When encoding is performed using a block code, control information, etc. (for example, CRC (cyclic redundancy)) When check), transmission parameters, etc.) are required, the number of bits constituting the coded block may be the sum of the number of bits constituting the block code and the number of bits such as control information.

FIG. 34 is a diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used. FIG. 34 shows, for example, a "block code" in the case where two streams s1 and s2 are transmitted and the transmitter has one encoder, as shown in the transmitter of FIG. It is a figure showing the change in the number of symbols and the number of slots required for one coded block when used. " (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 34, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Since the transmitter in FIG. 4 transmits two streams at the same time, when the modulation method is QPSK, the above 3000 symbols are assigned 1500 symbols to s1 and 1500 symbols to s2. 1500 slots (named "slots" here) are required to transmit 1500 symbols to be transmitted in s1 and 1500 symbols to be transmitted in s2.

Similarly, when the modulation scheme is 16QAM, 750 slots are required to transmit all the bits that make up one coded block, and when the modulation scheme is 64QAM, all that make up one block. 500 slots are required to send the bits.

Next, in the method of changing the phase regularly, the relationship between the slot defined above and the phase to be multiplied will be described.

Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase is set to 5. That is, it is assumed that five phase change values (or phase change sets) are prepared for the phase change unit of the transmitter of FIG. 4 (which is the "period" in the first to fourth embodiments). (As shown in FIG. 6, when the phase change is performed only on the baseband signal z2'after precoding, five phase change values may be prepared in order to perform the phase change in the period 5. Also, FIG. 26. When performing phase change for both the precoded baseband signals z1'and z2', two phase change values are required for one slot. These two phase change values are phased. It is called a change set. Therefore, in this case, in order to perform a phase change with a period of 5, it is sufficient to prepare five phase change sets). These five phase change values (or phase change sets) are represented as PHASE [0], PHASE [1], PHASE [2], PHASE [3], PHASE [4].

When the modulation method is QPSK, in the 1500 slots described above for transmitting 6000 bits that make up one coded block, there are 300 slots that use phase PHASE [0], and phase PHASE [ There are 300 slots that use 1], 300 slots that use phase PHASE [2], 300 slots that use phase PHASE [3], and 300 slots that use phase PHASE [4]. There is a need. This is because if there is a deviation in the phase used, the influence of the phase using a large number is large, and the receiving quality of the data depends on this influence in the receiving device.

Similarly, when the modulation scheme is 16QAM, among the 750 slots mentioned above for transmitting the 6000 bits that make up one coded block, there are 150 slots that use phase PHASE [0]. There are 150 slots that use phase PHASE [1], 150 slots that use phase PHASE [2], 150 slots that use phase PHASE [3], and 150 slots that use phase PHASE [4]. Must be a slot.

Similarly, when the modulation scheme is 64QAM, 100 slots use phase PHASE [0] in the 500 slots mentioned above for transmitting 6000 bits that make up one coded block. 100 slots using phase PHASE [1], 100 slots using phase PHASE [2], 100 slots using phase PHASE [3], 100 slots using phase PHASE [4] Must be a slot.

As described above, in the method of regularly changing the phase, N pieces of phase change values (or phase change sets) are prepared (N different phases are PHASE [0], PHASE [1], PHASE [2]. ], ..., PHASE [N-2], PHASE [N-1]), when transmitting all the bits that make up one coded block, the phase PHASE [ Set the number of slots that use 0] to K₀, K the number of slots that use phase PHASE [1]_1、K the number of slots that use phase PHASE [i]_i(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), K the number of slots using phase PHASE [N-1]_N-1When &lt;Condition # A01&gt; K₀= K₁= . . . = K_i= . . . = K_N-1, That is, K_a= K_{b b}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b).

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, it is preferable that &lt;condition # A01&gt; is satisfied in the supported modulation methods. ..

However, when multiple modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy &lt;Condition # A01&gt;. In this case, the following conditions should be satisfied instead of &lt;Condition # A01&gt;.

&lt;Condition # A02&gt; K_aAnd K_{b b}The difference between is 0 or 1, that is, | K_aK_{b b}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ···, N-1 (a is an integer greater than or equal to 0 and less than or equal to N-1, b is greater than or equal to 0 and N- Integers of 1 or less), a b) Fig. 35 is a diagram showing changes in the number of symbols and the number of slots required for two coded blocks when a block code is used. FIG. 35 shows the case where two streams of s1 and s2 are transmitted and the transmitter has two encoders as shown in the transmitter of FIG. 3 and the transmitter of FIG. "A diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used". (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 35, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Then, in the transmitter of FIG. 3 and the transmitter of FIG. 12, two streams are transmitted at the same time, and since there are two encoders, the two streams transmit different code blocks. become. Therefore, when the modulation method is QPSK, s1 and s2 transmit two coded blocks within the same interval. Therefore, for example, s1 transmits the first coded block, and s2 transmits the first coded block. Since 2 coded blocks will be transmitted, 3000 slots will be required to transmit the 1st and 2nd coded blocks.

Similarly, when the modulation scheme is 16QAM, 1500 slots are required to transmit all the bits that make up the two encoded blocks, and when the modulation scheme is 64QAM, the two encoded blocks are required. 1000 slots are required to transmit all the bits that make up the.

Next, in the method of changing the phase regularly, the relationship between the slot defined above and the phase to be multiplied will be described.

Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase is set to 5. That is, it is assumed that five phase change values (or phase change sets) are prepared for the phase change part of the transmitter of FIGS. 3 and 12 (the "period" in the first to fourth embodiments. (As shown in FIG. 6, when the phase change is performed only on the baseband signal z2'after precoding, five phase change values may be prepared in order to perform the phase change in the period 5. , As shown in FIG. 26, when performing a phase change for both the precoded baseband signals z1'and z2', two phase change values are required for one slot. These two phase changes. The value is called a phase change set. Therefore, in this case, in order to perform a phase change with a period of 5, it is sufficient to prepare five phase change sets). These five phase change values (or phase change sets) are represented as PHASE [0], PHASE [1], PHASE [2], PHASE [3], PHASE [4].

When the modulation method is QPSK, in the 3000 slots described above for transmitting the number of bits 6000 × 2 bits that make up the two coded blocks, the slots that use phase PHASE [0] are 600 slots and the phase. 600 slots using PHASE [1], 600 slots using phase PHASE [2], 600 slots using phase PHASE [3], 600 slots using phase PHASE [4] Must be. This is because if there is a deviation in the phase used, the influence of the phase using a large number is large, and the receiving quality of the data depends on this influence in the receiving device.

Also, in order to transmit the first coded block, there are 600 slots that use phase PHASE [0], 600 slots that use phase PHASE [1], and slots that use phase PHASE [2]. There must be 600 slots using phase PHASE [3] 600 times, 600 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 600 slots using [0], 600 slots using phase PHASE [1], 600 slots using phase PHASE [2], 600 slots using phase PHASE [3], It is recommended that the number of slots using the phase PHASE [4] is 600.

Similarly, when the modulation scheme is 16QAM, in the 1500 slots mentioned above for transmitting the number of bits 6000 × 2 bits that make up the two coded blocks, there are 300 slots that use phase PHASE [0]. Slots, 300 slots using phase PHASE [1], 300 slots using phase PHASE [2], 300 slots using phase PHASE [3], slots using phase PHASE [4] Must be 300 slots.

Also, in order to transmit the first coded block, the slot using phase PHASE [0] is 300 times, the slot using phase PHASE [1] is 300 times, and the slot using phase PHASE [2] is 300 times. There must be 300 slots using phase PHASE [3] 300 times, 300 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 300 slots using [0], 300 slots using phase PHASE [1], 300 slots using phase PHASE [2], 300 slots using phase PHASE [3], It is recommended that the number of slots using the phase PHASE [4] is 300.

Similarly, when the modulation scheme is 64QAM, in the 1000 slots mentioned above for transmitting the number of bits 6000 × 2 bits that make up the two coded blocks, there are 200 slots that use the phase PHASE [0]. Slots, 200 slots using phase PHASE [1], 200 slots using phase PHASE [2], 200 slots using phase PHASE [3], slots using phase PHASE [4] Must be 200 slots.

Also, in order to transmit the first coded block, there are 200 slots that use phase PHASE [0], 200 slots that use phase PHASE [1], and slots that use phase PHASE [2]. There must be 200 slots using phase PHASE [3] 200 times, 200 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 200 slots using [0], 200 slots using phase PHASE [1], 200 slots using phase PHASE [2], 200 slots using phase PHASE [3], It is recommended that the number of slots using the phase PHASE [4] is 200.

As described above, in the method of regularly changing the phase, the phase change value (or phase change set) to be prepared is PHASE [0], PHASE [1], PHASE [2], ..., PHASE [N. -2], PHASE [N-1]), the number of slots that use the phase PHASE [0] when transmitting all the bits that make up the two encoded blocks is K.₀, K the number of slots that use phase PHASE [1]_1、K the number of slots that use phase PHASE [i]_i(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), K the number of slots using phase PHASE [N-1]_N-1When &lt;Condition # A03&gt; K₀= K₁= . . . = K_i= . . . = K_N-1, That is, K_a= K_{b b}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b), and the number of times the phase PHASE [0] is used when transmitting all the bits that make up the first encoded block is K._0,1, K how many times to use phase PHASE [1]_1,1、K the number of times to use phase PHASE [i]_{i, 1}(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), the number of times to use phase PHASE [N-1] is K_N-1,1When &lt;Condition # A04&gt; K_0,1= K_1,1= . . . = K_{i, 1}= . . . = K_N-1,1, That is, K_{a, 1}= K_{b, 1}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b), and the number of times the phase PHASE [0] is used when transmitting all the bits that make up the second coded block is K._0,2, K how many times to use phase PHASE [1]_1,2、K the number of times to use phase PHASE [i]_{i, 2}(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), the number of times to use phase PHASE [N-1] is K_N-1,2When &lt;Condition # A05&gt; K_0,2= K_1,2= . . . = K_{i, 2}= . . . = K_N-1,2, That is, K_{a, 2}= K_{b, 2}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b).

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, &lt;condition # A03&gt; &lt;condition # A04&gt; &lt;conditions are used in the supported modulation methods. It would be good if # A05&gt; was established.

However, when multiple modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy &lt;Condition # A03&gt; &lt;Condition # A04&gt; &lt;Condition # A05&gt;. In this case, the following conditions should be satisfied instead of &lt;Condition # A03&gt; &lt;Condition # A04&gt; &lt;Condition # A05&gt;.

&lt;Condition # A06&gt; K_aAnd K_{b b}The difference between is 0 or 1, that is, | K_aK_{b b}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ···, N-1 (a is an integer greater than or equal to 0 and less than or equal to N-1, b is greater than or equal to 0 and N- Integer less than or equal to 1), a b) &lt;condition # A07&gt; K_{a, 1}And K_{b, 1}The difference between is 0 or 1, that is, | K_{a, 1}K_{b, 1}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ···, N-1 (a is an integer greater than or equal to 0 and less than or equal to N-1, b is greater than or equal to 0 and N- Integer less than or equal to 1), a b) &lt;condition # A08&gt; K_{a, 2}And K_{b, 2}The difference between is 0 or 1, that is, | K_{a, 2}K_{b, 2}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is between 0 and N-) Integers of 1 or less), a b) As described above, by associating the coded block with the multiplication phase, the phase used to transmit the coded block is not biased, so reception is performed. In the device, the effect of improving the reception quality of data can be obtained.

In the present embodiment, in the method of regularly changing the phase, N phase change values (or phase change sets) are required for the phase change method having a period N. At this time, PHASE [0], PHASE [1], PHASE [2], ..., PHASE [N-2], PHASE [N-1] are used as N phase change values (or phase change sets). However, there is also a method of arranging PHASE [0], PHASE [1], PHASE [2], ..., PHASE [N-2], PHASE [N-1] in this order in the frequency axis direction. However, it is not always limited to this, and N phase change values (or phase change sets) PHASE [0], PHASE [1]

, PHASE [2], ..., PHASE [N-2], PHASE [N-1] by arranging symbols for blocks on the time axis and frequency-time axis as in the first embodiment. , The phase can also be changed. Although the method of changing the phase of the period N is described, the same effect can be obtained by randomly using N phase change values (or phase change sets), that is, it is not always a rule. It is not necessary to use N phase change values (or phase change sets) so as to have a certain period, but the condition described above is satisfied in order to obtain high data reception quality in the receiving device. , Will be important.

Further, a spatial multiplex MIMO transmission method, a MIMO transmission method with a fixed precoding matrix, a spatiotemporal block coding method, a method of transmitting only one stream, and a method of regularly changing the phase (described in the first to fourth embodiments). The mode of the transmission method) exists, and the transmission device (broadcasting station, base station) may be able to select one of the transmission methods from these modes.

As shown in Non-Patent Document 3, the spatial multiplex MIMO transmission method is a method of transmitting signals s1 and s2 mapped by the selected modulation method from different antennas, and the precoding matrix is fixed. The MIMO transmission method is a method in which only precoding is performed (phase change is not performed) in the first to fourth embodiments. The space-time block coding method is a transmission method shown in Non-Patent Documents 9, 16 and 17. Transmission of only one stream is a method of transmitting the signal of the signal s1 mapped by the selected modulation method from the antenna after performing predetermined processing.

In addition, a multi-carrier transmission method such as OFDM is used, and a first carrier group composed of a plurality of carriers, a second carrier group different from the first carrier group composed of a plurality of carriers, ... Multi-carrier transmission is realized by multiple carrier groups, such as spatial multiplex MIMO transmission method, MIMO transmission method with fixed precoding matrix, spatiotemporal block coding method, transmission of only one stream, for each carrier group. It may be set to any one of the methods of regularly changing the phase, and in particular, in the (sub) carrier group in which the method of regularly changing the phase is selected, the present embodiment may be carried out.

When the phase change is performed on one of the precoded baseband signals, for example, when the phase change value of PHASE [i] is "X radian", FIGS. 3, 4, 6, and 12 , In the phase change section in FIGS. 25, 29, 51, 53, e^jXWill be multiplied by the precoded baseband signal z2'. Then, when the phase change is performed on the baseband signals after both precoding, for example, when the phase change set of PHASE [i] is "X radian" and "Y radian", FIGS. 26 and 27, In the phase change section in FIGS. 28, 52, and 54, e^jXWill be multiplied by the precoded baseband signal z2', e^jYWill be multiplied by the precoded baseband signal z1'.

(Embodiment B1) Hereinafter, application examples of the transmission method and the reception method shown in each of the above embodiments and a system configuration example using the same will be described.

FIG. 36 is a diagram showing a configuration example of a system including a device for executing the transmission method and the reception method shown in the above embodiment. The transmission method and the reception method shown in each of the above embodiments include a broadcasting station as shown in FIG. 36, a television (television) 3611, a DVD recorder 3612, an STB (Set Top Box) 3613, a computer 3620, and an in-vehicle television. It is implemented in the digital broadcasting system 3600 including various types of receivers such as 3641 and mobile phone 3630. Specifically, the broadcasting station 3601 transmits the multiplexed data in which video data, audio data, and the like are multiplexed to a predetermined transmission band by using the transmission method shown in each of the above embodiments.

The signal transmitted from the broadcasting station 3601 is received by an antenna (for example, antennas 3660 and 3640) built in or externally installed in each receiver and connected to the receiver. Each receiver demodulates the signal received at the antenna by using the receiving method shown in each of the above embodiments, and acquires the multiplexed data. Thereby, the digital broadcasting system 3600 can obtain the effect of the present invention described in each of the above embodiments.

Here, the video data included in the multiplexed data is encoded by using a video coding method compliant with standards such as MPEG (Moving Picture Experts Group) 2, MPEG4-AVC (Advanced Video Coding), and VC-1. ing. The audio data included in the multiplexed data is, for example, Dolby AC (Audio Coding) -3, Dolby Digital Plus, MLP (Meridian Lossless Packing), DTS (Digital Theater Systems), DTS-HD, linear PCM (Pulse Coding Modulation), etc. It is encoded by the voice coding method of.

FIG. 37 is a diagram showing an example of the configuration of the receiver 7900 that implements the receiving method described in each of the above embodiments. The receiver 3700 shown in FIG. 37 corresponds to the configuration provided in the television (television) 3611 shown in FIG. 36, the DVD recorder 3612, the STB (Set Top Box) 3613, the computer 3620, the in-vehicle television 3641, the mobile phone 3630, and the like. do. The receiver 3700 includes a tuner 3701 that converts a high-frequency signal received by the antenna 3760 into a baseband signal, and a demodulation unit 3702 that demodulates the frequency-converted baseband signal and acquires multiplexed data. The receiving method shown in each of the above embodiments is carried out by the demodulation unit 3702, whereby the effect of the present invention described in each of the above embodiments can be obtained.

Further, the receiver 3700 uses a stream input / output unit 3720 that separates video data and audio data from the multiplexed data obtained by the demodulation unit 3702, and a video decoding method corresponding to the separated video data. A signal processing unit 3704 that decodes data into a video signal and decodes the audio data into an audio signal using an audio decoding method corresponding to the separated audio data, and an audio output unit such as a speaker that outputs the decoded audio signal. It has a 3706 and a video display unit 3707 such as a display that displays the decoded video signal.

For example, the user uses the remote controller (remote controller) 3750 to transmit information on the selected channel (selected (television) program, selected audio broadcast) to the operation input unit 3710. Then, the receiver 3700 demodulates the signal corresponding to the selected channel in the received signal received by the antenna 3760, performs processing such as error correction and decoding, and obtains the received data. At this time, the receiver 3700 is a transmission method (transmission method, modulation method, error correction method, etc. described in the above embodiment) included in the signal corresponding to the selected channel (for this, FIGS. 5, FIG. It was transmitted by the broadcasting station (base station) by correctly setting the reception operation, demodulation method, error correction / decoding, etc. by obtaining the information of the control symbol including the information of (41). It is possible to obtain the data contained in the data symbol. In the above, the user has described an example of selecting a channel by using the remote controller 3750. However, even if the channel is selected by using the channel selection key mounted on the receiver 3700, the operation is the same as above. Become.

With the above configuration, the user can watch the program received by the receiver 3700 by the receiving method shown in each of the above embodiments.

Further, in the receiver 3700 of the present embodiment, the multiplexed data obtained by demodulating with the demodulation unit 3702 and performing error correction decoding (in some cases, with respect to the signal obtained by demodulation by the demodulation unit 3702). In addition, the receiver 3700 may be subjected to other signal processing after error correction and decoding. In the following, the same expression may be applied to this point. Is the same.), Or data equivalent to that data (for example, data obtained by compressing the data), video, and data obtained by processing audio to a magnetic disk. , A recording unit (drive) 3708 for recording on a recording medium such as an optical disk or a non-volatile semiconductor memory. Here, the optical disk is a recording medium such as a DVD (Digital Versatile Disc) or a BD (Blu-ray Disc) in which information is stored and read out using a laser beam. Magnetic disks are, for example, FD (Floppy Disk) (registered trademark) and hard disk (Hard). A recording medium such as Disk) that stores information by magnetizing a magnetic material using magnetic flux. A non-volatile semiconductor memory is a recording medium composed of semiconductor elements such as a flash memory and a ferroelectric memory (Ferroelectric Random Access Memory), and is an SD card or a Flash SSD (Solid State Drive) using the flash memory. ) And so on. It should be noted that the types of recording media listed here are just examples, and it goes without saying that recording may be performed using recording media other than the above-mentioned recording media.

With the above configuration, the user records and saves the program received by the receiver 3700 by the receiving method shown in each of the above embodiments, and the data recorded at any time after the broadcast time of the program. Can be read and viewed.

In the above description, the receiver 3700 demodulates with the demodulation unit 3702 and records the multiplexed data obtained by decoding the error correction with the recording unit 3708, but the data included in the multiplexed data. Some of the data may be extracted and recorded. For example, when the multiplexed data obtained by demodulating with the demodulating unit 3702 and decoding the error correction includes the contents of the data broadcasting service other than the video data and the audio data, the recording unit 3708 may use the demodulating unit 3702. Video data and audio data may be extracted from the multiplexed data demolished in step 1 and new multiplexed data may be recorded. Further, the recording unit 3708 demodulates with the demodulation unit 3702, and the new multiplexed data in which only one of the video data and the audio data included in the multiplexed data obtained by decoding the error correction is multiplexed. May be recorded. Then, the recording unit 3708 may record the content of the data broadcasting service included in the multiplexed data described above.

Furthermore, if the receiver 3700 described in the present invention is mounted on a television, a recording device (for example, a DVD recorder, a Blu-ray recorder, an HDD recorder, an SD card, etc.), or a mobile phone, the demodulator 3702 demodulates the data. However, the data, personal information, and recorded data leaked to the multiplexed data obtained by decrypting the error correction to correct defects (bugs) in the software used to operate the TV and recording device. If data for fixing a software defect (bug) to prevent the problem is included, the software defect of the television or recording device may be corrected by installing these data. Then, if the data includes data for correcting a software defect (bug) of the receiver 3700, this data can also be used to correct a defect of the receiver 3700. As a result, the television, recording device, and mobile phone equipped with the receiver 3700 can be operated more stably.

Here, the process of extracting a part of the data from the plurality of data included in the multiplexed data obtained by demodulating with the demodulation unit 3702 and performing error correction decoding and multiplexing is, for example, the stream input / output unit 3703. It is done in. Specifically, the stream input / output unit 3703 converts the multiplexed data demoded by the demodulation unit 3702 into video data, audio data, data broadcasting service content, etc. according to an instruction from a control unit such as a CPU (not shown). It separates into multiple data, extracts only the specified data from the separated data and multiplexes it, and generates new multiplexed data. The user may decide, for example, which data should be extracted from the separated data, or may be predetermined for each type of recording medium.

With the above configuration, the receiver 3700 can extract and record only the data necessary for viewing the recorded program, so that the data size of the recorded data can be reduced.

Further, in the above description, the recording unit 3708 is supposed to record the multiplexed data obtained by demodulating the data in the demodulatoring unit 3702 and decoding the error correction. The video data included in the multiplexed data obtained by performing the above is different from the video coding method applied to the video data so that the data size or bit rate is lower than that of the video data. It may be converted into video data encoded by the conversion method, and new multiplexed data in which the converted video data is multiplexed may be recorded. At this time, the moving image coding method applied to the original video data and the moving image coding method applied to the converted video data may comply with different standards or conform to the same standard. And only the parameters used at the time of encoding may be different. Similarly, the recording unit 3708 demodulates the audio data contained in the multiplexed data obtained by demodulating with the demodulating unit 3702 and decoding the error correction so that the data size or bit rate of the audio data is lower than that of the audio data. , The voice data may be converted into voice data encoded by a voice coding method different from the voice coding method applied to the voice data, and new multiplexed data in which the converted voice data is multiplexed may be recorded.

Here, the process of converting the video data and audio data contained in the multiplexed data obtained by demodulating with the demodulator 3702 and decoding the error correction into video data and audio data having different data sizes or bit rates is performed. For example, it is performed by the stream input / output unit 3703 and the signal processing unit 3704. Specifically, the stream input / output unit 3703 demodulates with the demodulation unit 3702 according to an instruction from a control unit such as a CPU, and the multiplexed data obtained by decoding the error correction is used as video data, audio data, and the like. Separate into multiple data such as data broadcasting service contents. The signal processing unit 3704 converts the separated video data into video data encoded by a video coding method different from the video coding method applied to the video data according to an instruction from the control unit. , And the process of converting the separated voice data into voice data encoded by a voice coding method different from the voice coding method applied to the voice data. The stream input / output unit 3703 multiplexes the converted video data and the converted audio data according to an instruction from the control unit, and generates new multiplexed data. Note that the signal processing unit 3704 may perform conversion processing on only one of the video data and the audio data, or perform conversion processing on both, in response to an instruction from the control unit. Is also good. Further, the data size or bit rate of the converted video data and audio data may be determined by the user or may be predetermined for each type of recording medium.

With the above configuration, the receiver 3700 changes the data size or bit rate of video data and audio data according to the data size that can be recorded on the recording medium and the speed at which the recording unit 3708 records or reads the data. can do. As a result, when the data size that can be recorded on the recording medium is smaller than the data size of the multiplexed data obtained by demodulating the data in the demodulator 3702 and performing error correction decoding, or when the recording unit records or reads the data. Even if the speed at which the data is performed is lower than the bit rate of the multiplexed data demolished by the demodulator 3702, the recording unit can record the program, so that the user can record the program at any time after the broadcast time of the program. It becomes possible to read out and view the data recorded in.

In addition, the receiver 3700 includes a stream output IF (Interface) 3709 that transmits the multiplexed data demodulated by the demodulation unit 3702 to an external device via the communication medium 3730. As an example of stream output IF3709, Wi-Fi (registered trademark) (IEEE802.11a, IEEE802.11b, IEEE802.11g, IEEE802.11n, etc.), WiGiG, WirelessHD, Bluetooth (registered trademark), Zigbee (registered trademark), etc. A wireless communication device that transmits multiplexed data modulated using a wireless communication method compliant with the wireless communication standard of the above to an external device via a wireless medium (corresponding to the communication medium 3730). In addition, the stream output IF3709 is Ethernet (registered trademark), USB (Universal Serial Bus), PLC (Power Line Communication), HDMI (High-Definition Multimedia). Wired communication that transmits multiplexed data modulated using a communication method compliant with a wired communication standard such as Interface) to an external device via a wired transmission line (corresponding to communication medium 3730) connected to the stream output IF3709. It may be a device.

With the above configuration, the user can use the multiplexed data received by the receiver 3700 by the receiving method shown in each of the above embodiments in the external device. The use of multiplexed data here means that the user can view the multiplexed data in real time using an external device, record the multiplexed data in the recording unit provided in the external device, and further from the external device. Includes sending multiplexed data to another external device, etc.

In the above explanation, the receiver 3700 demodulates with the demodulation unit 3702, and the stream output IF3709 outputs the multiplexed data obtained by decoding the error correction. However, the data included in the multiplexed data. Some of the data may be extracted and output. For example, when the multiplexed data obtained by demodulating with the demodulator 3702 and decoding the error correction includes the contents of the data broadcasting service other than the video data and the audio data, the stream output IF3709 uses the demodulator 3702. You may output the new multiplexed data by extracting the video data and the audio data from the multiplexed data obtained by demodulating with and decoding the error correction. Further, the stream output IF3709 may output new multiplexed data in which only one of the video data and the audio data included in the multiplexed data demodulated by the demodulation unit 3702 is multiplexed.

Here, the process of extracting a part of the data from the plurality of data included in the multiplexed data obtained by demodulating with the demodulation unit 3702 and performing error correction decoding and multiplexing is, for example, the stream input / output unit 3703. It is done in. Specifically, the stream input / output unit 3703 outputs the multiplexed data demoded by the demodulation unit 3702 to video data, audio data, and data broadcasting according to an instruction from a control unit such as a CPU (Central Processing Unit) (not shown). It separates into multiple data such as service contents, extracts only the specified data from the separated data and multiplexes it, and generates new multiplexed data. The user may decide, for example, which data should be extracted from the separated data, or may be predetermined for each type of stream output IF3709.

With the above configuration, the receiver 3700 can extract and output only the data required by the external device, so that the communication band consumed by the output of the multiplexed data can be reduced.

Further, in the above description, it is assumed that the stream output IF3709 outputs the multiplexed data obtained by demodulating the data in the demodulatoring unit 3702 and decoding the error correction. The video data included in the multiplexed data obtained by performing the above is different from the video coding method applied to the video data so that the data size or bit rate is lower than that of the video data. It may be converted into video data encoded by the conversion method, and new multiplexed data in which the converted video data is multiplexed may be output. At this time, the moving image coding method applied to the original video data and the moving image coding method applied to the converted video data may comply with different standards or conform to the same standard. And only the parameters used at the time of encoding may be different. Similarly, the stream output IF3709 demodulates the audio data contained in the multiplexed data obtained by demodulating with the demodulator 3702 and decoding the error correction so that the data size or bit rate is lower than that of the audio data. , The voice data may be converted into voice data encoded by a voice coding method different from the voice coding method applied to the voice data, and new multiplexed data in which the converted voice data is multiplexed may be output.

Here, the process of converting the video data and audio data contained in the multiplexed data obtained by demodulating with the demodulator 3702 and decoding the error correction into video data and audio data having different data sizes or bit rates is performed. For example, it is performed by the stream input / output unit 3703 and the signal processing unit 3704. Specifically, the stream input / output unit 3703 demodulates with the demodulation unit 3702 according to the instruction from the control unit, and the multiplexed data obtained by decoding the error correction is used as video data, audio data, and data broadcasting service. Separate into multiple data such as the contents of. The signal processing unit 3704 converts the separated video data into video data encoded by a video coding method different from the video coding method applied to the video data according to an instruction from the control unit. , And the process of converting the separated voice data into voice data encoded by a voice coding method different from the voice coding method applied to the voice data. The stream input / output unit 3703 multiplexes the converted video data and the converted audio data according to an instruction from the control unit, and generates new multiplexed data. Note that the signal processing unit 3704 may perform conversion processing on only one of the video data and the audio data, or perform conversion processing on both, in response to an instruction from the control unit. Is also good. Further, the data size or bit rate of the converted video data and audio data may be determined by the user or may be predetermined for each type of stream output IF3709.

With the above configuration, the receiver 3700 can output the video data and the audio data by changing the bit rate according to the communication speed with the external device. As a result, even if the communication speed with the external device is lower than the bit rate of the multiplexed data obtained by demodulating with the demodulation unit 3702 and performing error correction decoding, the stream output IF is used for new multiplexing of the external device. Since the demodulated data can be output, the user can use the new multiplexed data in other communication devices.

Further, the receiver 3700 includes an AV (Audio and Visual) output IF (Interface) 3711 that outputs a video signal and an audio signal decoded by the signal processing unit 3704 to an external device to an external communication medium. As an example of AV output IF3711, Wi-Fi (registered trademark) (IEEE802.11a, IEEE802.11b, IEEE802.11g, IEEE802.11n, etc.), WiGiG, WirelessHD, Bluetooth (registered trademark), Zigbee (registered trademark), etc. Examples thereof include a wireless communication device that transmits a video signal and an audio signal modulated by using a wireless communication method compliant with the wireless communication standard of the above to an external device via a wireless medium. In addition, the stream output IF3709 is a wired transmission in which video signals and audio signals modulated using a communication method compliant with wired communication standards such as Ethernet (registered trademark), USB, PLC, and HDMI are connected to the stream output IF3709. It may be a wired communication device that transmits to an external device via a road. Further, the stream output IF3709 may be a terminal for connecting a cable that outputs a video signal and an audio signal as analog signals.

With the above configuration, the user can use the video signal and the audio signal decoded by the signal processing unit 3704 in an external device.

Further, the receiver 3700 includes an operation input unit 3710 that receives an input of a user operation. The receiver 3700 switches the power ON / OFF, the receiving channel, the presence / absence of subtitle display, and the language to be displayed based on the control signal input to the operation input unit 3710 according to the user's operation. , Switching various operations such as changing the volume output from the audio output unit 3706, and changing the settings such as the setting of the receivable channel.

Further, the receiver 3700 may have a function of displaying an antenna level indicating the reception quality of the signal being received by the receiver 3700. Here, the antenna level is, for example, RSSI (Received Signal Strength Indication, Received Signal Strength Indicator, received signal strength), received electric field strength, C / N (Carrier-to-noise power ratio) of the signal received by the receiver 3700. , BER (Bit Error Rate), Packet Error Rate, Frame Error Rate, Channel State Information (Channel State) It is an index showing the reception quality calculated based on Information) and the like, and is a signal showing the signal level and the superiority or inferiority of the signal. In this case, the demodulation unit 3702 includes a reception quality measurement unit that measures RSSI, received electric field strength, C / N, BER, packet error rate, frame error rate, channel state information, etc. of the received signal, and the receiver 3700 is a user. The antenna level (signal level, signal indicating superiority or inferiority of the signal) is displayed on the video display unit 3707 in a user-identifiable format according to the operation of. The display format of the antenna level (signal level, signal indicating superiority or inferiority of the signal) displays numerical values according to RSSI, received electric field strength, C / N, BER, packet error rate, frame error rate, channel state information, etc. It may be such that different images are displayed according to RSSI, received electric field strength, C / N, BER, packet error rate, frame error rate, channel state information, and the like. Further, the receiver 3700 has a plurality of antenna levels (signal level, signal) obtained for each of a plurality of streams s1, s2, ... Received and separated by using the receiving method shown in each of the above embodiments. A signal indicating superiority or inferiority) may be displayed, or one antenna level (signal level, signal indicating superiority or inferiority of the signal) obtained from a plurality of streams s1, s2, ... may be displayed. Further, when the video data or audio data constituting the program is transmitted by the hierarchical transmission method, it is also possible to indicate the signal level (signal indicating superiority or inferiority of the signal) for each layer.

With the above configuration, the user can numerically or visually grasp the antenna level (signal level, signal indicating superiority or inferiority of the signal) when receiving using the receiving method shown in each of the above embodiments. Can be done.

In the above description, the case where the receiver 3700 includes an audio output unit 3706, a video display unit 3707, a recording unit 3708, a stream output IF3709, and an AV output IF3711 has been described as an example. You don't have to have all of them. If the receiver 3700 has at least one of the above configurations, the user can use the multiplexed data obtained by demodulating with the demodulation unit 3702 and performing error correction decoding. , Each receiver may be provided with any combination of the above configurations according to the intended use.

(Multiplexed data) Next, an example of the structure of the multiplexed data will be described in detail. MPEG2-Transport Stream (TS) is generally used as the data structure used for broadcasting, and MPEG2-TS will be described here as an example. However, the data structure of the multiplexed data transmitted by the transmission method and the reception method shown in each of the above embodiments is not limited to MPEG2-TS, and any other data structure will be described in each of the above embodiments. Needless to say, you can get the desired effect.

FIG. 38 is a diagram showing an example of the configuration of the multiplexed data. As shown in FIG. 38, the multiplexed data is an element that constitutes a program (program or an event that is a part thereof) currently provided by each service, for example, a video stream, an audio stream, or a presentation graphics stream (PG). ), Interactive Grafix Stream (IG), etc., obtained by multiplexing one or more of the elemental streams. If the program provided by the multiplexed data is a movie, the video stream is the main video and sub video of the movie, and the audio stream is the main audio part of the movie and the sub audio that mixes with the main audio, as the presentation graphics stream. Shows the subtitles of each movie. Here, the main image is a normal image displayed on the screen, and the sub image is an image displayed on a small screen in the main image (for example, a text data image showing the outline of a movie). be. In addition, the interactive graphics stream shows an interactive screen created by arranging GUI components on the screen.

Each stream contained in the multiplexed data is identified by a PID, which is an identifier assigned to each stream. For example, 0x1011 for video streams used for movie footage, 0x1100 to 0x111F for audio streams, 0x1200 to 0x121F for presentation graphics, and 0x1400 to 0x141F for interactive graphics streams. 0x1B00 to 0x1B1F are assigned to the video stream used for the secondary video, and 0x1A00 to 0x1A1F are assigned to the audio stream used for the secondary audio to be mixed with the main audio.

FIG. 39 is a diagram schematically showing an example of how the multiplexed data is multiplexed. First, a video stream 3901 consisting of a plurality of video frames and an audio stream 3904 consisting of a plurality of audio frames are converted into PES packet strings 3902 and 3905, respectively, and converted into TS packets 3903 and 3906, respectively. Similarly, the data of the presentation graphics stream 3911 and the interactive graphics 3914 are converted into PES packet columns 3912 and 3915, respectively, and further converted into TS packets 3913 and 3916. The multiplexed data 3917 consists of multiplexing these TS packets (3903, 3906, 3913, 3916) into one stream.

Figure 40 shows in more detail how the video stream is stored in the PES packet string. The first stage in FIG. 40 shows a video frame sequence of a video stream. The second row shows the PES packet sequence. As shown by the arrows yy1, yy2, yy3, yy4 in FIG. 40, I-pictures, B-pictures, and P-pictures, which are multiple Video Presentation Units in the video stream, are divided into pictures and stored in the payload of the PES packet. .. Each PES packet has a PES header, and the PES header stores PTS (Presentation Time-Stamp), which is the display time of the picture, and DTS (Decoding Time-Stamp), which is the decoding time of the picture.

FIG. 41 shows the format of the TS packet that is finally written to the multiplexed data. The TS packet is a 188-byte fixed-length packet consisting of a 4-byte TS header containing information such as a PID that identifies the stream and a 184-byte TS payload that stores data. The PES packet is divided and stored in the TS payload. Ru. In the case of BD-ROM, a 4-byte TP_Extra_Header is added to the TS packet, which constitutes a 192-byte source packet and is written to the multiplexed data. Information such as ATS (Arrival_Time_Stamp) is described in TP_Extra_Header. ATS indicates the transfer start time of the TS packet to the PID filter of the decoder. As shown in the lower part of FIG. 41, source packets are lined up in the multiplexed data, and the number incremented from the beginning of the multiplexed data is called SPN (source packet number).

In addition to each stream such as video stream, audio stream, and presentation graphics stream, TS packets included in the multiplexed data include PAT (Program Association Table), PMT (Program Map Table), and PCR (Program Clock Reference). There is. The PAT indicates what the PID of the PMT used in the multiplexed data is, and the PID of the PAT itself is registered as 0. PMT has the PID of each stream such as video, audio, and subtitles contained in the multiplexed data and the attribute information (frame rate, aspect ratio, etc.) of the stream corresponding to each PID, and also contains various descriptors related to the multiplexed data. Have. Descriptors include copy control information that instructs whether to allow or disallow copying of multiplexed data. PCR corresponds to ATS in which the PCR packet is transferred to the decoder in order to synchronize ATC (Arrival Time Clock), which is the time axis of ATS, with STC (System Time Clock), which is the time axis of PTS / DTS. Has information on STC time.

FIG. 42 is a diagram illustrating the data structure of the PMT in detail. At the beginning of the PMT, a PMT header that describes the length of the data contained in the PMT is placed. Behind it, a plurality of descriptors related to the multiplexed data are arranged. The copy control information and the like are described as descriptors. After the descriptor, a plurality of stream information about each stream included in the multiplexed data is arranged. The stream information is composed of a stream descriptor in which the stream type for identifying the compression codec of the stream, the PID of the stream, and the attribute information of the stream (frame rate, aspect ratio, etc.) are described. There are as many stream descriptors as there are streams in the multiplexed data.

When recording on a recording medium or the like, the multiplexed data is recorded together with the multiplexed data information file.

FIG. 43 is a diagram showing the structure of the multiplexed data information file. As shown in FIG. 43, the multiplexed data information file is the management information of the multiplexed data, has a one-to-one correspondence with the multiplexed data, and is composed of the multiplexed data information, the stream attribute information, and the entry map.

As shown in FIG. 43, the multiplexed data information is composed of a system rate, a reproduction start time, and a reproduction end time. The system rate indicates the maximum transfer rate of the multiplexed data to the PID filter of the system target decoder described later. The ATS interval included in the multiplexed data is set to be less than or equal to the system rate. The playback start time is set to the PTS of the video frame at the beginning of the multiplexed data, and the playback end time is set to the PTS of the video frame at the end of the multiplexed data plus the playback interval of one frame.

FIG. 44 is a diagram showing a configuration of stream attribute information included in the multiplexed data information file. As shown in FIG. 44, as the stream attribute information, the attribute information for each stream included in the multiplexed data is registered for each PID. The attribute information has different information for each of the video stream, audio stream, presentation graphics stream, and interactive graphics stream. The video stream attribute information includes what compression codec the video stream was compressed with, what the resolution of the individual picture data that makes up the video stream is, what the aspect ratio is, and the frame rate. It has information such as how much it is. The audio stream attribute information includes what compression codec the audio stream was compressed with, what number of channels the audio stream contains, what language it supports, what sampling frequency it is, and so on. Have information on. This information is used for initializing the decoder before the player plays it.

In this embodiment, among the above-mentioned multiplexed data, the stream type included in the PMT is used. When the multiplexed data is recorded on the recording medium, the video stream attribute information included in the multiplexed data information is used. Specifically, in the moving image coding method or apparatus shown in each of the above embodiments, the moving image coding shown in each of the above embodiments is applied to the stream type or video stream attribute information included in the PMT. Provide steps or means to set unique information indicating that the video data is generated by the method or device. With this configuration, it becomes possible to distinguish between the video data generated by the moving image coding method or the apparatus shown in each of the above embodiments and the video data conforming to other standards.

FIG. 45 shows an example of the configuration of a video / audio output device 4500 including a receiver 4504 that receives video and audio data transmitted from a broadcasting station (base station) or a modulated signal including data for data broadcasting. Is shown. The configuration of the receiving device 4504 corresponds to the receiving device 3700 in FIG. 37. The video / audio output device 4500 is equipped with an OS (Operating System), for example, and is used for a communication device 4506 (for example, wireless LAN (Local Area Network) or Ethernet) for connecting to the Internet. Communication device) is installed. As a result, in the part 4501 that displays the video, the video 4502 in the video and audio data or the data for data broadcasting, and the hypertext provided on the Internet (World Wide Web). Web: WWW)) 4503 can be displayed at the same time. Then, by operating the remote controller (which may be a mobile phone or keyboard) 4507, select either the video 4502 in the data for data broadcasting or the hypertext 4503 provided on the Internet, and change the operation. Will be done. For example, if Hypertext 4503 provided on the Internet is selected, the displayed WWW site can be changed by operating the remote controller. When the video 4502 in the video and audio data or the data for data broadcasting is selected, the channel selected by the remote controller 4507 (selected (television) program, selected audio broadcast). Send information. Then, the IF4505 acquires the information transmitted by the remote controller, and the receiving device 4504 demodulates the signal corresponding to the selected channel, performs processing such as error correction and decoding, and obtains the received data. At this time, the receiving device 4504 receives the information of the control symbol including the information of the transmission method (this is as described in FIG. 5) included in the signal corresponding to the selected channel. By correctly setting the operation, demodulation method, error correction / decoding method, etc., it is possible to obtain the data included in the data symbol transmitted by the broadcasting station (base station). In the above, the user has described an example of selecting a channel by using the remote controller 4507, but the same as above can be obtained even if the channel is selected by using the channel selection key mounted on the video / audio output device 4500. It becomes an operation.

Further, the video / audio output device 4500 may be operated using the Internet. For example, a recording (memory) reservation is made to the video / audio output device 4500 from another terminal connected to the Internet. (Therefore, the video / audio output device 4500 has a recording unit 3708 as shown in FIG. 37.) Then, before starting recording, the channel is selected, and the receiving device 4504 Will demodulate the signal corresponding to the selected channel, perform processing such as error correction and decoding, and obtain received data. At this time, the receiving device 4504 is a transmission method (transmission method, modulation method, error correction method, etc. described in the above embodiment) included in the signal corresponding to the selected channel (this is described in FIG. 5). By obtaining the information of the control symbol including the information of), the data symbol transmitted by the broadcasting station (base station) can be used by correctly setting the receiving operation, demodulation method, error correction / decoding, etc. It is possible to obtain the included data.

(Other supplements) In the present specification, it is considered that a transmission device is provided in, for example, a communication / broadcasting device such as a broadcasting station, a base station, an access point, a terminal, or a mobile phone. At this time, it is conceivable that the receiver is equipped with a communication device such as a television, a radio, a terminal, a personal computer, a mobile phone, an access point, and a base station. Further, the transmitting device and the receiving device in the present invention are devices having a communication function, and the device has some kind of interface to a device for executing an application such as a television, a radio, a personal computer, and a mobile phone. For example, it may be possible to connect via USB).

Further, in the present embodiment, symbols other than data symbols, for example, pilot symbols (pilot symbols may be referred to as preambles, unique words, postambles, reference symbols, scattered pilots, etc.), symbols for control information, etc. Etc. may be arranged in the frame. Here, the names are pilot symbols and symbols for control information, but any naming method may be used, and the function itself is important.

The pilot symbol may be, for example, a known symbol modulated using PSK modulation in the transmitter / receiver (or by synchronizing the receiver, the receiver may be able to know the symbol transmitted by the transmitter. The receiver may use this symbol for frequency synchronization, time synchronization, channel estimation (estimation of CSI (Channel State Information)) (estimation of CSI (Channel State Information)), signal detection, etc. Become.

In addition, the symbol for control information is information that needs to be transmitted to the communication partner (for example, the modulation method / error correction coding method used for communication) in order to realize communication other than data (such as an application). It is a symbol for transmitting error correction coding method coding rate, setting information in the upper layer, etc.).

It should be noted that the present invention is not limited to all embodiments, and various modifications can be made. For example, in the above embodiment, the case of performing as a communication device is described, but the present invention is not limited to this, and this communication method can also be performed as software.

Further, in the above, the phase change method in the method of transmitting two modulated signals from two antennas has been described, but the present invention is not limited to this, and the four mapped signals are precoded and the phase is changed. The method of changing to generate 4 modulated signals and transmitting from 4 antennas, that is, precoding the N mapped signals, generating N modulated signals, and N antennas. Similarly, in the method of transmitting from, the phase can be changed regularly, and the phase can be changed in the same manner.

Further, in the system example shown in the above embodiment, a MIMO type communication system in which two modulated signals are transmitted from two antennas and each is received by two antennas is disclosed, but the present invention naturally discloses MISO. It can also be applied to (Multiple Input Single Output) communication systems. In the case of the MISO method, the receiving device does not have the antenna 701_Y, the radio unit 703_Y, the channel fluctuation estimation unit 707_1 of the modulation signal z1, and the channel fluctuation estimation unit 707_2 of the modulation signal z2 in the configuration shown in FIG. Even in this case, r1 and r2 can be estimated by executing the process shown in the first embodiment. It is well known that a plurality of transmitted signals can be received and decoded by one antenna in the same frequency band and at the same time, and in the present specification, the phase changed on the transmitting side in the signal processing unit. The process for returning is the process added to the prior art.

Further, in the system example shown in the description of the present invention, a MIMO type communication system in which two modulated signals are transmitted from two antennas and each is received by two antennas is disclosed, but the present invention naturally discloses MISO. It can also be applied to (Multiple Input Single Output) communication systems. In the case of the MISO method, the point that precoding and phase change are applied in the transmitter is as described above. On the other hand, in the configuration shown in FIG. 7, the receiving device does not have the antenna 701_Y, the radio unit 703_Y, the channel fluctuation estimation unit 707_1 of the modulation signal z1, and the channel fluctuation estimation unit 707_2 of the modulation signal z2. Even so, the data transmitted by the transmitting device can be estimated by executing the processing shown in the present specification. It is well known that multiple transmitted signals can be received and decoded by one antenna in the same frequency band and at the same time (ML calculation, etc. (Max-log) in one antenna reception. It suffices to perform the processing of APP etc.). ), In the present invention, the signal processing unit 711 of FIG. 7 may perform demodulation (detection) in consideration of the precoding and phase change used on the transmitting side.

In this specification, terms such as "precoding", "precoding weight", and "precoding matrix" are used, but the term itself may be anything (for example, it may be called a codebook). Good), in the present invention, the signal processing itself is important.

Further, in the present specification, the case where the OFDM method is used as the transmission method has been mainly described, but the present invention is not limited to this, and the same applies to the case where a multi-carrier method or a single carrier method other than the OFDM method is used. It is possible to do so. At this time, the spread spectrum communication method may be used. When the single carrier method is used, the phase change is performed in the time axis direction.

Further, in this specification, the receiving device is described by using the ML operation, APP, Max-log APP, ZF, MMSE, etc. As a result, the soft determination result of each bit of the data transmitted by the transmitting device is obtained. (Log-likelihood, log-likelihood ratio) and hard judgment result ("0" or "1") will be obtained, but these may be collectively called detection, demodulation, detection, estimation, and separation.

Different data may be transmitted or the same data may be transmitted by the streams s1 (t) and s2 (t) (s1 (i), s2 (i)).

Also, regular phase changes and precoding are applied to the two-stream baseband signals s1 (i) and s2 (i) (where i represents the order (time or frequency (carrier))). In the baseband signals z1 (i) and z2 (i) after both signals processed, the baseband signals z1 (i) after both signals are generated. In-phase I component I₁(i) Q for orthogonal components₁Let (i) be the common mode I component of the baseband signal z2 (i) after processing both signals.₂(i) Q for orthogonal components₂Let it be (i). At this time, the baseband components are replaced, and the in-phase component of the baseband signal r1 (i) after replacement is changed to I.₁(i) Q for orthogonal components₂(i), I the in-phase component of the baseband signal r2 (i) after replacement₂(i) Q for orthogonal components₁As (i), the modulated signal corresponding to the replaced baseband signal r1 (i) is transmitted from the transmitting antenna 1, and the modulated signal corresponding to the replaced baseband signal r2 (i) is transmitted from the transmitting antenna 2 at the same time. The modulated signal corresponding to the replaced baseband signal r1 (i) and the replaced baseband signal r2 (i) are transmitted from different antennas at the same time using the same frequency, such as transmitting using the frequency. You may send it. In addition, . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i), I the orthogonal component₂(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₁(i) Q for orthogonal components₂(i) . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i), I the orthogonal component₁(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₁(i) Q for orthogonal components₂(i) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i), I the orthogonal component₂(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i), I the orthogonal component₁(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i) Q for orthogonal components₂(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₁(i), I the orthogonal component₂(i) . Q for the in-phase component of the baseband signal r1 (i) after replacement₂(i), I the orthogonal component₁(i), I the in-phase component of the baseband signal r2 (i) after replacement₂(i) Q for orthogonal components₁(i) . Q for the in-phase component of the baseband signal r1 (i) after replacement₂(i), I the orthogonal component₁(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₁(i), I the orthogonal component₂(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i), I the orthogonal component₂(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₁(i) Q for orthogonal components₂(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₂(i), I the orthogonal component₁(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₁(i) Q for orthogonal components₂(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i), I the orthogonal component₂(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₂(i), I the orthogonal component₁(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i) Q for orthogonal components₂(i), I the in-phase component of the baseband signal r1 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i) Q for orthogonal components₂(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₁(i), I the orthogonal component₂(i) . Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i), I the orthogonal component₁(i), I the in-phase component of the baseband signal r1 (i) after replacement₂(i) Q for orthogonal components₁(i) . Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i), I the orthogonal component₁(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₁(i), I the orthogonal component₂It may be (i). Further, in the above, both signals are processed for the signals of two streams, and the replacement of the in-phase component and the orthogonal component of the signals after the signal processing of both is described, but the present invention is not limited to this and is more than two streams. It is also possible to perform both signal processing on the signal and replace the in-phase component and the orthogonal component of the signal after both signal processing.

Further, in the above example, the replacement of the baseband signals at the same time (same frequency ((sub) carrier)) is described, but the replacement of the baseband signals at the same time does not have to be performed. As an example, it can be described as follows: . The in-phase component of the baseband signal r1 (i) after replacement is described as I.₁(i + v), Q for orthogonal component₂(i + w), I the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i + v), I the orthogonal component₂(i + w), Q the in-phase component of the baseband signal r2 (i) after replacement₁(i + v), Q for orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r2 (i) after replacement₁(i + v), Q for orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i + v), I the orthogonal component₂(i + w), Q the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i + v), Q for orthogonal component₂(i + w), Q the in-phase component of the baseband signal r2 (i) after replacement₁(i + v), I the orthogonal component₂(i + w) . Q for the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), I the orthogonal component₁(i + v), I the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . Q for the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r2 (i) after replacement₁(i + v), I the orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i + v), I the orthogonal component₂(i + w), Q the in-phase component of the baseband signal r1 (i) after replacement₁(i + v), Q for orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r2 (i) after replacement.₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r1 (i) after replacement₁(i + v), Q for orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i + v), I the orthogonal component₂(i + w), Q the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r2 (i) after replacement.₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i + v), Q for orthogonal component₂(i + w), I the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i + v), Q for orthogonal component₂(i + w), Q the in-phase component of the baseband signal r1 (i) after replacement₁(i + v), I the orthogonal component₂(i + w) . Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), I the orthogonal component₁(i + v), I the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r1 (i) after replacement₁(i + v), I the orthogonal component₂(i + w) FIG. 55 is a diagram showing a baseband signal replacement unit 5502 for explaining the above description. As shown in FIG. 55, in the baseband signals z1 (i) 5501_1 and z2 (i) 5501_2 after both signal processing, the in-phase I component of the baseband signal z1 (i) 5501_1 after both signal processing is I.₁(i) Q for orthogonal components₁Let (i) be the common mode I component of the baseband signal z2 (i) 5501_2 after processing both signals.₂(i) Q for orthogonal components₂Let it be (i). Then, I set the in-phase component of the baseband signal r1 (i) 5503_1 after replacement._r1(i) Q for orthogonal components_r1(i), I the in-phase component of the baseband signal r2 (i) 5503_2 after replacement_r2(i) Q for orthogonal components_r2If (i), the in-phase component I of the baseband signal r1 (i) 5503_1 after replacement_r1(i), Orthogonal component Q_r1(i), Baseband signal after replacement r2 (i) In-phase component I of 5503_2_r2(i) Q for orthogonal components_r2(i) shall be represented by any of the above. In this example, the replacement of the baseband signal after processing both signals at the same time (same frequency ((sub) carrier)) has been described, but as described above, different times (different frequency ((sub) carrier)) have been described. )) The baseband signal may be exchanged after processing both signals.

A single antenna described in the drawings for both the transmitting antenna of the transmitting device and the receiving antenna of the receiving device may be composed of a plurality of antennas.

In the present specification, "" represents a universal quantifier, and "" represents an existential quantifier.

Further, in the present specification, the unit of phase in the complex plane, for example, the argument angle, is referred to as "radian".

By using the complex plane, it can be displayed in polar format as a display in polar coordinates of complex numbers. When a point (a, b) on the complex plane is associated with a complex number z = a + jb (both a and b are real numbers and j is an imaginary unit), this point is in polar coordinates [r, θ. ], A = r × cosθ, b = r × sinθ

<math num="49"><img file="JP2022017567A_D0050.tif" /></math>

Is true, r is the absolute value of z (r = | z |), and θ is the argument. And z = a + jb is re^jθIs expressed.

In the description of the present invention, the baseband signal, s1, s2, z1, and z2 are complex signals, but the complex signal is I + jQ (when the in-phase signal is I and the orthogonal signal is Q, the complex signal is I + jQ ( j is an imaginary unit). At this time, I may be zero or Q may be zero.

FIG. 46 shows an example of a broadcasting system using the phase changing method described in the present specification. In FIG. 46, the video coding unit 4601 receives video as an input, performs video coding, and outputs data 4602 after video coding. The voice coding unit 4603 receives voice as an input, performs voice coding, and outputs data 4604 after voice coding. The data coding unit 4605 takes data as an input, encodes the data (for example, data compression), and outputs the data 4606 after the data coding. Collectively, these are referred to as the information source coding unit 4600.

The transmission unit 4607 inputs data 4602 after video coding, data 4604 after audio coding, and data 4606 after data coding, and any one of these data or all of these data is used as transmission data. Performs processing such as error correction coding, modulation, precoding, and phase change (for example, signal processing in the transmission device of FIG. 3), and outputs transmission signals 4608_1 to 4608_N. Then, the transmission signals 4608_1 to 4608_N are transmitted as radio waves by the antennas 4609_1 to 4609_N, respectively.

The receiving unit 4612 receives the received signals 4611_1 to 4611_M received by the antennas 4610_1 to 4610_M as inputs, and performs processing such as frequency conversion, phase change, precoding decoding, logarithmic likelihood ratio calculation, and error correction decoding (for example, in FIG. 7). Processing in the receiving device) is performed, and the received data 4613, 4615, 4617 are output. The information source decoding unit 4619 inputs received data 4613, 4615, 4617, and the video decoding unit 4614 inputs received data 4613, decodes for video, outputs a video signal, and outputs the video signal to the television. Displayed on the display. In addition, the voice decoding unit 4616 uses the received data 4615 as an input. Decoding for audio is performed, an audio signal is output, and audio flows from the speaker. Further, the data decoding unit 4618 takes the received data 4617 as an input, decodes the data, and outputs the data information.

Further, in the embodiment in which the present invention is described, in the multi-carrier transmission system such as the OFDM system as described above, the number of encoders possessed by the transmitter is any number. You may. Therefore, for example, as shown in FIG. 4, it is naturally possible to apply the method in which the transmitter is provided with one encoder and distributes the output to a multi-carrier transmission system such as the OFDM system. At this time, the wireless units 310A and 310B in FIG. 4 may be replaced with the OFDM method-related processing units 1301A and 1301B in FIG. At this time, the description of the OFDM method-related processing unit is as in the first embodiment.

Further, in the first embodiment, the equation (36) is given as an example of the precoding matrix, but a method of using the following equation as the precoding matrix can be considered separately.

<math num="50"><img file="JP2022017567A_D0051.tif" /></math>

In the precoding equations (36) and (50), it is described that the equations (37) and (38) are set as the values of α, but the present invention is not limited to this, and α = 1. If set, it becomes a simple precoding matrix, so this value is also one of the valid values.

Further, in the embodiment A1, the phase change value for the period N in the phase change portions in FIGS. 3, 4, 12, 12, 25, 29, 51, and 53 (FIG. 3, FIG. 3). 4, Fig. 6, Fig. 12, Fig. 25, Fig. 29, Fig. 51, and Fig. 53 show the phase change value because the phase change is given to only one baseband signal.) PHASE [i. ] (I = 0,1,2, ..., N-2, N-1 (i is an integer greater than or equal to 0 and less than or equal to N-1). When phase-changing the baseband signal (that is, Fig. 3, Fig. 4, Fig. 6, Fig. 12, Fig. 25, Fig. 29, Fig. 51, Fig. 53), Fig. 3, Fig. 4, Fig. 6, Fig. 12 In FIGS. 25, 29, 51, and 53, the phase change is given only to the baseband signal z2'after precoding. At this time, PHASE [k] is given as follows.

<math num="51"><img file="JP2022017567A_D0052.tif" /></math>

At this time, k = 0,1,2, ..., N-2, N-1 (k is an integer of 0 or more and N-1 or less). Then, when N = 5, 7, 9, 11, 15 it is possible to obtain good data reception quality in the receiving device.

Further, in the present specification, the phase change method in the case of transmitting two modulation signals by a plurality of antennas has been described in detail, but the present invention is not limited to this, and a base in which three or more modulation methods are mapped is performed. The same can be applied to the case where the band signal is precoded and the phase is changed, the baseband signal after the precoding and the phase change is subjected to predetermined processing, and is transmitted from a plurality of antennas.

For example, a program that executes the above communication method may be stored in ROM (Read Only Memory) in advance, and the program may be operated by a CPU (Central Processor Unit).

Further, the program that executes the above communication method is stored in a storage medium that can be read by a computer, the program stored in the storage medium is recorded in the RAM (Random Access Memory) of the computer, and the computer is operated according to the program. You may do so.

Then, each configuration such as each of the above-described embodiments may be realized as an LSI (Large Scale Integration), which is typically an integrated circuit. These may be individually integrated into one chip, or may be integrated into one chip so as to include all or a part of the configurations of each embodiment. Although it is referred to as LSI here, it may be referred to as IC (Integrated Circuit), system LSI, super LSI, or ultra LSI depending on the degree of integration. Further, the method of making an integrated circuit is not limited to the LSI, and may be realized by a dedicated circuit or a general-purpose processor. An FPGA (Field Programmable Gate Array) that can be programmed after the LSI is manufactured, or a reconfigurable processor that can reconfigure the connection and settings of circuit cells inside the LSI may be used.

Furthermore, if an integrated circuit technology that replaces an LSI appears due to advances in semiconductor technology or another technology derived from it, it is naturally possible to integrate functional blocks using that technology. The application of biotechnology may be possible.

(Embodiment C1) In the present embodiment, the case of switching the precoding matrix to be used when the transmission parameter is changed has been described in the first embodiment, but in the present embodiment, the detailed example thereof will be described. As mentioned in the above (other supplements), it is used as a transmission parameter when switching between the case of transmitting different data and the case of transmitting the same data in streams s1 (t) and s2 (t). A method of switching the precoding matrix and a method of changing the phase associated therewith will be described.

In the example of the present embodiment, when transmitting a modulated signal from two different transmitting antennas, the case where the same data is included in each modulated signal and the case where different data is transmitted in each modulated signal are switched. Explain when.

FIG. 56 shows an example of the configuration of the transmission device when the transmission method is switched as described above. In FIG. 56, the same reference numerals are given to those operating in the same manner as in FIG. 54. In FIG. 56, the distribution unit 404 differs from FIG. 54 in that the frame configuration signal 313 is input. The operation of the distribution unit 404 will be described with reference to FIG. 57.

FIG. 57 shows the operation of the distribution unit 404 when transmitting the same data and when transmitting different data. As shown in FIG. 57, assuming that the encoded data is x1, x2, x3, x4, x5, x6, ..., When the same data is transmitted, the distributed data 405A is x1, x2, x3. , X4, x5, x6, ..., and similarly, the distributed data 405B is represented as x1, x2, x3, x4, x5, x6, ....

On the other hand, when different data is transmitted, the data 405A after distribution is represented as x1, x3, x5, x7, x9, ..., And the data 405B after distribution is x2, x4, x6, x8, x10, It is expressed as ...

The distribution unit 404 determines whether the transmission mode transmits the same data or different data by the frame configuration signal 313 which is an input signal.

As another method described above, as shown in FIG. 58, when the same data is transmitted, the distribution unit 404 outputs x1, x2, x3, x4, x5, x6, ... As the distributed data 405A. , No output is performed to the data 405B after distribution. Therefore, when the frame configuration signal 313 indicates "same data transmission", the operation of the distribution unit 404 is as described above, and the interleaver 304B and the mapping unit 306B in FIG. 56 do not operate. Then, only the baseband signal 307A, which is the output of the mapping unit 306A in FIG. 56, becomes valid and becomes the input signals of both the weighting synthesis units 308A and 308B.

In the present embodiment, one feature is that the precoding matrix is switched when the transmission mode is switched between the case of transmitting the same data and the case of transmitting different data. As shown in the equations (36) and (39) of the first embodiment, when represented by a matrix composed of w11, w12, w21, and w22, the precoding matrix for transmitting the same data is as follows. It should be expressed as.

<math num="52"><img file="JP2022017567A_D0053.tif" /></math>

In equation (52), a is a real number (a may be a complex number, but the circuit scale is as large as possible and does not become complicated because the phase change is given to the input baseband signal by precoding. In addition, when a is 1, the weighted synthesis units 308A and 308B output the input signal as it is without performing the weighted synthesis operation. ..

Therefore, in the case of "transmitting the same data", the baseband signal 309A after weighting synthesis and the baseband signal 316B after weighting synthesis, which are the output signals of the weighted synthesis units 308A and 308B, are the same signal.

Then, when the phase change unit 5201 indicates that the frame configuration signal 313 "transmits the same data", the phase change unit 5201 applies a phase change to the weighted composite baseband signal 309A, and the phase change unit signal changes the phase. Output 5202. Then, when the phase changing unit 317B indicates that the frame configuration signal 313 "transmits the same data", the phase changing unit 317B performs a phase change on the weighted combined baseband signal 316B, and the phase changing baseband signal. Output 309B. Note that the phase change performed by the phase change unit 5201 is e.^{jA (t)}(Or e^{jA (f)}Or e^{jA (t, f)}) (However, t is time and f is frequency) (hence e^{jA (t)}(Or e^{jA (f)}Or e^{jA (t, f)}) Is a value to be multiplied by the input baseband signal. ), The phase change performed by the phase change unit 317B is e^{jB (t)}(Or e^{jB (f)}Or e^{jB (t, f)}) (However, t is time and f is frequency) (hence e^{jB (t)}(Or e^{jB (f)}Or e^{jB (t, f)}) Is a value to be multiplied by the input baseband signal. ), It is important to meet the following conditions.

<math num="53"><img file="JP2022017567A_D0054.tif" /></math>

By doing so, the transmission signal can reduce the influence of multipath, so that the reception quality of data can be improved in the receiving device. (However, the phase change may be performed only on one of the weighted-combined baseband signal 309A and the weighted-combined baseband signal 316B.) In FIG. 56, the phase-changed baseband signal may be used. When OFDM is used, the 5202 is subjected to processing such as IFFT and frequency conversion, and is transmitted from the transmitting antenna. (See FIG. 13) (Therefore, the phase-changed baseband signal 5202 can be considered to be the phase-changed baseband signal 1301A.) Similarly, the phase-changed baseband signal 309B uses OFDM. , IFFT, frequency conversion, etc., and transmitted from the transmitting antenna. (See FIG. 13) (Therefore, the phase-changed baseband signal 309B can be considered to be the signal 1301B of FIG. 13) On the other hand, when "transmit different data" is selected as the transmission mode. , As shown in the first embodiment, it shall be represented by any one of the formula (36), the formula (39), and the formula (50). At this time, it is important that the phase changing units 5201 and 317B in FIG. 56 perform a phase changing method different from the case of "transmitting the same data". In particular, in this case, as described in the first embodiment, for example, the phase changing unit 5201 performs the phase change, the phase changing unit 317B does not perform the phase change, or the phase changing unit 5201 does not perform the phase change. , The phase change unit 317B changes the phase, and if only one of the two phase change units changes the phase, the receiving device can be used in both the LOS environment and the NLOS environment. , Good data reception quality can be obtained.

When "Send different data" is selected as the transmission mode, the equation (52) may be used as the precoding matrix, but the equation (36), the equation (50), or the equation ( By using a precoding matrix expressed in 39) and different from Eq. (52), it may be possible to further improve the reception quality of data in the receiving device, especially in the LOS environment.

Further, the present embodiment has been described by taking the case where the OFDM method is used as the transmission method as an example, but the present invention is not limited to this, and the same applies to the case where a multi-carrier method or a single carrier method other than the OFDM method is used. It is possible to carry out. At this time, the spread spectrum communication method may be used. When the single carrier method is used, the phase change is performed in the time axis direction.

As described in the third embodiment, in the case of the transmission method of "transmitting different data", the phase is changed only for the data symbol. However, in the transmission method of "transmitting the same data" described in the present embodiment, the phase change is not limited to the data symbol, but a symbol such as a pilot symbol or a control symbol inserted in the transmission frame of the transmission signal. The phase will be changed for. (However, it is possible not to change the phase of symbols such as pilot symbols and control symbols, but it is preferable to change the phase in order to obtain diversity gain.) (Embodiment C2) In the embodiment, a method of configuring a base station to which the embodiment C1 is applied will be described.

Figure 59 shows the relationship between a base station (broadcasting station) and a terminal. The terminal P (5907) receives the transmission signal 5903A transmitted from the antenna 5904A of the base station A (5902A) and the transmission signal 5905A transmitted from the antenna 5906A, performs predetermined processing, and obtains the received data. And.

The terminal Q (5908) receives the transmission signal 5903A transmitted from the antenna 5904A of the base station A (5902A) and the transmission signal 5903B transmitted from the antenna 5904B of the base station B (5902B), performs predetermined processing, and performs predetermined processing. It is assumed that the received data has been obtained.

In FIGS. 60 and 61, the frequency allocation of the transmission signal 5903A and the transmission signal 5905A transmitted by the base station A (5902A) from the antenna 5904A and the antenna 5906A, and the frequency allocation of the base station B (5902B) from the antenna 5904B and the antenna 5906B are shown. The frequency allocation of the transmission signal 5903B and the transmission signal 5905B is shown. In the figures in FIGS. 60 and 61, the horizontal axis is the frequency and the vertical axis is the transmission power.

As shown in FIG. 60, the transmission signal 5903A and the transmission signal 5905A transmitted by the base station A (5902A), and the transmission signal 5903B and the transmission signal 5905B transmitted by the base station B (5902B) are at least frequency band X and frequency band. It is assumed that Y is used and the frequency band X is used to transmit the data of the first channel, and the frequency band Y is used to transmit the data of the second channel. do.

Therefore, the terminal P (5907) receives the transmission signal 5903A transmitted from the antenna 5904A of the base station A (5902A) and the transmission signal 5905A transmitted from the antenna 5906A, extracts the frequency band X, and performs a predetermined process. It will do and get the data of the first channel. Then, the terminal Q (5908) receives the transmission signal 5903A transmitted from the antenna 5904A of the base station A (5902A) and the transmission signal 5903B transmitted from the antenna 5904B of the base station B (5902B), and sets the frequency band Y. The data of the second channel will be obtained by extracting and performing the predetermined processing.

The configuration and operation of base station A (5902A) and base station B (5902B) at this time will be described.

Both base station A (5902A) and base station B (5902B) include a transmitter configured in FIGS. 56 and 13, as described in embodiment C1. Then, when the base station A (5902A) transmits as shown in FIG. 60, in the frequency band X, as described in the embodiment C1, two different modulated signals are generated (precoding and phase change). ), The two modulated signals are transmitted from the antennas 5904A and 5906A in FIG. 59, respectively. In the frequency band Y, the base station A (5902A) operates the antenna 304A, the mapping unit 306A, the weighted synthesis unit 308A, and the phase change unit 5201 in FIG. 56 to generate a modulation signal 5202, which corresponds to the modulation signal 5202. The transmitted signal to be transmitted is transmitted from the antenna 1310A of FIG. 13, that is, the antenna 5904A of FIG. 59. Similarly, in FIG. 56, the base station B (5902B) operates the antenna 304A, the mapping unit 306A, the weighting synthesis unit 308A, and the phase change unit 5201 to generate a modulation signal 5202, and a transmission signal corresponding to the modulation signal 5202. Is transmitted from the antenna 1310A of FIG. 13, that is, the antenna 5904B of FIG.

Regarding the creation of the coded data of the frequency band Y, as shown in FIG. 56, the base stations may individually generate the coded data, but the coding created by any of the base stations. Later data may be transferred to another base station. Alternatively, as another method, a modulation signal may be generated by one of the base stations, and the generated modulation signal may be passed to another base station.

Further, in FIG. 59, the signal 5901 contains information regarding the transmission mode ("send the same data" or "send different data"), and the base station acquires this signal. The method of generating the modulated signal in each frequency band will be switched. Here, the signal 5901 is input from another device or network as shown in FIG. 59. For example, the base station A (5902A) becomes the master station, and the signal corresponding to the signal 5901 is sent to the base station B (5902B). You may try to pass.

As described above, when the base station "transmits different data", a precoding matrix and a phase change method suitable for the transmission method are set, and a modulated signal is generated.

On the other hand, in the case of "transmitting the same data", each of the two base stations generates and transmits a modulated signal. At this time, each base station can generate a modulated signal for transmission from one antenna. When two base stations are considered together, the two base stations use the precoding matrix of Eq. (52). Corresponds to the setting. The phase changing method is as described in the embodiment C1, and it is preferable that the condition of (Equation 53) is satisfied, for example.

Further, the method of transmitting the frequency band X and the frequency band Y may be changed over time. Therefore , as shown in FIG. 61, the frequency allocation as shown in FIG. 60 may be changed to the frequency allocation as shown in FIG. 61 over time.

By following the present embodiment, it is possible to obtain the effect that the reception quality of data can be improved in the receiving device in both cases of "sending the same data" and "sending different data". At the same time, there is an advantage that the phase changing unit can be shared in the transmitting device.

Further, the present embodiment has been described by taking the case where the OFDM method is used as the transmission method as an example, but the present invention is not limited to this, and the same applies to the case where a multi-carrier method or a single carrier method other than the OFDM method is used. It is possible to carry out. At this time, the spread spectrum communication method may be used. When the single carrier method is used, the phase change is performed in the time axis direction.

As described in the third embodiment, in the case of the transmission method of "transmitting different data", the phase is changed only for the data symbol. However, in the transmission method of "transmitting the same data" described in the present embodiment, the phase change is not limited to the data symbol, but a symbol such as a pilot symbol or a control symbol inserted in the transmission frame of the transmission signal. The phase will be changed for. (However, it is possible not to change the phase of symbols such as pilot symbols and control symbols, but it is preferable to change the phase in order to obtain diversity gain.) (Embodiment C3) In the embodiment, a method of configuring a repeater to which the embodiment C1 is applied will be described. The repeater may also be referred to as a relay station.

FIG. 62 shows the relationship between a base station (broadcasting station), a repeater, and a terminal. As shown in FIG. 63, the base station 6201 transmits a modulated signal of at least frequency band X and frequency band Y. Base station 6201 transmits a modulated signal from antenna 6202A and antenna 6202B, respectively. The transmission method at this time will be described later with reference to FIG. 63.

The repeater A (6203A) obtains received data by performing processing such as demodulation of the received signal 6205A received by the receiving antenna 6204A and the received signal 6207A received by the receiving antenna 6206A. Then, in order to transmit the received data to the terminal, transmission processing is performed to generate modulated signals 6209A and 6211A, which are transmitted from the antennas 6210A and 6212A, respectively.

Similarly, the repeater B (6203B) performs processing such as demodulation of the received signal 6205B received by the receiving antenna 6204B and the received signal 6207B received by the receiving antenna 6206B to obtain received data. Then, in order to transmit the received data to the terminal, transmission processing is performed to generate modulated signals 6209B and 6211B, which are transmitted from the antennas 6210B and 6212B, respectively. Here, it is assumed that the repeater B (6203B) is a master repeater, the control signal 6208 is output, and the repeater A (6203A) inputs this signal. It is not always necessary to provide a master repeater, and the base station 6201 may individually transmit control information to the repeater A (6203A) and the repeater B (6203B).

The terminal P (5907) receives the modulated signal transmitted by the repeater A (6203A) and obtains data. The terminal Q (5908) receives the signals transmitted by the repeater A (6203A) and the repeater B (6203B), and obtains data. The terminal R (6213) receives the modulated signal transmitted by the repeater B (6203B) and obtains data.

FIG. 63 shows the frequency allocation of the modulated signal transmitted from the antenna 6202A and the frequency allocation of the modulated signal transmitted from the antenna 6202B among the transmitted signals transmitted by the base station. In FIG. 63, the horizontal axis is frequency and the vertical axis is transmission power.

As shown in FIG. 63, the modulation signal transmitted from the antenna 6202A and the modulation signal transmitted from the antenna 6202B use at least the frequency band X and the frequency band Y, and the frequency band X is used to use the first channel. It is assumed that the data of the second channel different from the first channel is transmitted by using the frequency band Y.

Then, the data of the first channel is transmitted in the mode of "transmitting different data" using the frequency band X as described in the embodiment C1. Therefore, as shown in FIG. 63, the modulated signal transmitted from the antenna 6202A and the modulated signal transmitted from the antenna 6202B include the component of the frequency band X. Then, the components of the frequency band X are received by the repeater A and the repeater B. Therefore, as described in the first embodiment and the C1 embodiment, the modulated signal in the frequency band X is precoded (weighted synthesis) and phase-changed on the mapped signal. ..

In FIG. 63, the data of the second channel is transmitted by the component of the frequency band Y transmitted from the antenna 6202A of FIG. 62. Then, the component of the frequency band Y is received by the repeater A and the repeater B.

FIG. 64 shows the frequency allocation of the modulation signal 6209A transmitted from the antenna 6210A of the repeater A, the modulation signal 6211A transmitted from the antenna 6212A, and the frequency allocation of the repeater B among the transmission signals transmitted by the repeater A and the repeater B. The frequency allocation of the modulation signal 6209B transmitted from the antenna 6210B and the modulation signal 6211B transmitted from the antenna 6212B is shown. In FIG. 64, the horizontal axis is frequency and the vertical axis is transmission power.

As shown in FIG. 64, the modulated signal 6209A transmitted from the antenna 6210A and the modulated signal 6211A transmitted from the antenna 6212A use at least the frequency band X and the frequency band Y, and the modulated signal transmitted from the antenna 6210B. The 6209B and the modulated signal 6211B transmitted from the antenna 6212B use at least the frequency band X and the frequency band Y, and use the frequency band X to transmit the data of the first channel, and also the frequency. It is assumed that the data of the second channel is transmitted using the band Y.

Then, the data of the first channel is transmitted in the mode of "transmitting different data" using the frequency band X as described in the embodiment C1. Therefore, as shown in FIG. 64, the modulation signal 6209A transmitted from the antenna 6210A and the modulation signal 6211A transmitted from the antenna 6212A include the component of the frequency band X. Then, the component of the frequency band X is received by the terminal P. Similarly, as shown in FIG. 64, the modulation signal 6209B transmitted from the antenna 6210B and the modulation signal 6211B transmitted from the antenna 6212B include the component of the frequency band X. Then, the component of the frequency band X is received by the terminal R. Therefore, as described in the first embodiment and the C1 embodiment, the modulated signal in the frequency band X is precoded (weighted synthesis) and phase-changed on the mapped signal. ..

The data of the second channel is shown in FIG. 64 using the component of the frequency band Y of the modulated signal transmitted from the antenna 6210A of the repeater A (6203A) of FIG. 62 and the antenna 6210B of the repeater B (6203B). It will be transmitted. At this time, the component of the frequency band Y of the modulation signal 6209A transmitted from the antenna 6210A of the repeater A (6203A) of FIG. 62 and the frequency band Y of the modulation signal 6209B transmitted from the antenna 6210B of the repeater B (6203B). Depending on the component, the "send identical data" transmission mode described in embodiment C1 will be used. Then, the component of the frequency band Y is received by the terminal Q.

Next, the configurations of the repeater A (6203A) and the repeater B (6203B) in FIG. 62 will be described with reference to FIG. 65.

FIG. 65 shows an example of the configuration of the receiving unit and the transmitting unit of the repeater, and the same reference numerals are given to those operating in the same manner as in FIG. 56. The receiving unit 6203X receives the received signal 6502a received by the receiving antenna 6501a and the received signal 6502b received by the receiving antenna 6501b as inputs, and performs signal processing (signal separation or synthesis, error correction decoding) for the components of the frequency band X. The base station obtains the data 6204X transmitted using the frequency band X, outputs it to the distribution unit 404, and obtains the transmission method information included in the control information (transmitted by the repeater). Information on the transmission method is also obtained), and the frame configuration signal 313 is output.

The receiving unit 6203X and later are processing units for generating a modulated signal for transmission in the frequency band X. Further, as shown in FIG. 65, the receiving unit includes not only the receiving unit in the frequency band X but also other receiving units in other frequency bands, and each receiving unit has the frequency band. It will be provided with a processing unit for generating a modulated signal for transmission using the above.

The outline of the operation of the distribution unit 404 is the same as the operation of the distribution unit in the base station described in the second embodiment C2.

When the repeater A (6203A) and the repeater B (6203B) transmit as shown in FIG. 64, the repeater A (6203A) and the repeater B (6203B) generate two different modulated signals in the frequency band X as described in the embodiment C1 (pre). (Coding and phase change), the repeater A (6203A) transmits from the antennas 6210A and 6212A of FIG. 62, and the repeater B (6203B) transmits from the antennas 6210B and 6212B of FIG. 62, respectively.

In the frequency band Y, the repeater A (6203A) is in FIG. 65 in the processing unit 6500 related to the frequency band Y corresponding to the signal processing unit 6500 related to the frequency band X (6500 is related to the frequency band X). Although it is a signal processing unit, the frequency band Y also has a similar signal processing unit, so it will be described with the added number in 6500), interleaver 304A, mapping unit 306A, weighted composition unit 308A, phase change unit 5201. Is operated to generate a modulation signal 5202, and a transmission signal corresponding to the modulation signal 5202 is transmitted from the antenna 1310A of FIG. 13, that is, the antenna 6210A of FIG. 62. Similarly, in FIG. 62, the repeater B (6203B) operates the antenna 304A, the mapping unit 306A, the weighted synthesis unit 308A, and the phase change unit 5201 in the frequency band Y to generate the modulation signal 5202, and the modulation signal 5202. The transmission signal corresponding to is transmitted from the antenna 1310A of FIG. 13, that is, the antenna 6210B of FIG.

As shown in FIG. 66 (FIG. 66 shows the frame configuration of the modulated signal transmitted by the base station, the horizontal axis time and the vertical axis frequency), the base station has information on the transmission method 6601 and a repeater. The repeater transmits the information 6602 and the data symbol 6603 related to the phase change performed by the repeater, and the repeater determines the method of the phase change applied to the transmission signal by obtaining the information 6601 regarding the transmission method and the information 6602 regarding the phase change performed by the repeater. can do. If the information 6602 regarding the phase change performed by the repeater in FIG. 66 is not included in the signal transmitted by the base station, the repeater B (6203B) becomes the master and the repeater A as shown in FIG. (6203A) may be instructed on the phase change method.

As described above, when the repeater "transmits different data", the precoding matrix and the phase change method suitable for the transmission method are set, and the modulated signal is generated.

On the other hand, in the case of "transmitting the same data", each of the two repeaters generates and transmits a modulated signal. At this time, each repeater can generate a modulated signal for transmission from one antenna. When two repeaters are considered together, the two repeaters can be used to generate the precoding matrix of Eq. (52). Corresponds to the setting. The phase changing method is as described in the embodiment C1, and it is preferable that the condition of (Equation 53) is satisfied, for example.

Further, as described in the embodiment C1, as in the frequency band X, both the base station and the repeater transmit the modulated signal from each of the two antennas, and transmit the same data from the two antennas. You may. The operation of the base station and the repeater at this time is as described in the embodiment C1.

By following the present embodiment, it is possible to obtain the effect that the reception quality of data can be improved in the receiving device in both cases of "sending the same data" and "sending different data". At the same time, there is an advantage that the phase changing unit can be shared in the transmitting device.

Further, the present embodiment has been described by taking the case where the OFDM method is used as the transmission method as an example, but the present invention is not limited to this, and the same applies to the case where a multi-carrier method or a single carrier method other than the OFDM method is used. It is possible to carry out. At this time, the spread spectrum communication method may be used. When the single carrier method is used, the phase change is performed in the time axis direction.

As described in the third embodiment, in the case of the transmission method of "transmitting different data", the phase is changed only for the data symbol. However, in the transmission method of "transmitting the same data" described in the present embodiment, the phase change is not limited to the data symbol, but a symbol such as a pilot symbol or a control symbol inserted in the transmission frame of the transmission signal. The phase will be changed for. (However, it is possible not to change the phase of symbols such as pilot symbols and control symbols, but it is preferable to change the phase in order to obtain diversity gain.) (Embodiment C4) In the embodiment, a phase changing method different from the phase changing method described in "Embodiment 1" and "Other Supplement" will be described.

In the first embodiment, the equation (36) is given as an example of the precoding matrix, and in other supplements, the equation (50) is given as an example of the precoding matrix. Then, in the embodiment A1, the phase change value for the period N in the phase change portions in FIGS. 3, 4, 12, 12, 25, 29, 51, and 53 (FIG. 3, FIG. 3). 4, Fig. 6, Fig. 12, Fig. 25, Fig. 29, Fig. 51, and Fig. 53 show the phase change value because the phase change is given to only one baseband signal.) PHASE [i. ] (I = 0,1,2, ..., N-2, N-1 (i is an integer between 0 and N-1)). Then, in the present specification, when the phase is changed for one of the precoded baseband signals (that is, FIG. 3, FIG. 4, FIG. 6, FIG. 12, FIG. 25, FIG. 29, FIG. 51, FIG. 53). ), Fig. 4, Fig. 6, Fig. 12, Fig. 25, Fig. 29, Fig. 51, and Fig. 53, the phase change is given only to the baseband signal z2'after precoding. At this time, PHASE [k] is given as follows.

<math num="54"><img file="JP2022017567A_D0055.tif" /></math>

At this time, k = 0,1,2, ..., N-2, N-1 (k is an integer of 0 or more and N-1 or less).

By doing so, it is possible to obtain the effect of improving the data reception quality in the receiving device, particularly when the radio wave propagation environment is the LOS environment. This is because in the LOS environment, what was a steady phase relationship when the phase change was not performed, the phase relationship is changed by performing the phase change, and as a result, the propagation environment is burst-like. This is because bad situations are avoided. Further, as a method different from the equation (54), PHASE [k] may be given as follows.

<math num="55"><img file="JP2022017567A_D0056.tif" /></math>

At this time, k = 0,1,2, ..., N-2, N-1 (k is an integer of 0 or more and N-1 or less).

Further, as another phase changing method, PHASE [k] may be given as follows.

<math num="56"><img file="JP2022017567A_D0057.tif" /></math>

At this time, k = 0,1,2, ..., N-2, N-1 (k is an integer of 0 or more and N-1 or less), and Z is a fixed value.

Further, as another phase changing method, PHASE [k] may be given as follows.

<math num="57"><img file="JP2022017567A_D0058.tif" /></math>

At this time, k = 0,1,2, ..., N-2, N-1 (k is an integer of 0 or more and N-1 or less), and Z is a fixed value.

As described above, by performing the phase change as in the present embodiment, it is possible to obtain the effect that the receiving device is more likely to obtain good reception quality.

The phase change of the present embodiment is not limited to the application to the single carrier system, but can also be applied to the case of multi-carrier transmission. Therefore, for example, the same can be carried out when the spectrum diffusion communication method, the OFDM method, the SC-FDMA, the SC-OFDM method, the wavelet OFDM method shown in Non-Patent Document 7 and the like are used. As described above, in the present embodiment, as an explanation for performing the phase change, the phase may be changed in the time t-axis direction, but as in the first embodiment, when the phase is changed in the frequency axis direction. Similarly, that is, in the present embodiment, in the description of the phase change in the t direction, t is replaced with f (f: frequency ((sub) carrier)) and considered, thereby explaining in the present embodiment. The phase change change can be applied to the phase change in the frequency direction. Further, the phase change method of the present embodiment can be applied to the phase change in the time-frequency direction as in the description of the first embodiment. Further, if the phase changing method described in the present embodiment satisfies the contents shown in the A1 embodiment, there is a high possibility that good data quality can be obtained in the receiving device.

(Embodiment C5) In the present embodiment, a phase change method different from the phase change method described in "Embodiment 1", "Other Supplement", and "Embodiment C4" will be described.

In the first embodiment, the equation (36) is given as an example of the precoding matrix, and in other supplements, the equation (50) is given as an example of the precoding matrix. Then, in the embodiment A1, the phase change value for the period N in the phase change portions in FIGS. 3, 4, 12, 12, 25, 29, 51, and 53 (FIG. 3, FIG. 3). 4, Fig. 6, Fig. 12, Fig. 25, Fig. 29, Fig. 51, and Fig. 53 show the phase change value because the phase change is given to only one baseband signal.) PHASE [i. ] (I = 0,1,2, ..., N-2, N-1 (i is an integer between 0 and N-1)). Then, in the present specification, when the phase is changed for one of the precoded baseband signals (that is, FIG. 3, FIG. 4, FIG. 6, FIG. 12, FIG. 25, FIG. 29, FIG. 51, FIG. 53). ), Fig. 4, Fig. 6, Fig. 12, Fig. 25, Fig. 29, Fig. 51, and Fig. 53, the phase change is given only to the baseband signal z2'after precoding.

The characteristic point of the phase changing method in this embodiment is that the period N = 2n + 1. Then, the number of different phase change values prepared to realize the period N = 2n + 1 is n + 1.

Then, of the n + 1 different phase change values, n phase change values are used twice in one cycle, and one phase change value is used once, so that the cycle N = 2n + 1 is realized. Hereinafter, the phase change value at this time will be described in detail.

PHASE [0], PHASE [1], ... PHASE [i], ···, PHASE [n-1], PHASE [n] (i = 0,1,2, ···, n-2, n-1, n (i is 0 or more n) The following integers))). At this time, examples of n + 1 different phase change values PHASE [0], PHASE [1], ..., PHASE [i], ..., PHASE [n-1], PHASE [n] are as follows. It is expressed as.

<math num="58"><img file="JP2022017567A_D0059.tif" /></math>

At this time, k = 0,1,2, ..., N-2, n-1, n (k is an integer of 0 or more and n or less). In equation (58), n + 1 different phase change values PHASE [0], PHASE [1], ···, PHASE [i], ···, PHASE [n-1], PHASE [n] Use PHASE [0] once and use PHASE [1] to PHASE [n] twice each (use PHASE [1] twice, use PHASE [2] twice, ..., PHASE [ Use n-1] twice, PHASE [n]

By using twice), a phase change method that regularly switches the phase change value with a period N = 2n + 1 is realized, and a phase change method that regularly switches the phase change value with a small number of phase change values is realized. The receiving device can obtain good data reception quality. Since the number of phase change values to be prepared is small, it is possible to obtain an effect that can reduce the effect of the transmitting device and the receiving device. As described above, in the receiving device, particularly when the radio wave propagation environment is the LOS environment, the effect of improving the data reception quality can be obtained. This is because in the LOS environment, what was a steady phase relationship when the phase change was not performed, the phase relationship is changed by performing the phase change, and as a result, the propagation environment is burst-like. This is because bad situations are avoided. Further, as a method different from the equation (58), PHASE [k] may be given as follows.

<math num="59"><img file="JP2022017567A_D0060.tif" /></math>

At this time, k = 0,1,2, ..., N-2, n-1, n (k is an integer of 0 or more and n or less).

In equation (59), n + 1 different phase change values PHASE [0], PHASE [1], ···, PHASE [i], ···, PHASE [n-1], PHASE [n] Use PHASE [0] once and use PHASE [1] to PHASE [n] twice each (use PHASE [1] twice, use PHASE [2] twice, ..., PHASE [ By using n-1] twice and PHASE [n] twice), the phase change method that switches the phase change value regularly with a period N = 2n + 1 is used, and the phase change value is small. The phase change method for switching the phase change value can be realized, and the receiving device can obtain good data reception quality. Since the number of phase change values to be prepared is small, it is possible to obtain an effect that can reduce the effect of the transmitting device and the receiving device.

Alternatively, PHASE [k] may be given as follows.

<math num="60"><img file="JP2022017567A_D0061.tif" /></math>

At this time, k = 0,1,2, ..., N-2, n-1, n (k is an integer of 0 or more and n or less), and Z is a fixed value.

In n + 1 different phase change values PHASE [0], PHASE [1], ···, PHASE [i], ···, PHASE [n-1], PHASE [n] in Eq. (60) Use PHASE [0] once and use PHASE [1] to PHASE [n] twice each (use PHASE [1] twice, use PHASE [2] twice, ..., PHASE [ By using n-1] twice and PHASE [n] twice), the phase change method that switches the phase change value regularly with a period N = 2n + 1 is used, and the phase change value is small. The phase change method for switching the phase change value can be realized, and the receiving device can obtain good data reception quality. Since the number of phase change values to be prepared is small, it is possible to obtain an effect that can reduce the effect of the transmitting device and the receiving device.

Alternatively, PHASE [k] may be given as follows.

<math num="61"><img file="JP2022017567A_D0062.tif" /></math>

At this time, k = 0,1,2, ..., N-2, n-1, n (k is an integer of 0 or more and n or less), and Z is a fixed value.

In n + 1 different phase change values PHASE [0], PHASE [1], ···, PHASE [i], ···, PHASE [n-1], PHASE [n] in Eq. (61) Use PHASE [0] once and use PHASE [1] to PHASE [n] twice each (use PHASE [1] twice, use PHASE [2] twice, ..., PHASE [ By using n-1] twice and PHASE [n] twice), the phase change method that switches the phase change value regularly with a period N = 2n + 1 is used, and the phase change value is small. The phase change method for switching the phase change value can be realized, and the receiving device can obtain good data reception quality. Since the number of phase change values to be prepared is small, it is possible to obtain an effect that can reduce the effect of the transmitting device and the receiving device.

As described above, by performing the phase change as in the present embodiment, it is possible to obtain the effect that the receiving device is more likely to obtain good reception quality.

The phase change of the present embodiment is not limited to the application to the single carrier method, but can also be applied to the case of multi-carrier transmission. Therefore, for example, the same can be carried out when the spectrum diffusion communication method, the OFDM method, the SC-FDMA, the SC-OFDM method, the wavelet OFDM method shown in Non-Patent Document 7 and the like are used. As described above, in the present embodiment, as an explanation for performing the phase change, the phase may be changed in the time t-axis direction, but as in the first embodiment, when the phase is changed in the frequency axis direction. Similarly, that is, in the present embodiment, in the description of the phase change in the t direction, t is replaced with f (f: frequency ((sub) carrier)) and considered, thereby explaining in the present embodiment. The phase change change can be applied to the phase change in the frequency direction. Further, the phase change method of the present embodiment can be applied to the phase change in the time-frequency direction as in the description of the first embodiment.

(Embodiment C6) In the present embodiment, as shown in Non-Patent Documents 12 to 15, QC (Quasi Cyclic) LDPC (Low-Density Parity-Check) code (however, QC-LDPC) A block code such as an LDPC (block) code that is not a code), a block code such as a concatenated code between an LDPC code and a BCH code (Bose-Chaudhuri-Hocquenghem code), a turbo code, or a block code such as Duo-Binary Turbo Code is used. In particular, the case where the phase change method for regularly switching the phase change value described in the embodiment C5 is used will be described in detail. Here, as an example, a case where two streams of s1 and s2 are transmitted will be described as an example. However, when coding is performed using the block code, when control information or the like is not required, the number of bits constituting the coded block is the number of bits constituting the block code (however, among these, the following It may contain control information and the like as described.) When encoding is performed using a block code, control information, etc. (for example, CRC (cyclic redundancy)) When check), transmission parameters, etc.) are required, the number of bits constituting the coded block may be the sum of the number of bits constituting the block code and the number of bits such as control information.

FIG. 34 is a diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used. FIG. 34 shows, for example, a "block code" in the case where two streams s1 and s2 are transmitted and the transmitter has one encoder, as shown in the transmitter of FIG. It is a figure showing the change in the number of symbols and the number of slots required for one coded block when used. " (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 34, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Since the transmitter in FIG. 4 transmits two streams at the same time, when the modulation method is QPSK, the above 3000 symbols are assigned 1500 symbols to s1 and 1500 symbols to s2. 1500 slots (named "slots" here) are required to transmit 1500 symbols to be transmitted in s1 and 1500 symbols to be transmitted in s2.

Similarly, when the modulation scheme is 16QAM, 750 slots are required to transmit all the bits that make up one coded block, and when the modulation scheme is 64QAM, all that make up one block. 500 slots are required to send the bits.

Next, the relationship between the slot and the phase defined above will be described in the method of regularly changing the phase.

Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase with a period of 5 is 5. That is, it is assumed that five phase change values (or phase change sets) for period 5 are prepared for the phase change part of the transmitter of FIG. However, as described in the embodiment C5, there are three different phase change values. Therefore, the same phase change value exists among the five phase change values for the period 5. (As shown in FIG. 6, when the phase change is performed only on the baseband signal z2'after precoding, five phase change values may be prepared in order to perform the phase change in the period 5. Also, FIG. 26. When performing phase change for both the precoded baseband signals z1'and z2', two phase change values are required for one slot. These two phase change values are phased. It is called a change set. Therefore, in this case, in order to perform a phase change with a period of 5, it is sufficient to prepare five phase change sets). Five phase change values (or phase change sets) for period 5 are represented as P [0], P [1], P [2], P [3], P [4].

Next, in the method of changing the phase regularly, the relationship between the slot and the phase defined above will be described.

When the modulation method is QPSK, in the 1500 slots described above for transmitting 6000 bits constituting one coded block, the slots using the phase change value P [0] are 300 slots and the phase. The slot using the change value P [1] is 300 slots, the slot using the phase change value P [2] is 300 slots, the slot using the phase change value P [3] is 300 slots, and the phase change value P [4]. ] Must be used in 300 slots. This is because if there is a deviation in the phase change value used, the reception quality of the data is greatly affected by the phase change value using a large number.

Similarly, when the modulation scheme is 16QAM, in the 750 slots mentioned above for transmitting the 6000 bits that make up one coded block, 150 slots use the phase change value P [0]. Slots, 150 slots using phase change value P [1], 150 slots using phase change value P [2], 150 slots using phase change value P [3], phase change value The slot using P [4] must be 150 slots.

Similarly, when the modulation method is 64QAM, in the 500 slots described above for transmitting 6000 bits constituting one coded block, 100 slots use the phase change value P [0]. 100 slots for slots, 100 slots for phase change value P [1], 100 slots for phase change value P [2], 100 slots for phase change value P [3], phase change value The number of slots that use P [4] must be 100.

As described above, in the phase change method for regularly switching the phase change values described in the embodiment C5, the phase change values P [0], P [1], .... ., P [2n-1], P [2n]

(However, P [0], P [1], ..., P [2n-1], P [2n] are PHASE [0], PHASE [1], PHASE [2], ..., PHASE. When [n-1] and PHASE [n] are used (see Embodiment C5)), the phase change value P is used when all the bits constituting one coded block are transmitted. Set the number of slots that use [0] to K₀, K the number of slots that use the phase change value P [1]_1、K the number of slots that use the phase change value P [i]_i(i = 0,1,2, ..., 2n-1,2n (i is an integer between 0 and 2n)), K the number of slots that use the phase change value P [2n]_2nWhen &lt;Condition # C01&gt; K₀= K₁= . . . = K_i= . . . = K_2n, That is, K_a= K_{b b}, (For a, b, but a, b = 0,1,2, ..., 2n-1,2n (a is an integer between 0 and 2n, b is an integer between 0 and 2n), It is good that a b).

In the phase change method for regularly switching the phase change values described in the embodiment C5, different phase change values PHASE [0], PHASE [1], PHASE [2], for realizing the period N = 2n + 1. ..., PHASE [n-1], PHASE [n], the number of slots that use the phase change value PHASE [0] when transmitting all the bits that make up one coded block is G.₀, G the number of slots that use the phase change value PHASE [1]_1、G the number of slots that use the phase change value PHASE [i]_i(i = 0,1,2, ..., n-1, n (i is an integer between 0 and n)), G is the number of slots that use the phase change value PHASE [n]._nThen, &lt;condition # C01&gt; can be expressed as follows.

&lt;Condition # C02&gt; 2 × G₀= G₁= . . . = G_i= . . . = G_nThat is, 2 × G₀= G_a, (For a, where a = 1,2, ..., n-1, n (a is an integer greater than or equal to 1 and less than or equal to n)) And the communication system supports multiple modulation schemes. When selecting from the supported modulation methods and using them, it is preferable that &lt;condition # C01&gt; (&lt;condition # C02&gt;) is satisfied in the supported modulation methods.

However, when multiple modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy &lt;Condition # C01&gt; (&lt;Condition # C02&gt;). In this case, the following conditions should be satisfied instead of &lt;Condition # C01&gt;.

&lt;Condition # C03&gt; K_aAnd K_{b b}The difference between is 0 or 1, that is, | K_aK_{b b}| Is 0 or 1 (for a, b, but a, b = 0,1,2, ..., 2n-1,2n (a is an integer between 0 and 2n, b is between 0 and 2n) Integer), a b) &lt;Condition # C03&gt; can be expressed differently as follows.

&lt;Condition # C04&gt; G_aAnd G_{b b}The difference between is 0 or 1 or 2, that is, | G_aG_{b b}| Is 0 or 1 or 2 (for a, b, but a, b = 1,2, ..., n-1, n (a is an integer from 1 to n, b is from 1 to n) Integer), a b) and 2 × G₀And G_aThe difference between is 0 or 1 or 2, that is, | 2 × G₀G_a| Is 0 or 1 or 2 (for a, where a = 1,2, ···, n-1, n (a is an integer between 1 and n)) Figure 35 shows when the block code is used. , Is a diagram showing changes in the number of symbols and the number of slots required for two coded blocks. FIG. 35 shows the case where two streams of s1 and s2 are transmitted and the transmitter has two encoders as shown in the transmitter of FIG. 3 and the transmitter of FIG. "A diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used". (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 35, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Then, in the transmitter of FIG. 3 and the transmitter of FIG. 12, two streams are transmitted at the same time, and since there are two encoders, the two streams transmit different code blocks. become. Therefore, when the modulation method is QPSK, s1 and s2 transmit two coded blocks within the same interval. Therefore, for example, s1 transmits the first coded block, and s2 transmits the first coded block. Since 2 coded blocks will be transmitted, 3000 slots will be required to transmit the 1st and 2nd coded blocks.

Similarly, when the modulation scheme is 16QAM, 1500 slots are required to transmit all the bits that make up the two encoded blocks, and when the modulation scheme is 64QAM, all that make up the two blocks. 1000 slots are required to send the bits.

Next, the relationship between the slot and the phase defined above will be described in the method of regularly changing the phase.

Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase with a period of 5 is 5. That is, it is assumed that five phase change values (or phase change sets) for period 5 are prepared for the phase change part of the transmitter of FIG. However, as described in the embodiment C5, there are three different phase change values. Therefore, the same phase change value exists among the five phase change values for the period 5. (As shown in FIG. 6, when the phase change is performed only on the baseband signal z2'after precoding, five phase change values may be prepared in order to perform the phase change in the period 5. Also, FIG. 26. When performing phase change for both the precoded baseband signals z1'and z2', two phase change values are required for one slot. These two phase change values are phased. It is called a change set. Therefore, in this case, in order to perform a phase change with a period of 5, it is sufficient to prepare five phase change sets). Five phase change values (or phase change sets) for period 5 are represented as P [0], P [1], P [2], P [3], P [4].

When the modulation method is QPSK, in the 3000 slots described above for transmitting the number of bits 6000 × 2 bits that make up the two coded blocks, the slot that uses the phase change value P [0] is 600 slots. , The slot that uses the phase change value P [1] is 600 slots, the slot that uses the phase change value P [2] is 600 slots, the slot that uses the phase change value P [3] is 600 slots, and the phase change value P The slot using [4] must be 600 slots. This is because if there is a deviation in the phase change value used, the reception quality of the data is greatly affected by the phase change value using a large number.

Also, in order to transmit the first coded block, the slot using the phase change value P [0] is 600 times, the slot using the phase change value P [1] is 600 times, and the phase change value P [2]. ] Must be 600 times, the slot using the phase change value P [3] 600 times, the slot using the phase change value P [4] 600 times, and the second Slots that use the phase change value P [0] 600 times, slots that use the phase change value P [1] 600 times, and slots that use the phase change value P [2] to transmit the coded block. Is 600 times, the slot using the phase change value P [3] is 600 times, and the slot using the phase change value P [4] is 600 times.

Similarly, when the modulation method is 16QAM, the slot using the phase change value P [0] in the 1500 slot described above for transmitting the number of bits 6000 × 2 bits constituting the two coded blocks. Is 300 slots, the slot that uses the phase change value P [1] is 300 slots, the slot that uses the phase change value P [2] is 300 slots, the slot that uses the phase change value P [3] is 300 slots, and the phase. The slot using the change value P [4] must be 300 slots.

Also, in order to transmit the first coded block, the slot using the phase change value P [0] is 300 times, the slot using the phase change value P [1] is 300 times, and the phase change value P [2]. ] Must be used 300 times, the slot using the phase change value P [3] 300 times, the slot using the phase change value P [4] 300 times, and the second code. The slot using the phase change value P [0] is 300 times, the slot using the phase change value P [1] is 300 times, and the slot using the phase change value P [2] is used to transmit the conversion block. It is preferable that the number of slots using the phase change value P [3] is 300 times, and the number of slots using the phase change value P [4] is 300 times.

Similarly, when the modulation method is 64QAM, the slot using the phase change value P [0] in the 1000 slots described above for transmitting the number of bits 6000 × 2 bits constituting the two coded blocks. 200 slots, 200 slots using the phase change value P [1], 200 slots using the phase change value P [2], 200 slots using the phase change value P [3], phase The slot using the change value P [4] must be 200 slots.

Also, in order to transmit the first coded block, the slot using the phase change value P [0] is 200 times, the slot using the phase change value P [1] is 200 times, and the phase change value P [2]. ] Must be used 200 times, the slot using the phase change value P [3] 200 times, the slot using the phase change value P [4] 200 times, and the second code. The slot that uses the phase change value P [0] 200 times, the slot that uses the phase change value P [1] 200 times, and the slot that uses the phase change value P [2] to transmit the conversion block It is preferable that the number of slots using the phase change value P [3] is 200 times, and the number of slots using the phase change value P [4] is 200 times.

As described above, in the phase change method for regularly switching the phase change values described in the embodiment C5, the phase change values P [0], P [1], .... ., P [2n-1], P [2n]

(However, P [0], P [1], ..., P [2n-1], P [2n] are PHASE [0], PHASE [1], PHASE [2], ..., PHASE. When [n-1] and PHASE [n] are used (see Embodiment C5)), the phase change value P is used when all the bits constituting the two encoded blocks are transmitted. Set the number of slots that use [0] to K₀, K the number of slots that use the phase change value P [1]_1、K the number of slots that use the phase change value P [i]_i(i = 0,1,2, ..., 2n-1,2n (i is an integer between 0 and 2n)), and the number of slots that use the phase change value P [2n] is K._2nWhen &lt;Condition # C05&gt; K₀= K₁= . . . = K_i= . . . = K_2n, That is, K_a= K_{b b}, (For a, b, but a, b = 0,1,2, ..., 2n-1,2n (a is an integer from 0 to 2n, b is an integer from 0 to 2n), a b), and the number of times the phase change value P [0] is used when transmitting all the bits that make up the first encoded block is K._0,1, K how many times to use the phase change value P [1]_1,1、K the number of times to use the phase change value P [i]_{i, 1}(i = 0,1,2, ..., 2n-1,2n (i is an integer between 0 and 2n)), and the number of times the phase change value P [2n] is used is K._{2n, 1}When &lt;Condition # C06&gt; K_0,1= K_1,1= . . . = K_{i, 1}= . . . = K_{2n, 1}, That is, K_{a, 1}= K_{b, 1}, (For a, b, but a, b = 0,1,2, ..., 2n-1,2n (a is an integer from 0 to 2n, b is an integer from 0 to 2n), a b), and the number of times the phase change value P [0] is used when transmitting all the bits that make up the second coded block is K._0,2, K how many times to use the phase change value P [1]_1,2、K the number of times to use the phase change value P [i]_{i, 2}(i = 0,1,2, ..., 2n-1,2n (i is an integer between 0 and 2n)), the number of times the phase change value P [2n] is used is K._{2n, 2}When &lt;Condition # C07&gt; K_0,2= K_1,2= . . . = K_{i, 2}= . . . = K_{2n, 2}, That is, K_{a, 2}= K_{b, 2}, (For a, b, but a, b = 0,1,2, ..., 2n-1,2n (a is an integer between 0 and 2n, b is an integer between 0 and 2n), It is good that a b).

In the phase change method for regularly switching the phase change values described in the embodiment C5, different phase change values PHASE [0], PHASE [1], PHASE [2], for realizing the period N = 2n + 1. ..., PHASE [n-1], PHASE [n], the number of slots that use the phase change value PHASE [0] when transmitting all the bits that make up the two encoded blocks is G.₀, G the number of slots that use the phase change value PHASE [1]_1、G the number of slots that use the phase change value PHASE [i]_i(i = 0,1,2, ..., n-1, n), G is the number of slots that use the phase change value PHASE [n]._nThen, &lt;condition # C05&gt; can be expressed as follows.

&lt;Condition # C08&gt; 2 × G₀= G₁= . . . = G_i= . . . = G_nThat is, 2 × G₀= G_a, (For a, where a = 1,2, ···, n-1, n (a is an integer between 1 and n)), and the bits that make up the first coded block G the number of times to use the phase change value PHASE [0] when transmitting all_0,1, K how many times to use the phase change value PHASE [1]_1,1、G the number of times to use the phase change value PHASE [i]_{i, 1}(i = 0,1,2, ..., n-1, n (i is an integer between 0 and n)), and the number of times the phase change value PHASE [n] is used is G._{n, 1}When, &lt;Condition # C09&gt; 2 × G_0,1= G_1,1= . . . = G_{i, 1}= . . . = G_{n, 1}That is, 2 × G_0,1= G_{a, 1}, (For a, where a = 1,2, ···, n-1, n (a is an integer between 1 and n)), and the bits that make up the second coded block G the number of times to use the phase change value PHASE [0] when transmitting all_0,2, The number of times to use the phase change value PHASE [1] is G_1,2、G the number of times to use the phase change value PHASE [i]_{i, 2}(i = 0,1,2, ..., n-1, n (i is an integer between 0 and n)), and the number of times the phase change value PHASE [n] is used is G._{n, 2}When, &lt;Condition # C10&gt; 2 × G_0,2= G_1,2= . . . = G_{i, 2}= . . . = G_{n, 2}That is, 2 × G_0,2= G_{a, 2}, (For a, where a = 1,2, ..., n-1, n (a is an integer between 1 and n)).

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, &lt;condition # C05&gt; &lt;condition # C06&gt; &lt;conditions are used in the supported modulation methods. It is good if # C07&gt; (&lt;condition # C08&gt; &lt;condition # C09&gt; &lt;condition # C10&gt;) is satisfied.

However, when multiple modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy &lt;Condition # C05&gt; &lt;Condition # C06&gt; &lt;Condition # C07&gt; (&lt;Condition # C08&gt; &lt;Condition # C09&gt; &lt;Condition # C10&gt;). In this case, the following conditions should be satisfied instead of &lt;Condition # C05&gt; &lt;Condition # C06&gt; &lt;Condition # C07&gt;.

&lt;Condition # C11&gt; K_aAnd K_{b b}The difference between is 0 or 1, that is, | K_aK_{b b}| Is 0 or 1 (for a, b, but a, b = 0,1,2, ..., 2n-1,2n (a is an integer between 0 and 2n, b is between 0 and 2n) Integer), a b) &lt;condition # C12&gt; K_{a, 1}And K_{b, 1}The difference between is 0 or 1, that is, | K_{a, 1}K_{b, 1}| Is 0 or 1 (for a, b, but a, b = 0,1,2, ..., 2n-1,2n (a is an integer between 0 and 2n, b is between 0 and 2n) Integer), a b) &lt;condition # C13&gt; K_{a, 2}And K_{b, 2}The difference between is 0 or 1, that is, | K_{a, 2}K_{b, 2}| Is 0 or 1 (for a, b, but a, b = 0,1,2, ..., 2n-1,2n (a is an integer between 0 and 2n, b is between 0 and 2n) Integer), a b) &lt;Condition # C11&gt; &lt;Condition # C12&gt; &lt;Condition # C13&gt; can be expressed differently as follows.

&lt;Condition # C14&gt; G_aAnd G_{b b}The difference between is 0 or 1 or 2, that is, | G_aG_{b b}| Is 0 or 1 or 2 (for a, b, but a, b = 1,2, ..., n-1, n (a is an integer from 1 to n, b is from 1 to n) Integer), a b) and 2 × G₀And G_aThe difference between is 0 or 1 or 2, that is, | 2 × G₀G_a| Is 0 or 1 or 2 (for a, where a = 1,2, ..., n-1, n (a is an integer between 1 and n)) &lt;Condition # C15&gt; G_{a, 1}And G_{b, 1}The difference between is 0 or 1 or 2, that is, | G_{a, 1}G_{b, 1}| Is 0 or 1 or 2 (for a, b, but a, b = 1,2, ..., n-1, n (a is an integer from 1 to n, b is from 1 to n) Integer), a b) and 2 × G_0,1And G_{a, 1}The difference between is 0 or 1 or 2, that is, | 2 × G_0,1G_{a, 1}| Is 0 or 1 or 2 (for a, where a = 1,2, ..., n-1, n (a is an integer between 1 and n)) &lt;Condition # C16&gt; G_{a, 2}And G_{b, 2}The difference between is 0 or 1 or 2, that is, | G_{a, 2}G_{b, 2}| Is 0 or 1 or 2 (for a, b, but a, b = 1,2, ..., n-1, n (a is an integer from 1 to n, b is from 1 to n) Integer), a b) and 2 × G_0,2And G_{a, 2}The difference between is 0 or 1 or 2, that is, | 2 × G_0,2G_{a, 2}| Is 0 or 1 or 2 (for a, where a = 1,2, ···, n-1, n (a is an integer between 1 and n)) and so on after encoding. By associating the block with the phase change value, the phase change value used for transmitting the coded block is not biased, so that the effect of improving the data reception quality in the receiving device can be obtained. can.

In the present embodiment, in the method of regularly changing the phase, N phase change values (or phase change sets) are required for the phase change method having a period N. At this time, as N phase change values (or phase change sets), P [0], P [1], P [2], ..., P [N-2], P [N-1] However, there is also a method of arranging P [0], P [1], P [2], ..., P [N-2], P [N-1] in this order in the frequency axis direction. However, it is not always limited to this, and N phase change values (or phase change sets) P [0], P [1], P [2], ..., P [N-2], P Similar to the first embodiment of [N-1], the phase can be changed by arranging symbols on the blocks on the time axis and the frequency-time axis. Although the method of changing the phase of the period N is described, the same effect can be obtained by randomly using N phase change values (or phase change sets), that is, it is not always a rule. It is not necessary to use N phase change values (or phase change sets) so as to have a certain period, but the condition described above is satisfied in order to obtain high data reception quality in the receiving device. , Will be important.

In addition, there are modes of spatial multiplex MIMO transmission method, MIMO transmission method with fixed precoding matrix, spatiotemporal block coding method, transmission of only one stream, and method of changing the phase regularly, and the transmission device (broadcasting station, The base station) may be able to select one of these transmission methods from these modes.

As shown in Non-Patent Document 3, the spatial multiplex MIMO transmission method is a method of transmitting signals s1 and s2 mapped by the selected modulation method from different antennas, and the precoding matrix is fixed. The MIMO transmission method is a method in which only precoding is performed (phase change is not performed). The space-time block coding method is a transmission method shown in Non-Patent Documents 9, 16 and 17. Transmission of only one stream is a method of transmitting the signal of the signal s1 mapped by the selected modulation method from the antenna after performing predetermined processing.

In addition, a multi-carrier transmission method such as OFDM is used, and a first carrier group composed of a plurality of carriers, a second carrier group different from the first carrier group composed of a plurality of carriers, ... Multi-carrier transmission is realized by multiple carrier groups, such as spatial multiplex MIMO transmission method, MIMO transmission method with fixed precoding matrix, spatiotemporal block coding method, transmission of only one stream, for each carrier group. It may be set to any one of the methods of regularly changing the phase, and in particular, in the (sub) carrier group in which the method of regularly changing the phase is selected, the present embodiment may be carried out.

When the phase change is performed on one of the precoded baseband signals, for example, when the phase change value of P [i] is "X radian", FIGS. 3, 4, 6, and 12 , In the phase change section in FIGS. 25, 29, 51, 53, e^jXWill be multiplied by the precoded baseband signal z2'. Then, when the phase change is performed on the baseband signals after both precoding, for example, when the phase change set of P [i] is "X radian" and "Y radian", FIGS. 26 and 27, In the phase change section in FIGS. 28, 52, and 54, e^jXWill be multiplied by the precoded baseband signal z2', e^jYWill be multiplied by the precoded baseband signal z1'.

(Embodiment C7) In the present embodiment, as shown in Non-Patent Documents 12 to 15, QC (Quasi Cyclic) LDPC (Low-Density Parity-Check) code (however, QC-LDPC) A block code such as an LDPC (block) code that is not a code), a block code such as a concatenated code between an LDPC code and a BCH code (Bose-Chaudhuri-Hocquenghem code), a turbo code, or a block code such as Duo-Binary Turbo Code is used. The case where the embodiment A1 and the embodiment C6 are generalized will be described. Here, as an example, a case where two streams of s1 and s2 are transmitted will be described as an example. However, when coding is performed using the block code, when control information or the like is not required, the number of bits constituting the coded block is the number of bits constituting the block code (however, among these, the following It may contain control information and the like as described.) When encoding is performed using a block code, control information, etc. (for example, CRC (cyclic redundancy)) When check), transmission parameters, etc.) are required, the number of bits constituting the coded block may be the sum of the number of bits constituting the block code and the number of bits such as control information.

FIG. 34 is a diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used. FIG. 34 shows, for example, a "block code" in the case where two streams s1 and s2 are transmitted and the transmitter has one encoder, as shown in the transmitter of FIG. It is a figure showing the change in the number of symbols and the number of slots required for one coded block when used. " (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 34, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Since the transmitter in FIG. 4 transmits two streams at the same time, when the modulation method is QPSK, the above 3000 symbols are assigned 1500 symbols to s1 and 1500 symbols to s2. 1500 slots (named "slots" here) are required to transmit 1500 symbols to be transmitted in s1 and 1500 symbols to be transmitted in s2.

Similarly, when the modulation scheme is 16QAM, 750 slots are required to transmit all the bits that make up one coded block, and when the modulation scheme is 64QAM, all that make up one block. 500 slots are required to send the bits.

Next, the relationship between the slot and the phase defined above will be described in the method of regularly changing the phase.

Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase with a period of 5 is 5. The phase change value (or phase change set) prepared for the method of regularly changing the phase in period 5 is P [0], P [1], P [2], P [3], P [4. ]. However, P [0], P [1], P [2], P [3], P [4] may contain at least two or more different phase change values (P [0]). , P [1], P [2], P [3], P [4] may contain the same phase change value). (As shown in FIG. 6, when the phase change is performed only on the baseband signal z2'after precoding, five phase change values may be prepared in order to perform the phase change in the period 5. Also, FIG. 26. When performing phase change for both the precoded baseband signals z1'and z2', two phase change values are required for one slot. These two phase change values are phased. It is called a change set. Therefore, in this case, in order to perform a phase change with a period of 5, it is sufficient to prepare five phase change sets).

When the modulation method is QPSK, in the 1500 slots described above for transmitting 6000 bits constituting one coded block, the slots using the phase change value P [0] are 300 slots and the phase. The slot using the change value P [1] is 300 slots, the slot using the phase change value P [2] is 300 slots, the slot using the phase change value P [3] is 300 slots, and the phase change value P [4]. ] Must be used in 300 slots. This is because if there is a deviation in the phase change value used, the reception quality of the data is greatly affected by the phase change value using a large number.

Similarly, when the modulation scheme is 16QAM, the phase change value P [0] in the 750 slots mentioned above for transmitting the 6000 bits that make up one coded block.

There are 150 slots that use the phase change value P [1], 150 slots that use the phase change value P [1], 150 slots that use the phase change value P [2], and slots that use the phase change value P [3]. 150 slots, the slot using the phase change value P [4] must be 150 slots.

Similarly, when the modulation method is 64QAM, in the 500 slots described above for transmitting 6000 bits constituting one coded block, 100 slots use the phase change value P [0]. 100 slots for slots, 100 slots for phase change value P [1], 100 slots for phase change value P [2], 100 slots for phase change value P [3], phase change value The number of slots that use P [4] must be 100.

As described above, the phase change values P [0], P [1], ..., P [N-2], P [N-1] in the phase change method in which the phase change values are regularly switched in the period N. It shall be expressed as. However, it is assumed that P [0], P [1], ..., P [N-2], P [N-1] are composed of at least two or more different phase change values. (P [0], P [1], ..., P [N-2], P [N-1] may contain the same phase change value.) One coded block K the number of slots that use the phase change value P [0] when transmitting all the bits that make up₀, K the number of slots that use the phase change value P [1]_1、K the number of slots that use the phase change value P [i]_i(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), and the number of slots that use the phase change value P [N-1] is K._N-1When &lt;Condition # C17&gt; K₀= K₁= . . . = K_i= . . . = K_N-1, That is, K_a= K_{b b}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b).

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, it is preferable that &lt;condition # C17&gt; is satisfied in the supported modulation methods. ..

However, when multiple modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy &lt;Condition # C17&gt;. In this case, the following conditions should be satisfied instead of &lt;Condition # C17&gt;.

&lt;Condition # C18&gt; K_aAnd K_{b b}The difference between is 0 or 1, that is, | K_aK_{b b}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ···, N-1 (a is an integer greater than or equal to 0 and less than or equal to N-1, b is greater than or equal to 0 and N- Integers of 1 or less), a b) Fig. 35 is a diagram showing changes in the number of symbols and the number of slots required for two coded blocks when a block code is used. FIG. 35 shows the case where two streams of s1 and s2 are transmitted and the transmitter has two encoders as shown in the transmitter of FIG. 3 and the transmitter of FIG. "A diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used". (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 35, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Then, in the transmitter of FIG. 3 and the transmitter of FIG. 12, two streams are transmitted at the same time, and since there are two encoders, the two streams transmit different code blocks. become. Therefore, when the modulation method is QPSK, s1 and s2 transmit two coded blocks within the same interval. Therefore, for example, s1 transmits the first coded block, and s2 transmits the first coded block. Since 2 coded blocks will be transmitted, 3000 slots will be required to transmit the 1st and 2nd coded blocks.

Similarly, when the modulation scheme is 16QAM, 1500 slots are required to transmit all the bits that make up the two encoded blocks, and when the modulation scheme is 64QAM, all that make up the two blocks. 1000 slots are required to send the bits.

Next, the relationship between the slot and the phase defined above will be described in the method of regularly changing the phase.

Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase with a period of 5 is 5. That is, for the phase change section of the transmitter in FIG. 4, five phase change values (or phase change sets) for period 5 P [0], P [1], P [2], P [3. ], P [4] shall be prepared. However, P [0], P [1], P [2], P [3], P [4] may contain at least two or more different phase change values (P [0]). , P [1], P [2], P [3], The same phase change value may be included in P [4]. ). (As shown in FIG. 6, when the phase change is performed only on the baseband signal z2'after precoding, five phase change values may be prepared in order to perform the phase change in the period 5. Also, FIG. 26. When performing phase change for both the precoded baseband signals z1'and z2', two phase change values are required for one slot. These two phase change values are phased. It is called a change set. Therefore, in this case, in order to perform a phase change with a period of 5, it is sufficient to prepare five phase change sets). Five phase change values (or phase change sets) for period 5 are represented as P [0], P [1], P [2], P [3], P [4].

When the modulation method is QPSK, in the 3000 slots described above for transmitting the number of bits 6000 × 2 bits that make up the two coded blocks, the slot that uses the phase change value P [0] is 600 slots. , The slot that uses the phase change value P [1] is 600 slots, the slot that uses the phase change value P [2] is 600 slots, the slot that uses the phase change value P [3] is 600 slots, and the phase change value P The slot using [4] must be 600 slots. This is because if there is a deviation in the phase change value used, the reception quality of the data is greatly affected by the phase change value using a large number.

Also, in order to transmit the first coded block, the slot using the phase change value P [0] is 600 times, the slot using the phase change value P [1] is 600 times, and the phase change value P [2]. ] Must be 600 times, the slot using the phase change value P [3] 600 times, the slot using the phase change value P [4] 600 times, and the second Slots that use the phase change value P [0] 600 times, slots that use the phase change value P [1] 600 times, and slots that use the phase change value P [2] to transmit the coded block. Is 600 times, the slot using the phase change value P [3] is 600 times, and the slot using the phase change value P [4] is 600 times.

Similarly, when the modulation method is 16QAM, the slot using the phase change value P [0] in the 1500 slot described above for transmitting the number of bits 6000 × 2 bits constituting the two coded blocks. Is 300 slots, the slot that uses the phase change value P [1] is 300 slots, the slot that uses the phase change value P [2] is 300 slots, the slot that uses the phase change value P [3] is 300 slots, and the phase. The slot using the change value P [4] must be 300 slots.

Also, in order to transmit the first coded block, the slot using the phase change value P [0] is 300 times, the slot using the phase change value P [1] is 300 times, and the phase change value P [2]. ] Must be used 300 times, the slot using the phase change value P [3] 300 times, the slot using the phase change value P [4] 300 times, and the second code. The slot using the phase change value P [0] is 300 times, the slot using the phase change value P [1] is 300 times, and the slot using the phase change value P [2] is used to transmit the conversion block. It is preferable that the number of slots using the phase change value P [3] is 300 times, and the number of slots using the phase change value P [4] is 300 times.

Similarly, when the modulation method is 64QAM, the slot using the phase change value P [0] in the 1000 slots described above for transmitting the number of bits 6000 × 2 bits constituting the two coded blocks. 200 slots, 200 slots using the phase change value P [1], 200 slots using the phase change value P [2], 200 slots using the phase change value P [3], phase The slot using the change value P [4] must be 200 slots.

Also, in order to transmit the first coded block, the slot using the phase change value P [0] is 200 times, the slot using the phase change value P [1] is 200 times, and the phase change value P [2]. ] Must be used 200 times, the slot using the phase change value P [3] 200 times, the slot using the phase change value P [4] 200 times, and the second code. The slot that uses the phase change value P [0] 200 times, the slot that uses the phase change value P [1] 200 times, and the slot that uses the phase change value P [2] to transmit the conversion block It is preferable that the number of slots using the phase change value P [3] is 200 times, and the number of slots using the phase change value P [4] is 200 times.

As described above, the phase change values in the phase change method for regularly switching the phase change values in the period N are P [0], P [1], P [2], ..., P [N-2], It shall be expressed as P [N-1]. However, P [0], P [1], P [2], ..., P [N-2], P [N-1] are composed of at least two or more different phase change values. And. (P [0], P [1], P [2], ..., P [N-2], P [N-1] may contain the same phase change value.) Two The number of slots that use the phase change value P [0] when transmitting all the bits that make up the encoded block is K.₀, K the number of slots that use the phase change value P [1]_1、K the number of slots that use the phase change value P [i]_i(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), and the number of slots that use the phase change value P [N-1] is K._N-1When &lt;Condition # C19&gt; K₀= K₁= . . . = K_i= . . . = K_N-1, That is, K_a= K_{b b}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b), and the number of times the phase change value P [0] is used when transmitting all the bits constituting the first encoded block is K._0,1, K how many times to use the phase change value P [1]_1,1、K the number of times to use the phase change value P [i]_{i, 1}(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), the number of times the phase change value P [N-1] is used is K._N-1,1When &lt;Condition # C20&gt; K_0,1= K_1,1= . . . = K_{i, 1}= . . . = K_N-1,1, That is, K_{a, 1}= K_{b, 1}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b), and the number of times the phase change value P [0] is used when transmitting all the bits that make up the second coded block is K._0,2, K how many times to use the phase change value P [1]_1,2、K the number of times to use the phase change value P [i]_{i, 2}(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), the number of times the phase change value P [N-1] is used is K._N-1,2When &lt;Condition # C21&gt; K_0,2= K_1,2= . . . = K_{i, 2}= . . . = K_N-1,2, That is, K_{a, 2}= K_{b, 2}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b).

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, &lt;condition # C19&gt; &lt;condition # C20&gt; &lt;conditions are used in the supported modulation methods. It would be good if # C21&gt; was established.

However, when multiple modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy &lt;Condition # C19&gt; &lt;Condition # C20&gt; &lt;Condition # C21&gt;. In this case, the following conditions should be satisfied instead of &lt;Condition # C19&gt; &lt;Condition # C20&gt; &lt;Condition # C21&gt;.

&lt;Condition # C22&gt; K_aAnd K_{b b}The difference between is 0 or 1, that is, | K_aK_{b b}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ..., N-1 (a is an integer greater than or equal to 0 and less than or equal to N-1, b is greater than or equal to 0 and N- Integer less than or equal to 1), a b) &lt;condition # C23&gt; K_{a, 1}And K_{b, 1}The difference between is 0 or 1, that is, | K_{a, 1}K_{b, 1}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ..., N-1 (a is an integer greater than or equal to 0 and less than or equal to N-1, b is greater than or equal to 0 and N- Integer less than or equal to 1), a b) &lt;condition # C24&gt; K_{a, 2}And K_{b, 2}The difference between is 0 or 1, that is, | K_{a, 2}K_{b, 2}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is between 0 and N-) Integers of 1 or less), a b) By associating the coded block with the phase change value as described above, there is no bias in the phase change value used to transmit the coded block. Therefore, in the receiving device, it is possible to obtain the effect of improving the reception quality of data.

In the present embodiment, in the method of regularly changing the phase, N phase change values (or phase change sets) are required for the phase change method having a period N. At this time, as N phase change values (or phase change sets), P [0], P [1], P [2], ..., P [N-2], P [N-1] However, there is also a method of arranging P [0], P [1], P [2], ..., P [N-2], P [N-1] in this order in the frequency axis direction. However, it is not always limited to this, and N phase change values (or phase change sets) P [0], P [1], P [2], ..., P [N-2], P Similar to the first embodiment of [N-1], the phase can be changed by arranging symbols on the blocks on the time axis and the frequency-time axis. Although the method of changing the phase of the period N is described, the same effect can be obtained by randomly using N phase change values (or phase change sets), that is, it is not always a rule. It is not necessary to use N phase change values (or phase change sets) so as to have a certain period, but the condition described above is satisfied in order to obtain high data reception quality in the receiving device. , Will be important.

In addition, there are modes of spatial multiplex MIMO transmission method, MIMO transmission method with fixed precoding matrix, spatiotemporal block coding method, transmission of only one stream, and method of changing the phase regularly, and the transmission device (broadcasting station, The base station) may be able to select one of these transmission methods from these modes.

As shown in Non-Patent Document 3, the spatial multiplex MIMO transmission method is a method of transmitting signals s1 and s2 mapped by the selected modulation method from different antennas, and the precoding matrix is fixed. The MIMO transmission method is a method in which only precoding is performed (phase change is not performed). The space-time block coding method is a transmission method shown in Non-Patent Documents 9, 16 and 17. Transmission of only one stream is a method of transmitting the signal of the signal s1 mapped by the selected modulation method from the antenna after performing predetermined processing.

In addition, a multi-carrier transmission method such as OFDM is used, and a first carrier group composed of a plurality of carriers, a second carrier group different from the first carrier group composed of a plurality of carriers, ... Multi-carrier transmission is realized by multiple carrier groups, such as spatial multiplex MIMO transmission method, MIMO transmission method with fixed precoding matrix, spatiotemporal block coding method, transmission of only one stream, for each carrier group. It may be set to any one of the methods of regularly changing the phase, and in particular, in the (sub) carrier group in which the method of regularly changing the phase is selected, the present embodiment may be carried out.

When the phase change is performed on one of the precoded baseband signals, for example, when the phase change value of P [i] is "X radian", FIGS. 3, 4, 6, and 12 , In the phase change section in FIGS. 25, 29, 51, 53, e^jXWill be multiplied by the precoded baseband signal z2'. Then, when the phase change is performed on the baseband signals after both precoding, for example, when the phase change set of P [i] is "X radian" and "Y radian", FIGS. 26 and 27, In the phase change section in FIGS. 28, 52, and 54, e^jXWill be multiplied by the precoded baseband signal z2', e^jYWill be multiplied by the precoded baseband signal z1'.

(Embodiment D1) In the present embodiment, first, a modified example of the first embodiment will be described. FIG. 67 is an example of the configuration of the transmission device according to the present embodiment, and the same reference numerals are given to those that operate in the same manner as in FIG. 3, and thereafter, the same as in the description in FIG. The description of the operation element part will be omitted. The difference between FIG. 67 and FIG. 3 is that the baseband signal replacement section 6702 is inserted immediately after the weighting synthesis section. Therefore, in the following, the operation around the baseband signal replacement unit 6702 will be mainly described.

FIG. 21 shows the configuration of the weighted composition unit (308A, 308B). The area surrounded by the dotted line in FIG. 21 is the weighted composition unit. The baseband signal 307A is multiplied by w11 to generate w11 · s1 (t) and multiplied by w21 to generate w21 · s1 (t). Similarly, the baseband signal 307B multiplies w12 to generate w12 · s2 (t) and multiplies w22 to generate w22 · s2 (t). Next, we obtain z1 (t) = w11 · s1 (t) + w12 · s2 (t) and z2 (t) = w21 · s1 (t) + w22 · s2 (t). At this time, s1 (t) and s2 (t) are BPSK (Binary Phase Shift Keying), QPSK, 8PSK (8 Phase Shift Keying), 16QAM, 32QAM (32 Quadrature Amplitude), as can be seen from the description of the first embodiment. Modulation), 64QAM, 256QAM, 16APSK (16 Amplitude Phase Shift) It is a baseband signal of a modulation method such as Keying). Here, both weighting and synthesizing units shall execute weighting using a fixed precoding matrix, and as an example of the precoding matrix, under the conditions of the following equation (63) or equation (64). There is a method using equation (62). However, this is an example, and the value of α is not limited to the equation (63) and the equation (64), and another value, for example, α may be 1, and α may be 0. (Α may be a real number greater than or equal to 0, and α may be an imaginary number).

The precoding matrix is

<math num="62"><img file="JP2022017567A_D0063.tif" /></math>

However, in the above equation (62), α is

<math num="63"><img file="JP2022017567A_D0064.tif" /></math>

Is.

Alternatively, in the above equation (62), α is

<math num="64"><img file="JP2022017567A_D0065.tif" /></math>

Is.

Also, the precoding matrix is not limited to Eq. (62).

<math num="65"><img file="JP2022017567A_D0066.tif" /></math>

a = Ae^jδ11, B = Be^jδ12, C = Ce^jδ21, D = De^jδ22It should be represented by. Further, any one of a, b, c, and d may be "zero". For example, (1) a is zero, b, c, d are non-zero, (2) b is zero, a, c, d are non-zero, (3) c is zero, a, b. , D may be non-zero, (4) d may be zero, and a, b, c may be non-zero.

Further, two values of a, b, c and d may be set to zero. For example, it is effective that (1) a and d are zero and b and c are not zero, and (2) b and c are zero and a and d are not zero.

When any one of the modulation method, the error correction code, and the coding rate thereof is changed, the precoding matrix to be used may be set or changed, and the precoding matrix may be used fixedly.

Next, the baseband signal replacement unit 6702 in FIG. 67 will be described. The baseband signal replacement unit 6702 receives the signal 309A after weighting synthesis and the signal 316B after weighting synthesis as inputs, performs baseband signal replacement, and outputs the baseband signal 6701A after replacement and the baseband signal 6701B after replacement. .. The details of the replacement of the baseband signal are as described with reference to FIG. 55. In the replacement of the baseband signal of the present embodiment, the signal for replacing the baseband signal is different from that in FIG. 55. Hereinafter, the replacement of the baseband signal of the present embodiment will be described with reference to FIG. 68.

In FIG. 68, the common mode I component I of the signal 309A (p1 (i)) after the weighted synthesis._p1(i) Q for the orthogonal Q component_p1Representing (i), common mode I component I of signal 316B (p2 (i)) after weighted synthesis_p2(i) Q for the orthogonal Q component_p2It is expressed as (i). Then, after the replacement, the common mode I component I of the baseband signal 6701A (q1 (i))_q1(i) Q for the orthogonal Q component_q1Represents as (i), and after replacement, the in-phase I component I of the baseband signal 6701B (q2 (i))_q2(i) Q for the orthogonal Q component_q2It is expressed as (i). (However, i represents the order (time or frequency (carrier)). In the example of FIG. 67, i is time, but when FIG. 67 uses the OFDM method as shown in FIG. When applied, i may be a frequency (carrier). This point will be described later.) At this time, the baseband signal replacement unit 6702 replaces the baseband components. I the in-phase component of signal q1 (i)_p1(i) Q for orthogonal components_p2(i), I the in-phase component of the baseband signal q2 (i) after replacement_p2(i) Q for orthogonal components_p1As (i), the modulated signal corresponding to the replaced baseband signal q1 (i) is transmitted from the transmitting antenna 1, and the modulated signal corresponding to the replaced baseband signal q2 (i) is transmitted from the transmitting antenna 2 at the same time. The modulated signal corresponding to the replaced baseband signal q1 (i) and the replaced baseband signal q2 (i) are transmitted from different antennas at the same time using the same frequency, such as transmitting using the frequency. You may send it. In addition, . I set the in-phase component of the baseband signal q1 (i) after replacement._p1(i), I the orthogonal component_p2(i) Q for the in-phase component of the baseband signal q2 (i) after replacement_p1(i) Q for orthogonal components_p2(i) . I set the in-phase component of the baseband signal q1 (i) after replacement._p2(i), I the orthogonal component_p1(i) Q for the in-phase component of the baseband signal q2 (i) after replacement_p1(i) Q for orthogonal components_p2(i) . I set the in-phase component of the baseband signal q1 (i) after replacement._p1(i), I the orthogonal component_p2(i) Q for the in-phase component of the baseband signal q2 (i) after replacement_p2(i) Q for orthogonal components_p1(i) . I set the in-phase component of the baseband signal q1 (i) after replacement._p2(i), I the orthogonal component_p1(i) Q for the in-phase component of the baseband signal q2 (i) after replacement_p2(i) Q for orthogonal components_p1(i) . I set the in-phase component of the baseband signal q1 (i) after replacement._p1(i) Q for orthogonal components_p2(i) Q for the in-phase component of the baseband signal q2 (i) after replacement_p1(i), I the orthogonal component_p2(i) . Q the in-phase component of the baseband signal q1 (i) after replacement_p2(i), I the orthogonal component_p1(i), I the in-phase component of the baseband signal q2 (i) after replacement_p2(i) Q for orthogonal components_p1(i) . Q the in-phase component of the baseband signal q1 (i) after replacement_p2(i), I the orthogonal component_p1(i) Q for the in-phase component of the baseband signal q2 (i) after replacement_p1(i), I the orthogonal component_p2(i) . I set the in-phase component of the baseband signal q2 (i) after replacement._p1(i), I the orthogonal component_p2(i) Q for the in-phase component of the baseband signal q1 (i) after replacement_p1(i) Q for orthogonal components_p2(i) . I set the in-phase component of the baseband signal q2 (i) after replacement._p2(i), I the orthogonal component_p1(i) Q for the in-phase component of the baseband signal q1 (i) after replacement_p1(i) Q for orthogonal components_p2(i) . I set the in-phase component of the baseband signal q2 (i) after replacement._p1(i), I the orthogonal component_p2(i) Q for the in-phase component of the baseband signal q1 (i) after replacement_p2(i) Q for orthogonal components_p1(i) . I set the in-phase component of the baseband signal q2 (i) after replacement._p2(i), I the orthogonal component_p1(i) Q for the in-phase component of the baseband signal q1 (i) after replacement_p2(i) Q for orthogonal components_p1(i) . I set the in-phase component of the baseband signal q2 (i) after replacement._p1(i) Q for orthogonal components_p2(i), I the in-phase component of the baseband signal q1 (i) after replacement_p2(i) Q for orthogonal components_p1(i) . I set the in-phase component of the baseband signal q2 (i) after replacement._p1(i) Q for orthogonal components_p2(i) Q for the in-phase component of the baseband signal q1 (i) after replacement_p1(i), I the orthogonal component_p2(i) . Q for the in-phase component of the baseband signal q2 (i) after replacement_p2(i), I the orthogonal component_p1(i), I the in-phase component of the baseband signal q1 (i) after replacement_p2(i) Q for orthogonal components_p1(i) . Q for the in-phase component of the baseband signal q2 (i) after replacement_p2(i), I the orthogonal component_p1(i) Q for the in-phase component of the baseband signal q1 (i) after replacement_p1(i), I the orthogonal component_p2It may be (i). Further, in the above description, the replacement of the in-phase component and the orthogonal component of the signal 309A after the weighted synthesis and the signal 316B after the weighted synthesis has been described, but the present invention is not limited to this, and the signal in-phase component and the orthogonal component having more than two signals are described. It is also possible to replace.

Further, in the above example, the replacement of the baseband signals at the same time (same frequency ((sub) carrier)) is described, but the replacement of the baseband signals at the same time (same frequency ((sub) carrier)) is described. It does not have to be. As an example, it can be described as follows.

. I set the in-phase component of the baseband signal q1 (i) after replacement._p1(i + v), Q for orthogonal component_p2(i + w), I the in-phase component of the baseband signal q2 (i) after replacement_p2(i + w), Q for orthogonal component_p1(i + v) . I set the in-phase component of the baseband signal q1 (i) after replacement._p1(i + v), I the orthogonal component_p2(i + w), Q the in-phase component of the baseband signal q2 (i) after replacement_p1(i + v), Q for orthogonal component_p2(i + w) . I set the in-phase component of the baseband signal q1 (i) after replacement._p2(i + w), I the orthogonal component_p1(i + v), Q the in-phase component of the baseband signal q2 (i) after replacement_p1(i + v), Q for orthogonal component_p2(i + w) . I set the in-phase component of the baseband signal q1 (i) after replacement._p1(i + v), I the orthogonal component_p2(i + w), Q the in-phase component of the baseband signal q2 (i) after replacement_p2(i + w), Q for orthogonal component_p1(i + v) . I set the in-phase component of the baseband signal q1 (i) after replacement._p2(i + w), I the orthogonal component_p1(i + v), Q the in-phase component of the baseband signal q2 (i) after replacement_p2(i + w), Q for orthogonal component_p1(i + v) . I set the in-phase component of the baseband signal q1 (i) after replacement._p1(i + v), Q for orthogonal component_p2(i + w), Q the in-phase component of the baseband signal q2 (i) after replacement_p1(i + v), I the orthogonal component_p2(i + w) . Q the in-phase component of the baseband signal q1 (i) after replacement_p2(i + w), I the orthogonal component_p1(i + v), I the in-phase component of the baseband signal q2 (i) after replacement_p2(i + w), Q for orthogonal component_p1(i + v) . Q the in-phase component of the baseband signal q1 (i) after replacement_p2(i + w), I the orthogonal component_p1(i + v), Q the in-phase component of the baseband signal q2 (i) after replacement_p1(i + v), I the orthogonal component_p2(i + w) . I set the in-phase component of the baseband signal q2 (i) after replacement._p1(i + v), I the orthogonal component_p2(i + w), Q the in-phase component of the baseband signal q1 (i) after replacement_p1(i + v), Q for orthogonal component_p2(i + w) . I set the in-phase component of the baseband signal q2 (i) after replacement._p2(i + w), I the orthogonal component_p1(i + v), Q the in-phase component of the baseband signal q1 (i) after replacement_p1(i + v), Q for orthogonal component_p2(i + w) . I set the in-phase component of the baseband signal q2 (i) after replacement._p1(i + v), I the orthogonal component_p2(i + w), Q the in-phase component of the baseband signal q1 (i) after replacement_p2(i + w), Q for orthogonal component_p1(i + v) . I set the in-phase component of the baseband signal q2 (i) after replacement._p2(i + w), I the orthogonal component_p1(i + v), Q the in-phase component of the baseband signal q1 (i) after replacement_p2(i + w), Q for orthogonal component_p1(i + v) . I set the in-phase component of the baseband signal q2 (i) after replacement._p1(i + v), Q for orthogonal component_p2(i + w), I the in-phase component of the baseband signal q1 (i) after replacement_p2(i + w), Q for orthogonal component_p1(i + v) . I set the in-phase component of the baseband signal q2 (i) after replacement._p1(i + v), Q for orthogonal component_p2(i + w), Q the in-phase component of the baseband signal q1 (i) after replacement_p1(i + v), I the orthogonal component_p2(i + w) . Q for the in-phase component of the baseband signal q2 (i) after replacement_p2(i + w), I the orthogonal component_p1(i + v), I the in-phase component of the baseband signal q1 (i) after replacement_p2(i + w), Q for orthogonal component_p1(i + v) . Q the in-phase component of the baseband signal q2 (i) after replacement_p2(i + w), I the orthogonal component_p1(i + v), Q the in-phase component of the baseband signal q1 (i) after replacement_p1(i + v), I the orthogonal component_p2(i + w) Homeomorphic I component I of signal 309A (p1 (i)) after weighted synthesis_p1(i) Q for the orthogonal Q component_p1Representing (i), common mode I component I of signal 316B (p2 (i)) after weighted synthesis_p2(i) Q for the orthogonal Q component_p2It is expressed as (i). Then, after the replacement, the common mode I component I of the baseband signal 6701A (q1 (i))_q1(i) Q for the orthogonal Q component_q1Represents as (i), and after replacement, the in-phase I component I of the baseband signal 6701B (q2 (i))_q2(i) Q for the orthogonal Q component_q2It is expressed as (i).

FIG. 68 is a diagram for explaining the above description, and as described above, FIG. 68 is a common mode I component I of the signal 309A (p1 (i)) after weighted synthesis._p1(i) Q for the orthogonal Q component_p1Representing (i), common mode I component I of signal 316B (p2 (i)) after weighted synthesis_p2(i) Q for the orthogonal Q component_p2It is expressed as (i). Then, after the replacement, the common mode I component I of the baseband signal 6701A (q1 (i))_q1(i) Q for the orthogonal Q component_q1Represents as (i), and after replacement, the in-phase I component I of the baseband signal 6701B (q2 (i))_q2(i) Q for the orthogonal Q component_q2It is expressed as (i).

Then, after replacement, the common mode I component I of the baseband signal 6701A (q1 (i))_q1(i) Q for the orthogonal Q component_q1(i) and common mode I component I of the baseband signal 6701B (q2 (i)) after replacement_q2(i) Q for the orthogonal Q component_q2(i) It shall be represented by any of the above.

Then, the modulated signal corresponding to the replaced baseband signal 6701A (q1 (i)) is transmitted from the transmitting antenna 312A, and the modulated signal corresponding to the replaced baseband signal 6701B (q2 (i)) is transmitted from the transmitting antenna 312B at the same time. A modulated signal corresponding to the replaced baseband signal 6701A (q1 (i)) and a modulated signal corresponding to the replaced baseband signal 6701B (q2 (i)) are transmitted from different antennas, such as transmitting using the same frequency. , Will be transmitted at the same time and using the same frequency.

The phase change unit 317B receives the replacement baseband signal 6701B and the information 315 regarding the signal processing method as inputs, and periodically changes the phase of the replacement baseband signal 6701B and outputs the signal. To change regularly means to change the phase in a predetermined period (for example, every n symbols (n is an integer of 1 or more) or every predetermined time) according to a predetermined phase change pattern. .. The details of the phase change pattern are as described in the fourth embodiment.

The radio unit 310B receives the phase-changed signal 309B as an input, performs processing such as quadrature modulation, band limitation, frequency conversion, and amplification, outputs the transmission signal 311B, and the transmission signal 311B is output as a radio wave from the antenna 312B. To.

Note that FIG. 67 has been described with the case where there are a plurality of encoders as shown in FIG. 3, but with respect to FIG. 67, as shown in FIG. 4, a encoder and a distributor are provided, and a signal output by the distributor is provided. Each of these is used as an input signal of the interleaver, and thereafter, even in the case of following the configuration of FIG. 67, the operation can be performed in the same manner as described above.

FIG. 5 shows an example of a frame configuration on the time axis of the transmitter according to the present embodiment. Symbol 500_1 is a symbol for notifying the receiving device of the transmission method, for example, an error correction method used for transmitting a data symbol, information on its coding rate, and a modulation method used for transmitting the data symbol. Information etc. is transmitted.

Symbol 501_1 is a symbol for estimating the channel variation of the modulated signal z1 (t) {where t is time} transmitted by the transmitter. Symbol 502_1 is a data symbol transmitted by the modulation signal z1 (t) to symbol number u (on the time axis), and symbol 503_1 is a data symbol transmitted by modulation signal z1 (t) to symbol number u + 1.

Symbol 501_2 is a symbol for estimating the channel variation of the modulated signal z2 (t) {where t is time} transmitted by the transmitter. Symbol 502_2 is a data symbol transmitted by the modulation signal z2 (t) to the symbol number u, and symbol 503_2 is a data symbol transmitted by the modulation signal z2 (t) to the symbol number u + 1.

At this time, in the symbol at z1 (t) and the symbol at z2 (t), the symbols at the same time (same time) are transmitted from the transmitting antenna using the same (common) frequency.

The relationship between the modulated signal z1 (t) and the modulated signal z2 (t) transmitted by the transmitting device and the received signals r1 (t) and r2 (t) in the receiving device will be described.

In FIG. 5, 504 # 1 and 504 # 2 indicate the transmitting antenna in the transmitting device, 505 # 1 and 505 # 2 indicate the receiving antenna in the receiving device, and the transmitting device transmits the modulated signal z1 (t) to the transmitting antenna 504. # 1, the modulation signal z2 (t) is transmitted from the transmission antenna 504 # 2. At this time, it is assumed that the modulated signal z1 (t) and the modulated signal z2 (t) occupy the same (common) frequency (band). The channel fluctuations of each transmitting antenna of the transmitting device and each antenna of the receiving device are set to h11 (t), h12 (t), h21 (t), and h22 (t), respectively, and the reception received by the receiving antenna 505 # 1 of the receiving device. Assuming that the signal is r1 (t) and the received signal received by the receiving antenna 505 # 2 of the receiving device is r2 (t), the following relational expression is established.

<math num="66"><img file="JP2022017567A_D0067.tif" /></math>

FIG. 69 is a diagram related to the weighting method (precoding method), the baseband signal replacement, and the phase change method in the present embodiment, and the weighting synthesis unit 600 is the same as the weighting composition unit 308A in FIG. It is a weighted composition unit that integrates both of 308B. As shown in FIG. 69, streams s1 (t) and streams s2 (t) correspond to the baseband signals 307A and 307B in FIG. 3, that is, the base according to the mapping of modulation schemes such as QPSK, 16QAM, 64QAM. It becomes the common mode I component and the quadrature Q component of the band signal. Then, as in the frame configuration of FIG. 69, the stream s1 (t) represents the signal of the symbol number u as s1 (u), the signal of the symbol number u + 1 as s1 (u + 1), and so on. Similarly, the stream s2 (t) represents the signal with the symbol number u as s2 (u), the signal with the symbol number u + 1 as s2 (u + 1), and so on. Then, the weighting / combining unit 600 inputs the baseband signals 307A (s1 (t)) and 307B (s2 (t)) in FIG. 67 and the information 315 regarding the signal processing method, and weights according to the information 315 regarding the signal processing method. Is applied, and the signals 309A (p1 (t)) and 316B (p2 (t)) after the weighted composition shown in FIG. 67 are output.

At this time, p1 (t) can be expressed by the following equation (67), where W1 = (w11, w12) is the vector of the first row in the fixed precoding matrix F.

<math num="67"><img file="JP2022017567A_D0068.tif" /></math>

On the other hand, p2 (t) can be expressed by the following equation (68), where W2 = (w21, w22) is the vector of the second row in the precoding matrix F.

<math num="68"><img file="JP2022017567A_D0069.tif" /></math>

Therefore, the precoding matrix F can be expressed by the following equation.

<math num="69"><img file="JP2022017567A_D0070.tif" /></math>

After the replacement of the baseband signal, the common mode I component I of the baseband signal 6701A (q1 (i)) after the replacement_q1(i) Q for the orthogonal Q component_q1(i) and common mode I component I of the baseband signal 6701B (q2 (i)) after replacement_q2(i) Q for the orthogonal Q component_q2The relationship between (i) and p1 (t) and p2 (t) is as described above. Then, assuming that the phase change equation by the phase change unit is y (t), the baseband signal 309B (q2'(i)) after the phase change can be expressed by the following equation (70).

<math num="70"><img file="JP2022017567A_D0071.tif" /></math>

Here, y (t) is an equation for changing the phase according to a predetermined method. For example, assuming that the period is 4, the phase changing equation at time u is expressed by, for example, equation (71). be able to.

<math num="71"><img file="JP2022017567A_D0072.tif" /></math>

Similarly, the phase change equation at time u + 1 can be expressed by, for example, equation (72).

<math num="72"><img file="JP2022017567A_D0073.tif" /></math>

That is, the phase change equation at time u + k can be expressed by equation (73).

<math num="73"><img file="JP2022017567A_D0074.tif" /></math>

The regular phase change examples shown in Eqs. (71) to (73) are only examples.

The period of regular phase change is not limited to 4. The larger the number of cycles, the more it may be possible to promote the improvement of the reception performance (more accurately, error correction performance) of the receiving device (although it is not necessary to have a large cycle, 2). It is likely that you should avoid small values such as).

Further, in the phase change example shown in the above equations (71) to (73), a configuration is shown in which the phase is sequentially rotated by a predetermined phase (in the above equation, by π / 2), but the same phase amount is rotated. Instead, the phase may be changed randomly. For example, the phase of y (t) to be multiplied in the order shown in Eqs. (74) and (75) may be changed according to a predetermined period. What is important in the regular change of phase is that the phase of the modulated signal is changed regularly, and the degree of the changed phase is as uniform as possible, for example, from -π radian to π radian. On the other hand, although it is desirable to have a uniform distribution, it may be random.

<math num="74"><img file="JP2022017567A_D0075.tif" /></math>

<math num="75"><img file="JP2022017567A_D0076.tif" /></math>

As described above, the weighted synthesis unit 600 of FIG. 6 executes precoding using a predetermined fixed precoding weight, and the baseband signal replacement unit replaces the above-mentioned baseband signal to change the phase. The unit changes the phase of the input signal while regularly changing the degree of change.

In the LOS environment, the reception quality may be greatly improved by using a special precoding matrix, but depending on the direct wave situation, the special precoding matrix depends on the phase and amplitude component of the direct wave when it is received. different. However, there is a certain rule in the LOS environment, and if the phase of the transmitted signal is changed regularly according to this rule, the data reception quality is greatly improved. The present invention proposes a signal processing method for improving the LOS environment.

FIG. 7 shows an example of the configuration of the receiving device 700 according to the present embodiment. The radio unit 703_X receives the received signal 702_X received by the antenna 701_X as an input, performs processing such as frequency conversion and orthogonal demodulation, and outputs the baseband signal 704_X.

The channel variation estimation unit 705_1 in the modulated signal z1 transmitted by the transmitter takes the baseband signal 704_X as an input, extracts the reference symbol 501_1 for channel estimation in FIG. 5, and obtains the value corresponding to h11 in the equation (66). Estimate and output the channel estimation signal 706_1.

The channel variation estimation unit 705_2 in the modulated signal z2 transmitted by the transmitter takes the baseband signal 704_X as an input, extracts the reference symbol 501_2 for channel estimation in FIG. 5, and obtains the value corresponding to h12 in Eq. (66). Estimate and output the channel estimation signal 706_2.

The radio unit 703_Y receives the received signal 702_Y received by the antenna 701_Y as an input, performs processing such as frequency conversion and orthogonal demodulation, and outputs the baseband signal 704_Y.

The channel variation estimation unit 707_1 in the modulated signal z1 transmitted by the transmitter takes the baseband signal 704_Y as an input, extracts the reference symbol 501_1 for channel estimation in FIG. 5, and obtains the value corresponding to h21 in the equation (66). Estimate and output the channel estimation signal 708_1.

The channel variation estimation unit 707_2 in the modulated signal z2 transmitted by the transmitter takes the baseband signal 704_Y as an input, extracts the reference symbol 501_2 for channel estimation in FIG. 5, and obtains the value corresponding to h22 in Eq. (66). Estimate and output the channel estimation signal 708_2.

The control information decoding unit 709 inputs the baseband signals 704_X and 704_Y, detects the symbol 500_1 for notifying the transmission method of FIG. 5, and outputs the signal 710 regarding the transmission method information notified by the transmission device.

The signal processing unit 711 receives the baseband signals 704_X, 704_Y, the channel estimation signals 706_1, 706_2, 708_1, 708_2, and the signal 710 related to the transmission method information notified by the transmission device as inputs, detects and decodes them, and receives the received data. Output 712_1 and 712_2.

Next, the operation of the signal processing unit 711 of FIG. 7 will be described in detail. FIG. 8 shows an example of the configuration of the signal processing unit 711 according to the present embodiment. Figure 8 is mainly INNER It consists of a MIMO detector, a soft-in / soft-out decoder, and a coefficient generator. The method of iterative decoding in this configuration is described in detail in Non-Patent Document 2 and Non-Patent Document 3, but the MIMO transmission method described in Non-Patent Document 2 and Non-Patent Document 3 is spatial multiplex MIMO transmission. Although it is a method, the transmission method in the present embodiment is a MIMO transmission method in which the phase of the signal is regularly changed with time, the precoding matrix is used, and the baseband signal is replaced. The point is that it differs from Non-Patent Document 2 and Non-Patent Document 3. The (channel) matrix in Eq. (66) is H (t), the precoding weight matrix in FIG. 69 is F (where the precoding matrix is fixed and unchanged in the received signal of 1), FIG. 69. The matrix of the phase change equation by the phase change part is Y (t) (where Y (t) changes with t), and the reception vector is R (t) = (r1 (t), r2 from the replacement of the baseband signal. (t))^T, And stream vector S (t) = (s1 (t), s2 (t))^TIt is possible to perform MIMO detection by deriving the relationship between the above and applying the decoding methods of Non-Patent Document 2 and Non-Patent Document 3 to R (t) of the received vector.

Therefore, the coefficient generation unit 819 in FIG. 8 is a signal 818 regarding the transmission method information (information for specifying the fixed precoding matrix used and the phase change pattern when the phase is changed) notified by the transmission device. It takes (corresponding to 710 in Fig. 7) as an input and outputs a signal 820 related to information on the signal processing method.

The INNER MIMO detection unit 803 receives a signal 820 related to information on the signal processing method as an input, and uses this signal to perform repeated detection / decoding, and the operation thereof will be described.

In the signal processing unit having the configuration shown in FIG. 8, it is necessary to perform the processing method as shown in FIG. 10 in order to perform iterative decoding (repeated detection). First, one codeword (or one frame) of the modulated signal (stream) s1 and one codeword (or one frame) of the modulated signal (stream) s2 are decoded. As a result, from the soft-in / soft-out decoder, one codeword (or one frame) of the modulated signal (stream) s1 and one codeword (or one frame) of the modulated signal (stream) s2 are each. The log-likelihood ratio (LLR) of the bit is obtained. Then, the detection / decoding is performed again using the LLR. This operation is performed multiple times (this operation is called iterative decoding (repeated detection)). In the following, the method of creating the log-likelihood ratio (LLR) of a symbol at a specific time in one frame will be mainly described.

In FIG. 8, the storage unit 815 includes a baseband signal 801X (corresponding to the baseband signal 704_X in FIG. 7), a channel estimation signal group 802X (corresponding to the channel estimation signals 706_1 and 706_2 in FIG. 7), and a baseband. To realize iterative decoding (repeated detection) by inputting the signal 801Y (corresponding to the baseband signal 704_Y in FIG. 7) and the channel estimation signal group 802Y (corresponding to the channel estimation signals 708_1 and 708_2 in FIG. 7). The calculated matrix is stored as a modified channel signal group. Then, the storage unit 815 outputs the above signals as a baseband signal 816X, a modified channel estimation signal group 817X, a baseband signal 816Y, and a modified channel estimation signal group 817Y when necessary.

Subsequent operations will be described separately for the case of initial detection and the case of iterative decoding (repeated detection).

&lt;In the case of initial detection&gt; The INNER MIMO detection unit 803 inputs the baseband signal 801X, the channel estimation signal group 802X, the baseband signal 801Y, and the channel estimation signal group 802Y. Here, the modulation method of the modulated signal (stream) s1 and the modulated signal (stream) s2 will be described as 16QAM.

The INNER MIMO detection unit 803 first obtains a candidate signal point corresponding to the baseband signal 801X from the channel estimation signal group 802X and the channel estimation signal group 802Y. The situation at that time is shown in FIG. In FIG. 11, (black circle) is a candidate signal point in the IQ plane, and since the modulation method is 16QAM, there are 256 candidate signal points. (However, since FIG. 11 shows an image diagram, not all 256 candidate signal points are shown.) Here, the 4 bits transmitted by the modulated signal s1 are b0, b1, b2, b3, and the modulated signal s2. Assuming that the 4 bits transmitted in 1 are b4, b5, b6, and b7, there are candidate signal points corresponding to (b0, b1, b2, b3, b4, b5, b6, b7) in FIG. Then, the square Euclidean distance between the received signal point 1101 (corresponding to the baseband signal 801X) and each candidate signal point is obtained. Then, each squared Euclidean distance is the noise variance σ²Divide by. Therefore, the value obtained by dividing the candidate signal point corresponding to (b0, b1, b2, b3, b4, b5, b6, b7) and the Euclidean distance squared to the received signal point by the noise variance is E._X(b0, b1, b2, b3, b4, b5, b6, b7) will be obtained. The baseband signals, modulation signals s1 and s2 are complex signals.

Similarly, from the channel estimation signal group 802X and the channel estimation signal group 802Y, the candidate signal points corresponding to the baseband signal 801Y are obtained, and the squared Euclidean distance from the received signal point (corresponding to the baseband signal 801Y) is obtained. , This squared Euclidean distance is the signal dispersion σ²Divide by. Therefore, the value obtained by dividing the candidate signal point corresponding to (b0, b1, b2, b3, b4, b5, b6, b7) and the Euclidean distance squared to the received signal point by the noise variance is E._Y(b0, b1, b2, b3, b4, b5, b6, b7) will be obtained.

And E_X(b0, b1, b2, b3, b4, b5, b6, b7) + E_YFind (b0, b1, b2, b3, b4, b5, b6, b7) = E (b0, b1, b2, b3, b4, b5, b6, b7).

The INNER MIMO detector 803 outputs E (b0, b1, b2, b3, b4, b5, b6, b7) as a signal 804.

The log-likelihood calculation unit 805A takes the signal 804 as an input, calculates the log-likelihood of the bits b0 and b1 and b2 and b3, and outputs the log-likelihood signal 806A. However, in the calculation of the log-likelihood, the log-likelihood when it is "1" and the log-likelihood when it is "0" are calculated. The calculation method is as shown in the formula (28), the formula (29), and the formula (30), and the details are shown in Non-Patent Document 2 and Non-Patent Document 3.

Similarly, the log-likelihood calculation unit 805B takes the signal 804 as an input, calculates the log-likelihood of the bits b4 and b5 and b6 and b7, and outputs the log-likelihood signal 806B.

The deinterleaver (807A) takes the log-likelihood signal 806A as an input, performs deinterleave corresponding to the interleaver (interleaver (304A) in FIG. 67), and outputs the log-likelihood signal 808A after deinterleave.

Similarly, the deinterleaver (807B) takes the log-likelihood signal 806B as an input, performs deinterleave corresponding to the interleaver (interleaver (304B) in FIG. 67), and outputs the log-likelihood signal 808B after deinterleave.

The log-likelihood ratio calculation unit 809A uses the deinterleaved log-likelihood signal 808A as an input and calculates the log-likelihood ratio (LLR: Log-Likelihood Ratio) of the bits encoded by the encoder 302A in FIG. Then, the log-likelihood ratio signal 810A is output.

Similarly, the log-likelihood ratio calculation unit 809B takes the deinterleaved log-likelihood signal 808B as an input, and the log-likelihood ratio (LLR: Log-Likelihood Ratio) of the bits encoded by the encoder 302B of FIG. ) Is calculated, and the log-likelihood ratio signal 810B is output.

The Soft-in / soft-out decoder 811A takes a log-likelihood ratio signal 810A as an input, performs decoding, and outputs a log-likelihood ratio 812A after decoding.

Similarly, the Soft-in / soft-out decoder 811B takes the log-likelihood ratio signal 810B as an input, performs decoding, and outputs the log-likelihood ratio 812B after decoding.

&lt;In the case of iterative decoding (repetitive detection), the number of iterations k&gt; The interleaver (813A) takes the log-likelihood ratio 812A after decoding obtained by the k-1th soft-in / soft-out decoding as an input and interleaves. Is performed, and the log-likelihood ratio 814A after interleaving is output. At this time, the interleave pattern of the interleave (813A) is the same as the interleave pattern of the interleaver (304A) of FIG.

The interleaver (813B) inputs the log-likelihood ratio 812B after decoding obtained by the k-1st soft-in / soft-out decoding, performs interleaving, and outputs the log-likelihood ratio 814B after interleaving. .. At this time, the interleave pattern of the interleave (813B) is the same as the interleave pattern of the interleaver (304B) of FIG.

The INNER MIMO detector 803 inputs the baseband signal 816X, the modified channel estimation signal group 817X, the baseband signal 816Y, the modified channel estimation signal group 817Y, the log-likelihood ratio 814A after interleaving, and the log-likelihood ratio 814B after interleaving. And. Here, instead of the baseband signal 801X, the channel estimation signal group 802X, the baseband signal 801Y, and the channel estimation signal group 802Y, the baseband signal 816X, the modified channel estimation signal group 817X, the baseband signal 816Y, and the modified channel estimation signal group 817Y Is used because there is a delay time due to repeated decoding.

The difference between the operation during repeated decoding of the INNER MIMO detector 803 and the operation during initial detection is that the log-likelihood ratio 814A after interleaving and the log-likelihood ratio 814B after interleaving are used for signal processing. Is. The INNER MIMO detection unit 803 first obtains E (b0, b1, b2, b3, b4, b5, b6, b7) as in the case of initial detection. In addition, the coefficients corresponding to equations (11) and (32) are obtained from the log-likelihood ratio 814A after interleaving and the log-likelihood ratio 914B after interleaving. Then, the value of E (b0, b1, b2, b3, b4, b5, b6, b7) is corrected using this obtained coefficient, and the value is corrected by E'(b0, b1, b2, b3, b4, b5). , B6, b7) and output as signal 804.

The log-likelihood calculation unit 805A takes the signal 804 as an input, calculates the log-likelihood of the bits b0 and b1 and b2 and b3, and outputs the log-likelihood signal 806A. However, in the calculation of the log-likelihood, the log-likelihood when it is "1" and the log-likelihood when it is "0" are calculated. The calculation method is as shown in Equation (31), Equation (Equation 32), Equation (33), Equation (34), and Equation (35), and is shown in Non-Patent Document 2 and Non-Patent Document 3. There is.

Similarly, the log-likelihood calculation unit 805B takes the signal 804 as an input, calculates the log-likelihood of the bits b4 and b5 and b6 and b7, and outputs the log-likelihood signal 806B. The operation after the demodulator is the same as the initial detection.

Note that FIG. 8 shows the configuration of the signal processing unit when performing repeated detection, but repeated detection is not necessarily an essential configuration for obtaining good reception quality, and is a configuration part required only for repeated detection. , The configuration may not have interleavers 813A and 813B. At this time, the INNER MIMO detection unit 803 does not perform repetitive detection.

As shown in Non-Patent Document 5 and the like, initial detection and repeated detection may be performed using QR decomposition. Further, as shown in Non-Patent Document 11, MMSE (Minimum Mean Square Error) and ZF (Zero Forcing) may be linearly calculated to perform initial detection.

FIG. 9 shows a configuration of a signal processing unit different from that of FIG. 8, and is a signal processing unit for a modulated signal transmitted by a transmission device to which the encoder and the distributor of FIG. 4 are applied with respect to FIG. 67. The difference from FIG. 8 is the number of soft-in / soft-out decoders. The soft-in / soft-out decoder 901 receives log-likelihood ratio signals 810A and 810B as inputs, performs decoding, and after decoding. The log-likelihood ratio 902 is output. The distribution unit 903 receives the log-likelihood ratio 902 after decoding as an input and distributes. For the other parts, the operation is the same as in FIG.

As described above, as in the present embodiment, when the transmitting device of the MIMO transmission system transmits a plurality of modulated signals from a plurality of antennas, the precoding matrix is multiplied and the phase is changed with time, and the phase is changed. By making regular changes, it is possible to obtain the effect of improving the data reception quality in the receiving device as compared with the case of using the conventional spatial multiplex MIMO transmission in the LOS environment where the direct wave is dominant.

In the present embodiment, in particular, regarding the configuration of the receiving device, the operation is described by limiting the number of antennas, but the same can be performed even if the number of antennas increases. That is, the number of antennas in the receiving device does not affect the operation and effect of the present embodiment.

Further, in the present embodiment, the coding is not limited to the LDPC code in particular, and the decoding method is not limited to the sum-product decoding as the soft-in / soft-out decoder. There are other soft-in / soft-out decoding methods, such as BCJR algorithm, SOVA algorithm, Max-log-MAP algorithm, etc. Details are shown in Non-Patent Document 6.

Further, in the above description, the single carrier method has been described as an example, but the present invention is not limited to this, and the same can be applied even when multi-carrier transmission is performed. Therefore, for example, the same can be carried out when the spectrum diffusion communication method, the OFDM method, the SC-FDMA, the SC-OFDM method, the wavelet OFDM method shown in Non-Patent Document 7 and the like are used. Further, in the present embodiment, symbols other than the data symbols, for example, pilot symbols (preambles, unique words, etc.), symbols for transmitting control information, and the like may be arranged in the frame.

Next, as an example of the multi-carrier method, an example when the OFDM method is used will be described.

FIG. 70 shows the configuration of the transmitter when the OFDM method is used. In FIG. 70, the same reference numerals are given to those operating in the same manner as in FIGS. 3, 12, and 67.

The OFDM system-related processing unit 1201A receives the weighted signal 309A as an input, performs OFDM system-related processing, and outputs a transmission signal 1202A. Similarly, the OFDM method-related processing unit 1201B takes the phase-changed signal 309B as an input and outputs the transmission signal 1202B.

FIG. 13 shows an example of the configuration of the OFDM method-related processing units 1201A and 1201B and later in FIG. 70, and the parts related to 1201A to 312A in FIG. 70 are 1301A to 1310A and the parts related to 1201B to 312B. Is from 1301B to 1310B.

The serial-parallel conversion unit 1302A performs serial-parallel conversion of the baseband signal 1301A after replacement (corresponding to the baseband signal 6701A after replacement in FIG. 70), and outputs a parallel signal 1303A.

The rearrangement unit 1304A receives the parallel signal 1303A as an input, performs rearrangement, and outputs the rearranged signal 1305A. The rearrangement will be described in detail later.

The inverse fast Fourier transform unit 1306A takes the rearranged signal 1305A as an input, performs an inverse fast Fourier transform, and outputs the signal 1307A after the inverse Fourier transform.

The radio unit 1308A receives the signal 1307A after the inverse Fourier transform as an input, performs processing such as frequency conversion and amplification, outputs the modulated signal 1309A, and the modulated signal 1309A is output as a radio wave from the antenna 1310A.

The serial-parallel conversion unit 1302B performs serial-parallel conversion on the signal 1301B after the phase change (corresponding to the signal 309B after the phase change in FIG. 12), and outputs the parallel signal 1303B.

The rearrangement unit 1304B receives the parallel signal 1303B as an input, performs rearrangement, and outputs the rearranged signal 1305B. The rearrangement will be described in detail later.

The inverse fast Fourier transform unit 1306B takes the rearranged signal 1305B as an input, performs an inverse fast Fourier transform, and outputs the signal 1307B after the inverse Fourier transform.

The radio unit 1308B receives the signal 1307B after the inverse Fourier transform as an input, performs processing such as frequency conversion and amplification, outputs the modulated signal 1309B, and the modulated signal 1309B is output as a radio wave from the antenna 1310B.

Since the transmission device of FIG. 67 is not a transmission method using a multi-carrier, the phase is changed so as to have four cycles as shown in FIG. 69, and the symbols after the phase change are arranged in the time axis direction. When a multi-carrier transmission method such as the OFDM method shown in FIG. 70 is used, naturally, the symbol after precoding and baseband signal replacement and the phase is changed as shown in FIG. 67 is displayed in the time axis direction. In the case of the multi-carrier transmission method, a method of arranging in the frequency axis direction or using both the frequency axis and the time axis can be considered. Hereinafter, this point will be described.

FIG. 14 shows an example of a method of rearranging symbols in the rearrangement portions 1301A and 1301B of FIG. 13 on the horizontal axis frequency and the vertical axis time, and the frequency axis is from (sub) carrier 0 to (sub) carrier 9. The modulated signals z1 and z2 use the same frequency band at the same time (time), and FIG. 14 (A) shows the method of rearranging the symbols of the modulated signal z1 and FIG. 14 (B). Shows how to rearrange the symbols of the modulated signal z2. The symbols of the replaced baseband signal 1301A input by the serial-parallel converter 1302A are numbered in order as # 0, # 1, # 2, # 3, .... Here, since the case of cycle 4 is considered, # 0, # 1, # 2, and # 3 are for one cycle. Considering the same, # 4n, # 4n + 1, # 4n + 2, and # 4n + 3 (n is an integer of 0 or more) are for one cycle.

At this time, as shown in FIG. 14 (a), symbols # 0, # 1, # 2, # 3, ... Are arranged in order from carrier 0, and symbols # 0 to # 9 are arranged at time $ 1. After that, symbols # 10 to # 19 shall be arranged regularly, such as at time $ 2. The modulated signals z1 and z2 are complex signals.

Similarly, the symbols of the signal 1301B after the phase input by the serial-parallel converter 1302B is changed are numbered in order as # 0, # 1, # 2, # 3, .... Here, since the case of period 4 is considered, # 0, # 1, # 2, and # 3 have different phase changes, and # 0, # 1, # 2, and # 3 are one. It is for the cycle. Thinking in the same way, # 4n, # 4n + 1, # 4n + 2, and # 4n + 3 (n is an integer greater than or equal to 0) have different phase changes, and # 4n and # 4n + 1 , # 4n + 2 and # 4n + 3 are for one cycle.

At this time, as shown in FIG. 14 (b), symbols # 0, # 1, # 2, # 3, ... Are arranged in order from carrier 0, and symbols # 0 to # 9 are arranged at time $ 1. After that, symbols # 10 to # 19 shall be arranged regularly, such as at time $ 2.

The symbol group 1402 shown in FIG. 14B is a symbol for one cycle when the phase changing method shown in FIG. 69 is used, and symbol # 0 is a symbol when the phase at time u in FIG. 69 is used. Symbol # 1 is a symbol when the phase of time u + 1 in FIG. 69 is used, symbol # 2 is a symbol when the phase of time u + 2 in FIG. 69 is used, and symbol # 2. 3 is a symbol when the phase of time u + 3 in FIG. 69 is used. Therefore, in symbol #x, when x mod 4 (the remainder when x is divided by 4, so mod: modulo) is 0, symbol #x is the symbol when the phase of time u in FIG. 69 is used. Yes, when x mod 4 is 1, the symbol #x is the symbol using the phase of time u + 1 in Figure 69, and when x mod 4 is 2, the symbol #x is the time u + in Figure 69. It is a symbol when the phase of 2 is used, and when x mod 4 is 3, the symbol #x is the symbol when the phase of time u + 3 in FIG. 69 is used.

In the present embodiment, the phase of the modulated signal z1 shown in FIG. 14A is not changed.

As described above, when a multi-carrier transmission method such as the OFDM method is used, the symbols can be arranged in the frequency axis direction, unlike the case of single-carrier transmission. The arrangement of symbols is not limited to the arrangement as shown in FIG. Other examples will be described with reference to FIGS. 15 and 16.

FIG. 15 shows an example of the symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 14, and FIG. 15 (A) shows the modulation signal z1. The method of rearranging the symbols of the above, FIG. 15 (B) shows the method of rearranging the symbols of the modulated signal z2. The difference between FIGS. 15 (A) and 15 (B) is that the method of rearranging the symbols of the modulated signal z1 and the method of rearranging the symbols of the modulated signal z2 are different. Place 0 to # 5 on carriers 4 to 9, symbols # 6 to # 9 on carriers 0 to 3, and then place symbols # 10 to # 19 on each carrier according to the same rules. At this time, similarly to FIG. 14 (B), the symbol group 1502 shown in FIG. 15 (B) is a symbol for one cycle when the phase changing method shown in FIG. 6 is used.

FIG. 16 shows an example of the symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 14, and FIG. 16 (A) shows the modulation signal z1. The method of rearranging the symbols, FIG. 16 (B) shows the method of rearranging the symbols of the modulated signal z2. The difference between FIGS. 16 (A) and 16 (B) is that the symbols are arranged in order on the carrier in FIG. 14, whereas the symbols are not arranged in order on the carrier in FIG. It is a point. As a matter of course, in FIG. 16, as in FIG. 15, the method of rearranging the symbols of the modulated signal z1 and the method of rearranging the modulated signal z2 may be different.

FIG. 17 shows an example of the symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIGS. 14 to 16, and FIG. 17 (A) shows modulation. The method of rearranging the symbols of the signal z1 and FIG. 17B show the method of rearranging the symbols of the modulated signal z2. In FIGS. 14 to 16, the symbols are arranged in the frequency axis direction, but in FIG. 17, the symbols are arranged using both the frequency and the time axis.

In FIG. 69, an example of switching the phase change in 4 slots has been described, but here, a case of switching in 8 slots will be described as an example. The symbol group 1702 shown in FIG. 17 is a symbol for one cycle (hence, 8 symbols) when the phase change method is used, and symbol # 0 is a symbol when the phase at time u is used, and the symbol # 1 is a symbol when the phase of time u + 1 is used, symbol # 2 is a symbol when the phase of time u + 2 is used, and symbol # 3 is a symbol when the phase of time u + 3 is used. Symbol # 4 is a symbol when the phase of time u + 4, symbol # 5 is a symbol when the phase of time u + 5 is used, and symbol # 6 is time u +. It is a symbol when the phase of 6 is used, and symbol # 7 is a symbol when the phase of time u + 7 is used. Therefore, in symbol #x, when x mod 8 is 0, symbol #x is the symbol when the phase of time u is used, and when x mod 8 is 1, symbol # x is the phase of time u + 1. When x mod 8 is 2, the symbol #x is the symbol when the phase of time u + 2 is used, and x When mod 8 is 3, the symbol #x is the symbol when the phase at time u + 3 is used, and when x mod 8 is 4, the symbol #x is the symbol when the phase at time u + 4 is used. So, when x mod 8 is 5, the symbol #x is the symbol when using the phase at time u + 5, and when x mod 8 is 6, the symbol #x uses the phase at time u + 6. The symbol when I was there, x mod When 8 is 7, symbol #x is the symbol when the phase of time u + 7 is used. In the symbol arrangement in FIG. 17, symbols for one cycle are arranged using a total of 4 × 2 = 8 slots, 4 slots in the time axis direction and 2 slots in the frequency axis direction. At this time, one cycle is arranged. The number of minute symbols is m × n symbols (that is, there are m × n types of phases to be multiplied.) The frequency axis slot (number of carriers) used to place symbols for one cycle is n, and the time axis. If the slot used in the direction is m, then m&gt; n. This is because the phase of the direct wave, the fluctuation in the time axis direction is gradual as compared with the fluctuation in the frequency axis direction. Therefore, since the regular phase change of the present embodiment is performed in order to reduce the influence of the steady direct wave, it is desired to reduce the fluctuation of the direct wave in the period of performing the phase change. Therefore, m&gt; n should be set. In consideration of the above points, it is better to rearrange the symbols using both the frequency axis and the time axis as shown in FIG. 17 rather than rearranging the symbols only in the frequency axis direction or only in the time axis direction. Is likely to be stationary, and the effect of the present invention can be easily obtained. However, when arranging in the direction of the frequency axis, the fluctuation of the frequency axis is steep, so there is a possibility that diversity gain can be obtained. It is not always the method.

FIG. 18 shows an example of a symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 17, and FIG. 18 (A) shows the modulation signal z1. The method of rearranging the symbols of the above, FIG. 18 (B) shows the method of rearranging the symbols of the modulated signal z2. In FIG. 18, the symbols are arranged using both the frequency and the time axis as in FIG. 17, but the difference from FIG. 17 is that in FIG. 17, the frequency direction is prioritized and then in the time axis direction. Whereas the symbols are arranged, in FIG. 18, the time axis direction is prioritized, and then the symbols are arranged in the frequency axis direction. In FIG. 18, the symbol group 1802 is a symbol for one cycle when the phase change method is used.

In addition, in FIGS. 17 and 18, similarly to FIG. 15, even if the symbol arrangement method of the modulation signal z1 and the symbol arrangement method of the modulation signal z2 are arranged differently, it can be carried out in the same manner, and it is expensive. The effect of being able to obtain reception quality can be obtained. Further, in FIGS. 17 and 18, even if the symbols are not arranged in order as in FIG. 16, the same can be performed, and the effect that high reception quality can be obtained can be obtained. can.

FIG. 22 shows an example of a symbol rearrangement method in the rearrangement portions 1301A and 130B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from the above. Consider the case where the phase is changed regularly using 4 slots such as the time u ~ u + 3 in FIG. 69. The characteristic point in FIG. 22 is that the symbols are arranged in order in the frequency axis direction, but when the symbols are advanced in the time axis direction, the symbols are cyclically shifted by n (n = 1 in the example of FIG. 22). Is. In the four symbols shown in the symbol group 2210 in the frequency axis direction in FIG. 22, the phase of time u to u + 3 in FIG. 69 shall be changed.

At this time, the # 0 symbol uses the phase of time u to change the phase, # 1 uses the phase of time u + 1, and # 2 uses the phase of time u + 2, and # 3 changes the phase. Now, it is assumed that the phase is changed using the phase at time u + 3.

Similarly for the symbol group 2220 in the frequency axis direction, the phase change using the phase of time u in the symbol of # 4, the phase change using the phase of time u + 1 in # 5, and the phase change of time u + 2 in # 6. It is assumed that the phase is changed using the phase, and in # 7, the phase is changed using the phase at time u + 3.

The phase was changed as described above for the symbol of time $ 1, but since it is cyclically shifted in the time axis direction, the phase of the symbols 2201, 2202, 2203, and 2204 is changed as follows. Will do.

In the symbol group 2201 in the time axis direction, the # 0 symbol uses the phase change at time u, the # 9 uses the phase change at time u + 1, and the # 18 uses the phase at time u + 2. It is assumed that the phase is changed using the phase at time u + 3 in # 27.

In the symbol group 2202 in the time axis direction, the phase of the symbol of # 28 uses the phase change of time u, the phase change of # 1 uses the phase of time u + 1, and the phase of # 10 uses the phase of time u + 2. It is assumed that the phase change that was performed, and in # 19, the phase change using the phase at time u + 3 is performed.

In the symbol group 2203 in the time axis direction, the phase of the symbol of # 20 uses the phase change of time u, the phase change of # 29 uses the phase of time u + 1, and the phase of # 2 uses the phase of time u + 2. It is assumed that the phase is changed using the phase at time u + 3 in # 11.

In the symbol group 2204 in the time axis direction, the # 12 symbol uses the phase change at time u, the # 21 uses the phase change at time u + 1, and the # 30 uses the phase at time u + 2. It is assumed that the phase change was performed, and in # 3, the phase is changed using the phase at time u + 3.

The feature in FIG. 22 is that, for example, when focusing on the symbol of # 11, the symbols (# 10 and # 12) on both sides in the frequency axis direction at the same time both change the phase using a phase different from that of # 11. At the same time, the symbols (# 2 and # 20) on both sides of the same carrier of the symbol of # 11 in the time axis direction change the phase using a phase different from that of # 11. And this is not limited to the symbol of # 11, and all the symbols having symbols on both sides in the frequency axis direction and the time axis direction have the same characteristics as the symbol of # 11. As a result, the phase is effectively changed, and it is less likely to be affected by the constant condition of the direct wave, so that the data reception quality is likely to be improved.

In FIG. 22, the explanation is made with n = 1, but the present invention is not limited to this, and the same can be performed with n = 3. Further, in FIG. 22, the above characteristics are realized by arranging the symbols on the frequency axis and cyclically shifting the order of the arrangement of the symbols when the time advances in the axial direction, but the symbols are random. There is also a method to realize the above characteristics by arranging them (which may be regular).

In the present embodiment, as a modification of the first embodiment, a configuration in which the baseband signal replacement portion is inserted before the phase change is shown. However, the present embodiment and the second embodiment are combined and shown in FIG. 26. , In FIG. 28, the replacement portion of the baseband signal may be inserted and carried out before the phase change is performed. Therefore, in FIG. 26, the phase changing unit 317A inputs the replacement baseband signal 6701A (q1 (i)), and the phase changing unit 317B inputs the replacement baseband signal 6701B (q2 (i)). It will be. The same applies to the phase changing unit 317A and the phase changing unit 317B in FIG. 28.

Next, in the receiving devices that will be scattered in various places from the viewpoint of the transmitting device, a method for each receiving device to obtain good data reception quality regardless of where the receiving device is arranged will be disclosed.

FIG. 31 shows an example of the frame configuration of some symbols of the signal on the time-frequency axis when a multi-carrier method such as the OFDM method is used in the transmission method in which the phase is regularly changed.

FIG. 31 shows the frame configuration of the modulated signal z2'corresponding to the replaced baseband signal which is the input of the phase change unit 317B shown in FIG. 67, and one square is a symbol (however, precoding is performed). Therefore, it usually contains both signals of s1 and s2, but depending on the configuration of the precoding matrix, it may be only one signal of s1 and s2).

Here, we focus on the symbol 3100 of carrier 2 and time $ 2 in Fig. 31. Although it is described as a carrier here, it may also be referred to as a subcarrier.

In carrier 2, the symbols closest to time $ 2, that is, the symbol 3103 at time $ 1 of carrier 2 and the symbol 3101 at time $ 3, are the channel states of carrier 2, the symbol 3100 at time $ 2, and so on. Very high correlation.

Similarly, at time $ 2, the channel states of the frequency symbol closest to carrier 2 in the frequency axis direction, namely carrier 1, time $ 2 symbol 3104 and time $ 2, carrier 3 symbol 3104, are both carriers. 2. Very high correlation with the channel state of symbol 3100 at time $ 2.

As mentioned above, the channel states of symbols 3101, 3102, 3103, and 3104 are highly correlated with the channel states of symbol 3100.

In the present specification, it is assumed that N kinds of phases (where N is an integer of 2 or more) are prepared as the phases to be multiplied in the transmission method in which the phases are regularly changed. The symbols shown in FIG. 31 include, for example, "e".^j0This is for the signal z2'in FIG. 6 in this symbol, which is "e".^j0"Is multiplied to mean that the phase has been changed. That is, the value described in each symbol in FIG. 31 is the value of y (t) in the equation (70).

In the present embodiment, high data reception quality is obtained on the receiving device side by utilizing the high correlation between the channel states of the symbols adjacent to each other in the frequency axis direction and / or the symbols adjacent to each other in the time axis direction. Discloses the symbol arrangement of the phase-changed symbols obtained.

Condition # D1-1 and condition # D1-2 can be considered as conditions for obtaining high data reception quality on the receiving side.

&lt;Condition # D1-1&gt; As shown in Fig. 69, when a multi-carrier transmission method such as OFDM is used in the transmission method for regularly changing the phase of the replaced baseband signal q2, the time X -Carrier Y is a symbol for data transmission (hereinafter referred to as data symbol), and adjacent symbols in the time axis direction, that is, time X-1 · carrier Y and time X + 1 · carrier Y are all data. It is a symbol and the swapped baseband signal q2 corresponding to these three data symbols, that is, the swapped bases at time X · carrier Y, time X-1 · carrier Y and time X + 1 · carrier Y respectively. In the band signal q2, different phase changes are performed.

&lt;Condition # D1-2&gt; As shown in Fig. 69, when a multi-carrier transmission method such as OFDM is used in the transmission method that regularly changes the phase of the replaced baseband signal q2, the time X -Carrier Y is a symbol for data transmission (hereinafter referred to as data symbol), and adjacent symbols in the frequency axis direction, that is, time X · carrier Y-1 and time X · carrier Y + 1 are both data. If it is a symbol, the swapped baseband signal q2 corresponding to these three data symbols, that is, after each swap in time X · carrier Y, time X · carrier Y-1 and time X · carrier Y + 1. The baseband signal q2 undergoes different phase changes.

Then, it is preferable that there is a data symbol that satisfies &lt;condition # D1-1&gt;. Similarly, it is desirable that there is a data symbol that satisfies &lt;condition # D1-2&gt;.

The reason why the &lt;condition # D1-1&gt; and &lt;condition # D1-2&gt; are derived is as follows.

There is a certain symbol (hereinafter referred to as symbol A) in the transmission signal, and the channel state of each symbol temporally adjacent to the symbol A has a high correlation with the channel state of the symbol A as described above.

Therefore, if different phases are used for three symbols that are adjacent in time, the symbol A has poor reception quality (although the reception quality is high for SNR, the phase relationship of the direct wave is poor) in the LOS environment. Even if the reception quality is poor due to the poor situation), it is very likely that good reception quality can be obtained with the two symbols adjacent to the remaining symbol A, and as a result, after error correction and decoding. Can obtain good reception quality.

Similarly, there is a certain symbol (hereinafter referred to as symbol A) in the transmission signal, and the channel state of each symbol frequency-adjacent to the symbol A has a high correlation with the channel state of the symbol A as described above. ..

Therefore, if different phases are used for the three symbols that are adjacent in frequency, the symbol A has poor reception quality (although the reception quality is high for SNR, the phase relationship of the direct wave is poor) in the LOS environment. Even if the reception quality is poor due to the poor situation), it is very likely that good reception quality can be obtained with the two symbols adjacent to the remaining symbol A, and as a result, after error correction and decoding. Can obtain good reception quality.

Further, by combining &lt;condition # D1-1&gt; and &lt;condition # D1-2&gt;, there is a possibility that the data reception quality can be further improved in the receiving device. Therefore, the following conditions can be derived.

&lt;Condition # D1-3&gt; As shown in Fig. 69, when a multi-carrier transmission method such as OFDM is used in the transmission method that regularly changes the phase of the replaced baseband signal q2, the time X -Carrier Y is a symbol for data transmission (hereinafter referred to as data symbol), and adjacent symbols in the time axis direction, that is, time X-1 · carrier Y and time X + 1 · carrier Y are all data. If the symbols are adjacent in the frequency axis direction, that is, the time X carrier Y-1 and the time X carrier Y + 1 are both data symbols, after the replacement corresponding to these five data symbols. After each replacement of the baseband signal q2, ie, time X · carrier Y and time X-1 · carrier Y and time X + 1 · carrier Y and time X · carrier Y-1 and time X · carrier Y + 1 respectively. In the baseband signal q2 of, different phase changes are made.

Here, a supplement is given regarding "different phase changes". The phase change will be defined from 0 radians to 2π radians. For example, at time X and carrier Y, the phase change applied to the baseband signal q2 after the replacement in FIG. 69 is performed.^{jθX, Y}, At time X-1 and carrier Y, change the phase of the baseband signal q2 after replacement in Fig. 69.^{jθX-1, Y}, At time X + 1 and carrier Y, change the phase of the baseband signal q2 after replacement in Fig. 69.^{jθX + 1, Y}Then 0 radians θ_{X, Y}&lt;2π, 0 radians θ_{X-1, Y}&lt;2π, 0 radians θ_{X + 1, Y}&lt;2π. Therefore, in &lt;condition # D1-1&gt;, θ_{X, Y} θ_{X-1, Y}And θ_{X, Y} θ_{X + 1, Y}And θ_{X + 1, Y} θ_{X-1, Y}Will be established. Considering the same, in &lt;Condition # D1-2&gt;, θ_{X, Y} θ_{X, Y-1}And θ_{X, Y} θ_{X, Y + 1}And θ_{X, Y-1} θ_{X-1, Y + 1}Will be satisfied, and in &lt;condition # D1-3&gt;, θ_{X, Y} θ_{X-1, Y}And θ_{X, Y} θ_{X + 1, Y}And θ_{X, Y} θ_{X, Y-1}And θ_{X, Y} θ_{X, Y + 1}And θ_{X-1, Y} θ_{X + 1, Y}And θ_{X-1, Y} θ_{X, Y-1}And θ_{X-1, Y} θ_{X, Y + 1}And θ_{X + 1, Y} θ_{X, Y-1}And θ_{X + 1, Y} θ_{X, Y + 1}And θ_{X, Y-1} θ_{X, Y + 1}Will be established.

Then, it is preferable that there is a data symbol that satisfies &lt;condition # D1-3&gt;.

FIG. 31 is an example of &lt;condition # D1-3&gt;, in which the phase multiplied by the replaced baseband signal q2 in FIG. 69 corresponding to the symbol 3100 corresponding to the symbol A and the symbol 3100 are temporally Corresponds to the phase multiplied by the replaced baseband signal q2 in FIG. 69 corresponding to the adjacent symbol 3101 and the replaced baseband signal q2 in FIG. 69 corresponding to 3103, and the frequency-adjacent symbol 3102. The phases of the replaced baseband signals q2 in FIG. 69, which correspond to the replaced baseband signals q2 in FIG. 69, are arranged so as to be different from each other, whereby the symbol 3100 is arranged on the receiving side. Even if the reception quality is poor, the reception quality of the adjacent symbol is very high, so that high reception quality after error correction and decoding can be ensured.

Figure 32 shows an example of the arrangement of symbols obtained by changing the phase under this condition.

As can be seen from FIG. 32, in any data symbol, the degree of phase change for the symbols whose phases are adjacent to each other in both the frequency axis direction and the time axis direction is different from each other. ing. By doing so, the error correction capability of the receiving device can be further improved.

That is, in FIG. 32, when a data symbol exists in an adjacent symbol in the time axis direction, &lt;condition # D1-1&gt; is satisfied for all X and all Y.

Similarly, in FIG. 32, when data symbols exist in adjacent symbols in the frequency direction, &lt;condition # D1-2&gt; is satisfied for all X and all Y.

Similarly, in FIG. 32, if the data symbol exists in the adjacent symbol in the frequency direction and the data symbol exists in the adjacent symbol in the time axis direction, &lt;condition # D1-3&gt; is all X. , It holds for all Y.

Next, an example of the case where the phase of the two swapped baseband signals q2 described above is changed (see FIG. 68) will be described.

When giving a phase change to both the replaced baseband signal q1 and the replaced baseband signal q2, there are several methods for changing the phase. This point will be explained in detail.

As method 1, the phase change of the baseband signal q2 after the replacement is performed as shown in FIG. 32 as described above. In FIG. 32, the phase change of the baseband signal q2 after the replacement has a period of 10. However, as mentioned above, in order to satisfy &lt;Condition # D1-1&gt; &lt;Condition # D1-2&gt; &lt;Condition # D1-3&gt;, the baseband after replacement in (sub) carrier 1 The phase change applied to the signal q2 is changed over time. (Although such a change is made in FIG. 32, a period of 10 may be used and another phase change method may be used.) Then, the phase change of the baseband signal q1 after the replacement is as shown in FIG. 33. For the phase change of the baseband signal q2 after replacement, the phase change value for one cycle of cycle 10 is constant. In FIG. 33, at time $ 1 including one cycle (of the phase change of the baseband signal q2 after the replacement), the value of the phase change of the baseband signal q1 after the replacement is e.^j0At time $ 2, which includes the next cycle (of the phase change of the baseband signal q2 after replacement), the value of the phase change of the baseband signal q1 after replacement is e.^{jπ / 9}And ...

The symbols shown in FIG. 33 include, for example, "e".^j0Is attached, but this is the signal q1 in FIG. 26 in this symbol, which is "e".^j0"Is multiplied to mean that the phase has been changed.

As shown in FIG. 33, the phase change of the baseband signal q1 after the replacement is performed by changing the phase of the baseband signal q2 after the replacement after the precoding by setting the phase change value for one cycle of the cycle 10 to be constant. The value should be changed along with the number for one cycle. (As mentioned above, in FIG. 33, in the first cycle, e^j0And in the second cycle, e^{jπ / 9}, ... ) By doing the above, the phase change of the baseband signal q2 after the replacement has a period of 10, but both the phase change of the baseband signal q1 after the replacement and the phase change of the baseband signal q2 after the replacement can be performed. The effect that the period when considered can be made larger than 10 can be obtained. This may improve the reception quality of the data of the receiving device.

As the method 2, the phase change of the baseband signal q2 after the replacement is performed as shown in FIG. 32 as described above. In FIG. 32, the phase change of the baseband signal q2 after the replacement has a period of 10. However, as mentioned above, in order to satisfy &lt;Condition # D1-1&gt; &lt;Condition # D1-2&gt; &lt;Condition # D1-3&gt;, the baseband after replacement in (sub) carrier 1 The phase change applied to the signal q2 is changed over time. (Although such a change is made in FIG. 32, a period of 10 may be used and another phase change method may be used.) Then, the phase change of the baseband signal q1 after the replacement is as shown in FIG. The phase change of the baseband signal q2 after the replacement is performed in a period 3 different from the period 10.

The symbols shown in FIG. 30 include, for example, "e".^j0Is attached, but this is for the baseband signal q1 after replacement in this symbol, "e".^j0"Is multiplied to mean that the phase has been changed.

By doing so, the phase change of the baseband signal q2 after the replacement has a period of 10, but both the phase change of the baseband signal q1 after the replacement and the phase change of the baseband signal q2 after the replacement are taken into consideration. The period when can. This may improve the reception quality of the data of the receiving device. One effective method of method 2 is when the phase change cycle of the baseband signal q1 after replacement is N and the phase change cycle of the baseband signal q2 after replacement is M, especially N and M. If is in a prime relationship with each other, the period when both the phase change of the baseband signal q1 after replacement and the phase change of the baseband signal q2 after replacement are taken into consideration is easily set to a large period of N × M. Although it has the advantage of being able to do this, it is possible to increase the period even if N and M are in a prime relationship with each other.

The above-mentioned phase change method is an example, and is not limited to this. The phase change is performed in the frequency axis direction, the phase change is performed in the time axis direction, and the phase change is performed in the time-frequency block. Similarly, it has the effect of improving the reception quality of data in the receiving device.

In addition to the frame configuration described above, it is conceivable that a pilot symbol (SP (Scattered Pilot)) or a symbol for transmitting control information may be inserted between the data symbols. The phase change in this case will be described in detail.

FIG. 47 shows the frame configuration of the modulated signal (baseband signal q1 after replacement) z1 or z1'and the modulated signal (baseband signal q2 after replacement) z2' on the time-frequency axis. ) Is the time of the modulated signal (baseband signal q1 after replacement) z1 or z1'-frame configuration on the frequency axis, and Fig. 47 (b) is the time of the modulated signal (baseband signal q2 after replacement) z2'-. It is a frame configuration on the frequency axis. In FIG. 47, 4701 indicates a pilot symbol, 4702 indicates a data symbol, and the data symbol 4702 is a symbol that has undergone phase change with the replaced baseband signal or the replaced baseband signal.

FIG. 47 shows the symbol arrangement when the phase is changed for the replaced baseband signal q2 as shown in FIG. 69 (the phase is not changed for the replaced baseband signal q1). (Note that FIG. 69 shows the case where the phase is changed in the time axis direction, but in FIG. 69, by replacing the time t with the carrier f, it is equivalent to performing the phase change in the frequency direction. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, the base after replacement in FIG. 47. Band signal q₂The numerical value described in the symbol of indicates the change value of the phase. Since the phase of the symbol of the baseband signal q1 (z1) after the replacement in FIG. 47 is not changed, the numerical value is not described.

The important point in FIG. 47 is that the phase change for the baseband signal q2 after the replacement is applied to the data symbol, that is, the symbol to which the precoding and the baseband signal replacement have been performed. (Here, it is described as a symbol, but since the symbol described here is precoded, it includes both the s1 symbol and the s2 symbol.) Therefore. , The phase change will not be applied to the pilot symbol inserted in z2'.

FIG. 48 shows the frame configuration of the modulated signal (baseband signal q1 after replacement) z1 or z1'and the modulated signal (baseband signal q2 after replacement) z2' on the time-frequency axis. ) Is the time of the modulated signal (baseband signal q1 after replacement) z1 or z1'-frame configuration on the frequency axis, and Fig. 48 (b) is the time of the modulated signal (baseband signal q2 after replacement) z2'-. It is a frame configuration on the frequency axis. In FIG. 48, 4701 indicates a pilot symbol, 4702 indicates a data symbol, and the data symbol 4702 is a symbol that has undergone precoding and phase change.

FIG. 48 shows the symbol arrangement when the phase of the replaced baseband signal q1 and the replaced baseband signal q2 is changed. Therefore, the numerical values described in the symbols of the replaced baseband signal q1 and the replaced baseband signal q2 in FIG. 48 indicate the phase change value.

The important point in FIG. 48 is that the phase change for the baseband signal q1 after the replacement is applied to the data symbol, that is, the symbol to which the precoding and the baseband signal have been replaced, and the base after the replacement. The phase change for the band signal q2 is applied to the data symbol, that is, the symbol to which the precoding and the baseband signal have been exchanged. (Here, it is described as a symbol, but since the symbol described here is precoded, it includes both the s1 symbol and the s2 symbol.) Therefore. , The phase change is not applied to the pilot symbol inserted in z1', and the phase change is not applied to the pilot symbol inserted in z2'.

FIG. 49 shows the frame configuration of the modulated signal (baseband signal q1 after replacement) z1 or z1'and the modulated signal (baseband signal q2 after replacement) z2' on the time-frequency axis. ) Is the time of the modulated signal (baseband signal q1 after replacement) z1 or z1'-frame configuration on the frequency axis, and Fig. 49 (b) is the time of the modulated signal (baseband signal q2 after replacement) z2'-. It is a frame configuration on the frequency axis. In FIG. 49, 4701 is a pilot symbol, 4702 is a data symbol, 4901 is a null symbol, the in-phase component I = 0 of the baseband signal, and the orthogonal component Q = 0. At this time, the data symbol 4702 becomes a precoding or a symbol that has undergone phase change with precoding. The difference between FIGS. 49 and 47 is the method of constructing symbols other than the data symbol, where the modulated signal z2'is a null symbol at the time and carrier when the pilot symbol is inserted in the modulated signal z1', and vice versa. In addition, the modulation signal z1'is a null symbol at the time and carrier when the pilot symbol is inserted in the modulation signal z2'.

FIG. 49 shows the symbol arrangement when the phase is changed for the replaced baseband signal q2 as shown in FIG. 69 (the phase is not changed for the replaced baseband signal q1). (Note that FIG. 69 shows the case where the phase is changed in the time axis direction, but in FIG. 6, by replacing the time t with the carrier f, it is equivalent to performing the phase change in the frequency direction. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, the base after replacement in FIG. 49. The numerical value described in the symbol of the band signal q2 indicates the phase change value. Since the phase of the symbol of the baseband signal q1 after the replacement in FIG. 49 is not changed, the numerical value is not described.

The important point in FIG. 49 is that the phase change for the baseband signal q2 after the replacement is applied to the data symbol, that is, the symbol to which the precoding and the baseband signal replacement have been performed. (Here, it is described as a symbol, but since the symbol described here is precoded, it includes both the s1 symbol and the s2 symbol.) Therefore. , The phase change will not be applied to the pilot symbol inserted in z2'.

FIG. 50 shows the frame configuration of the modulated signal (baseband signal q1 after replacement) z1 or z1'and the modulated signal (baseband signal q2 after replacement) z2' on the time-frequency axis. ) Is the time of the modulated signal (baseband signal q1 after replacement) z1 or z1'-frame configuration on the frequency axis, and Fig. 50 (b) is the time of the modulated signal (baseband signal q2 after replacement) z2'-. It is a frame configuration on the frequency axis. In FIG. 50, 4701 is a pilot symbol, 4702 is a data symbol, 4901 is a null symbol, the in-phase component I = 0 of the baseband signal, and the orthogonal component Q = 0. At this time, the data symbol 4702 becomes a precoding or a symbol that has undergone phase change with precoding. The difference between FIGS. 50 and 48 is the method of constructing symbols other than the data symbol, where the modulated signal z2'is a null symbol at the time and carrier when the pilot symbol is inserted in the modulated signal z1', and vice versa. In addition, the modulation signal z1'is a null symbol at the time and carrier when the pilot symbol is inserted in the modulation signal z2'.

FIG. 50 shows the symbol arrangement when the phase of the replaced baseband signal q1 and the replaced baseband signal q2 is changed. Therefore, the numerical values shown in the symbols of the replaced baseband signal q1 and the replaced baseband signal q2 in FIG. 50 indicate the phase change value.

The important point in FIG. 50 is that the phase change for the replaced baseband signal q1 is applied to the data symbol, that is, the symbol to which the precoding and the baseband signal have been replaced, and the replaced baseband. The phase change for signal q2 is that it is applied to the data symbol, that is, the symbol that has undergone precoding and baseband signal replacement. (Here, it is described as a symbol, but since the symbol described here is precoded, it includes both the s1 symbol and the s2 symbol.) Therefore. , The phase change is not applied to the pilot symbol inserted in z1', and the phase change is not applied to the pilot symbol inserted in z2'.

FIG. 51 shows an example of the configuration of a transmission device that generates and transmits a modulated signal having the frame configuration of FIGS. 47 and 49, and the same reference numerals are given to those that operate in the same manner as in FIG. .. Although the baseband signal replacement section shown in FIGS. 67 and 70 is not shown in FIG. 51, the base band signal replacement section is shown between the weighting synthesis section and the phase change section in FIG. 51, as in FIGS. 67 and 70. The band signal replacement part may be inserted.

In FIG. 51, the weighting synthesis units 308A and 308B, the phase change unit 317B, and the baseband signal replacement unit operate only when the frame configuration signal 313 indicates the timing of the data symbol.

When the pilot symbol (which also serves as null symbol generation) generation unit 5101 of FIG. 51 indicates that the frame configuration signal 313 is a pilot symbol (and a null symbol), the baseband signal 5102A of the pilot symbol and Output 5102B.

Although not shown in the frame configurations of FIGS. 47 to 50, no precoding (and no phase rotation) is applied, for example, a method of transmitting a modulated signal from one antenna (in this case, the other antenna). When the control information symbol is transmitted using a transmission method using a spatiotemporal code (particularly, a spatiotemporal block code), the control information symbol 5104 is the control information 5103, When the frame configuration signal 313 is input and the frame configuration signal 313 indicates that it is a control information symbol, the baseband signals 5102A and 5102B of the control information symbol are output.

The radio units 310A and 310B of FIG. 51 select a desired baseband signal from the plurality of baseband signals based on the frame configuration signal 313 among the plurality of input baseband signals. Then, the OFDM-related signal processing is performed, and the modulated signals 311A and 311B according to the frame configuration are output, respectively.

FIG. 52 shows an example of the configuration of the transmission device that generates and transmits the modulated signal having the frame configuration of FIGS. 48 and 50, and the same reference numerals are given to those that operate in the same manner as those of FIGS. 4 and 51. is doing. The phase change unit 317A added to FIG. 51 operates only when the frame configuration signal 313 indicates the timing of the data symbol. Others are the same as in FIG. 51. Although the baseband signal replacement section shown in FIGS. 67 and 70 is not shown in FIG. 52, the base band signal replacement section is shown between the weighting synthesis section and the phase change section in FIG. 52, as in FIGS. 67 and 70. The band signal replacement part may be inserted.

FIG. 53 shows a transmission device configuration method different from that of FIG. 51. Although the baseband signal replacement section shown in FIGS. 67 and 70 is not shown in FIG. 53, the baseband signal replacement section is shown between the weighting synthesis section and the phase change section in FIG. 53, as in FIGS. 67 and 70. The band signal replacement part may be inserted. The differences will be described below. As shown in FIG. 53, the phase changing unit 317B inputs a plurality of baseband signals. When the frame configuration signal 313 indicates that it is a data symbol, the phase changing unit 317B performs a phase change on the precoded baseband signal 316B. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase change unit 317B stops the phase change operation and the baseband signal of each symbol. Is output as it is. (Interpretation is "e^j0It can be considered that the phase rotation corresponding to "" is forcibly performed. ) The selection unit 5301 takes a plurality of baseband signals as inputs, selects and outputs the baseband signal of the symbol indicated by the frame configuration signal 313.

FIG. 54 is a method of configuring a transmitter different from that of FIG. 52. Although the baseband signal replacement section shown in FIGS. 67 and 70 is not shown in FIG. 54, the base band signal replacement section is shown between the weighting synthesis section and the phase change section in FIG. 54, as in FIGS. 67 and 70. The band signal replacement part may be inserted. The differences will be described below. As shown in FIG. 54, the phase changing unit 317B inputs a plurality of baseband signals. When the frame configuration signal 313 indicates that it is a data symbol, the phase changing unit 317B performs a phase change on the precoded baseband signal 316B. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase change unit 317B stops the phase change operation and the baseband signal of each symbol. Is output as it is. (Interpretation is "e^j0It can be considered that the phase rotation corresponding to "" is forcibly performed. ) Similarly, the phase changing unit 5201 inputs a plurality of baseband signals as shown in FIG. 54. When the frame configuration signal 313 indicates that it is a data symbol, the phase changing unit 5201 performs a phase change on the precoded baseband signal 309A. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase change unit 5201 stops the phase change operation and the baseband signal of each symbol. Is output as it is. (Interpretation is "e^j0It can be considered that the phase rotation corresponding to "" is forcibly performed. ) In the above explanation, the pilot symbol, the control symbol, and the data symbol have been described as an example, but the present invention is not limited to this, and a transmission method different from the precoding, for example, one antenna transmission and a spatiotemporal block code is used. Similarly, if the symbol is transmitted using a transmission method, etc., it is important not to give a phase change. On the contrary, for a symbol that has been precoded and the baseband signal is replaced, it is important. , It is important in the present invention to change the phase.

Therefore, it is a feature of the present invention that the phase change is not performed on all the symbols in the frame configuration on the time-frequency axis, and the phase change is given only to the signal obtained by precoding and baseband signal replacement.

Next, as shown in Non-Patent Documents 12 to 15, QC (Quasi Cyclic) LDPC (Low-Density Parity-Check) code (not QC-LDPC code, LDPC code may be used). , LDPC code and BCH code (Bose-Chaudhuri-Hocquenghem code) concatenated code, turbo code using tail biting or block code such as Duo-Binary Turbo Code to change the phase regularly explain in detail. Here, as an example, a case where two streams of s1 and s2 are transmitted will be described as an example. However, when coding is performed using the block code, when control information or the like is not required, the number of bits constituting the coded block is the number of bits constituting the block code (however, among these, the following It may contain control information and the like as described.) When encoding is performed using a block code, control information, etc. (for example, CRC (cyclic redundancy)) When check), transmission parameters, etc.) are required, the number of bits constituting the coded block may be the sum of the number of bits constituting the block code and the number of bits such as control information.

FIG. 34 is a diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used. In FIG. 34, for example, the encoder and the distributor as shown in FIG. 4 are applied to the transmitters of FIGS. 69 and 70 to transmit two streams of s1 and s2, and one transmitter is used. It is a "figure showing the change in the number of symbols and the number of slots required for one coded block when a block code is used" in the case of having a encoder. (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 34, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Since the above-mentioned transmitter transmits two streams at the same time, when the modulation method is QPSK, the above-mentioned 3000 symbols are assigned 1500 symbols to s1 and 1500 symbols to s2. Therefore, s1 1500 slots (named "slots" here) are required to send the 1500 symbols sent by and the 1500 symbols sent by s2.

Similarly, when the modulation scheme is 16QAM, 750 slots are required to transmit all the bits that make up one coded block, and when the modulation scheme is 64QAM, all that make up one block. 500 slots are required to send the bits.

Next, in the method of changing the phase regularly, the relationship between the slot defined above and the phase to be multiplied will be described.

Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase is set to 5. That is, it is assumed that five phase change values (or phase change sets) are prepared for the phase change unit of the above-mentioned transmitter. (As shown in FIG. 69, when the phase change is performed only on the baseband signal q2 after the replacement, five phase change values may be prepared in order to perform the phase change in the period 5. Also, the base after the replacement. When the phase change is performed for both the band signal q1 and the replaced baseband signal q2, two phase change values are required for one slot. These two phase change values are called a phase change set. Therefore, in this case, in order to change the phase of period 5, it is sufficient to prepare five phase change sets.) These five phase change values (or phase change sets) are set to PHASE [0], PHASE [1]. , PHASE [2], PHASE [3], PHASE [4].

When the modulation method is QPSK, in the 1500 slots described above for transmitting 6000 bits that make up one coded block, there are 300 slots that use phase PHASE [0], and phase PHASE [ There are 300 slots that use 1], 300 slots that use phase PHASE [2], 300 slots that use phase PHASE [3], and 300 slots that use phase PHASE [4]. There is a need. This is because if there is a deviation in the phase used, the influence of the phase using a large number is large, and the receiving quality of the data depends on this influence in the receiving device.

Similarly, when the modulation scheme is 16QAM, among the 750 slots mentioned above for transmitting the 6000 bits that make up one coded block, there are 150 slots that use phase PHASE [0]. There are 150 slots that use phase PHASE [1], 150 slots that use phase PHASE [2], 150 slots that use phase PHASE [3], and 150 slots that use phase PHASE [4]. Must be a slot.

Similarly, when the modulation scheme is 64QAM, 100 slots use phase PHASE [0] in the 500 slots mentioned above for transmitting 6000 bits that make up one coded block. 100 slots using phase PHASE [1], 100 slots using phase PHASE [2], 100 slots using phase PHASE [3], 100 slots using phase PHASE [4] Must be a slot.

As described above, in the method of regularly changing the phase, N pieces of phase change values (or phase change sets) are prepared (N different phases are PHASE [0], PHASE [1], PHASE [2]. ], ..., PHASE [N-2], PHASE [N-1]), when transmitting all the bits that make up one coded block, the phase PHASE [ Set the number of slots that use 0] to K₀, K the number of slots that use phase PHASE [1]_1、K the number of slots that use phase PHASE [i]_i(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), K the number of slots using phase PHASE [N-1]_N-1When &lt;Condition # D1-4&gt; K₀= K₁= . . . = K_i= . . . = K_N-1, That is, K_a= K_{b b}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b).

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, it is preferable that &lt;condition # D1-4&gt; is satisfied in the supported modulation methods. become.

However, when multiple modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy &lt;Condition # D1-4&gt;. In this case, the following conditions should be satisfied instead of &lt;Condition # D1-4&gt;.

&lt;Condition # D1-5&gt; K_aAnd K_{b b}The difference between is 0 or 1, that is, | K_aK_{b b}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ···, N-1 (a is an integer greater than or equal to 0 and less than or equal to N-1, b is greater than or equal to 0 and N- Integers of 1 or less), a b) Fig. 35 is a diagram showing changes in the number of symbols and the number of slots required for two coded blocks when a block code is used. FIG. 35 shows the case where two streams of s1 and s2 are transmitted and the transmitter has two encoders as shown in the transmitter of FIG. 67 and the transmitter of FIG. 70. "A diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used". (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 35, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Then, in the transmitter of FIG. 67 and the transmitter of FIG. 70, two streams are transmitted at the same time, and since there are two encoders, the two streams transmit different code blocks. become. Therefore, when the modulation method is QPSK, s1 and s2 transmit two coded blocks within the same interval. Therefore, for example, s1 transmits the first coded block, and s2 transmits the first coded block. Since 2 coded blocks will be transmitted, 3000 slots will be required to transmit the 1st and 2nd coded blocks.

Similarly, when the modulation scheme is 16QAM, 1500 slots are required to transmit all the bits that make up the two encoded blocks, and when the modulation scheme is 64QAM, the two encoded blocks are required. 1000 slots are required to transmit all the bits that make up the.

Next, in the method of changing the phase regularly, the relationship between the slot defined above and the phase to be multiplied will be described.

Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase is set to 5. That is, it is assumed that five phase change values (or phase change sets) are prepared for the phase change unit of the transmitter of FIG. 67 and the transmitter of FIG. 70. (As shown in FIG. 69, when the phase change is performed only on the baseband signal q2 after the replacement, five phase change values may be prepared in order to perform the phase change in the period 5. Also, the base after the replacement. Band signal q₁And when the phase change is performed for both the baseband signal q2 after the replacement, two phase change values are required for one slot. These two phase change values are called a phase change set. Therefore, in this case, in order to change the phase of period 5, it is sufficient to prepare five phase change sets.) These five phase change values (or phase change sets) are set to PHASE [0], PHASE [1]. , PHASE [2], PHASE [3], PHASE [4].

When the modulation method is QPSK, in the 3000 slots described above for transmitting the number of bits 6000 × 2 bits that make up the two coded blocks, the slots that use phase PHASE [0] are 600 slots and the phase. 600 slots using PHASE [1], 600 slots using phase PHASE [2], 600 slots using phase PHASE [3], 600 slots using phase PHASE [4] Must be. This is because if there is a deviation in the phase used, the influence of the phase using a large number is large, and the receiving quality of the data depends on this influence in the receiving device.

Also, in order to transmit the first coded block, there are 600 slots that use phase PHASE [0], 600 slots that use phase PHASE [1], and slots that use phase PHASE [2]. There must be 600 slots using phase PHASE [3] 600 times, 600 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 600 slots using [0], 600 slots using phase PHASE [1], 600 slots using phase PHASE [2], 600 slots using phase PHASE [3], It is recommended that the number of slots using the phase PHASE [4] is 600.

Similarly, when the modulation scheme is 16QAM, in the 1500 slots mentioned above for transmitting the number of bits 6000 × 2 bits that make up the two coded blocks, there are 300 slots that use phase PHASE [0]. Slots, 300 slots using phase PHASE [1], 300 slots using phase PHASE [2], 300 slots using phase PHASE [3], slots using phase PHASE [4] Must be 300 slots.

Also, in order to transmit the first coded block, the slot using phase PHASE [0] is 300 times, the slot using phase PHASE [1] is 300 times, and the slot using phase PHASE [2] is 300 times. There must be 300 slots using phase PHASE [3] 300 times, 300 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 300 slots using [0], 300 slots using phase PHASE [1], 300 slots using phase PHASE [2], 300 slots using phase PHASE [3], It is recommended that the number of slots using the phase PHASE [4] is 300.

Similarly, when the modulation scheme is 64QAM, in the 1000 slots mentioned above for transmitting the number of bits 6000 × 2 bits that make up the two coded blocks, there are 200 slots that use the phase PHASE [0]. Slots, 200 slots using phase PHASE [1], 200 slots using phase PHASE [2], 200 slots using phase PHASE [3], slots using phase PHASE [4] Must be 200 slots.

Also, in order to transmit the first coded block, there are 200 slots that use phase PHASE [0], 200 slots that use phase PHASE [1], and slots that use phase PHASE [2]. There must be 200 slots using phase PHASE [3] 200 times, 200 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 200 slots using [0], 200 slots using phase PHASE [1], 200 slots using phase PHASE [2], 200 slots using phase PHASE [3], It is recommended that the number of slots using the phase PHASE [4] is 200.

As described above, in the method of regularly changing the phase, N prepared phase change values (or phase change sets) (N different phases are PHASE [0], PHASE [1], PHASE [2]. ], ..., PHASE [N-2], PHASE [N-1]), when transmitting all the bits that make up the two encoded blocks, the phase PHASE [ Set the number of slots that use 0] to K₀, K the number of slots that use phase PHASE [1]_1、K the number of slots that use phase PHASE [i]_i(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), K the number of slots using phase PHASE [N-1]_N-1When &lt;Condition # D1-6&gt; K₀= K₁= . . . = K_i= . . . = K_N-1, That is, K_a= K_{b b}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b), and the number of times the phase PHASE [0] is used when transmitting all the bits that make up the first encoded block is K._0,1, K how many times to use phase PHASE [1]_1,1、K the number of times to use phase PHASE [i]_{i, 1}(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), the number of times to use phase PHASE [N-1] is K_N-1,1When &lt;Condition # D1-7&gt; K_0,1= K_1,1= . . . = K_{i, 1}= . . . = K_N-1,1, That is, K_{a, 1}= K_{b, 1}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b), and the number of times the phase PHASE [0] is used when transmitting all the bits that make up the second coded block is K._0,2, K how many times to use phase PHASE [1]_1,2、K the number of times to use phase PHASE [i]_{i, 2}(i = 0,1,2, ..., N-1 (i is an integer between 0 and N-1)), the number of times to use phase PHASE [N-1] is K_N-1,2When &lt;Condition # D1-8&gt; K_0,2= K_1,2= . . . = K_{i, 2}= . . . = K_N-1,2, That is, K_{a, 2}= K_{b, 2}, (For a, b, but a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is an integer between 0 and N-1) ), A b).

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, &lt;condition # D1-6&gt; &lt;condition # D1- 7&gt; It is good if &lt;Condition # D1-8&gt; is satisfied.

However, when multiple modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy &lt;Condition # D1-6&gt; &lt;Condition # D1-7&gt; &lt;Condition # D1-8&gt;. In this case, the following conditions should be satisfied instead of &lt;Condition # D1-6&gt; &lt;Condition # D1-7&gt; &lt;Condition # D1-8&gt;.

&lt;Condition # D1-9&gt; K_aAnd K_{b b}The difference between is 0 or 1, that is, | K_aK_{b b}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is between 0 and N-) Integer less than or equal to 1), a b) &lt;condition # D1-10&gt; K_{a, 1}And K_{b, 1}The difference between is 0 or 1, that is, | K_{a, 1}K_{b, 1}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is between 0 and N-) Integer less than or equal to 1), a b) &lt;condition # D1-11&gt; K_{a, 2}And K_{b, 2}The difference between is 0 or 1, that is, | K_{a, 2}K_{b, 2}| Is 0 or 1 (for a, b, where a, b = 0,1,2, ..., N-1 (a is an integer between 0 and N-1, b is between 0 and N-) Integers of 1 or less), a b) As described above, by associating the coded block with the multiplication phase, the phase used to transmit the coded block is not biased, so reception is performed. In the device, the effect of improving the reception quality of data can be obtained.

In the above, in the method of regularly changing the phase, N phase change values (or phase change sets) are required for the phase change method of period N. At this time, PHASE [0], PHASE [1], PHASE [2], ..., PHASE [N-2], PHASE [N-1] are used as N phase change values (or phase change sets). However, there is also a method of arranging PHASE [0], PHASE [1], PHASE [2], ..., PHASE [N-2], PHASE [N-1] in this order in the frequency axis direction. However, it is not always limited to this, and N phase change values (or phase change sets) PHASE [0], PHASE [1], PHASE [2], ..., PHASE [N-2], It is also possible to change the phase by arranging a symbol for PHASE [N-1] on the time axis and frequency-time axis blocks. Although the method of changing the phase of the period N is described, the same effect can be obtained by randomly using N phase change values (or phase change sets), that is, it is not always a rule. It is not necessary to use N phase change values (or phase change sets) so as to have a certain period, but the condition described above is satisfied in order to obtain high data reception quality in the receiving device. , Will be important.

In addition, there are modes of spatial multiplex MIMO transmission method, MIMO transmission method with fixed precoding matrix, spatiotemporal block coding method, transmission of only one stream, and method of changing the phase regularly, and the transmission device (broadcasting station, The base station) may be able to select one of these transmission methods from these modes.

As shown in Non-Patent Document 3, the spatial multiplex MIMO transmission method is a method of transmitting signals s1 and s2 mapped by the selected modulation method from different antennas, and the precoding matrix is fixed. The MIMO transmission method is a method in which only precoding is performed (phase change is not performed). The space-time block coding method is a transmission method shown in Non-Patent Documents 9, 16 and 17. Transmission of only one stream is a method of transmitting the signal of the signal s1 mapped by the selected modulation method from the antenna after performing predetermined processing.

In addition, a multi-carrier transmission method such as OFDM is used, and a first carrier group composed of a plurality of carriers, a second carrier group different from the first carrier group composed of a plurality of carriers, ... Multi-carrier transmission is realized by multiple carrier groups, such as spatial multiplex MIMO transmission method, MIMO transmission method with fixed precoding matrix, spatiotemporal block coding method, transmission of only one stream, for each carrier group. It may be set to any of the methods of regularly changing the phase, and the above may be carried out particularly for the (sub) carrier group in which the method of regularly changing the phase is selected.

It should be noted that the transmission device described in this embodiment, which performs precoding, replacement of baseband signals, and phase change, and the contents described in the present specification can be used in combination, and in particular, in the present embodiment. It is possible to use all the contents related to the phase change described in the present specification in combination with the phase change unit described.

(Embodiment D2) In the present embodiment, in the case of the transmission device of FIG. 4, when the transmission device of FIG. 4 is compatible with a multi-carrier method such as the OFDM method, the transmission device of FIGS. 67 and 70 is used. As shown in FIG. 4, a method for initializing the phase change when the phase change is regularly performed as described in the present specification in the case where one encoder and the distribution unit are applied will be described.

As shown in Non-Patent Documents 12 to 15, QC (Quasi Cyclic) LDPC (Low-Density Parity-Check) code (not QC-LDPC code, LDPC code may be used), LDPC code. Consider the case where the phase is regularly changed when the concatenated code of BCH code (Bose-Chaudhuri-Hocquenghem code), the turbo code using tail biting, or the block code such as Duo-Binary Turbo Code is used.

Here, as an example, a case where two streams of s1 and s2 are transmitted will be described as an example. However, when coding is performed using the block code, when control information or the like is not required, the number of bits constituting the coded block is the number of bits constituting the block code (however, among these, the following It may contain control information and the like as described.) When control information (for example, CRC (cyclic redundancy check), transmission parameter, etc.) is required when encoding is performed using a block code, the number of bits constituting the coded block is the block code. It may be the sum of the number of constituent bits and the number of bits such as control information.

FIG. 34 is a diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used. FIG. 34 shows, for example, "when a block code is used, when two streams s1 and s2 are transmitted to the above-mentioned transmitter and the transmitter has one encoder. It is a figure which showed the change of the number of symbols and the number of slots required for one coded block. (At this time, either single-carrier transmission or multi-carrier transmission such as OFDM may be used as the transmission method.) As shown in FIG. 34, the bits constituting one coded block in the block code. Let the number be 6000 bits. In order to transmit this 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when 16QAM, and 1000 symbols are required when 64QAM.

Since the above-mentioned transmitter transmits two streams at the same time, when the modulation method is QPSK, the above-mentioned 3000 symbols are assigned 1500 symbols to s1 and 1500 symbols to s2. Therefore, s1 1500 slots (named "slots" here) are required to send the 1500 symbols sent by and the 1500 symbols sent by s2.

Similarly, when the modulation scheme is 16QAM, 750 slots are required to transmit all the bits that make up one coded block, and when the modulation scheme is 64QAM, all that make up one block. 500 slots are required to send the bits.

Next, consider the case where the transmitting device transmits a modulated signal in the frame configuration as shown in FIG. 71. FIG. 71 (a) shows the frame configuration of the modulated signal z1'or z1 (transmitted by antenna 312A) on the time and frequency axes. Further, FIG. 71 (b) shows the frame configuration of the modulated signal z2 (transmitted by the antenna 312B) on the time and frequency axes. At this time, it is assumed that the frequency (band) used by the modulated signal z1'or z1 and the frequency (band) used by the modulated signal z2 are the same, and the modulated signal z1'or z1 and the modulated signal at the same time. z2 will exist.

As shown in FIG. 71 (a), the transmitting device transmits a preamble (control symbol) in the section A, which is a symbol for transmitting control information to the communication partner, and in particular, here, the first and the first. 2 It is assumed that the information of the modulation method for transmitting the coded block is included. The transmitting device will transmit the first coded block in the section B. The transmitter will transmit the second coded block in section C.

The transmission device transmits a preamble (control symbol) in the section D, and is a symbol for transmitting control information to the communication partner. In particular, here, the third, fourth, ..., Coding blocks are used. It is assumed that the information of the modulation method for transmission is included. The transmitting device will transmit the third coded block in the section E. The transmitting device will transmit the fourth coded block in the section F.

As shown in FIG. 71 (b), the transmitting device transmits a preamble (control symbol) in the section A, which is a symbol for transmitting control information to the communication partner, and in particular, here, the first and the first. 2 It is assumed that the information of the modulation method for transmitting the coded block is included. The transmitting device will transmit the first coded block in the section B. The transmitter will transmit the second coded block in section C.

The transmission device transmits a preamble (control symbol) in the section D, and is a symbol for transmitting control information to the communication partner. In particular, here, the third, fourth, ..., Coding blocks are used. It is assumed that the information of the modulation method for transmission is included. The transmitting device will transmit the third coded block in the section E. The transmitting device will transmit the fourth coded block in the section F.

FIG. 72 shows the number of slots used when transmitting a coded block as shown in FIG. 34, especially when 16QAM is used as the modulation method in the first coded block, and the first coded block is shown. 750 slots are required to transmit.

Similarly, the second coded block shows the number of slots used when QPSK is used as the modulation method, and 1500 slots are required to transmit the second coded block.

FIG. 73 shows the number of slots used when the coded block is transmitted as shown in FIG. 34, especially when QPSK is used as the modulation method in the third coded block, and the third coded block is shown. 1500 slots are required to transmit.

Then, as described in the present specification, the modulation signal z1, that is, the modulation signal transmitted by the antenna 312A is not phase-changed, and the modulation signal z2, that is, the modulation signal transmitted by the antenna 312B is not changed. Then, consider the case of changing the phase. At this time, FIGS. 72 and 73 show a method of changing the phase.

First, as a premise, in order to change the phase, seven different phase change values are prepared, and the seven phase change values are named # 0, # 1, # 2, # 3, # 4, # 5, and # 6. Further, the phase change shall be used regularly and periodically. That is, the phase change values are # 0, # 1, # 2, # 3, # 4, # 5, # 6, # 0, # 1, # 2, # 3, # 4, # 5, # 6, # Changes shall be made regularly and periodically, such as 0, # 1, # 2, # 3, # 4, # 5, # 6, and so on.

As shown in FIG. 72, first, in the first block coding block, there are 750 slots, so if the phase change value is started from # 0, # 0, # 1, # 2, # 3, # 4, # 5, # 6, # 0, # 1, # 2, ..., # 4, # 5, # 6, # 0, and the 750th slot ends with # 0.

Next, the phase change is applied to each slot of the second coded block. Since this specification assumes the case of applying to multicast communication and broadcasting, it is conceivable that a receiving terminal does not require the first coded block and extracts only the second coded block. In this case, even though the phase change value # 0 was used to transmit the last slot of the first coded block, the phase change value # 1 was used first to transmit the second coded block. It shall be. Then, (a): The above-mentioned terminal monitors how the first coded block is transmitted, that is, what pattern the phase change value is for the transmission of the last slot of the first coded block. Monitor and estimate the phase change value to be used for the first slot of the second coded block, (b): To avoid doing (a), the transmitter is used for the first slot of the second coded block. A method of transmitting information on the phase change value to be performed can be considered. In the case of (a), the terminal needs to monitor the transmission of the first coded block, so that the power consumption increases, and in the case of (b), the data transmission efficiency is lowered.

Therefore, there is room for improvement in the allocation of the phase change value as described above. Therefore, we propose a method of fixing the phase change value used to transmit the first slot of each coded block. Therefore, as shown in FIG. 72, the phase change value used to transmit the first slot of the second coded block is the phase change value used to transmit the first slot of the first coded block. Similarly, set it to # 0.

Similarly, as shown in FIG. 73, the phase change value used to transmit the first slot of the third coded block is not # 3, but the first of the first and second coded blocks. It is set to # 0, which is the same as the phase change value used to transmit the slot.

By doing so, it is possible to obtain the effect that the problems that occur in (a) and (b) can be suppressed.

In this embodiment, the method of initializing the phase change value for each coded block, that is, the phase change value used for the first slot of any coded block is fixed to # 0 and the method is described. , Alternatively, it can be done on a frame-by-frame basis. For example, in a symbol for transmitting information after transmission of a preamble or a control symbol, the phase change value used in the first slot may be fixed to # 0.

(Embodiment D3) In each of the above-described embodiments, the precoding matrix used by the weighting synthesizer for precoding is represented by a complex number, but the precoding matrix can also be represented by a real number.

That is, for example, the baseband signals (of the modulation method used) after the two mappings are s1 (i) and s2 (i) (where i is the time or frequency), and the two precodings are obtained. Let z1 (i) and z2 (i) be the baseband signals after coding. Then, the baseband signal (of the modulation method used) after mapping is the in-phase component of s1 (i)._s1(i) Q for orthogonal components_s1(i), the baseband signal after mapping (of the modulation method used) is the in-phase component of s2 (i) I_s2(i) Q for orthogonal components_s2(i), the baseband signal after precoding is z1 (i) and the in-phase component is I_z1(i) Q for orthogonal components_z1(i), the baseband signal after precoding is z2 (i), and the in-phase component is I._z2(i) Q for orthogonal components_z2If (i), then the precoding matrix H composed of real numbers_rWhen is used, the following relational expression is established.

<math num="76"><img file="JP2022017567A_D0077.tif" /></math>

However, the precoding matrix H composed of real numbers_rIs expressed as follows.

<math num="77"><img file="JP2022017567A_D0078.tif" /></math>

At this time, a₁₁, A₁₂, A₁₃, A₁₄, A₂₁, A₂₂, A₂₃, A₂₄, A₃₁, A₃₂, A₃₃, A₃₄, A₄₁, A₄₂, A₄₃, A₄₄Is a real number. However, {a₁₁= 0 and a₁₂= 0 and a₁₃= 0 and a₁₄= 0} must not hold and {a₂₁= 0 and a₂₂= 0 and a₂₃= 0 and a₂₄= 0} must not hold and {a₃₁= 0 and a₃₂= 0 and a₃₃= 0 and a₃₄= 0} must not hold and {a₄₁= 0 and a₄₂= 0 and a₄₃= 0 and a₄₄= 0} must not hold. And {a₁₁= 0 and a₂₁= 0 and a₃₁= 0 and a₄₁= 0} must not hold and {a₁₂= 0 and a₂₂= 0 and a₃₂= 0 and a₄₂= 0} must not hold and {a₁₃= 0 and a₂₃= 0 and a₃₃= 0 and a₄₃= 0} must not hold and {a₁₄= 0 and a₂₄= 0 and a₃₄= 0 and a₄₄= 0} must not hold.

(Embodiment E1) In the present embodiment, the transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is DVB (Digital Video Broadcasting) -T2 (T: Terrestrial). ) Explain the case of applying to the broadcasting system using the standard. First, the frame configuration of the broadcasting system using the DVB-T2 standard will be described.

FIG. 74 shows an outline of the frame configuration of the signal transmitted by the broadcasting station in the DVB-T2 standard. Since the DVB-T2 standard uses the OFDM method, the frame is configured on the time-frequency axis. FIG. 74 shows the frame configuration on the time-frequency axis, and the frames are P1 Signaling data (7401), L1 Pre-Signalling data (7402), L1 Post-Signalling data (7403), Common PLP (7404), It is composed of PLP # 1 ~ # N (7405_1 ~ 7405_N) (PLP: Physical Layer Pipe). (Here, L1 Pre-Signalling data (7402) and L1 Post-Signalling data (7403) are called P2 symbols.) Thus, P1 Signaling data (7401), L1 Pre-Signalling data (7402), L1 Post. -Signalling data (7403), Common The frame composed of PLP (7404) and PLP # 1 ~ # N (7405_1 ~ 7405_N) is named T2 frame, which is one unit of the frame structure.

P1 Signaling data (7401) is a symbol for the receiver to perform signal detection and frequency synchronization (including frequency offset estimation), and at the same time, FFT (Fast Fourier Transform) size information in the frame, SISO (Single-Input). Information on which method of single-output) / MISO (Multiple-Input Single-Output) is used to transmit the modulated signal is transmitted. (In the case of the SISO method, it is a method of transmitting one modulated signal, and in the case of the MISO method, it is a method of transmitting a plurality of modulated signals, and the spatiotemporal block shown in Non-Patent Documents 9, 16 and 17. The code is used.) L1 Pre-Signalling data (7402) provides information on the guard interval used in the transmission frame, information on the signal processing method used to reduce PAPR (Peak to Average Power Ratio), and L1 Post- Modulation method and error correction method (FEC:) when transmitting Signaling data Forward Error Correction), error correction method coding rate information, L1 Post-Signalling data size and information size information, pilot pattern information, cell (frequency area) unique number information, normal mode and extended mode (normal mode) And in the extended mode, the number of subcarriers used for data transmission is different.) Information on which method is used is transmitted.

Based on L1 Post-Signalling data (7403), information on the number of PLPs, information on the frequency region used, information on the unique number of each PLP, modulation method used to transmit each PLP, error correction method, error correction method. Information on the coding rate of, information on the number of blocks to be transmitted by each PLP, etc. are transmitted.

Common PLP (7404) and PLP # 1 ~ # N (7405_1 ~ 7405_N) are areas for transmitting data.

In the frame configuration shown in FIG. 74, P1 Signaling data (7401), L1 Pre-Signalling data (7402), L1 Post-Signalling data (7403), Common PLP (7404), and PLP # 1 to # N (7405_1 to 6105_N) are Although it is described as being transmitted in time division, in reality, there are two or more types of signals at the same time. An example is shown in FIG. As shown in FIG. 75, L1 Pre-Signalling data, L1 Post-Signalling data, and Common PLP may exist at the same time, or PLP # 1 and PLP # 2 may exist at the same time. .. That is, each signal uses both time division and frequency division to form a frame.

FIG. 76 shows a transmission device to which a transmission method for performing a phase change on a signal after precoding (or after precoding and baseband signal replacement) is applied to a transmission device in the DVB-T2 standard (for example, a broadcasting station). An example of the configuration of is shown.

The PLP signal generation unit 7602 receives transmission data 7601 (data for multiple PLPs) for PLP and control signal 7609 as inputs, and error correction coding information, modulation method information, etc. of each PLP included in the control signal 7609. Based on the information, error correction coding and mapping based on the modulation method are performed, and the (orthogonal) baseband signal 7603 of the PLP is output.

The P2 symbol signal generation unit 7605 receives the transmission data 7604 for the P2 symbol and the control signal 7609 as inputs, and performs error correction coding based on information such as error correction information and modulation method information of the P2 symbol included in the control signal 7609. , Performs mapping based on the modulation method and outputs the (orthogonal) baseband signal 7606 of the P2 symbol.

The control signal generation unit 7608 inputs the transmission data 7607 for the P1 symbol and the transmission data 7604 for the P2 symbol, and each symbol group in FIG. 74 (P1 Signaling data (7401), L1 Pre-Signalling data (7402), L1 Post. -Signalling data (7403), Common PLP (7404), PLP # 1 ~ # N (7405_1 ~ 7405_N)) transmission method (error correction code, error correction code coding rate, modulation method, block length, frame configuration, Information on selected transmission methods, including transmission methods that regularly switch precoding matrices, pilot symbol insertion methods, IFFT (Inverse Fast Fourier Transform) / FFT information, PAPR reduction method information, guard interval insertion method information) Is output as a control signal 7609.

The frame configuration unit 7610 receives the PLP baseband signal 7603, the P2 symbol baseband signal 7606, and the control signal 7609 as inputs, and sorts them on the frequency and time axes based on the frame configuration information included in the control signal. Stream 1 (orthogonal) baseband signal 7611_1 (mapped signal, that is, baseband signal based on the modulation method used), stream 2 (orthogonal) baseband signal 7611_2 (mapped signal) according to the frame configuration. That is, a baseband signal based on the modulation method used) is output.

The signal processing unit 7612 inputs the baseband signal 7611_1 of the stream 1, the baseband signal 7611_2 of the stream 2, and the control signal 7609, and the modulated signal 1 (7613_1) after signal processing based on the transmission method included in the control signal 7609. And output the modulated signal 2 (7613_2) after signal processing.

The characteristic point here is that when a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is selected as the transmission method, the signal processing unit displays FIG. Similar to FIGS. 25, 26, 27, 28, 29, and 69, the signal after precoding (or after precoding and replacement of the baseband signal) is processed to change the phase, and this signal processing is performed. The generated signals become the modulated signal 1 (7613_1) after signal processing and the modulated signal 2 (7613_2) after signal processing.

The pilot insertion unit 7614_1 takes the modulated signal 1 (7613_1) after signal processing and the control signal 7609 as inputs, and based on the information on the method of inserting the pilot symbol included in the control signal 7609, the modulated signal 1 (7613_1) after signal processing. The pilot symbol is inserted in, and the modulation signal 7615_1 after the pilot symbol is inserted is output.

The pilot insertion unit 7614_2 receives the modulated signal 2 (7613_2) after signal processing and the control signal 7609 as inputs, and the modulated signal 2 (7613_2) after signal processing is based on the information on the method of inserting the pilot symbol included in the control signal 7609. The pilot symbol is inserted in, and the modulation signal 7615_2 after the pilot symbol is inserted is output.

The IFFT (Inverse Fast Fourier Transform) section 7616_1 takes the modulation signal 7615_1 and the control signal 7609 after inserting the pilot symbol as inputs, performs IFFT based on the information of the IFFT method included in the control signal 7609, and applies the IFFT to the signal 7617_1 after IFFT. Is output.

The IFFT unit 7616_2 inputs the modulated signal 7615_2 and the control signal 7609 after inserting the pilot symbol, performs IFFT based on the information of the IFFT method included in the control signal 7609, and outputs the signal 7617_2 after IFFT.

The PAPR reduction unit 7618_1 inputs the signal 7617_1 after IFFT and the control signal 7609, and based on the information on PAPR reduction contained in the control signal 7609, processes the signal 7617_1 after IFFT for PAPR reduction, and after PAPR reduction. Signal 7619_1 is output.

The PAPR reduction unit 7618_2 takes the signal 7617_2 after IFFT and the control signal 7609 as inputs, and based on the information on PAPR reduction contained in the control signal 7609, processes the signal 7617_2 after IFFT for PAPR reduction, and after PAPR reduction. Signal 7619_2 is output.

The guard interval insertion unit 7620_1 inputs the PAPR reduced signal 7619_1 and the control signal 7609, and inserts the guard interval into the PAPR reduced signal 7619_1 based on the information on the guard interval insertion method included in the control signal 7609. The signal 7621_1 after the guard interval is inserted is output.

The guard interval insertion unit 7620_2 receives the PAPR reduced signal 7619_2 and the control signal 7609 as inputs, and inserts the guard interval into the PAPR reduced signal 7619_2 based on the information on the guard interval insertion method included in the control signal 7609. The signal 7621_2 after the guard interval is inserted is output.

The P1 symbol insertion unit 7622 inputs the signal 7621_1 after inserting the guard interval, the signal 7621_2 after inserting the guard interval, and the transmission data 7607 for the P1 symbol, and generates the signal of the P1 symbol from the transmission data 7607 for the P1 symbol. The P1 symbol was added to the signal 7621_1 after the guard interval was inserted, and the P1 symbol was added to the signal 7623_1 after the P1 symbol was added, and the P1 symbol was added to the signal 7621_2 after the guard interval was inserted. The later signal 7623_2 is output. The signal of the P1 symbol may be added to both the signal 7623_1 after the P1 symbol is added and the signal 7623_2 after the P1 symbol is added, or may be added to either of them. When it is added to one of them, in the section where the added signal is added, a zero signal exists as a baseband signal in the signal not added.

The wireless processing unit 7624_1 takes the signal 7623_1 and the control signal 7609 after adding the P1 symbol as inputs, performs processing such as frequency conversion and amplification, and outputs the transmission signal 7625_1. Then, the transmission signal 7625_1 is output as a radio wave from the antenna 7626_1.

The wireless processing unit 7624_2 receives the processed signal 7623_2 and the control signal 7609 for the P1 symbol as inputs, performs processing such as frequency conversion and amplification, and outputs the transmission signal 7625_2. Then, the transmission signal 7625_2 is output as a radio wave from the antenna 7626_2.

Figure 77 shows the P1 symbol, P2 symbol, and Common. An example of the frame configuration on the frequency-time axis when transmitting multiple PLPs after transmitting PLPs is shown. In FIG. 77, stream s1 (the signal after mapping, that is, the baseband signal based on the modulation method used) uses subcarriers # 1 to subcarrier #M in the frequency axis, and similarly stream s2 (mapping). The later signal, that is, the baseband signal based on the modulation method used) also uses subcarriers # 1 to subcarrier #M in the frequency axis. Therefore, if the symbols exist at the same time of the same subcarrier in both s1 and s2, the symbols of the two streams exist at the same frequency. As described in other embodiments, when a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, s1 and s2 are precoded. Weighting and synthesis are performed using a matrix (and, in some cases, baseband signal replacement is performed thereafter), and in addition, phase change is performed. As a result, if the obtained signals are z1 and z2 here, z1 and z2 will be output from the antenna, respectively.

As shown in FIG. 77, in section 1, stream s1 and stream s2 are used to transmit the symbol group 7701 of PLP # 1, and the spatial multiplex MIMO transmission method shown in FIG. 23 or the precoding matrix is fixed. Data shall be transmitted using the MIMO transmission method of (No phase change shall be performed).

In section 2, stream s1 is used to transmit the symbol group 7702 of PLP # 2, and data is transmitted by transmitting one modulated signal.

In section 3, stream s1 and stream s2 are used to transmit the symbol group 7703 of PLP # 3, and a transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is used. It shall be used to transmit data.

In section 4, stream s1 and stream s2 are used to transmit the symbol group 7704 of PLP # 4, and data is transmitted using the spatiotemporal block code shown in Non-Patent Documents 9, 16 and 17. And.

When a broadcasting station transmits each PLP as shown in FIG. 77, the receiving device that receives the transmission signal of FIG. 77 needs to know the transmission method of each PLP. Therefore, as described above, it is necessary to transmit information on the transmission method of each PLP using the P2 symbol L1 Post-Signalling data (7403 in FIG. 74). Hereinafter, an example of the method of constructing the P1 symbol and the method of constructing the P2 symbol at this time will be described.

Table 2 shows specific examples of control information transmitted using the P1 symbol.

<tables><img file="JP2022017567A_D0079.tif" /></tables>

In the DVB-T2 standard, whether or not the DVB-T2 standard is used based on the S1 control information (3-bit information), and if the DVB-T2 standard is used, the receiving device determines the transmission method used. You can judge.

As shown in Table 2 above, when "000" is set as the 3-bit S1 information, the modulated signal to be transmitted conforms to "one modulated signal transmission of the DVB-T2 standard". ..

Further, when "001" is set as the 3-bit S1 information, the modulated signal to be transmitted conforms to "transmission using the spatio-temporal block code of the DVB-T2 standard".

In the DVB-T2 standard, "010" to "111" are "Reserve" for the future. Here, in order to apply the present invention so as to be compatible with DVB-T2, for example, when "010" is set as the 3-bit S1 information (other than "000" and "001" may be used. ), We decided to show that the modulated signal to be transmitted complies with standards other than DVB-T2, and when the receiving device of the terminal finds that this information is "010", the modulated signal transmitted by the broadcasting station is You can know that it complies with standards other than DVB-T2.

Next, an example of how to configure the P2 symbol when the modulated signal transmitted by the broadcasting station complies with a standard other than DVB-T2 will be described. The first example describes a method using P2 symbols in the DVB-T2 standard.

Table 3 shows the first example of control information transmitted by L1 Post-Signalling data among P2 symbols.

<tables><img file="JP2022017567A_D0080.tif" /></tables>

In Table 3 above, each abbreviation is used with the following meaning.

SISO: Single-Input Single-Output (Transmission of one modulated signal, received by one antenna) SIMO: Single-Input Multiple-Output (Transmission of one modulated signal, received by multiple antennas) MISO: Multiple-Input Single-Output (Multiple modulated signals are transmitted by multiple antennas and received by one antenna) MIMO: Multiple-Input Multiple-Output (Transmit multiple modulated signals with multiple antennas, receive with multiple antennas) The 2-bit information "PLP_MODE" shown in Table 3 is each PLP (as shown in FIG. 77). In FIG. 77, the symbol group of PLP # 1 is shown by the symbol group of # 4. Hereinafter, "symbol group" is omitted for the sake of brevity.) Control information for notifying the terminal of the transmission method. Therefore, the information of PLP_MODE will exist for each PLP. That is, in the case of FIG. 77, the PLP_MODE information for PLP # 1, the PLP_MODE information for PLP # 2, the PLP_MODE information for PLP # 3, the PLP_MODE information for PLP # 4, and so on. , Will be transmitted from the broadcasting station. As a matter of course, the terminal can recognize the transmission method used by the broadcasting station for PLP by demodulating this information (and also performing error correction and decoding).

When "00" is set as "PLP_MODE", the PLP transmits data by a method of "transmitting one modulated signal". When set to "01", the PLP is a method of "transmitting a plurality of modulated signals subjected to spatiotemporal block coding", and data is transmitted. When set to "10", the PLP transmits data using "a transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement)". When set to "11", data is transmitted to the PLP using "MIMO method with fixed precoding matrix or spatial multiplex MIMO transmission method".

If "PLP_MODE" is set to any of "01" to "11", what kind of processing was specifically performed by the broadcasting station (for example, after precoding (or precoding and baseband)). It is necessary to transmit to the terminal a specific switching method in the transmission method for changing the phase of the signal (after signal replacement), the spatiotemporal block coding method used, and the configuration of the matrix used as the precoding matrix). The method of configuring the control information, which is different from that in Table 3, including the configuration of the control information at this time, will be described below.

Table 4 is a second example of the P2 symbol, which is different from Table 3 of the control information transmitted by L1 Post-Signalling data.

<tables><img file="JP2022017567A_D0081.tif" /></tables>

As shown in Table 4, the 1-bit information "PLP_MODE", the 1-bit information "MIMO_MODE", the 2-bit information "MIMO_PATTERN # 1", and the 2-bit information "MIMO_PATTERN # 2" are These four control information exist and, as shown in FIG. 77, are information for notifying the terminal of the transmission method of each PLP (PLP # 1 to # 4 in FIG. 77), and therefore these four. Control information will exist for each PLP. That is, in the case of FIG. 77, PLP_MODE information / MIMO_MODE information for PLP # 1 / MIMO_PATTERN # 1 information / MIMO_PATTERN # 2, PLP_MODE information for PLP # 2 / MIMO_MODE information / MIMO_PATTERN # 1 Information / MIMO_PATTERN # 2, PLP_MODE information for PLP # 3 / MIMO_MODE information / MIMO_PATTERN # 1 information / MIMO_PATTERN # 2, PLP_MODE information for PLP # 4 / MIMO_MODE information / MIMO_PATTERN Information of # 1 / Information of MIMO_PATTERN # 2 ... will be transmitted from the broadcasting station. As a matter of course, the terminal can recognize the transmission method used by the broadcasting station for PLP by demodulating this information (and also performing error correction and decoding).

When "0" is set as "PLP_MODE", the PLP "transmits one modulated signal" to transmit data. When set to "1", the PLP "transmits multiple modulated signals with spatiotemporal block encoding" and "phase changes to the signal after precoding (or after precoding and baseband signal replacement)". Data is transmitted by any of "transmission method", "MIMO method with fixed precoding matrix", and "spatial multiplex MIMO transmission method".

If "PLP_MODE" is set to "1", the "MIMO_MODE" information is valid, and if "MIMO_MODE" is set to "0", after precoding (or precoding and baseband signal replacement). Data is transmitted without using a transmission method that changes the phase of the signal (later). When "1" is set as "MIMO_MODE", data is transmitted using a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement).

When "PLP_MODE" is set to "1" and "MIMO_MODE" is set to "0", the information of "MIMO_PATTERN # 1" is valid information, and when "MIMO_PATTERN # 1" is set to "00", when Data is transmitted using the spatial block code. When "01" is set, the data is transmitted by using the precoding method in which the precoding matrix # 1 is fixedly used for weighted synthesis. When "10" is set, data is transmitted using a precoding method in which precoding matrix # 2 is fixedly used for weighted synthesis. (However, the precoding matrix # 1 and the precoding matrix # 2 are different matrices.) When "11" is set, data is transmitted using the spatial multiplex MIMO transmission method.

When "PLP_MODE" is set to "1" and "MIMO_MODE" is set to "1", the information of "MIMO_PATTERN # 2" is valid information, and when "MIMO_PATTERN # 2" is set to "00", the phase is Data is transmitted using a transmission method that modifies the signal after precoding of change # 1 (or after precoding and baseband signal replacement). When "01" is set, data is transmitted using a transmission method that changes the phase of the signal after precoding of phase change # 2 (or after precoding and baseband signal replacement). When set to "10", data is transmitted using a transmission method that changes the phase of the signal after precoding of phase change # 3 (or after precoding and baseband signal replacement). When set to "11", data is transmitted using a transmission method that changes the phase of the signal after precoding of phase change # 4 (or after precoding and baseband signal replacement). Here, the phase changes # 1 to # 4 are different methods, but at this time, if # A and #B are different methods, for example, . Multiple phase changes used for #A and # Among the multiple phase changes used for B, the same phase change is included, but the period is different. . There is a phase change value that is included in #A but not in #B. There are three methods that the multiple phase changes used in A are not included in the phase changes used in the #B method.

In the above, the control information in Tables 3 and 4 has been described as being transmitted by L1 Post-Signalling data among the P2 symbols. However, in the DVB-T2 standard, there is a limit to the amount of information that can be transmitted as a P2 symbol. Therefore, if the limit of the amount of information that can be transmitted as a P2 symbol is exceeded by adding the information in Tables 3 and 4 in addition to the information that needs to be transmitted by the P2 symbol in the DVB-T2 standard, as shown in Fig. 78. Signaling PLP (7801) may be provided in, and the control information required for standards other than the DVB-T2 standard (which may be a part, that is, transmitted by both L1 Post-Signalling data and Signaling PLP) may be transmitted. .. In FIG. 78, the frame configuration is the same as that in FIG. 74, but the frame configuration is not limited to this, and the Signaling PLP is set on the time-frequency axis as in the L1 Pre-signaling data in FIG. 75. , Specific time-may be assigned to a specific carrier area, i.e., on the time-frequency axis, Signaling You can assign PLPs in any way you like.

As described above, the signal after precoding (or after precoding and baseband signal replacement) is used while maintaining compatibility with the DVB-T2 standard while using a multi-carrier transmission method such as the OFDM method. By making it possible to select a transmission method for changing the phase, it is possible to obtain an advantage that high reception quality can be obtained and a high transmission speed can be obtained for the LOS environment. In this embodiment, as the transmission method in which the carrier group can be set, "spatial multiplex MIMO transmission method, MIMO method using a fixed precoding matrix, after precoding (or after precoding and baseband signal replacement). ) Is a transmission method that changes the phase of the signal, spatiotemporal block coding, and a transmission method that transmits only stream s1, but it is not limited to this.

Then, "spatial multiplex MIMO transmission method, MIMO method using a fixed precoding matrix, transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement), spatiotemporal block coding". , A transmission method that transmits only stream s1 "was explained in the example that the broadcasting station can select, but all of these transmission methods do not have to be selectable transmission methods. The MIMO method to be used, the transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), the spatiotemporal block coding, and the transmission method that transmits only the stream s1 can be selected. MIMO method using a typical precoding matrix, a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), and a transmission method that can select spatiotemporal block coding. A transmission method that can select a MIMO method that uses a fixed precoding matrix, a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), and a transmission method that transmits only the stream s1. Transmission method that can select the transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), spatiotemporal block coding, and transmission method that transmits only stream s1 . Fixed precoding MIMO method using a matrix, transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) . Phase to the signal after precoding (or after precoding and baseband signal replacement) Transmission method to change, transmission method with selectable spatiotemporal block coding . After precoding (or precoding), such as a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), or a transmission method that can select a transmission method that transmits only stream s1. And by including a transmission method that changes the phase of the signal (after replacing the baseband signal), high-speed data transmission can be performed in the LOS environment, and the reception data quality of the receiving device can be ensured. The effect can be obtained.

At this time, as described above, it is necessary to set S1 in the P1 symbol, and as a P2 symbol, as a control information setting method different from Table 3 (setting method of the transmission method of each PLP), for example, a table. 5 can be considered.

<tables><img file="JP2022017567A_D0082.tif" /></tables>

The difference between Table 5 and Table 3 is that when "PLP_MODE" is set to "11", it is set to Reserve. In this way, when the selectable transmission method as the PLP transmission method is as shown in the above example, the number of bits constituting PLP_MODE in Tables 3 and 5, for example, depends on the number of selectable transmission methods. It may be larger or smaller.

The same applies to Table 4. For example, if the MIMO transmission method only supports a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), "MIMO_MODE" is selected. No control information is needed. Further, in "MIMO_PATTERN # 1", for example, if the precoding matrix does not support a fixed MIMO method, the control information of "MIMO_PATTERN # 1" may not be required, and the precoding matrix is fixed. If multiple precoding matrices used in a typical MIMO system are not required, 1-bit control information may be used instead of 2-bit control information, and if multiple precoding matrices can be set, 2 It may be control information of bits or more.

You can think of "MIMO_PATTERN # 2" in the same way, if you do not need multiple phase change switching methods as a transmission method to change the phase of the signal after precoding (or after precoding and baseband signal replacement). It may be 1-bit control information instead of 2-bit control information, and may be 2 or more bits of control information when a plurality of phase change switching methods can be set.

Further, in the present embodiment, the case where the number of antennas of the transmitting device is 2 has been described, but the present invention is not limited to this, and control information may be similarly transmitted even when the number of antennas is larger than 2. At this time, in addition to the case where the modulated signal is transmitted using the two antennas, there is a case where it is necessary to increase the number of bits constituting each control information in order to carry out the case where the modulated signal is transmitted using the four antennas. do. At this time, the point that the control information is transmitted by the P1 symbol and the control information is transmitted by the P2 symbol is the same as the case described above.

Regarding the frame configuration of the PLP symbol group transmitted by the broadcasting station, a method of transmitting in time division as shown in FIG. 77 has been described, but a modified example thereof will be described below.

Figure 79 shows the P1 symbol, P2 symbol, and Common, which are different from Figure 77. An example of how to arrange the symbols of streams s1 and s2 on the frequency-time axis after transmitting the PLP is shown. In FIG. 79, the symbol described as "# 1" indicates one of the symbols of PLP # 1 in FIG. 77. Similarly, the symbol labeled "# 2" indicates one of the symbols in PLP # 2 in FIG. 77, and the symbol labeled "# 3" represents the PLP in FIG. 77. It indicates one symbol of the symbol group of # 3, and the symbol described as "# 4" indicates one symbol of the symbol group of PLP # 4 in FIG. 77. Then, as in FIG. 77, PLP # 1 shall transmit data using the spatial multiplex MIMO transmission method shown in FIG. 23 or the MIMO transmission method having a fixed precoding matrix. Then, PLP # 2 shall transmit data by transmitting one modulated signal. PLP # 3 shall transmit data using a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement). PLP # 4 shall transmit data using the spatiotemporal block code.

In FIG. 79, when the symbols exist at the same time of the same subcarrier (referred to as carrier in FIG. 79) in both s1 and s2, the symbols of the two streams exist at the same frequency. Become. As described in other embodiments, when a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, s1 and s2 are precoded. Weighting and synthesis are performed using a matrix (and, in some cases, baseband signal replacement ), and in addition, phase change is performed. As a result, if the obtained signals are z1 and z2 here, z1 and z2 will be output from the antenna, respectively.

The difference between FIG. 79 and FIG. 77 is that, as described above, FIG. 77 shows an example in which a plurality of PLPs are arranged in time division, but in FIG. 79, unlike FIG. 77, time division and frequency division are shown. In combination with, multiple PLPs are present. That is, for example, at time 1, the symbol of PLP # 1 and the symbol of PLP # 2 exist, and at time 3, the symbol of PLP # 3 and the symbol of PLP # 4 exist. In this way, PLP symbols with different indexes (#X; X = 1, 2, ...) can be assigned to each symbol (consisting of 1 time, 1 subcarrier).

In addition, in FIG. 79, simply, at time 1, only "# 1" and "# 2" exist, but the index is not limited to this, and "# 1" and "# 2" are indexes other than PLP. The PLP symbol of PLP may exist at time 1, and the relationship between the subcarrier and the PLP index at time 1 is not limited to FIG. 79, and the PLP symbol of which index is assigned to the subcarrier. Is also good. Similarly, at other times, the PLP symbol of any index may be assigned to the subcarrier.

FIG. 80 shows an example of how the symbols of streams s1 and s2 are arranged on the frequency-time axis after transmitting P1 symbols, P2 symbols, and Common PLP different from those in FIG. 77. The characteristic part in FIG. 80 is that in the T2 frame, when the transmission method of PLP is based on the transmission of multiple antennas, the "transmission method of transmitting only the stream s1" cannot be selected.

Therefore, in FIG. 80, it is assumed that the symbol group 8001 of PLP # 1 is transmitted by "spatial multiplex MIMO transmission method or MIMO method using a fixed precoding matrix". It is assumed that the symbol group 8002 of PLP # 2 is transmitted with data by "a transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement)". It is assumed that data is transmitted in the symbol group 8003 of PLP # 3 by the "space-time block code". The PLP symbol group in the T2 frame after the PLP # 3 symbol group 8003 is "spatial multiplex MIMO transmission method or MIMO method using a fixed precoding matrix", "after precoding (or precoding)". Data will be transmitted by either a transmission method of changing the phase of the signal (after coding and baseband signal replacement) or a spatiotemporal block code.

FIG. 81 shows an example of how the symbols of the streams s1 and s2 are arranged on the frequency-time axis after transmitting the P1 symbol, the P2 symbol, and the Common PLP, which are different from those in FIG. 79. In FIG. 81, the symbol described as "# 1" indicates one of the symbols of PLP # 1 in FIG. 80. Similarly, the symbol described as "# 2" indicates one of the symbols in PLP # 2 in FIG. 80, and the symbol described as "# 3" indicates PLP in FIG. 80. Shows one symbol in the # 3 symbol group. Then, as in FIG. 80, PLP # 1 shall transmit data using the spatial multiplex MIMO transmission method shown in FIG. 23 or the MIMO transmission method having a fixed precoding matrix. Then, PLP # 2 shall transmit data by using a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement). PLP # 3 shall transmit data using a space-time block code.

In FIG. 81, if the symbols exist at the same time of the same subcarrier (referred to as carrier in FIG. 81) in both s1 and s2, it means that the symbols of the two streams exist at the same frequency. .. As described in other embodiments, when a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, s1 and s2 are precoded. Weighting and synthesis are performed using a matrix (and, in some cases, baseband signal replacement is performed thereafter), and in addition, phase change is performed. As a result, if the obtained signals are z1 and z2 here, z1 and z2 will be output from the antenna, respectively.

In FIG. 81, unlike FIG. 80, a plurality of PLPs are present by using time division and frequency division in combination. That is, for example, at time 1, the symbol of PLP # 1 and the symbol of PLP # 2 exist. In this way, PLP symbols with different indexes (#X; X = 1, 2, ...) can be assigned to each symbol (consisting of 1 time, 1 subcarrier).

In addition, in FIG. 81, simply, at time 1, only "# 1" and "# 2" exist, but the index is not limited to this, and "# 1" and "# 2" are indexes other than PLP. The PLP symbol of PLP may exist at time 1, and the relationship between the subcarrier and the PLP index at time 1 is not limited to FIG. 81, and the PLP symbol of which index is assigned to the subcarrier. Is also good. Similarly, at other times, the PLP symbol of any index may be assigned to the subcarrier. On the other hand, at a certain time, such as time 3, only one PLP symbol may be assigned. That is, the PLP symbols may be assigned in any time-frequency frame method.

In this way, since there is no PLP using the "transmission method that transmits only stream s1" in the T2 frame, the dynamic range of the received signal received by the terminal can be suppressed, and good reception quality can be obtained. The effect of being able to increase the sex can be obtained.

In the description of FIG. 81, as the transmission method, "spatial multiplex MIMO transmission method or MIMO method using a fixed precoding matrix", "after precoding (or after precoding and baseband signal replacement)" Although the explanation was given in the example of selecting either "transmission method for changing the phase of the signal of" or "spatio-temporal block code", it is not necessary to assume that all of these transmission methods can be selected. "Transmission method that changes the phase of the signal after coding (or after precoding and baseband signal replacement)", "spatio-temporal block code", and "MIMO method using a fixed precoding matrix" can be selected. "Transmission method to change the phase of the signal after coding (or after precoding and baseband signal replacement)" and "spatio-temporal block code" can be selected.-After precoding (or after precoding and baseband signal replacement) ), A transmission method that changes the phase of the signal, and a MIMO method that uses a fixed precoding matrix may be selectable.

In the above, the case where a plurality of PLPs exist in the T2 frame has been described, but the case where only one PLP exists in the T2 frame will be described below.

FIG. 82 shows an example of the frame configuration of streams s1 and s2 on the time-frequency axis when there is only one PLP in the T2 frame. In FIG. 82, the term "control symbol" is used, which means a symbol such as the P1 symbol and the P2 symbol described above. Then, in FIG. 82, the first T2 frame is transmitted using the section 1, the second T2 frame is transmitted using the section 2, and the third T2 is transmitted using the section 3. The frame is being transmitted, and the fourth T2 frame is being transmitted using section 4.

Further, in FIG. 82, in the first T2 frame, the symbol group 8101 of PLP # 1-1 is transmitted, and as the transmission method, "spatial multiplex MIMO transmission method or a fixed precoding matrix is used. "MIMO method" is selected.

In the second T2 frame, the symbol group 8102 of PLP # 2-1 is transmitted, and "a method of transmitting one modulated signal" is selected as the transmission method.

In the third T2 frame, the symbol group 8103 of PLP # 3-1 is transmitted, and the transmission method is "to change the phase of the signal after precoding (or after precoding and baseband signal replacement)". "Send method" is selected.

In the fourth T2 frame, the symbol group 8104 of PLP # 4-1 is transmitted, and "space-time block code" is selected as the transmission method.

In FIG. 82, when the symbols exist at the same time of the same subcarrier in both s1 and s2, the symbols of the two streams exist at the same frequency. As described in other embodiments, when a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, s1 and s2 are precoded. Weighting and synthesis are performed using a matrix (and, in some cases, baseband signal replacement is performed thereafter), and in addition, phase change is performed. As a result, if the obtained signals are z1 and z2 here, z1 and z2 will be output from the antenna, respectively.

By doing so, the transmission method can be set in consideration of the data transmission speed and the data reception quality of the terminal for each PLP, so that the improvement of the data transmission speed and the assurance of the data reception quality can be achieved at the same time. It becomes possible. An example of a method for configuring control information such as a transmission method for P1 symbols and P2 symbols (in some cases, Signaling PLP) can be similarly implemented by configuring as shown in Tables 2 to 5 above. .. The difference between FIG. 82 and FIG. 77 is that in the frame configuration shown in FIG. 77 and the like, since one T2 frame has a plurality of PLPs, control information such as a transmission method for a plurality of PLPs is required. In the case of the frame configuration shown in FIG. 82, since there is only one PLP in one T2 frame, only control information such as the transmission method for that one PLP is required.

In the above, the method of transmitting information on the PLP transmission method using the P1 symbol and the P2 symbol (Signalling PLP in some cases) has been described, but in the following, in particular, the PLP transmission method without using the P2 symbol. Describes how to transmit information about.

FIG. 83 shows a frame configuration on the time-frequency axis when the terminal to which the broadcasting station transmits data supports a standard other than the DVB-T2 standard. In FIG. 83, the same reference numerals are given to the same configurations as those in FIG. 74. The frame in FIG. 83 is composed of P1 Signaling data (7401), 1st Signaling data (8301), 2nd Signaling data (8302), Common PLP (7404), and PLP # 1 ~ # N (7405_1 ~ 7405_N). (PLP: Physical Layer Pipe). In this way, a frame composed of P1 Signaling data (7401), 1st Signaling data (8301), 2nd Signaling data (8302), Common PLP (7404), PLP # 1 ~ # N (7405_1 ~ 7405_N). Is the unit of one frame.

P1 Signaling data (7401) is a symbol for the receiver to perform signal detection and frequency synchronization (including frequency offset estimation), and at the same time, to identify whether it is a DVB-T2 standard frame. Data, for example, S1 shown in Table 2, must be transmitted to be / not a DVB-T2 standard signal.

According to the first Signaling data (8301), for example, information on the guard interval used in the transmission frame, information on the signal processing method used to reduce PAPR (Peak to Average Power Ratio), and the second Signaling data are transmitted. Modulation method, error correction method, error correction method coding rate information, second Signaling data size and information size information, pilot pattern information, cell (frequency region) unique number information, normal mode and extended mode A method of transmitting information such as which method is used can be considered. At this time, the first Signaling data (8301) does not necessarily have to transmit data conforming to the DVB-T2 standard.

According to the second Signaling data (8302), for example, information on the number of PLPs, information on the frequency region used, information on the unique number of each PLP, the modulation method used to transmit each PLP, error correction method, and error correction. Information on the coding rate of the method, information on the number of blocks to be transmitted by each PLP, etc. are transmitted.

In the frame configuration of FIG. 83, the first Signaling data (8301), the second Signaling data (8302), the L1 Post-Signalling data (7403), the Common PLP (7404), and the PLP # 1 to # N (7405_1 to 7405_N) are Although it is described as being transmitted in time division, in reality, there are two or more types of signals at the same time. An example is shown in FIG. As shown in FIG. 84, the first Signaling data, the second Signaling data, and the Common PLP may exist at the same time, or PLP # 1 and PLP # 2 may exist at the same time. That is, each signal uses both time division and frequency division to form a frame.

FIG. 85 shows the phase change of the transmitter of a standard different from that of DVB-T2 (for example, a broadcasting station) to the signal after precoding (or after precoding and baseband signal replacement) described above. An example of the configuration of the transmission device to which the transmission method of performing the above is applied is shown. In FIG. 85, those operating in the same manner as in FIG. 76 are designated by the same reference numerals, and the description of the operation is the same as described above.

The control signal generation unit 7608 inputs the transmission data 8501 for the first and second signaling data and the transmission data 7607 for the P1 symbol, and the transmission method (error correction code, code of the error correction code) of each symbol group in FIG. PAPR reduction methods such as conversion rate, modulation method, block length, frame configuration, selected transmission method including transmission method to switch precoding matrix regularly, pilot symbol insertion method, IFFT (Inverse Fast Fourier Transform) / FFT information, etc. Information, information on how to insert the guard interval) is output as the control signal 7609.

The control symbol signal generation unit 8502 receives the transmission data 8501 and the control signal 7609 for the first and second signaling data as inputs, and the error correction information and the modulation method of the first and second signaling data included in the control signal 7609. Based on information such as information, error correction coding and mapping based on the modulation method are performed, and the (orthogonal) baseband signal 8503 of the first and second Signaling data is output.

In the case of FIG. 85, the frame component unit 7610 inputs the baseband signal 8503 generated by the control symbol signal generation unit 8502 instead of the baseband signal 7606 generated by the P2 symbol signal generation unit 7605 shown in FIG. ..

Next, a broadcasting station (base station) when a transmission method that changes the phase of the precoded (or after precoding and baseband signal replacement) transmission method is applied to a system with a standard different from DVB-T2. The frame configuration of the transmission signal and the transmission method of control information (P1 symbol and information transmitted by the first and second Signaling data) will be described in detail with reference to FIG. 77.

FIG. 77 shows an example of the frame configuration on the frequency-time axis when transmitting a plurality of PLPs after transmitting the P1 symbol, the first and second Signaling data, and the Common PLP. In FIG. 77, the stream s1 uses subcarriers # 1 to subcarrier #M on the frequency axis, and similarly, the stream s2 uses subcarriers # 1 to subcarrier #M on the frequency axis. Therefore, if the symbols exist at the same time of the same subcarrier in both s1 and s2, the symbols of the two streams exist at the same frequency. As described in other embodiments, when a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, s1 and s2 are precoded. Weighting and synthesis are performed using a matrix (and, in some cases, baseband signal replacement is performed thereafter), and in addition, phase change is performed. As a result, if the obtained signals are z1 and z2 here, z1 and z2 will be output from the antenna, respectively.

As shown in FIG. 77, in section 1, stream s1 and stream s2 are used to transmit the symbol group 7701 of PLP # 1, and the spatial multiplex MIMO transmission method shown in FIG. 23 or the precoding matrix is fixed. Data shall be transmitted using the MIMO transmission method of.

In section 2, stream s1 is used to transmit the symbol group 7702 of PLP # 2, and data is transmitted by transmitting one modulated signal.

In section 3, stream s1 and stream s2 are used to transmit the symbol group 7703 of PLP # 3, and a transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is used. It shall be used to transmit data.

In section 4, stream s1 and stream s2 are used to transmit the symbol group 7704 of PLP # 4, and data is transmitted using the spatiotemporal block code.

When a broadcasting station transmits each PLP as shown in FIG. 77, the receiving device that receives the transmission signal of FIG. 64 needs to know the transmission method of each PLP. Therefore, as described above, it is necessary to transmit information on the transmission method of each PLP using the first and second Signaling data. Hereinafter, an example of the method of configuring the P1 symbol at this time and the method of configuring the first and second Signaling data will be described. Table 2 shows specific examples of control information transmitted using the P1 symbol.

In the DVB-T2 standard, whether or not the DVB-T2 standard is used based on the S1 control information (3-bit information), and if the DVB-T2 standard is used, the receiving device determines the transmission method used. You can judge. When "000" is set as the 3-bit S1 information, the modulated signal to be transmitted conforms to "one modulated signal transmission of the DVB-T2 standard".

Further, when "001" is set as the 3-bit S1 information, the modulated signal to be transmitted conforms to "transmission using the spatio-temporal block code of the DVB-T2 standard".

In the DVB-T2 standard, "010" to "111" are "Reserve" for the future. Here, in order to apply the present invention so as to be compatible with DVB-T2, for example, when "010" is set as the 3-bit S1 information (other than "000" and "001" may be used. ), We decided to show that the modulated signal to be transmitted complies with standards other than DVB-T2, and when the receiving device of the terminal finds that this information is "010", the modulated signal transmitted by the broadcasting station is You can know that it complies with standards other than DVB-T2.

Next, an example of how to configure the first and second Signaling data when the modulated signal transmitted by the broadcasting station complies with a standard other than DVB-T2 will be described. Table 3 shows the first example of the control information of the first and second Signaling data.

As shown in Fig. 77, "PLP_MODE", which is the 2-bit information shown in Table 3, is the control information for notifying the terminal of the transmission method of each PLP (PLP # 1 to # 4 in Fig. 77). Yes, PLP_MODE information will exist for each PLP. That is, in the case of FIG. 77, the PLP_MODE information for PLP # 1, the PLP_MODE information for PLP # 2, the PLP_MODE information for PLP # 3, the PLP_MODE information for PLP # 4, and so on. , Will be transmitted from the broadcasting station. As a matter of course, the terminal can recognize the transmission method used by the broadcasting station for PLP by demodulating this information (and also performing error correction and decoding).

When "00" is set as "PLP_MODE", the PLP "transmits one modulated signal" to transmit data. When set to "01", the PLP "transmits a plurality of modulated signals with spatiotemporal block coding" to transmit data. When set to "10", the PLP transmits data using "a transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement)". When set to "11", data is transmitted to the PLP using "MIMO method with fixed precoding matrix or spatial multiplex MIMO transmission method".

If "PLP_MODE" is set to any of "01" to "11", what kind of processing was specifically performed by the broadcasting station (for example, after precoding (or precoding and baseband)). It is necessary to transmit to the terminal a specific phase switching method in the transmission method for changing the phase of the signal (after signal replacement), the spatiotemporal block coding method used, and the configuration of the matrix used as the precoding matrix). The method of configuring the control information, which is different from that in Table 3, including the configuration of the control information at this time, will be described below.

Table 4 shows the second example of the control information of the first and second Signaling data.

As shown in Table 4, the 1-bit information "PLP_MODE", the 1-bit information "MIMO_MODE", the 2-bit information "MIMO_PATTERN # 1", and the 2-bit information "MIMO_PATTERN # 2" are These four control information exist and, as shown in FIG. 77, are information for notifying the terminal of the transmission method of each PLP (PLP # 1 to # 4 in FIG. 77), and therefore these four. Control information will exist for each PLP. That is, in the case of FIG. 77, PLP_MODE information / MIMO_MODE information for PLP # 1 / MIMO_PATTERN # 1 information / MIMO_PATTERN # 2, PLP_MODE information for PLP # 2 / MIMO_MODE information / MIMO_PATTERN # 1 Information / MIMO_PATTERN # 2, PLP_MODE information for PLP # 3 / MIMO_MODE information / MIMO_PATTERN # 1 information / MIMO_PATTERN # 2, PLP_MODE information for PLP # 4 / MIMO_MODE information / MIMO_PATTERN Information of # 1 / Information of MIMO_PATTERN # 2 ... will be transmitted from the broadcasting station. As a matter of course, the terminal can recognize the transmission method used by the broadcasting station for PLP by demodulating this information (and also performing error correction and decoding).

When "0" is set as "PLP_MODE", the PLP "transmits one modulated signal" to transmit data. When set to "1", the PLP "transmits multiple modulated signals with spatiotemporal block encoding" and "phase changes to the signal after precoding (or after precoding and baseband signal replacement)". Data is transmitted by any of "transmission method", "MIMO method with fixed precoding matrix", and "spatial multiplex MIMO transmission method".

If "PLP_MODE" is set to "1", the "MIMO_MODE" information is valid, and if "MIMO_MODE" is set to "0", after precoding (or precoding and baseband signal replacement). Data is transmitted without using a transmission method that changes the phase of the signal (later). When "1" is set as "MIMO_MODE", data is transmitted using a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement).

When "PLP_MODE" is set to "1" and "MIMO_MODE" is set to "0", the information of "MIMO_PATTERN # 1" is valid information. At this time, if "00" is set as "MIMO_PATTERN # 1", data is transmitted using the space-time block code. When "01" is set, the data is transmitted by using the precoding method in which the precoding matrix # 1 is fixedly used for weighted synthesis. When "10" is set, data is transmitted using a precoding method in which precoding matrix # 2 is fixedly used for weighted synthesis. (However, the precoding matrix # 1 and the precoding matrix # 2 are different matrices.) When "11" is set, data is transmitted using the spatial multiplex MIMO transmission method.

When "PLP_MODE" is set to "1" and "MIMO_MODE" is set to "1", the information of "MIMO_PATTERN # 2" is valid information. At this time, if "00" is set as "MIMO_PATTERN # 2", a transmission method that changes the phase of the signal after precoding of phase change # 1 (or after precoding and baseband signal replacement) is used. , Data is transmitted. When "01" is set, data is transmitted using a transmission method that changes the phase of the signal after precoding of phase change # 2 (or after precoding and baseband signal replacement). When set to "10", data is transmitted using a transmission method that changes the phase of the signal after precoding of phase change # 3 (or after precoding and baseband signal replacement). When set to "11", data is transmitted using a transmission method that changes the phase of the signal after precoding of phase change # 4 (or after precoding and baseband signal replacement). Here, the phase changes # 1 to # 4 are different methods, but at this time, if # A and #B are different methods, for example, . Multiple phase changes used for #A and # Among the multiple phase changes used for B, the same phase change is included, but the period is different. . There is a phase change value that is included in #A but not in #B. There are three methods that the multiple phase changes used in #B are not included in the phase change used in #B method.

In the above, the control information in Tables 3 and 4 has been described as being transmitted by the first and second Signaling data. In this case, there is an advantage that it is not necessary to use PLP in particular to transmit control information.

As described above, after precoding (or precoding) for a standard different from DVB-T2 while using a multi-carrier transmission method such as the OFDM method and being able to distinguish from the DVB-T2 standard. And by making it possible to select a transmission method that changes the phase of the signal (after replacing the baseband signal), it is possible to obtain high reception quality and high transmission speed for the LOS environment. You can get the benefits. In this embodiment, as the transmission method in which the carrier group can be set, "spatial multiplex MIMO transmission method, MIMO method using a fixed precoding matrix, after precoding (or after precoding and baseband signal replacement). ) Is a transmission method that changes the phase of the signal, spatiotemporal block coding, and a transmission method that transmits only stream s1, but it is not limited to this.

Then, "spatial multiplex MIMO transmission method, MIMO method using a fixed precoding matrix, transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement), spatiotemporal block coding". , A transmission method that transmits only stream s1 "was explained in the example where the broadcasting station can select, but all of these transmission methods do not have to be selectable transmission methods. The MIMO method to be used, the transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), the spatiotemporal block coding, and the transmission method that transmits only the stream s1 can be selected. MIMO method using a typical precoding matrix, a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), and a transmission method that can select spatiotemporal block coding . Fixed MIMO method using precoding matrix, transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), transmission method that can select the transmission method that transmits only stream s1 . After precoding Transmission method that can select the transmission method that changes the phase of the signal (or after precoding and baseband signal replacement), spatiotemporal block coding, and transmission method that transmits only the stream s1 . Use a fixed precoding matrix MIMO method, transmission method to change the phase of the signal after precoding (or after precoding and baseband signal replacement) . Phase change to the signal after precoding (or after precoding and baseband signal replacement) Transmission method, transmission method that can select spatiotemporal block coding . Transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), and transmission method that transmits only stream s1 can be selected. After precoding (well, like the transmission method)In addition, by including a transmission method that changes the phase of the signal (after precoding and baseband signal replacement), high-speed data transmission can be performed in the LOS environment, and the received data quality of the receiving device is ensured. You can get the effect that you can.

At this time, it is necessary to set S1 in the P1 symbol as described above, and as the first and second Signaling data, the control information setting method different from that in Table 3 (setting method of the transmission method of each PLP). For example, Table 5 can be considered.

The difference between Table 5 and Table 3 is that when "PLP_MODE" is set to "11", it is set to Reserve. In this way, when the selectable transmission method as the PLP transmission method is as shown in the above example, the number of bits constituting PLP_MODE in Tables 3 and 5, for example, depends on the number of selectable transmission methods. It may be larger or smaller.

The same applies to Table 4. For example, if the MIMO transmission method only supports a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), "MIMO_MODE" is selected. No control information is needed. Further, in "MIMO_PATTERN # 1", for example, if the precoding matrix does not support a fixed MIMO method, the control information of "MIMO_PATTERN # 1" may not be required, and the precoding matrix is fixed. If multiple precoding matrices used in a typical MIMO system are not required, 1-bit control information may be used instead of 2-bit control information, and if multiple precoding matrices can be set, 2 It may be control information of bits or more.

You can think of "MIMO_PATTERN # 2" in the same way, and if you do not need multiple phase change methods as a transmission method to change the phase of the signal after precoding (or after precoding and baseband signal replacement), 2 bits. It may be 1-bit control information instead of the control information of, and if it is possible to set a plurality of phase change methods, it may be 2 bits or more of control information.

Further, in the present embodiment, the case where the number of antennas of the transmitting device is 2 has been described, but the present invention is not limited to this, and control information may be similarly transmitted even when the number of antennas is larger than 2. At this time, in addition to the case where the modulated signal is transmitted using the two antennas, there is a case where it is necessary to increase the number of bits constituting each control information in order to carry out the case where the modulated signal is transmitted using the four antennas. do. At this time, the point that the control information is transmitted by the P1 symbol and the control information is transmitted by the first and second Signaling data is the same as the case described above.

Regarding the frame configuration of the PLP symbol group transmitted by the broadcasting station, a method of transmitting in time division as shown in FIG. 77 has been described, but a modified example thereof will be described below.

FIG. 79 shows an example of how the symbols of streams s1 and s2 are arranged on the frequency-time axis after transmitting the P1 symbols, the first and second Signaling data, and the Common PLP, which are different from those in FIG. 77.

In FIG. 79, the symbol described as "# 1" indicates one of the symbols of PLP # 1 in FIG. 77. Similarly, the symbol labeled "# 2" indicates one of the symbols in PLP # 2 in FIG. 77, and the symbol labeled "# 3" represents the PLP in FIG. 77. It indicates one symbol of the symbol group of # 3, and the symbol described as "# 4" indicates one symbol of the symbol group of PLP # 4 in FIG. 77. Then, as in FIG. 77, PLP # 1 shall transmit data using the spatial multiplex MIMO transmission method shown in FIG. 23 or the MIMO transmission method having a fixed precoding matrix. Then, PLP # 2 shall transmit data by transmitting one modulated signal. PLP # 3 shall transmit data using a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement). PLP # 4 shall transmit data using the spatiotemporal block code.

In FIG. 79, when the symbols exist at the same time of the same subcarrier in both s1 and s2, the symbols of the two streams exist at the same frequency. As described in other embodiments, when a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, s1 and s2 are precoded. Weighting and synthesis are performed using a matrix (and, in some cases, baseband signal replacement is performed thereafter), and in addition, phase change is performed. As a result, if the obtained signals are z1 and z2 here, z1 and z2 will be output from the antenna, respectively.

The difference between FIG. 79 and FIG. 77 is that, as described above, FIG. 77 shows an example in which a plurality of PLPs are arranged in time division, but in FIG. 79, unlike FIG. 77, time division and frequency division are shown. In combination with, multiple PLPs are present. That is, for example, at time 1, the symbol of PLP # 1 and the symbol of PLP # 2 exist, and at time 3, the symbol of PLP # 3 and the symbol of PLP # 4 exist. In this way, PLP symbols with different indexes (#X; X = 1, 2, ...) can be assigned to each symbol (consisting of 1 time, 1 subcarrier).

In addition, in FIG. 79, simply, at time 1, only "# 1" and "# 2" exist, but the index is not limited to this, and "# 1" and "# 2" are indexes other than PLP. The PLP symbol of PLP may exist at time 1, and the relationship between the subcarrier and the PLP index at time 1 is not limited to FIG. 79, and the PLP symbol of which index is assigned to the subcarrier. Is also good. Similarly, at other times, the PLP symbol of any index may be assigned to the subcarrier.

FIG. 80 shows an example of how to arrange the symbols of streams s1 and s2 on the frequency-time axis after transmitting the P1 symbols, the first and second Signaling data, and the Common PLP, which are different from those in FIG. 77. The characteristic part in FIG. 80 is that in the T2 frame, when the transmission method of PLP is based on the transmission of multiple antennas, the "transmission method of transmitting only the stream s1" cannot be selected.

Therefore, in FIG. 80, it is assumed that the symbol group 8001 of PLP # 1 is transmitted by "spatial multiplex MIMO transmission method or MIMO method using a fixed precoding matrix". It is assumed that the symbol group 8002 of PLP # 2 is transmitted with data by "a transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement)". It is assumed that data is transmitted in the symbol group 8003 of PLP # 3 by the "space-time block code". The PLP symbol group in the unit frame after the PLP # 3 symbol group 8003 is "spatial multiplex MIMO transmission method or MIMO method using a fixed precoding matrix", "after precoding (or precoding)". Data will be transmitted by either a transmission method of changing the phase of the signal (after coding and baseband signal replacement) or a spatiotemporal block code.

FIG. 81 shows an example of how to arrange the symbols of streams s1 and s2 on the frequency-time axis after transmitting the P1 symbol, the first and second Signaling data, and the Common PLP, which are different from those in FIG. 79.

In FIG. 81, the symbol described as "# 1" indicates one of the symbols of PLP # 1 in FIG. 80. Similarly, the symbol described as "# 2" indicates one of the symbols in PLP # 2 in FIG. 80, and the symbol described as "# 3" indicates PLP in FIG. 80. Shows one symbol in the # 3 symbol group. Then, as in FIG. 80, PLP # 1 shall transmit data by using the spatial multiplex MIMO transmission method shown in FIG. 23 or the MIMO transmission method in which the precoding matrix is fixed. Then, PLP # 2 shall transmit data by using a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement). PLP # 3 shall transmit data using a space-time block code.

In FIG. 81, when the symbols exist at the same time of the same subcarrier in both s1 and s2, the symbols of the two streams exist at the same frequency. As described in other embodiments, when a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, s1 and s2 are precoded. Weighting and synthesis are performed using a matrix (and, in some cases, baseband signal replacement is performed thereafter), and in addition, phase change is performed. As a result, if the obtained signals are z1 and z2 here, z1 and z2 will be output from the antenna, respectively.

The difference between FIG. 81 and FIG. 80 is that, as described above, FIG. 80 shows an example in which a plurality of PLPs are arranged in time division, but in FIG. 81, unlike FIG. 80, time division and frequency division are shown. In combination with, multiple PLPs are present. That is, for example, at time 1, the symbol of PLP # 1 and the symbol of PLP # 2 exist. In this way, PLP symbols with different indexes (#X; X = 1, 2, ...) can be assigned to each symbol (consisting of 1 time, 1 subcarrier).

In addition, in FIG. 81, simply, at time 1, only "# 1" and "# 2" exist, but the index is not limited to this, and "# 1" and "# 2" are indexes other than PLP. The PLP symbol of PLP may exist at time 1, and the relationship between the subcarrier and the PLP index at time 1 is not limited to FIG. 81, and the PLP symbol of which index is assigned to the subcarrier. Is also good. Similarly, at other times, the PLP symbol of any index may be assigned to the subcarrier. On the other hand, at a certain time, such as time 3, only one PLP symbol may be assigned. That is, the PLP symbols may be assigned in any time-frequency frame method.

In this way, since there is no PLP that uses the "transmission method that transmits only stream s1" within a unit frame, the dynamic range of the received signal received by the terminal can be suppressed, and good reception quality can be obtained. The effect of being able to increase the sex can be obtained.

In the description of FIG. 81, as the transmission method, "spatial multiplex MIMO transmission method or MIMO method using a fixed precoding matrix", "after precoding (or after precoding and baseband signal replacement)" Although the explanation was given in the example of selecting either "transmission method for changing the phase of the signal of" or "spatio-temporal block code", it is not necessary to assume that all of these transmission methods can be selected. "Transmission method that changes the phase of the signal after coding (or after precoding and baseband signal replacement)", "spatio-temporal block code", and "MIMO method using a fixed precoding matrix" can be selected. "Transmission method to change the phase of the signal after coding (or after precoding and baseband signal replacement)" and "spatio-temporal block code" can be selected.-After precoding (or after precoding and baseband signal replacement) ), A transmission method that changes the phase of the signal, and a MIMO method that uses a fixed precoding matrix may be selectable.

In the above, the case where a plurality of PLPs exist in the unit frame has been described, but the case where only one PLP exists in the unit frame will be described below.

FIG. 82 shows an example of the frame configuration of streams s1 and s2 on the time-frequency axis when there is only one PLP in a unit frame.

In FIG. 82, the term "control symbol" is used, which means the P1 symbol described above and symbols such as the first and second Signaling data. Then, in FIG. 82, the first unit frame is transmitted using the section 1, and similarly, the second unit frame is transmitted using the section 2, and the third unit is transmitted using the section 3. The frame is being transmitted, and the fourth unit frame is being transmitted using section 4.

Further, in FIG. 82, in the first unit frame, the symbol group 8101 of PLP # 1-1 is transmitted, and as the transmission method, "spatial multiplex MIMO transmission method or a fixed precoding matrix is used. "MIMO method" is selected.

In the second unit frame, the symbol group 8102 of PLP # 2-1 is transmitted, and "a method of transmitting one modulated signal" is selected as the transmission method.

In the third unit frame, the symbol group 8103 of PLP # 3-1 is transmitted, and the transmission method is "to change the phase of the signal after precoding (or after precoding and baseband signal replacement)". "Send method" is selected.

In the fourth unit frame, the symbol group 8104 of PLP # 4-1 is transmitted, and "space-time block code" is selected as the transmission method.

In FIG. 82, when the symbols exist at the same time of the same subcarrier in both s1 and s2, the symbols of the two streams exist at the same frequency. When a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, s1 and s2 are weighted and synthesized using the precoding matrix. (In some cases, the baseband signal is replaced after that), and in addition, the phase is changed. As a result, if the obtained signals are z1 and z2 here, z1 and z2 will be output from the antenna, respectively.

By doing so, the transmission method can be set in consideration of the data transmission speed and the data reception quality of the terminal for each PLP, so that the improvement of the data transmission speed and the assurance of the data reception quality can be achieved at the same time. It becomes possible. An example of a control information configuration method such as a P1 symbol, a transmission method of the first and second Signaling data, and the like can be similarly implemented by configuring as shown in Tables 2 to 5 above. The difference is that in the frame configuration shown in FIG. 77, since one unit frame has a plurality of PLPs, control information such as a transmission method for a plurality of PLPs is required. In this case, since there is only one PLP in one unit frame, only control information such as a transmission method for that one PLP is required.

In this embodiment, the application method when the transmission method of changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is applied to the system using the DVB standard has been described. At this time, an example of a transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is as shown in the present specification. Further, in the present embodiment, the control information is specially referred to, but the designation does not affect the present invention.

Next, the spatiotemporal block code described in the present specification including the present embodiment will be described.

FIG. 94 shows the configuration of the modulated signal when the spatiotemporal block code is used. The spatiotemporal block coding unit (9402) of FIG. 94 receives a baseband signal based on a certain modulated signal as an input. For example, the space-time block coding unit (9402) inputs symbols s1, symbols s2, and so on. Then, as shown in Fig. 94, spatiotemporal block coding is performed, and z1 (9403A) is "s1 as symbol # 0" and "-s2 as symbol # 1".^*"S3 as symbol # 2" "-s4 as symbol # 3"^*"... and z2 (9403B) is" s2 as symbol # 0 "and" s1 as symbol # 1 ".^*"S4 as symbol # 2" "s3 as symbol # 3"^*"... At this time, the symbol #X in z1 and the symbol #X in z2 are transmitted from different antennas at the same time and at the same frequency. The arrangement of the symbols of the spatiotemporal block code is not limited to the time direction, and may be arranged in the frequency axis direction or may be appropriately arranged in the symbol group formed by the time-frequency. Further, as the spatiotemporal block code, each embodiment of the present specification may be implemented by using another spatiotemporal block code, which is an example of the spatiotemporal block coding method in FIG. 94.

(Embodiment E2) In the present embodiment, the phase of the signal after precoding (or after precoding and baseband signal replacement) is added to the communication system using the DVB-T2 standard described in the embodiment E1. The reception method when the method to which the transmission method for changing is applied is used, and the configuration of the receiving device will be described in detail.

FIG. 86 shows the configuration of the receiving device of the terminal when the transmitting device of the broadcasting station of FIG. 76 applies a transmission method of performing a phase change to the signal after precoding (or after precoding and baseband signal replacement). An example is shown, and the same reference numerals are given to those that operate in the same manner as in FIG. 7.

In FIG. 86, the P1 symbol detection / decoding unit 8601 receives the signal transmitted by the broadcasting station, inputs the baseband signals 704_X and 704_Y, and detects the P1 symbol to perform signal detection and time-frequency synchronization. At the same time, the control information contained in the P1 symbol is obtained (by demodulation and error correction / decoding), and the P1 symbol control information 8602 is output.

The OFDM method related processing units 8600_X and 8600_Y receive P1 symbol control information 8602 as an input, and based on this information, change the signal processing method (signal processing such as Fourier transform) for the OFDM method. (This is because the information on the transmission method of the signal transmitted by the broadcasting station is included in the P1 symbol as described in the embodiment E1.) The OFDM method related processing unit 8600_X and 8600_Y are set. The baseband signals 704_X and 704_Y demodrated based on the signal processing method used are output.

The P2 symbol (may include Signaling PLP) demodulation unit 8603 inputs the baseband signals 704_X, 704_Y, and P1 symbol control information 8602, performs signal processing based on the P1 symbol control information, and demodulates (error). Performs correction / decoding) and outputs P2 symbol control information 8604.

The control information generation unit 8605 inputs P1 symbol control information 8602 and P2 symbol control information 8604, and outputs control information (related to reception operation) as a spring and control signal 8606. Then, the control signal 8606 is input to each part as shown in FIG. 86.

The signal processing unit 711 takes the signals 706_1, 706_2, 708_1, 708_2, 704_X, 704_Y, and the control signal 8606 as inputs, and uses the transmission method / modulation used to transmit each PLP included in the control signal 8606. Based on information such as the method, error correction coding method, error correction coding coding rate, and error correction code block size, demodulation and decoding are performed, and the received data 712 is output.

At this time, in order to transmit PLP, a spatial multiplex MIMO transmission method, a MIMO method using a fixed precoding matrix, and transmission in which the phase is changed to the signal after precoding (or after precoding and baseband signal replacement). When using one of the transmission methods of the method, the relationship between the output result of the channel fluctuation estimation unit (705_1, 705_2, 707_1, 707_2) and the transmission signal from the reception (baseband) signal is used, and reception (baseband) is used. The signal will be obtained and demoted. When a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, the output result and reception of the channel fluctuation estimation unit (705_1, 705_2, 707_1, 707_2) are used. Demodulation will be performed using the (baseband) signal and the relationship of equation (48).

FIG. 87 shows the configuration of the receiving device of the terminal when the transmitting device of the broadcasting station of FIG. 85 applies a transmission method of performing a phase change to the signal after precoding (or after precoding and baseband signal replacement). An example is shown, and the same reference numerals are given to those that operate in the same manner as in FIGS. 7 and 86.

The difference between the receiver of FIG. 87 and the receiver of FIG. 86 is that the receiver of FIG. 86 can receive signals of the DVB-T2 standard and other standards and obtain data, whereas the receiver of FIG. 87 can obtain data. The receiving device can receive only signals other than the DVB-T2 standard and obtain data.

In FIG. 87, the P1 symbol detection / decoding unit 8601 receives the signal transmitted by the broadcasting station, inputs the baseband signals 704_X and 704_Y, and detects the P1 symbol to perform signal detection and time-frequency synchronization. At the same time, the control information contained in the P1 symbol is obtained (by demodulation and error correction / decoding), and the P1 symbol control information 8602 is output.

The OFDM system related processing unit 8600_X and 8600_Y receive P1 symbol control information 8602 as an input, and based on this information, the signal processing method for the OFDM system is changed. (This is because the information on the transmission method of the signal transmitted by the broadcasting station is included in the P1 symbol as described in the embodiment E1.) The OFDM method related processing unit 8600_X and 8600_Y are set. The baseband signals 704_X and 704_Y demodrated based on the signal processing method used are output.

The first and second Signaling data demodulation units 8701 input the baseband signals 704_X, 704_Y, and P1 symbol control information 8602, perform signal processing based on the P1 symbol control information, and demodulate (including error correction and decoding). Is performed, and the first and second Signaling data control information 8702 is output.

The control information generation unit 8605 inputs the P1 symbol control information 8602 and the first and second signaling data control information 8702, and outputs the control information (related to the reception operation) as a spring and a control signal 8606. Then, the control signal 8606 is input to each part as shown in FIG. 86.

The signal processing unit 711 takes the signals 706_1, 706_2, 708_1, 708_2, 704_X, 704_Y, and the control signal 8606 as inputs, and uses the transmission method / modulation used to transmit each PLP included in the control signal 8606. Based on information such as the method, error correction coding method, error correction coding coding rate, and error correction code block size, demodulation and decoding are performed, and the received data 712 is output.

At this time, in order to transmit PLP, a spatial multiplex MIMO transmission method, a MIMO method using a fixed precoding matrix, and transmission in which the phase is changed to the signal after precoding (or after precoding and baseband signal replacement). When using one of the transmission methods of the method, the relationship between the output result of the channel fluctuation estimation unit (705_1, 705_2, 707_1, 707_2) and the transmission signal from the reception (baseband) signal is used, and reception (baseband) is used. The signal will be obtained and demoted. When a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is used, the output result and reception of the channel fluctuation estimation unit (705_1, 705_2, 707_1, 707_2) are used. Demodulation will be performed using the (baseband) signal and the relationship of equation (48).

FIG. 88 shows the configuration of the receiver of the terminal that corresponds to the DVB-T2 standard and also supports the standards other than DVB-T2. Is attached.

The difference between the receiver of FIG. 88 and the receivers of FIGS. 86 and 87 is that the receiver of FIG. 88 can demodulate both the DVB-T2 standard and the signals of other standards. It is a point that includes the P2 symbol or the first and second signaling data demodulation units 8801.

The P2 symbol or the first and second Signaling data demodulators 8801 input the baseband signals 704_X, 704_Y, and P1 symbol control information 8602, and the received signal is DVB-T2 based on the P1 symbol control information. Determine whether the signal is compatible with the standard or other standards (for example, it can be determined from Table 2), perform signal processing, and demodulate (including error correction / decoding). And outputs control information 8802 including information on what standard the received signal corresponds to. For the other parts, the operation is the same as in FIGS. 86 and 87.

As described above, by configuring the receiving device as shown in the present embodiment, the signal transmitted by the transmitting device of the broadcasting station described in the embodiment E1 is received and appropriate signal processing is performed. Therefore, data with high reception quality can be obtained. In particular, when a signal of a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is received, the data transmission efficiency and data reception quality are improved in the LOS environment. Can be achieved at the same time.

In addition, in this embodiment, since the configuration of the receiving device corresponding to the transmission method of the broadcasting station described in the embodiment E1 has been described, the configuration of the receiving device when the number of receiving antennas is two has been described. The number of antennas of the device is not limited to two, and the same can be applied to three or more antennas. At this time, the diversity gain is improved, so that the data reception quality can be improved. Further, even when the number of transmitting antennas of the transmitting device of the broadcasting station is 3 or more and the number of transmitting modulation signals is 3 or more, the same can be performed by increasing the number of receiving antennas of the receiving device of the terminal. .. Further, even if the number of antennas of the receiving device is one, maximum likelihood detection or approximate maximum likelihood detection can be applied. At this time, as a transmission method, it is desirable to apply a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement).

Further, the transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is not limited to the specific example described in the present specification, and precoding is performed and then. The present embodiment can be similarly implemented as long as the phase is changed or the phase is changed before the phase is changed.

(Embodiment E3) In the system in which the transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is applied to the DVB-T2 standard described in the embodiment E1. In L1 Pre-Signalling, there is control information that specifies the insertion pattern of the pilot. In this embodiment, an application method of a transmission method for changing the phase of a signal after precoding (or after precoding and baseband signal replacement) when changing the pilot insertion pattern by L1 pre-signaling will be described. ..

FIGS. 89 and 90 show an example of a frame configuration on the frequency-time axis of the DVB-T2 standard when a transmission method of transmitting a plurality of modulated signals from a plurality of antennas using the same frequency band is used. There is. In FIGS. 89 and 90, the horizontal axis indicates the frequency, that is, the carrier number, the vertical axis indicates the time, and (A) is the frame of the modulated signal z1 in the embodiment described so far. Configuration, (B) shows the frame configuration of the modulated signal z2 in the embodiments described so far. The carrier number is indexed as "f0, f1, f2, ...", and the time is indexed as "t1, t2, t3, ...". Then, in FIGS. 89 and 90, the symbols having the same carrier number and the same time are symbols existing at the same frequency and the same time.

FIGS. 89 and 90 are examples of insertion positions of pilot symbols in the DVB-T2 standard. (In the DVB-T2 standard, when transmitting multiple modulated signals using multiple antennas, there are eight methods for inserting the pilot, and Fig. 89 and Fig. 90 show two of them. In FIGS. 89 and 90, two types of symbols, a symbol for a pilot and a symbol for data transmission, are shown. As described in other embodiments, a transmission method in which the signal after precoding (or after precoding and baseband signal replacement) is phase-changed, or a precoding method in which the precoding matrix is fixed is used. When, the symbol for data transmission of the modulated signal z1 becomes the symbol after weighting and synthesis of stream s1 and stream s2, and the symbol for data transmission of the modulated signal z2 is also the symbol of stream s1 and stream s2. It becomes a symbol after weighted composition. (However, if a transmission method that changes the phase of the signal after precoding (or after precoding and replacement of the baseband signal) is used, the phase may be further changed.) Spatio-temporal block code, space When using the multiplex MIMO transmission method, the symbol for data transmission of the modulated signal z1 is either the symbol of stream s1 or stream s2, and the symbol for data transmission of the modulated signal z2 is also stream s1. Or it becomes one of the symbols of stream s2. In FIGS. 89 and 90, the symbol for the pilot is attached with either an index of "PP1" or "PP2", and "PP1" and "PP2" are pilot symbols having different configuration methods. As mentioned above, the DVB-T2 standard allows broadcasters to specify one of eight types of pilot insertion methods (the frequency of insertion in the frame of the pilot symbol is different). , Fig. 89 and Fig. 90 show two types of pilot insertion methods out of the above eight types. Shows the law. Then, the information regarding the pilot insertion method selected from the eight types by the broadcasting station is transmitted to the terminal as the transmission destination as the L1 Pre-Signalling data among the P2 symbols described in the embodiment E1.

Next, a method of applying the transmission method of changing the phase of the signal after precoding (or after precoding and baseband signal replacement) accompanying the pilot insertion method will be described. As an example, there are 10 different phase change values prepared in the transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement), and the phase change value is F [0], It shall be expressed as F [1], F [2], F [3], F [4], F [5], F [6], F [7], F [8], F [9]. In the frame configuration on the frequency-time axis shown in FIG. 89, when the phase change value is assigned when the transmission method for changing the phase is applied to the signal after precoding (or after precoding and replacement of the baseband signal). The phase change value when the transmission method of performing the phase change is applied to the signal after precoding (or after precoding and baseband signal replacement) in the frame configuration in the frequency-time of FIG. 90 in FIG. 91. Figure 92 shows the situation when the above is assigned. For example, in both the frame configuration of the modulated signal z1 of FIG. 91 (A) and the frame configuration of the modulated signal z2 of (B), "# 1" is described in the symbols of f1 and t1. The symbols of, f1 and t1 mean that the phase change is performed using the phase change value of F [1]. Therefore, in FIGS. 91 and 92, "#Z" is described in the symbols of the carriers fx (x = 0, 1, 2, ...) And ty (y = 1, 2, 3, ...). If so, the symbols fx and ty mean that the phase change is performed using the phase change value of F [Z].

As a matter of course, the method of inserting the pilot symbol (insertion interval) is different in the frame configuration on the frequency-time axis of FIGS. 91 and 92. Further, for the pilot symbol, the transmission method of changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is not applied. Therefore, in FIGS. 91 and 92, pre-pres of the same period (the number of different phase change values prepared as a transmission method for phase-changing the signal after precoding (or after precoding and baseband signal replacement)). Even if a transmission method that changes the phase is applied to the signal after coding (or after precoding and baseband signal replacement), as can be seen from FIGS. 91 and 92, the same carrier and the same are used in FIGS. 91 and 92. Even with the time symbol, the assigned phase change value may be different. For example, the symbols of f5 and t2 in FIG. 91 are shown as "# 7", and the phase change is performed by the phase change value of F [7]. On the other hand, the symbols of f5 and t2 in FIG. 92 are shown as "# 8", and the phase change is performed by the phase change value of F [8].

Therefore, the broadcasting station transmits the control information indicating the pilot pattern (pilot insertion method) by the L1 Pre-Signalling data, and the control information indicating this pilot pattern indicates the pilot insertion method and at the same time, Table 3 Or, according to the control information in Table 4, if the broadcasting station selects a transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) as the transmission method for transmitting PLP, precoding. The method of assigning the phase change value in the transmission method of performing the phase change to the later (or after precoding and baseband signal replacement) signal may be shown. Therefore, the receiving device of the terminal that receives the modulated signal transmitted by the broadcasting station is L1 Pre-Signaling. By obtaining the control information indicating the pilot pattern in data, it is possible to know the method of assigning the phase change value in the transmission method of performing the phase change to the signal after precoding (or after precoding and baseband signal replacement). (At this time, as a transmission method for the broadcasting station to transmit the PLP according to the control information in Table 3 or Table 4, a transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is used. It is assumed that it has been selected.) Here, L1 Pre-Signalling data is used for explanation, but in the case of the frame configuration shown in FIG. 83 in which the P2 symbol does not exist, the pilot pattern and pre-signing are used. The control information indicating the method of assigning the phase change value in the transmission method of performing the phase change to the signal after coding (or after precoding and baseband signal replacement) exists in the first and second Signaling data.

In the following, yet another example will be described. Table 6 shows an example of the phase change pattern according to the modulation method.

<tables><img file="JP2022017567A_D0083.tif" /></tables>

For example, as shown in Table 6, the phase change value used in the transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is determined at the same time as the modulation method is specified. In this case, it can be considered in the same manner as described above, and by transmitting only the control information of the pilot pattern, the control information of the transmission method of the PLP, and the control information of the modulation method of the P2 symbol, the receiving device of the terminal can think of these. To estimate the method of assigning the phase change value (on the frequency-time axis) of the transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) by obtaining the control information of. Can be done. In Table 6, in the column of the phase change pattern, "-" indicates that the phase change is not performed, and "#A", "#B", and "#C" are #A, #B, respectively. Indicates that the phase of #C is changed. Similarly, as shown in Table 1, it is used in a transmission method in which the modulation method and error correction code method are specified and at the same time the phase is changed to the signal after precoding (or after precoding and baseband signal replacement). When the phase change value is determined, the receiving device of the terminal transmits only the pilot pattern control information, the PLP transmission method control information, the modulation method control information, and the error correction code method of the P2 symbol. By obtaining these control information, the method of assigning the phase change value (on the frequency-time axis) of the transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) is estimated. can do.

However, unlike Tables 1 and 6, even if the modulation method is determined, one of the transmission methods that changes the phase of two or more different precoded signals (or after precoding and baseband signal replacement). Can be selected (for example, a transmission method that changes the phase of a signal with a different period, after precoding (or after precoding and baseband signal replacement), or a different phase change value itself, after precoding. (Or you can select from the transmission methods that change the phase of the signal after precoding and baseband signal replacement), or even if you decide the modulation method / error correction method, two or more different types after precoding (or after precoding) Alternatively, you can choose between a transmission method that changes the phase of the precoding and baseband signal replacement), or even if you decide on an error correction method, there are two or more different types of post-precoding (or). If you can choose from transmission methods that change the phase of the precoded (after precoding and baseband signal replacement) signal, then phase change the precoding (or after precoding and baseband signal replacement) signal, as shown in Table 4. In addition to transmitting the method of switching the phase change value of the transmission method to be performed, in addition to this, the phase change value (frequency-) of the phase change is added to the signal after precoding (or after precoding and baseband signal replacement). Information about the allocation method (on the time axis) may be transmitted.

Configuration example of control information related to information on the allocation method (frequency-time axis) of the phase change value of the transmission method that changes the phase of the signal after precoding (or after precoding and baseband signal replacement) at that time. Is shown in Table 7.

<tables><img file="JP2022017567A_D0084.tif" /></tables>

For example, it is assumed that the transmitting device of the broadcasting station selects FIG. 89 as the insertion pattern of the pilot, and the transmission method changes the phase of the signal after precoding (or after precoding and baseband signal replacement). , A method is selected. At this time, it is assumed that the transmitting device of the broadcasting station can select either FIG. 91 or FIG. 93 as the method of assigning the phase change value (on the frequency-time axis). For example, if the transmitter of the broadcasting station selects FIG. 91, "PHASE _FRAME_ARRANGEMENT" in Table 7 is set to "00", and if FIG. 93 is selected, "PHASE _FRAME_ARRANGEMENT" in Table 7 is set to "01". It shall be set. Then, the receiving device of the terminal can know the method of assigning the phase change value (on the frequency-time axis) by obtaining the control information in Table 7. The control information in Table 7 can be transmitted by the P2 symbol, and can also be transmitted by the first, second, and signalling data.

As described above, the method of assigning the phase change value of the transmission method for changing the phase to the signal after precoding (or after precoding and baseband signal replacement) based on the pilot insertion method is realized, and the method thereof is realized. By accurately transmitting the allocation method information to the transmission partner, the receiving device of the terminal as the transmission partner has the effect of improving both the data transmission efficiency and the data reception quality. be able to.

In the present embodiment, the case where the number of transmission signals of the broadcasting station is 2 has been described, but also when the number of transmission antennas of the transmission device of the broadcasting station is 3 or more and the number of transmission modulation signals is 3 or more. , Can be carried out in the same way. Further, the transmission method for changing the phase of the signal after precoding (or after precoding and baseband signal replacement) is not limited to the specific example described in the present specification, and precoding is performed and then. The present embodiment can be similarly implemented as long as the phase is changed or the phase is changed before the phase is changed.

The method for configuring the pilot signal is not limited to the present embodiment, and a transmission method for changing the phase of the signal after precoding (or after precoding and replacement of the baseband signal) is used in the receiving device. If so, it may be a signal that can be derived from the relationship of Eq. (48) (for example, the receiving device may be a known signal that knows the pilot signal transmitted by the transmitting device in advance). It should be noted that this can be applied to all the specification of the present invention.

In addition, in the drawing of the transmission device related to the invention of this specification, FIG. 3, FIG. 4, FIG. 12, FIG. 13, FIG. 51, FIG. 52, FIG. 67, FIG. 70, FIG. 76, FIG. 85, etc., two transmissions are performed. When the modulation signals transmitted from the antennas are the modulation signal # 1 and the modulation signal # 2, respectively, the average transmission power of the modulation signal # 1 and the average transmission power of the modulation signal # 2 may be set in any way. For example, when setting the average transmission power of both modulated signals to be different, the average transmission power and modulation of the modulated signal # 1 can be performed by applying the transmission power control technology used in a general wireless communication system. The average transmission power of signal # 2 can be set differently. At this time, the transmission power control may be performed by controlling the power of the signal depending on the state of the baseband signal (for example, the transmission power control is performed at the time of mapping the modulation method to be used), or the power amplifier in front of the antenna (for example, the power amplifier in front of the antenna). The transmission power may be controlled by the power amplifier).

(Embodiment F1) For the modulated signal after precoding described in Embodiment 1-4, Embodiment A1, Embodiment C1-C7, Embodiment D1-D3 and Embodiment E1-E3. The method of changing the phase regularly is applicable to any baseband signals s1 and s2 mapped to the IQ plane. Therefore, in Embodiment 1-4, Embodiment A1, Embodiment C1-C7, Embodiment D1-D3 and Embodiment E1-E3, the baseband signals s1 and s2 are not described in detail. On the other hand, for example, when the method of regularly changing the phase of the precoded modulated signal is applied to the baseband signals s1 and s2 generated from the error correction coded data, s1 and s2 It is possible that even better reception quality can be obtained by controlling the average power (average value) of. In the present embodiment, a method of regularly changing the phase of the precoded modulated signal for the baseband signals s1 and s2 generated from the error correction encoded data is applied. The method of setting the average power (mean value) of s1 and s2 is described.

Here, as an example, the modulation method applied to the baseband signal s1 will be described as QPSK, and the modulation method applied to the baseband signal s2 will be described as 16QAM.

Since the modulation method of s1 is QPSK, s1 will transmit 2 bits of data per symbol. The two bits to be transmitted are named b0 and b1. On the other hand, since the modulation method of s2 is 16QAM, s2 transmits 4 bits of data per symbol. The 4 bits to be transmitted are named b2, b3, b4, and b5. Since the transmitter transmits one slot consisting of one symbol of s1 and one symbol of s2, six-bit data of b0, b1, b2, b3, b4, and b5 will be transmitted per slot. ..

For example, in FIG. 95, which is an example of 16QAM signal point arrangement in the IQ plane, (b2, b3, b4, b5) = (0, 0, 0, 0) is (I, Q) = (3 × g, 3). × g), (b2, b3, b4, b5) = (0, 0, 0, 1) to (I, Q) = (3 × g, 1 × g), (b2, b3, b4, b5) ) = (0, 0, 1, 0) is (I, Q) = (1 × g, 3 × g), (b2, b3, b4, b5) = (0, 0, 1, 1) is ( I, Q) = (1 × g, 1 × g), and (b2, b3, b4, b5) = (0, 1, 0, 0) is (I, Q) = (3 × g, -3 ×) In g), ..., (b2, b3, b4, b5) = (1, 1, 1, 0) becomes (I, Q) = (-1 × g, -3 × g), (b2, b3, b4, b5) = (1, 1, 1, 1) is mapped to (I, Q) = (-1 × g, -1 × g). In addition, b2 to b5 shown on the right shoulder of FIG. 95 show the arrangement with each bit of the numerical value shown in the IQ plane, respectively.

Further, in FIG. 96, which is an example of the signal point arrangement of QPSK in the IQ plane, (b0, b1) = (0, 0) becomes (I, Q) = (1 × h, 1 × h), and (b0, b0, b1) = (0, 1) is (I, Q) = (1 × h, -1 × h), (b0, b1) = (1, 0) is (I, Q) = (-1 × h) , 1 × h), and (b0, b1) = (1, 1) is mapped to (I, Q) = (-1 × h, -1 × h). Note that b0 and b1 shown on the right shoulder of FIG. 96 indicate the arrangement with each bit of the numerical value shown on the IQ plane.

Here, when the average power of s1 and the average power of s2 are equalized, that is, h shown in FIG. 96 is represented by the following equation (78), and g shown in FIG. 95 is represented by the following equation (79). Suppose.

<math num="78"><img file="JP2022017567A_D0085.tif" /></math>

<math num="79"><img file="JP2022017567A_D0086.tif" /></math>

FIG. 97 shows the relationship of the log-likelihood ratio obtained by the receiving device in this case. FIG. 97 is a diagram schematically showing the absolute value of the log-likelihood ratio of b0 to b5 when the receiving device obtains the log-likelihood ratio. In FIG. 97, 9700 is the absolute value of the log-likelihood ratio of b0, 9701 is the absolute value of the log-likelihood ratio of b1, 9702 is the absolute value of the log-likelihood ratio of b2, and 9703 is the absolute value of the log-likelihood ratio of b3. The value, 9704, is the absolute value of the log-likelihood ratio of b4, and 9705 is the absolute value of the log-likelihood ratio of b5. At this time, as shown in FIG. 97, comparing the absolute value of the log-likelihood ratio of b0 and b1 transmitted by QPSK with the absolute value of the log-likelihood ratio of b2 to b5 transmitted by 16QAM, The absolute value of the log-likelihood ratio of b0 and b1 is greater than the absolute value of the log-likelihood ratio of b2 to b5. This means that the reliability of the receivers of b0 and b1 is higher than that of the receivers of b2 to b5. This is because, when g is as shown in Eq. (79) in FIG. 95, the minimum Euclidean distance of the signal point in the IQ plane of QPSK is

<math num="80"><img file="JP2022017567A_D0087.tif" /></math>

On the other hand, in FIG. 96, when h is as shown in Eq. (78), the minimum Euclidean distance of the signal point in the IQ plane of QPSK is

<math num="81"><img file="JP2022017567A_D0088.tif" /></math>

Because it becomes.

When the receiving device performs error correction decoding (for example, when the communication system uses LDPC code, reliability propagation decoding such as sum-product decoding), "absolute log-likelihood ratio of b0 and b1" is performed. The difference in reliability that the value is larger than the absolute value of the log-likelihood ratio of b2 to b5 is affected by the absolute value of the log-likelihood ratio of b2 to b5, and the reception quality of the data of the receiving device deteriorates. The problem arises.

To overcome this problem, as shown in FIG. 98, "the difference between the absolute value of the log-likelihood ratio of b0 and b1 and the absolute value of the log-likelihood ratio of b2 to b5" as shown in FIG. Just make it smaller. "

Therefore, consider "making the average power (average value) of s1 different from the average power (average value) of s2". 99 and 100 show signal processing related to the power changing unit (here, it is called the power changing unit, but it may also be called the amplitude changing unit and the weighting unit), and the weighting synthesis (precoding) unit. An example of the structure of the part is shown. In FIG. 99, the same reference numerals are given to those operating in the same manner as in FIGS. 3 and 6. Further, in FIG. 100, the same reference numerals are given to those operating in the same manner as in FIGS. 3, 6, and 99.

Hereinafter, some examples of the operation of the power changing unit will be described.

(Example 1) First, an example of operation will be described with reference to FIG. 99. Note that s1 (t) is a baseband signal (signal after mapping) of the modulation method QPSK, the mapping method is as shown in FIG. 96, and h is as shown in equation (78). Further, s2 (t) is a baseband signal (signal after mapping) of the modulation method 16QAM, the mapping method is as shown in FIG. 95, and g is as shown in Eq. (79). Note that t is a time, and in the present embodiment, the time axis direction will be described as an example.

The power change unit (9901B) inputs the baseband signal (signal after mapping) 307B and control signal (9900) of the modulation method 16QAM, and sets the value for power change based on the control signal (9900) u. Then, a signal (9902B) obtained by multiplying the baseband signal (signal after mapping) 307B of the modulation method 16QAM by u is output. Note that u is a real number and u&gt; 1.0. For the modulated signal after precoding, the precoding matrix in the method of regularly changing the phase is F, and the phase change value for regularly changing the phase is y (t) (y (t) is the absolute value. An imaginary number of 1 (including real numbers), that is, ejθ^(t)(Can be expressed as), then the following equation holds.

<math num="82"><img file="JP2022017567A_D0089.tif" /></math>

Therefore, the ratio of the average power of QPSK to the average power of 16QAM is 1: u.²Will be set. As a result, the reception state is such that the absolute value of the log-likelihood ratio shown in FIG. 98 can be obtained, so that the reception quality of data in the receiving device can be improved.

For example, the ratio of the average power of QPSK to the average power of 16QAM 1: u²About u,

<math num="83"><img file="JP2022017567A_D0090.tif" /></math>

If set to, the minimum Euclidean distance of the signal point in the IQ plane of QPSK can be made equal to the minimum Euclidean distance of the signal point in the IQ plane of 16QAM, and good reception quality may be obtained.

However, the condition that the minimum Euclidean distances of the signal points in the IQ planes of the two different modulation methods are equal is just an example of how to set the ratio between the average power of QPSK and the average power of 16QAM. For example, depending on other conditions such as the code length and code rate of the error correction code used for error correction coding, the value u for power change is the minimum Euclidean of the signal point in the IQ plane of two different modulation schemes. It is possible to obtain better reception quality by setting a different value (larger value or smaller value) from the value at which the distance is equal. In addition, a value in consideration of processing efficiency, for example,

<math num="84"><img file="JP2022017567A_D0091.tif" /></math>

It is conceivable to set. Details will be described later.

Conventionally, the transmission power control generally controls the transmission power based on the feedback information from the communication partner. In the present embodiment, the feature of the present invention is that the transmission power is controlled regardless of the feedback information from the communication partner, and this point will be described in detail.

In the above, it was stated that "the value u for power change is set by the control signal (9900)", but in the following, the control signal (9900) is used to further improve the data reception quality in the receiving device. The method of setting the value u for power change by is described in detail.

(Example 1-1) s1 and s2 when the transmitter supports error correction codes of multiple block lengths (the number of bits constituting one coded block, also called the code length). A method of setting the average power (average value) of s1 and s2 according to the block length of the error correction code applied to the data used for the generation of is described.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of block lengths are used. Is supported. The coded data with error correction coding of the block length selected from the supported multiple block lengths is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the block length of the above-selected error correction code, and the power change unit (9901B) sets a value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901B) sets the value u for power change according to the selected block length indicated by the control signal (9900). Here, u is the value for power change according to the block length X._LXIt will be described in the form of.

For example, if 1000 is selected as the block length, the power change section (9901B) is the value u for power change._L1000When 1500 is selected as the block length, the power change section (9901B) is the value u for power change._L1500When 3000 is selected as the block length, the power change section (9901B) is the value u for power change._L3000To set. At this time, for example, u_L1000, U_L1500, U_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. However, depending on the code length to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the code length is changed, it is not necessary to change the value for changing the power. (For example, u_L1000= u_L1500It may be. The important thing is (u_L1000, U_L1500, U_L3000) Has two or more values. ) In the above, the case of three code lengths has been described as an example, but the present invention is not limited to this, and when two or more code lengths can be set in the transmitter, the value for power change that can be set is set. When there are two or more and the code length is set, the transmitter can select one of the values for power change from multiple configurable values for power change and change the power. What you can do is important.

(Example 1-2) When the transmitter supports multiple code rate error correction codes, depending on the code rate of the error correction code applied to the data used to generate s1 and s2. This section describes how to set the average power (mean value) of s1 and s2.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of codes are coded. Rate is supported. Error correction of the code rate selected from a plurality of supported code rates The coded data is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the coding rate of the above-selected error correction code, and the power change unit (9901B) sets the value u for power change according to the control signal (9900). ..

A feature of the present invention is that the power change unit (9901B) sets the value u for power change according to the selected coding rate indicated by the control signal (9900). Here, u is the value for power change according to the code rate rx._rXIt will be described in the form of.

For example, when r1 is selected as the code rate, the power change unit (9901B) is the value u for power change._r1When r2 is selected as the code rate, the power change unit (9901B) is the value u for power change._r2When r3 is selected as the code rate, the power change unit (9901B) is the value u for power change._r3To set. At this time, for example, u_r1, U_r2, U_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. However, depending on the coding rate to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the coding rate is changed, it is not necessary to change the value for changing the power. (For example, u_r1= u_r2It may be. The important thing is (u_r1, U_r2, U_r3) Has two or more values. ) As an example of the above r1, r2, and r3, when the error correction code is an LDPC code, it is conceivable that the coding rates are 1/2, 2/3, and 3/4, respectively.

In the above, the case of three code rates has been described as an example, but the present invention is not limited to this, and the value for power change that can be set when two or more code rates can be set in the transmission device. When there are two or more and the code rate is set, the transmitter selects one of the values for power change from the values for power change that can be set, and changes the power. It is important to be able to do it.

(Example 1-3) In order for the receiving device to obtain better data reception quality, it is important to carry out the following.

A method of setting the average power (mean value) of s1 and s2 according to the modulation method used to generate s1 and s2 when the transmitter supports a plurality of modulation methods will be described.

Here, as an example, the modulation method of s1 is fixed to QPSK, and the modulation method of s2 is changed from 16QAM to 64QAM (or 16QAM or 64QAM can be set) by the control signal. think. When the modulation method of s2 (t) is 64QAM, the mapping method of s2 (t) is as shown in Fig. 101, and k is in Fig. 101.

<math num="85"><img file="JP2022017567A_D0092.tif" /></math>

Suppose that When such mapping is performed, the average power becomes equal when h is set to Eq. (78) for Fig. 96 in QPSK and when g is set to Eq. (79) for Fig. 95 in 16QAM. .. In addition, 64QAM mapping will determine the I and Q values from the 6-bit input, and this point can be carried out in the same way as the explanation of QPSK and 16QAM mapping.

That is, in FIG. 101, which is an example of the signal point arrangement of 64QAM in the IQ plane, (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0) is (I, Q). ) = (7 × k, 7 × k), (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 1) is (I, Q) = (7 × k, 5 × k), (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 1, 0) is (I, Q) = (5 × k, 7 × k) ), (B0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 1, 1) to (I, Q) = (5 × k, 5 × k), (b0 , B1, b2, b3, b4, b5) = (0, 0, 0, 1, 0, 0) becomes (I, Q) = (7 × k, 1 × k), ..., (b0) , B1, b2, b3, b4, b5) = (1, 1, 1, 1, 1, 0) becomes (I, Q) = (-3 × k, -1 × k), (b0, b1, b2, b3, b4, b5) = (1, 1, 1, 1, 1, 1) is mapped to (I, Q) = (-3 × k, -3 × k). Note that b0 to b5 shown on the right shoulder of FIG. 101 indicate the arrangement with each bit of the numerical value shown on the IQ plane.

In FIG. 99, when the modulation method of s2 is 16QAM, the power change unit 9901B is u = u.₁₆When the modulation method of s2 is 64QAM, u = u₆₄It shall be set as. At this time, due to the relationship of the minimum Euclidean distance, u₁₆&lt;u₆₄Then, regardless of whether the modulation method of s2 is 16QAM or 64QAM, the receiving device can obtain high data reception quality.

In the above description, "fixing the modulation method of s1 to QPSK" has been described, but "fixing the modulation method of s2 to QPSK" can be considered. At this time, the power is not changed for the fixed modulation method (here, QPSK), and the power is changed for multiple configurable modulation methods (here, 16QAM and 64QAM). do. That is, in this case, the transmitter is not configured as shown in FIG. 99, but is configured to exclude the power changing unit 9901B from the configuration shown in FIG. 99 and to provide the power changing unit on the s1 (t) side. Then, when the fixed modulation method (here, QPSK) is set to s2, the following relational expression (86) is established.

<math num="86"><img file="JP2022017567A_D0093.tif" /></math>

Then, even if "fix the modulation method of s2 to QPSK and change the modulation method of s1 from 16QAM to 64QAM (set it to either 16QAM or 64QAM)", u₁₆&lt;u₆₄It is good to say. (Note that the value multiplied for power change at 16QAM is u₁₆And at 64QAM the value multiplied for the power change is u₆₄And QPSK shall not change power. ) Also, if the set of (s1 modulation method, s2 modulation method) can be set to either (QPSK, 16QAM) or (16QAM, QPSK) or (QPSK, 64QAM) or (64QAM, QPSK). , U₁₆&lt;u₆₄It is good to satisfy the relationship of.

Hereinafter, a case where the above contents are generalized will be described.

The modulation method of s1 is fixed, and the number of signal points in the IQ plane is c. Further, as the modulation method of s2, either the modulation method A having a number of signal points in the IQ plane or the modulation method B (a&gt; b&gt; c) having b number of signal points in the IQ plane can be set. It is possible. (However, it is assumed that the average power value (mean value) at the time of s2 of the modulation method A is equal to the average power value (mean value) at the time of s2 of the modulation method B.) At this time, the modulation is performed as the modulation method of s2. When method A is set, the value for changing the power to be set is u_aAnd. Also, when modulation method B is set as the modulation method of s2, the value for changing the power to be set is u._{b b}And. At this time, u_{b b}&lt;u_aThen, the receiving device can obtain high data reception quality.

A fixed modulation method (here, modulation method C) is not changed in power, and a plurality of configurable modulation methods (here, modulation method A and modulation method B) are changed in power. I think. Then, even when "the modulation method of s2 is fixed to the modulation method C and the modulation method of s1 is changed from the modulation method A to the modulation method B (set to either the modulation method A or the modulation method B)", u_{b b}&lt;u_aIt is good to say. Also, a set of (modulation method of s1, modulation method of s2) can be set to (modulation method C, modulation method A) or (modulation method A, modulation method C) or (modulation method C, modulation method B) or (modulation method). If either B or modulation method C) can be set, u_{b b}&lt;u_aIt is good to satisfy the relationship of.

(Example 2) An example of an operation different from that of Example 1 will be described with reference to FIG. 99. Note that s1 (t) is a baseband signal (signal after mapping) of the modulation method 64QAM, the mapping method is as shown in FIG. 101, and k is as shown in equation (85). Further, s2 (t) is a baseband signal (signal after mapping) of the modulation method 16QAM, the mapping method is as shown in FIG. 95, and g is as shown in Eq. (79). Note that t is a time, and in the present embodiment, the time axis direction will be described as an example.

The power change unit (9901B) inputs the baseband signal (signal after mapping) 307B and control signal (9900) of the modulation method 16QAM, and sets the value for power change based on the control signal (9900) u. Then, a signal (9902B) obtained by multiplying the baseband signal (signal after mapping) 307B of the modulation method 16QAM by u is output. Note that u is a real number and u &lt;1.0. For the modulated signal after precoding, the precoding matrix in the method of regularly changing the phase is F, and the phase change value for regularly changing the phase is y (t) (y (t) is the absolute value. An imaginary number of 1 (including real numbers), that is, ejθ^(t)(Can be expressed as), then the following equation holds.

Therefore, the ratio of the average power of 64QAM to the average power of 16QAM is 1: u.²Will be set. As a result, the reception state as shown in FIG. 98 is obtained, so that the reception quality of data in the receiving device can be improved.

Conventionally, the transmission power control generally controls the transmission power based on the feedback information from the communication partner. In the present embodiment, the feature of the present invention is that the transmission power is controlled regardless of the feedback information from the communication partner, and this point will be described in detail.

In the above, it was stated that "the value u for power change is set by the control signal (9900)", but in the following, the control signal (9900) is used to further improve the data reception quality in the receiving device. The method of setting the value u for power change by is described in detail.

(Example 2-1) s1 and s2 when the transmitter supports error correction codes of multiple block lengths (the number of bits that make up one coded block, also called the code length). A method of setting the average power (average value) of s1 and s2 according to the block length of the error correction code applied to the data used for the generation of is described.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of block lengths are used. Is supported. The coded data with error correction coding of the block length selected from the supported multiple block lengths is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the block length of the above-selected error correction code, and the power change unit (9901B) sets a value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901B) sets the value u for power change according to the selected block length indicated by the control signal (9900). Here, u is the value for power change according to the block length X._LXIt will be described in the form of.

For example, if 1000 is selected as the block length, the power change section (9901B) is the value u for power change._L1000When 1500 is selected as the block length, the power change section (9901B) is the value u for power change._L1500When 3000 is selected as the block length, the power change section (9901B) is the value u for power change._L3000To set. At this time, for example, u_L1000, U_L1500, U_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. However, depending on the code length to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the code length is changed, it is not necessary to change the value for changing the power. (For example, u_L1000= u_L1500It may be. The important thing is (u_L1000, U_L1500, U_L3000) Has two or more values. ) In the above, the case of three code lengths has been described as an example, but the present invention is not limited to this, and when two or more code lengths can be set in the transmitter, the value for power change that can be set is set. When there are two or more and the code length is set, the transmitter can select one of the values for power change from multiple configurable values for power change and change the power. What you can do is important.

(Example 2-2) When the transmitter supports multiple code rate error correction codes, depending on the code rate of the error correction code applied to the data used to generate s1 and s2. This section describes how to set the average power (mean value) of s1 and s2.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of codes are coded. Rate is supported. Error correction of the code rate selected from a plurality of supported code rates The coded data is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the coding rate of the above-selected error correction code, and the power change unit (9901B) sets the value u for power change according to the control signal (9900). ..

A feature of the present invention is that the power change unit (9901B) sets the value u for power change according to the selected coding rate indicated by the control signal (9900). Here, u is the value for power change according to the code rate rx._rxIt will be described in the form of.

For example, when r1 is selected as the code rate, the power change unit (9901B) is the value u for power change._r1When r2 is selected as the code rate, the power change unit (9901B) is the value u for power change._r2When r3 is selected as the code rate, the power change unit (9901B) is the value u for power change._r3To set. At this time, for example, u_r1, U_r2, U_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. However, depending on the coding rate to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the coding rate is changed, it is not necessary to change the value for changing the power. (For example, u_r1= u_r2It may be. The important thing is (u_r1, U_r2, U_r3) Has two or more values. ) As an example of the above r1, r2, and r3, when the error correction code is an LDPC code, it is conceivable that the coding rates are 1/2, 2/3, and 3/4, respectively.

In the above, the case of three code rates has been described as an example, but the present invention is not limited to this, and the value for power change that can be set when two or more code rates can be set in the transmission device. When there are two or more and the code rate is set, the transmitter selects one of the values for power change from the values for power change that can be set, and changes the power. It is important to be able to do it.

(Example 2-3) In order for the receiving device to obtain better data reception quality, it is important to carry out the following.

A method of setting the average power (mean value) of s1 and s2 according to the modulation method used to generate s1 and s2 when the transmitter supports a plurality of modulation methods will be described.

Here, as an example, the modulation method of s1 is fixed to 64QAM, and the modulation method of s2 is changed from 16QAM to QPSK (or 16QAM or QPSK can be set) by the control signal. think. When the modulation method of s1 is 64QAM, the mapping method of s1 (t) is as shown in FIG. 101, and in FIG. 101, k is equation (85). When the modulation method of s2 is 16QAM, the mapping method of s2 (t) is as shown in Fig. 95, g is equation (79) in Fig. 95, and the modulation method of s2 (t) is QPSK. Then, it is assumed that the mapping method of s2 (t) is as shown in FIG. 96, and h is the equation (78) in FIG. 96.

With such mapping, the average power (mean value) is the same for 16QAM and QPSK.

In FIG. 99, when the modulation method of s2 is 16QAM, the power change unit 9901B is u = u.₁₆When the modulation method of s2 is QPSK, u = u₄It shall be set as. At this time, due to the relationship of the minimum Euclidean distance, u₄&lt;u₁₆Then, regardless of whether the modulation method of s2 is 16QAM or QPSK, the receiving device can obtain high data reception quality.

In the above explanation, "s1 modulation method is fixed to 64QAM", but "s2 modulation method is fixed to 64QAM and s1 modulation method is changed from 16QAM to QPSK (either 16QAM or QPSK). Even if it is set), u₄&lt;u₁₆(You can think in the same way as the explanation in Example 1-3). (Note that the value multiplied for power change at 16QAM is u₁₆And the value multiplied for the power change at QPSK is u₄And 64QAM shall not be powered. ) Also, if the set of (s1 modulation method, s2 modulation method) can be set to either (64QAM, 16QAM) or (16QAM, 64QAM) or (64QAM, QPSK) or (QPSK, 64QAM). , U₄&lt;u₁₆It is good to satisfy the relationship of.

Hereinafter, a case where the above contents are generalized will be described.

The modulation method of s1 is fixed, and the number of signal points in the IQ plane is c. Further, as the modulation method of s2, either the modulation method A having a number of signal points in the IQ plane or the modulation method B (c&gt; b&gt; a) having b number of signal points in the IQ plane can be set. It is possible. (However, it is assumed that the average power value (mean value) at the time of s2 of the modulation method A is equal to the average power value (mean value) at the time of s2 of the modulation method B.) At this time, the modulation is performed as the modulation method of s2. When method A is set, the value for changing the power to be set is u_aAnd. Also, when modulation method B is set as the modulation method of s2, the value for changing the power to be set is u._{b b}And. At this time, u_a&lt;u_{b b}Then, the receiving device can obtain high data reception quality.

A fixed modulation method (here, modulation method C) is not changed in power, and a plurality of configurable modulation methods (here, modulation method A and modulation method B) are changed in power. I think. Then, even when "fixing the modulation method of s2 to the modulation method C and changing the modulation method of s1 from the modulation method A to the modulation method B (set to either the modulation method A or the modulation method B)", u_a&lt;u_{b b}It is good to say. Also, a set of (modulation method of s1, modulation method of s2) can be set to (modulation method C, modulation method A) or (modulation method A, modulation method C) or (modulation method C, modulation method B) or (modulation method). If either B or modulation method C) can be set, u_a&lt;u_{b b}It is good to satisfy the relationship of.

(Example 3) An example of an operation different from that of Example 1 will be described with reference to FIG. 99. Note that s1 (t) is a baseband signal (signal after mapping) of the modulation method 16QAM, the mapping method is as shown in FIG. 95, and g is as shown in equation (79). Further, s2 (t) is a baseband signal (signal after mapping) of the modulation method 64QAM, the mapping method is as shown in FIG. 101, and k is as shown in equation (85). Note that t is a time, and in the present embodiment, the time axis direction will be described as an example.

The power change unit (9901B) inputs the baseband signal (signal after mapping) 307B and control signal (9900) of the modulation method 64QAM, and sets the value for power change based on the control signal (additional 400). If u, a signal (9902B) obtained by multiplying the baseband signal (signal after mapping) 307B of the modulation method 64QAM by u is output. Note that u is a real number and u&gt; 1.0. For the modulated signal after precoding, the precoding matrix in the method of regularly changing the phase is F, and the phase change value for regularly changing the phase is y (t) (y (t) is the absolute value. An imaginary number of 1 (including real numbers), that is, ejθ^(t)(Can be expressed as), then the following equation holds.

Therefore, the ratio of 16QAM average power to 64QAM average power is 1: u²Will be set. As a result, the reception state as shown in FIG. 98 is obtained, so that the reception quality of data in the receiving device can be improved.

Conventionally, the transmission power control generally controls the transmission power based on the feedback information from the communication partner. In the present embodiment, the feature of the present invention is that the transmission power is controlled regardless of the feedback information from the communication partner, and this point will be described in detail.

In the above, it was stated that "the value u for power change is set by the control signal (9900)", but in the following, the control signal (9900) is used to further improve the data reception quality in the receiving device. The method of setting the value u for power change by is described in detail.

(Example 3-1) s1 and s2 when the transmitter supports error correction codes with multiple block lengths (the number of bits that make up one coded block, also known as the code length). A method of setting the average power (average value) of s1 and s2 according to the block length of the error correction code applied to the data used for the generation of is described.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of block lengths are used. Is supported. The coded data with error correction coding of the block length selected from the supported multiple block lengths is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the block length of the above-selected error correction code, and the power change unit (9901B) sets a value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901B) sets the value u for power change according to the selected block length indicated by the control signal (9900). Here, u is the value for power change according to the block length X._LXIt will be described in the form of.

For example, if 1000 is selected as the block length, the power change section (9901B) is the value u for power change._L1000When 1500 is selected as the block length, the power change section (9901B) is the value u for power change._L1500When 3000 is selected as the block length, the power change section (9901B) is the value u for power change._L3000To set. At this time, for example, u_L1000, U_L1500, U_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. However, depending on the code length to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the code length is changed, it is not necessary to change the value for changing the power. (For example, u_L1000= u_L1500It may be. The important thing is (u_L1000, U_L1500, U_L3000) Has two or more values. ) In the above, the case of three code lengths has been described as an example, but the present invention is not limited to this, and when two or more code lengths can be set in the transmitter, the value for power change that can be set is set. When there are two or more and the code length is set, the transmitter can select one of the values for power change from multiple configurable values for power change and change the power. What you can do is important.

(Example 3-2) When the transmitter supports multiple code rate error correction codes, depending on the code rate of the error correction code applied to the data used to generate s1 and s2. This section describes how to set the average power (mean value) of s1 and s2.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of codes are coded. Rate is supported. Error correction of the code rate selected from a plurality of supported code rates The coded data is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the coding rate of the above-selected error correction code, and the power change unit (9901B) sets the value u for power change according to the control signal (9900). ..

A feature of the present invention is that the power change unit (9901B) sets the value u for power change according to the selected coding rate indicated by the control signal (9900). Here, u is the value for power change according to the code rate rx._rxIt will be described in the form of.

For example, when r1 is selected as the code rate, the power change unit (9901B) is the value u for power change._r1When r2 is selected as the code rate, the power change unit (9901B) is the value u for power change._r2When r3 is selected as the code rate, the power change unit (9901B) is the value u for power change._r3To set. At this time, for example, u_r1, U_r2, U_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. However, depending on the coding rate to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the coding rate is changed, it is not necessary to change the value for changing the power. (For example, u_r1= u_r2It may be. The important thing is (u_r1, U_r2, U_r3) Has two or more values. ) As an example of the above r1, r2, and r3, when the error correction code is an LDPC code, it is conceivable that the coding rates are 1/2, 2/3, and 3/4, respectively.

In the above, the case of three code rates has been described as an example, but the present invention is not limited to this, and the value for power change that can be set when two or more code rates can be set in the transmission device. When there are two or more and the code rate is set, the transmitter selects one of the values for power change from the values for power change that can be set, and changes the power. It is important to be able to do it.

(Example 3-3) In order for the receiving device to obtain better data reception quality, it is important to carry out the following.

A method of setting the average power (mean value) of s1 and s2 according to the modulation method used to generate s1 and s2 when the transmitter supports a plurality of modulation methods will be described.

Here, as an example, the modulation method of s1 is fixed to 16QAM, and the modulation method of s2 is changed from 64QAM to QPSK (or 64QAM or QPSK can be set) by the control signal. think. When the modulation method of s1 is 16QAM, the mapping method of s2 (t) is as shown in Fig. 95, and g is Eq. (79) in Fig. 95. When the modulation method of s2 is 64QAM, the mapping method of s1 (t) is as shown in Fig. 101, k is equation (85) in Fig. 101, and the modulation method of s2 (t) is QPSK. Then, it is assumed that the mapping method of s2 (t) is as shown in FIG. 96, and that h is given by Eq. (78) in FIG. 96.

With such mapping, the average power is equal for 16QAM and QPSK.

In Figure 99, u = u when the modulation method of s2 is 64QAM.₆₄Set and u = u when the modulation method of s2 is QPSK₄It shall be set as. At this time, due to the relationship of the minimum Euclidean distance, u₄&lt;u₆₄Then, regardless of whether the modulation method of s2 is 16QAM or 64QAM, the receiving device can obtain high data reception quality.

In the above explanation, it was explained that "the modulation method of s1 is fixed to 16QAM", but "the modulation method of s2 is fixed to 16QAM and the modulation method of s1 is changed from 64QAM to QPSK (either 64QAM or QPSK). (Set to) ", even if u₄&lt;u₆₄(You can think in the same way as the explanation in Example 1-3). (Note that the value multiplied for power change at 64QAM is u₆₄And the value multiplied for the power change at QPSK is u₄Therefore, 16QAM shall not be powered. ) Also, if the set of (s1 modulation method, s2 modulation method) can be set to either (16QAM, 64QAM) or (64QAM, 16QAM) or (16QAM, QPSK) or (QPSK, 16QAM) , U₄&lt;u₆₄It is good to satisfy the relationship of.

Hereinafter, a case where the above contents are generalized will be described.

The modulation method of s1 is fixed, and the number of signal points in the IQ plane is c. Further, as the modulation method of s2, either the modulation method A having a number of signal points in the IQ plane or the modulation method B (c&gt; b&gt; a) having b number of signal points in the IQ plane can be set. It is possible. (However, it is assumed that the average power value (mean value) at the time of s2 of the modulation method A is equal to the average power value (mean value) at the time of s2 of the modulation method B.) At this time, the modulation is performed as the modulation method of s2. When method A is set, the value for changing the power to be set is u_aAnd. Also, when modulation method B is set as the modulation method of s2, the value for changing the power to be set is u._{b b}And. At this time, u_a&lt;u_{b b}Then, the receiving device can obtain high data reception quality.

A fixed modulation method (here, modulation method C) is not changed in power, and a plurality of configurable modulation methods (here, modulation method A and modulation method B) are changed in power. I think. Then, even when "fixing the modulation method of s2 to the modulation method C and changing the modulation method of s1 from the modulation method A to the modulation method B (set to either the modulation method A or the modulation method B)", u_a&lt;u_{b b}It is good to say. Also, a set of (modulation method of s1, modulation method of s2) can be set to (modulation method C, modulation method A) or (modulation method A, modulation method C) or (modulation method C, modulation method B) or (modulation method). If either B or modulation method C) can be set, u_a&lt;u_{b b}It is good to satisfy the relationship of.

(Example 4) In the above, the case of changing the power of one of s1 and s2 has been described, but here, the case of changing the power of both s1 and s2 will be described.

An example of the operation will be described with reference to FIG. 100. Note that s1 (t) is a baseband signal (signal after mapping) of the modulation method QPSK, the mapping method is as shown in FIG. 96, and h is as shown in equation (78). Further, s2 (t) is a baseband signal (signal after mapping) of the modulation method 16QAM, the mapping method is as shown in FIG. 95, and g is as shown in Eq. (79). Note that t is a time, and in the present embodiment, the time axis direction will be described as an example.

The power change unit (9901A) inputs the baseband signal (signal after mapping) 307A and control signal (9900) of the modulation method QPSK, and sets the value for power change based on the control signal (9900). Then, a signal (9902A) obtained by multiplying the baseband signal (signal after mapping) 307A of the modulation method QPSK by v is output.

The power change unit (9901B) inputs the baseband signal (signal after mapping) 307B and control signal (9900) of the modulation method 16QAM, and sets the value for power change based on the control signal (9900) u. Then, a signal (9902B) obtained by multiplying the baseband signal (signal after mapping) 307B of the modulation method 16QAM by u is output. Then, u = v × w (w&gt; 1.0).

Assuming that the precoding matrix in the method of regularly changing the phase is F [t], the following equation (87) holds.

For the modulated signal after precoding, the precoding matrix in the method of regularly changing the phase is F, and the phase change value for regularly changing the phase is y (t) (y (t) is the absolute value. An imaginary number of 1 (including real numbers), that is, ejθ^(t)(Can be expressed as), then the following equation (87) holds.

<math num="87"><img file="JP2022017567A_D0094.tif" /></math>

Therefore, the ratio of the average power of QPSK to the average power of 16QAM is v²: u²= v²: v²× w²= 1: w²Will be set. As a result, the reception state as shown in FIG. 98 is obtained, so that the reception quality of data in the receiving device can be improved.

Conventionally, the transmission power control generally controls the transmission power based on the feedback information from the communication partner. In the present embodiment, the feature of the present invention is that the transmission power is controlled regardless of the feedback information from the communication partner, and this point will be described in detail.

In the above, it was stated that "the values v and u for power change are set by the control signal (9900)", but in the following, the control signal (in order to further improve the data reception quality in the receiving device) The setting of the values v and u for power change by 9900) will be explained in detail.

(Example 4-1) s1 and s2 when the transmitter supports error correction codes with multiple block lengths (the number of bits that make up one coded block, also known as the code length). A method of setting the average power (average value) of s1 and s2 according to the block length of the error correction code applied to the data used for the generation of is described.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of block lengths are used. Is supported. The coded data with error correction coding of the block length selected from the supported multiple block lengths is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the block length of the above-selected error correction code, and the power change unit (9901A) sets a value v for power change according to the control signal (9900). Similarly, the power change unit (9901B) sets the value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901A, 9901B) sets the values v and u for power change according to the selected block length indicated by the control signal (9900). Here, the values for power change according to the block length X are v._LX, U_LXIt will be described in the form of.

For example, if 1000 is selected as the block length, the power change section (9901A) is the value v for power change._L1000If 1500 is selected as the block length, the power change section (9901A) is the value for power change v_L1500If 3000 is selected as the block length, the power change section (9901A) is the value v for power change._L3000To set.

On the other hand, when 1000 is selected as the block length, the power change unit (9901B) is the value u for power change._L1000When 1500 is selected as the block length, the power change section (9901B) is the value u for power change._L1500When 3000 is selected as the block length, the power change section (9901B) is the value u for power change._L3000To set.

At this time, for example, v_L1000, V_L1500, V_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. Similarly, u_L1000, U_L1500, U_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. However, depending on the code length to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the code length is changed, it is not necessary to change the value for changing the power. (For example, u_L1000= u_L1500It can also be v_L1000= v_L1500It may be. The important thing is (v_L1000, V_L1500, V_L3000There are two or more values in the set of).

Also, (u_L1000, U_L1500, U_L3000There are two or more values in the set of). ) In addition, v_LXAnd u_LXAnd the ratio of average power values, 1: w²As described above, it is set to satisfy.

In the above, the case of three code lengths has been described as an example, but the present invention is not limited to this, and the value u for power change that can be set when two or more code lengths can be set in the transmitting device._LXWhen there is more than one and the code length is set, the transmitter will have multiple configurable power change values u_LXOne important point is that the power can be changed by selecting one of the values for power change from among them, and when two or more code lengths can be set in the transmitter. Value for configurable power change v_LXWhen there is more than one and the code length is set, the transmitter will have multiple configurable power change values v_LXIt is also important to be able to select one of the values for power change and change the power.

(Example 4-2) When the transmitter supports multiple code rate error correction codes, depending on the code rate of the error correction code applied to the data used to generate s1 and s2. This section describes how to set the average power (mean value) of s1 and s2.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of codes are coded. Rate is supported. Error correction of the code rate selected from a plurality of supported code rates The coded data is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the coding rate of the above-selected error correction code, and the power change unit (9901A) sets a value v for power change according to the control signal (9900). .. Further, the power change unit (9901B) sets the value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901A, 9901B) sets the values v and u for power change according to the selected coding rate indicated by the control signal (9900). Here, the values for power change according to the coding rate rx are v, respectively._rx, U_rxIt will be described in the form of.

For example, when r1 is selected as the code rate, the power change section (9901A) is the value v for power change._r1And when r2 is selected as the code rate, the power change section (9901A) is the value v for power change._r2And when r3 is selected as the code rate, the power change section (9901A) is the value v for power change._r3To set.

When r1 is selected as the code rate, the power change unit (9901B) is the value u for power change._r1When r2 is selected as the code rate, the power change unit (9901B) is the value u for power change._r2When r3 is selected as the code rate, the power change unit (9901B) is the value u for power change._r3To set.

At this time, for example, v_r1, V_r2, V_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. Similarly, u_r1, U_r2, U_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. However, depending on the coding rate to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the coding rate is changed, it is not necessary to change the value for changing the power. (For example, v_r1= v_r2It can also be u_r1= u_r2It may be. The important thing is (v_r1, V_r2, V_r3There are two or more values in the set of). Also, (u_r1, U_r2, U_r3There are two or more values in the set of). ) In addition, v_rXAnd u_rXAnd the ratio of average power values, 1: w²As described above, it is set to satisfy.

Further, as an example of the above r1, r2, and r3, when the error correction code is an LDPC code, it is conceivable that the coding rates are 1/2, 2/3, and 3/4, respectively.

In the above, the case of three code rates has been described as an example, but the present invention is not limited to this, and the value for power change that can be set when two or more code rates can be set in the transmitter. u u_rxWhen there is more than one and the code rate is set, the transmitter will have multiple configurable values for power changes u_rxIt is important to be able to select one of the values for power change from among them and change the power, and set it when two or more coding rates can be set in the transmitter. Value for possible power changes v_rXWhen there is more than one and the code rate is set, the transmitter will have multiple configurable values for power changes v_rXIt is also important to be able to select one of the values for power change and change the power.

(Example 4-3) In order for the receiving device to obtain better data reception quality, it is important to carry out the following.

A method of setting the average power (mean value) of s1 and s2 according to the modulation method used to generate s1 and s2 when the transmitter supports a plurality of modulation methods will be described.

Here, as an example, consider a case where the modulation method of s1 is fixed to QPSK and the modulation method of s2 is changed from 16QAM to 64QAM (or 16QAM or 64QAM can be set) by a control signal. When the modulation method of s1 is QPSK, the mapping method of s1 (t) is as shown in FIG. 96, and h is equation (78) in FIG. 96. When the modulation method of s2 is 16QAM, the mapping method of s2 (t) is as shown in Fig. 95, g is equation (79) in Fig. 95, and the modulation method of s2 (t) is 64QAM. Then, it is assumed that the mapping method of s2 (t) is as shown in FIG. 101, and that k is the equation (85) in FIG. 101.

In FIG. 100, when the modulation method of s1 is QPSK and the modulation method of s2 is 16QAM, v = α and u = α × w.₁₆It shall be set. At this time, the ratio of the average power of QPSK and the average power of 16QAM is v.²: u²= α²: α²× w₁₆²= 1: w₁₆²Will be.

Then, in FIG. 100, when the modulation method of s1 is QPSK and the modulation method of s2 is 64QAM, v = β and u = β × w.₆₄It shall be set. At this time, the ratio of the average power of QPSK to the average power of 64QAM is v: u = β.²: β²× w₆₄²= 1: w₆₄²Will be. At this time, 1.0 &lt;w₁₆&lt;w₆₄Then, regardless of whether the modulation method of s2 is 16QAM or 64QAM, the receiving device can obtain high data reception quality.

In the above description, "fixing the modulation method of s1 to QPSK" has been described, but "fixing the modulation method of s2 to QPSK" can be considered. At this time, the power is not changed for the fixed modulation method (here, QPSK), but the power is changed for a plurality of configurable modulation methods (here, 16QAM and 64QAM). Then, when the fixed modulation method (here, QPSK) is set to s2, the following relational expression (88) is established.

<math num="88"><img file="JP2022017567A_D0095.tif" /></math>

Then, even if "fix the modulation method of s2 to QPSK and change the modulation method of s1 from 16QAM to 64QAM (set to either 16QAM or 64QAM)", 1.0 &lt;w₁₆&lt;w₆₄It is good to say. (Note that the value multiplied for power change at 16QAM is u = α × w₁₆And the value multiplied for power change at 64QAM is u = β × w₆₄The value for changing the power of QPSK is v = α when a plurality of configurable modulation methods are 16QAM, and v = β when a plurality of configurable modulation methods are 64QAM. ) Also, if the set of (s1 modulation method, s2 modulation method) can be set to either (QPSK, 16QAM) or (16QAM, QPSK) or (QPSK, 64QAM) or (64QAM, QPSK). , 1.0 &lt;w₁₆&lt;w₆₄It is good to satisfy the relationship of.

Hereinafter, a case where the above contents are generalized will be described.

When generalized, the modulation method of s1 is fixed, and the number of signal points in the IQ plane is c modulation method C. As the modulation method of s2, it is possible to set either the modulation method A having a number of signal points in the IQ plane or the modulation method B (a&gt; b&gt; c) having b number of signal points in the IQ plane. Suppose there is. At this time, the ratio of the average power when the modulation method of s1 is the modulation method C and the modulation method A is set as the modulation method of s2 is 1: w._a²And. The ratio of the average power when the modulation method of s1 is modulation method C and the modulation method B is set as the modulation method of s2 is 1: w._{b b}²And. At this time, w_{b b}&lt;w_aThen, the receiving device can obtain high data reception quality.

Therefore, in the above example, it was described as "fixing the modulation method of s1 to the modulation method C", but "fixing the modulation method of s2 to the modulation method C and changing the modulation method of s1 from the modulation method A to the modulation method B". Even when "changed (set to either modulation method A or modulation method B)", w regarding the average power_{b b}&lt;w_aIt is good to say. (At this time, similarly to the above, when the average power of the modulation method C is 1, the average power of the modulation method A is w._a²And the average power of modulation method B is w_{b b}²Is. ) Also, a set of (modulation method of s1, modulation method of s2) can be set to (modulation method C, modulation method A) or (modulation method A, modulation method C) or (modulation method C, modulation method B) or (modulation method B). If either method B or modulation method C) can be set, w regarding the average power_{b b}&lt;w_aIt is good to satisfy the relationship of.

(Example 5) An example of an operation different from that of Example 4 will be described with reference to FIG. 100. Note that s1 (t) is a baseband signal (signal after mapping) of the modulation method 64QAM, the mapping method is as shown in FIG. 101, and k is as shown in equation (85). Further, s2 (t) is a baseband signal (signal after mapping) of the modulation method 16QAM, the mapping method is as shown in FIG. 95, and g is as shown in Eq. (79). Note that t is a time, and in the present embodiment, the time axis direction will be described as an example.

The power change unit (9901A) inputs the baseband signal (signal after mapping) 307A and control signal (9900) of the modulation method 64QAM, and sets the value for power change based on the control signal (9900). Then, a signal (9902A) obtained by multiplying the baseband signal (signal after mapping) 307A of the modulation method 64QAM by v is output.

The power change unit (9901B) inputs the baseband signal (signal after mapping) 307B and control signal (9900) of the modulation method 16QAM, and sets the value for power change based on the control signal (9900) u. Then, a signal (9902B) obtained by multiplying the baseband signal (signal after mapping) 307B of the modulation method 16QAM by u is output. Then, u = v × w (w &lt;1.0).

For the modulated signal after precoding, the precoding matrix in the method of regularly changing the phase is F, and the phase change value for regularly changing the phase is y (t) (y (t) is the absolute value. An imaginary number of 1 (including real numbers), that is, ejθ^(t)(Can be expressed as), then the above equation (87) holds.

Therefore, the ratio of the average power of 64QAM to the average power of 16QAM is v²: u²= v²: v²× w²= 1: w²Will be set. As a result, the reception state as shown in FIG. 98 is obtained, so that the reception quality of data in the receiving device can be improved.

Conventionally, the transmission power control generally controls the transmission power based on the feedback information from the communication partner. In the present embodiment, the feature of the present invention is that the transmission power is controlled regardless of the feedback information from the communication partner, and this point will be described in detail.

In the above, it was stated that "the values v and u for power change are set by the control signal (9900)", but in the following, the control signal (in order to further improve the data reception quality in the receiving device) The setting of the values v and u for power change by 9900) will be explained in detail.

(Example 5-1) s1 and s2 when the transmitter supports error correction codes with multiple block lengths (the number of bits that make up one coded block, also known as the code length). A method of setting the average power (average value) of s1 and s2 according to the block length of the error correction code applied to the data used for the generation of is described.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of block lengths are used. Is supported. The coded data with error correction coding of the block length selected from the supported multiple block lengths is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the block length of the above-selected error correction code, and the power change unit (9901A) sets a value v for power change according to the control signal (9900). Similarly, the power change unit (9901B) sets the value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901A, 9901B) sets the values v and u for power change according to the selected block length indicated by the control signal (9900). Here, the values for power change according to the block length X are v._LX, U_LXIt will be described in the form of.

For example, if 1000 is selected as the block length, the power change section (9901A) is the value v for power change._L1000If 1500 is selected as the block length, the power change section (9901A) is the value for power change v_L1500If 3000 is selected as the block length, the power change section (9901A) is the value v for power change._L3000To set.

On the other hand, when 1000 is selected as the block length, the power change unit (9901B) is the value u for power change._L1000When 1500 is selected as the block length, the power change section (9901B) is the value u for power change._L1500When 3000 is selected as the block length, the power change section (9901B) is the value u for power change._L3000To set.

At this time, for example, v_L1000, V_L1500, V_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. Similarly, u_L1000, U_L1500, U_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. However, depending on the code length to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the code length is changed, it is not necessary to change the value for changing the power. (For example, u_L1000= u_L1500It can also be v_L1000= v_L1500It may be. The important thing is (v_L1000, V_L1500, V_L3000There are two or more values in the set of).

Also, (u_L1000, U_L1500, U_L3000There are two or more values in the set of). ) In addition, v_LXAnd u_LXAnd the ratio of average power values, 1: w²As described above, it is set to satisfy.

In the above, the case of three code lengths has been described as an example, but the present invention is not limited to this, and the value u for power change that can be set when two or more code lengths can be set in the transmitting device._LXWhen there is more than one and the code length is set, the transmitter will have multiple configurable power change values u_LXOne important point is that the power can be changed by selecting one of the values for power change from among them, and when two or more code lengths can be set in the transmitter. Value for configurable power change v_LXWhen there is more than one and the code length is set, the transmitter will have multiple configurable power change values v_LXIt is also important to be able to select one of the values for power change and change the power.

(Example 5-2) When the transmitter supports multiple code rate error correction codes, depending on the code rate of the error correction code applied to the data used to generate s1 and s2. This section describes how to set the average power (mean value) of s1 and s2.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of codes are coded. Rate is supported. Error correction of the code rate selected from a plurality of supported code rates The coded data is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the coding rate of the above-selected error correction code, and the power change unit (9901A) sets a value v for power change according to the control signal (9900). .. Further, the power change unit (9901B) sets the value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901A, 9901B) sets the values v and u for power change according to the selected coding rate indicated by the control signal (9900). Here, the values for power change according to the coding rate rx are v, respectively._rx, U_rxIt will be described in the form of.

For example, when r1 is selected as the code rate, the power change section (9901A) is the value v for power change._r1And when r2 is selected as the code rate, the power change section (9901A) is the value v for power change._r2And when r3 is selected as the code rate, the power change section (9901A) is the value v for power change._r3To set.

When r1 is selected as the code rate, the power change unit (9901B) is the value u for power change._r1When r2 is selected as the code rate, the power change unit (9901B) is the value u for power change._r2When r3 is selected as the code rate, the power change unit (9901B) is the value u for power change._r3To set.

At this time, for example, v_r1, V_r2, V_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. Similarly, u_r1, U_r2, U_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. However, depending on the coding rate to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the coding rate is changed, it is not necessary to change the value for changing the power. (For example, v_r1= v_r2It can also be u_r1= u_r2It may be. The important thing is (v_r1, V_r2, V_r3There are two or more values in the set of). Also, (u_r1, U_r2, U_r3There are two or more values in the set of). ) In addition, v_rXAnd u_rXAnd the ratio of average power values, 1: w²As described above, it is set to satisfy.

Further, as an example of the above r1, r2, and r3, when the error correction code is an LDPC code, it is conceivable that the coding rates are 1/2, 2/3, and 3/4, respectively.

In the above, the case of three code rates has been described as an example, but the present invention is not limited to this, and the value for power change that can be set when two or more code rates can be set in the transmitter. u u_rxWhen there is more than one and the code rate is set, the transmitter will have multiple configurable values for power changes u_rxIt is important to be able to select one of the values for power change from among them and change the power, and set it when two or more coding rates can be set in the transmitter. Value for possible power changes v_rXWhen there is more than one and the code rate is set, the transmitter will have multiple configurable values for power changes v_rXIt is also important to be able to select one of the values for power change and change the power.

(Example 5-3) In order for the receiving device to obtain better data reception quality, it is important to carry out the following.

A method of setting the average power (mean value) of s1 and s2 according to the modulation method used to generate s1 and s2 when the transmitter supports a plurality of modulation methods will be described.

Here, as an example, consider a case where the modulation method of s1 is fixed to 64QAM and the modulation method of s2 is changed from 16QAM to QPSK (or 16QAM or QPSK can be set) by a control signal. When the modulation method of s1 is 64QAM, the mapping method of s1 (t) is as shown in FIG. 101, and in FIG. 101, k is equation (85). When the modulation method of s2 is 16QAM, the mapping method of s2 (t) is as shown in Fig. 95, g is equation (79) in Fig. 95, and the modulation method of s2 (t) is QPSK. Then, it is assumed that the mapping method of s2 (t) is as shown in FIG. 96, and h is the equation (78) in FIG. 96.

In FIG. 100, when the modulation method of s1 is 64QAM and the modulation method of s2 is 16QAM, v = α and u = α × w.₁₆It shall be set. At this time, the ratio of the average power of 64QAM to the average power of 16QAM is v.²: u²= α²: α²× w₁₆²= 1: w₁₆²Will be.

Then, in FIG. 100, when the modulation method of s1 is 64QAM and the modulation method of s2 is QPSK, v = β and u = β × w.₄It shall be set. At this time, the ratio of the average power of 64QAM and the average power of QPSK is v.²: u²= β²: β²× w₄²= 1: w₄²Will be. At this time, from the relation of the minimum Euclidean distance, w₄&lt;w₁₆When &lt;1.0 is set, the receiving device can obtain high data reception quality regardless of whether the modulation method of s2 is 16QAM or QPSK.

In the above explanation, it was explained that "the modulation method of s1 is fixed to 64QAM", but "the modulation method of s2 is fixed to 64QAM and the modulation method of s1 is changed from 16QAM to QPSK (either 16QAM or QPSK). (Set to) ", but w₄&lt;w₁₆&lt;1.0 should be set. (You can think in the same way as the explanation in Example 4-3.). (Note that the value multiplied for power change at 16QAM is u = α × w₁₆And the value multiplied for power change at QPSK is u = β × w₄The value for changing the power of 64QAM is v = α when a plurality of configurable modulation methods are 16QAM, and v = β when a plurality of configurable modulation methods are QPSK. ) Also, if the set of (s1 modulation method, s2 modulation method) can be set to either (64QAM, 16QAM) or (16QAM, 64QAM) or (64QAM, QPSK) or (QPSK, 64QAM). , W₄&lt;w₁₆It is good to satisfy the relationship of &lt;1.0.

Hereinafter, a case where the above contents are generalized will be described.

When generalized, the modulation method of s1 is fixed, and the number of signal points in the IQ plane is c modulation method C. As the modulation method of s2, it is possible to set either the modulation method A having a number of signal points in the IQ plane or the modulation method B (c&gt; b&gt; a) having b number of signal points in the IQ plane. Suppose there is. At this time, the ratio of the average power when the modulation method of s1 is the modulation method C and the modulation method A is set as the modulation method of s2 is 1: w._a²And. The ratio of the average power when the modulation method of s1 is modulation method C and the modulation method B is set as the modulation method of s2 is 1: w._{b b}²And. At this time, w_a&lt;w_{b b}Then, the receiving device can obtain high data reception quality.

Therefore, although it was explained that "the modulation method of s1 is fixed to the modulation method C", "the modulation method of s2 is fixed to the modulation method C and the modulation method of s1 is changed from the modulation method A to the modulation method B (modulation method). Even if A or modulation method B is set), w_a&lt;w_{b b}It is good to say. (At this time, similarly to the above, when the average power of the modulation method C is 1, the average power of the modulation method A is w._a²And the average power of modulation method B is w_{b b}²Is. ) Also, a set of (modulation method of s1, modulation method of s2) can be set to (modulation method C, modulation method A) or (modulation method A, modulation method C) or (modulation method C, modulation method B) or (modulation method B). If either method B or modulation method C) can be set, w regarding the average power_a&lt;w_{b b}It is good to satisfy the relationship of.

(Example 6) An example of an operation different from that of Example 4 will be described with reference to FIG. 100. Note that s1 (t) is a baseband signal (signal after mapping) of the modulation method 16QAM, the mapping method is as shown in FIG. 101, and g is as shown in equation (79). Further, s2 (t) is a baseband signal (signal after mapping) of the modulation method 64QAM, the mapping method is as shown in FIG. 101, and k is as shown in equation (85). Note that t is a time, and in the present embodiment, the time axis direction will be described as an example.

The power change unit (9901A) inputs the baseband signal (signal after mapping) 307A and control signal (9900) of the modulation method 16QAM, and sets the value for power change based on the control signal (9900). Then, a signal (9902A) obtained by multiplying the baseband signal (signal after mapping) 307A of the modulation method 16QAM by v is output.

The power change unit (9901B) inputs the baseband signal (signal after mapping) 307B and control signal (9900) of the modulation method 64QAM, and sets the value for power change based on the control signal (9900) u. Then, a signal (9902B) obtained by multiplying the baseband signal (signal after mapping) 307B of the modulation method 64QAM by u is output. Then, u = v × w (w &lt;1.0).

For the modulated signal after precoding, the precoding matrix in the method of regularly changing the phase is F, and the phase change value for regularly changing the phase is y (t) (y (t) is the absolute value. An imaginary number of 1 (including real numbers), that is, ejθ^(t)(Can be expressed as), then the above equation (87) holds.

Therefore, the ratio of the average power of 64QAM to the average power of 16QAM is v²: u²= v²: v²× w²= 1: w²Will be set. As a result, the reception state as shown in FIG. 98 is obtained, so that the reception quality of data in the receiving device can be improved.

Conventionally, the transmission power control generally controls the transmission power based on the feedback information from the communication partner. In the present embodiment, the feature of the present invention is that the transmission power is controlled regardless of the feedback information from the communication partner, and this point will be described in detail.

In the above, it was stated that "the values v and u for power change are set by the control signal (9900)", but in the following, the control signal (in order to further improve the data reception quality in the receiving device) The setting of the values v and u for power change by 9900) will be explained in detail.

(Example 6-1) s1 and s2 when the transmitter supports error correction codes with multiple block lengths (the number of bits that make up one coded block, also known as the code length). A method of setting the average power (average value) of s1 and s2 according to the block length of the error correction code applied to the data used for the generation of is described.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of block lengths are used. Is supported. The coded data with error correction coding of the block length selected from the supported multiple block lengths is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the block length of the above-selected error correction code, and the power change unit (9901A) sets a value v for power change according to the control signal (9900). Similarly, the power change unit (9901B) sets the value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901A, 9901B) sets the values v and u for power change according to the selected block length indicated by the control signal (9900). Here, the values for power change according to the block length X are v._LX, U_LXIt will be described in the form of.

For example, if 1000 is selected as the block length, the power change section (9901A) is the value v for power change._L1000If 1500 is selected as the block length, the power change section (9901A) is the value for power change v_L1500If 3000 is selected as the block length, the power change section (9901A) is the value v for power change._L3000To set.

On the other hand, when 1000 is selected as the block length, the power change unit (9901B) is the value u for power change._L1000When 1500 is selected as the block length, the power change section (9901B) is the value u for power change._L1500When 3000 is selected as the block length, the power change section (9901B) is the value u for power change._L3000To set.

At this time, for example, v_L1000, V_L1500, V_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. Similarly, u_L1000, U_L1500, U_L3000By setting different values for each, it may be possible to obtain high error correction capability at each code length. However, depending on the code length to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the code length is changed, it is not necessary to change the value for changing the power. (For example, u_L1000= u_L1500It can also be v_L1000= v_L1500It may be. The important thing is (v_L1000, V_L1500, V_L3000There are two or more values in the set of).

Also, (u_L1000, U_L1500, U_L3000There are two or more values in the set of). ) In addition, v_LXAnd u_LXAnd the ratio of average power values, 1: w²As described above, it is set to satisfy.

In the above, the case of three code lengths has been described as an example, but the present invention is not limited to this, and the value u for power change that can be set when two or more code lengths can be set in the transmitting device._LXWhen there is more than one and the code length is set, the transmitter will have multiple configurable power change values u_LXOne important point is that the power can be changed by selecting one of the values for power change from among them, and when two or more code lengths can be set in the transmitter. Value for configurable power change v_LXWhen there is more than one and the code length is set, the transmitter will have multiple configurable power change values v_LXIt is also important to be able to select one of the values for power change and change the power.

(Example 6-2) When the transmitter supports multiple code rate error correction codes, depending on the code rate of the error correction code applied to the data used to generate s1 and s2. Describes how to set the average power of s1 and s2.

The error correction code includes, for example, a tail-biting turbo code or a duobinary turbo code, and a block code such as an LDPC code. In many communication systems or broadcasting systems, a plurality of codes are coded. Rate is supported. Error correction of the code rate selected from a plurality of supported code rates The coded data is distributed to the two systems. The coded data distributed to the two systems is modulated by the modulation method of s1 and the modulation method of s2, respectively, and the baseband signals (signals after mapping) s1 (t) and s2 (t) are generated.

The control signal (9900) is a signal indicating the coding rate of the above-selected error correction code, and the power change unit (9901A) sets a value v for power change according to the control signal (9900). .. Further, the power change unit (9901B) sets the value u for power change according to the control signal (9900).

A feature of the present invention is that the power change unit (9901A, 9901B) sets the values v and u for power change according to the selected coding rate indicated by the control signal (9900). Here, the values for power change according to the coding rate rx are v, respectively._rx, U_rxIt will be described in the form of.

For example, when r1 is selected as the code rate, the power change section (9901A) is the value v for power change._r1And when r2 is selected as the code rate, the power change section (9901A) is the value v for power change._r2And when r3 is selected as the code rate, the power change section (9901A) is the value v for power change._r3To set.

When r1 is selected as the code rate, the power change unit (9901B) is the value u for power change._r1When r2 is selected as the code rate, the power change unit (9901B) is the value u for power change._r2When r3 is selected as the code rate, the power change unit (9901B) is the value u for power change._r3To set.

At this time, for example, v_r1, V_r2, V_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. Similarly, u_r1, U_r2, U_r3By setting different values for each, it may be possible to obtain a high error correction capability at each coding rate. However, depending on the coding rate to be set, the effect may not be obtained even if the value for changing the power is changed. In that case, even if the coding rate is changed, it is not necessary to change the value for changing the power. (For example, v_r1= v_r2It can also be u_r1= u_r2It may be. The important thing is (v_r1, V_r2, V_r3There are two or more values in the set of). Also, (u_r1, U_r2, U_r3There are two or more values in the set of). ) In addition, v_rXAnd u_rXAnd the ratio of average power values, 1: w²As described above, it is set to satisfy.

Further, as an example of the above r1, r2, and r3, when the error correction code is an LDPC code, it is conceivable that the coding rates are 1/2, 2/3, and 3/4, respectively.

In the above, the case of three code rates has been described as an example, but the present invention is not limited to this, and the value for power change that can be set when two or more code rates can be set in the transmitter. u u_rxWhen there is more than one and the code rate is set, the transmitter will have multiple configurable values for power changes u_rxIt is important to be able to select one of the values for power change from among them and change the power, and set it when two or more coding rates can be set in the transmitter. Value for possible power changes v_rXWhen there is more than one and the code rate is set, the transmitter will have multiple configurable values for power changes v_rXIt is also important to be able to select one of the values for power change and change the power.

(Example 6-3) In order for the receiving device to obtain better data reception quality, it is important to carry out the following.

A method of setting the average power (mean value) of s1 and s2 according to the modulation method used to generate s1 and s2 when the transmitter supports a plurality of modulation methods will be described.

Here, as an example, consider a case where the modulation method of s1 is fixed to 16QAM and the modulation method of s2 is changed from 64QAM to QPSK (or 16QAM or QPSK can be set) by a control signal. When the modulation method of s1 is 16QAM, the mapping method of s1 (t) is as shown in FIG. 95, and g is equation (79) in FIG. 95. When the modulation method of s2 is 64QAM, the mapping method of s2 (t) is as shown in Fig. 101, k is equation (85) in Fig. 101, and the modulation method of s2 (t) is QPSK. Then, it is assumed that the mapping method of s2 (t) is as shown in FIG. 96, and h is the equation (78) in FIG. 96.

In FIG. 100, when the modulation method of s1 is 16QAM and the modulation method of s2 is 64QAM, v = α and u = α × w.₆₄It shall be set. At this time, the ratio of the average power of 64QAM to the average power of 16QAM is v.²: u²= α²: α²× w₆₄²= 1: w₆₄²Will be.

Then, in FIG. 100, when the modulation method of s1 is 16QAM and the modulation method of s2 is QPSK, v = β and u = β × w.₄It shall be set. At this time, the ratio of the average power of 64QAM and the average power of QPSK is v.²: u²= β²: β²× w₄²= 1: w₄²Will be. At this time, from the relation of the minimum Euclidean distance, w₄&lt;w₆₄Then, the receiving device can obtain high data reception quality regardless of whether the modulation method of s2 is 64QAM or QPSK.

In the above explanation, it was explained that "the modulation method of s1 is fixed to 16QAM", but "the modulation method of s2 is fixed to 16QAM and the modulation method of s1 is changed from 64QAM to QPSK (either 16QAM or QPSK). (Set to) ", but w₄&lt;w₆₄It is good to say.

(You can think in the same way as the explanation in Example 4-3.). (Note that the value multiplied for power change at 16QAM is u = α × w₁₆And the value multiplied for power change at QPSK is u = β × w₄The value for changing the power of 64QAM is v = α when a plurality of configurable modulation methods are 16QAM, and v = β when a plurality of configurable modulation methods are QPSK. ) Also, if the set of (s1 modulation method, s2 modulation method) can be set to either (16QAM, 64QAM) or (64QAM, 16QAM) or (16QAM, QPSK) or (QPSK, 16QAM) , W₄&lt;w₆₄It is good to satisfy the relationship of.

Hereinafter, a case where the above contents are generalized will be described.

When generalized, the modulation method of s1 is fixed, and the number of signal points in the IQ plane is c modulation method C. As the modulation method of s2, it is possible to set either the modulation method A having a number of signal points in the IQ plane or the modulation method B (c&gt; b&gt; a) having b number of signal points in the IQ plane. Suppose there is. At this time, the ratio of the average power when the modulation method of s1 is the modulation method C and the modulation method A is set as the modulation method of s2 is 1: w._a²And. The ratio of the average power when the modulation method of s1 is modulation method C and the modulation method B is set as the modulation method of s2 is 1: w._{b b}²And. At this time, w_a&lt;w_{b b}Then, the receiving device can obtain high data reception quality.

Therefore, although it was explained that "the modulation method of s1 is fixed to the modulation method C", "the modulation method of s2 is fixed to the modulation method C and the modulation method of s1 is changed from the modulation method A to the modulation method B (modulation method). Even if A or modulation method B is set), w_a&lt;w_{b b}It is good to say. (At this time, similarly to the above, when the average power of the modulation method C is 1, the average power of the modulation method A is w._a²And the average power of modulation method B is w_{b b}²Is. ) Also, a set of (modulation method of s1, modulation method of s2) can be set to (modulation method C, modulation method A) or (modulation method A, modulation method C) or (modulation method C, modulation method B) or (modulation method B). If either method B or modulation method C) can be set, w regarding the average power_a&lt;w_{b b}It is good to satisfy the relationship of.

In the present specification shown in the above "Embodiment 1" and the like, when α = 1 is set in the precoding matrix equation (36) used for the method of regularly changing the phase, "s1" is set as described above. Even if the average power of s1 and the average power of s2 are different when the modulation method of s2 and the modulation method of s2 are different, the average power of z1 and the average power of z2 are equal, and the transmission power amplifier provided in the transmitter Since it does not lead to an increase in PAPR (Peak-to-Average Power Ratio), it is possible to obtain the effect of reducing the power consumption of the transmitter.

However, even if α 1, there is a precoding matrix used for the method of changing the phase regularly, which has little effect on PAPR. For example, when a method of regularly changing the phase using the precoding matrix represented by the equation (36) in the first embodiment is realized, the influence of PAPR is small even if α 1.

(Operation of receiving device) Next, the operation of the receiving device will be described. The operation of the receiving device is as described in the first embodiment and the like. For example, the configuration of the receiving device is shown in FIGS. 7, 8, 9, 86, 87, and 88.

From the relationship of Fig. 5, when the received signals r1 (t) and r2 (t) are channel fluctuation values, h11 (t), h12 (t), h21 (t), and h22 (t), Fig. 99, Fig. When the transmitting device transmits a modulated signal as in 100, one of the following two equations holds.

In the case of Example 1, Example 2, and Example 3, the relationship shown in the following equation (89) can be derived from FIG.

<math num="89"><img file="JP2022017567A_D0096.tif" /></math>

Further, as described in Example 1, Example 2, and Example 3, the relationship may be as shown in the following equation (90).

<math num="90"><img file="JP2022017567A_D0097.tif" /></math>

Using the above relationship, the receiving device will perform demodulation (detection) (estimate the bits transmitted by the transmitting device) (may be performed in the same manner as described in the first embodiment or the like). become).

On the other hand, in the case of Example 4, Example 5, and Example 6, the relationship shown in the following equation (91) can be derived from FIG.

<math num="91"><img file="JP2022017567A_D0098.tif" /></math>

Further, as described in Example 3, Example 4, and Example 5, the relationship may be as shown in the following equation (92).

<math num="92"><img file="JP2022017567A_D0099.tif" /></math>

Using the above relationship, the receiving device will perform demodulation (detection) (estimate the bits transmitted by the transmitting device) (may be performed in the same manner as described in the first embodiment or the like). become).

In Examples 1 to 6, the configuration in which the power changing unit is added to the transmission device is shown, but the power may be changed at the mapping stage.

Further, as described in Example 1, Example 2, and Example 3, in particular, as shown in Equation (89), the mapping unit 306B in FIGS. 3 and 4 may output u × s2 (t). , The power change part may be omitted. In this case, the method of regularly changing the phase of the precoded modulated signal is applied to the mapped signal s1 (t) and the mapped signal u × s2 (t). ..

Then, as described in Example 1, Example 2, and Example 3, in particular, as shown in Equation (90), the mapping unit 306A in FIGS. 3 and 4 may output u × s1 (t). , The power change part may be omitted. In this case, the method of regularly changing the phase of the precoded modulated signal is applied to the mapped signal u × s1 (t) and the mapped signal s2 (t). ..

Further, in the cases of Example 4, Example 5, and Example 6, in particular, as shown in the equation (91), the mapping unit 306A in FIGS. 3 and 4 has v × s1 (t), and the mapping unit 306B has u × s2. In some cases, (t) may be output, and the power change unit may be omitted in either case. In this case, the method of regularly changing the phase of the precoded modulated signal for the mapped signal v × s1 (t) and the mapped signal u × s2 (t) shall be applied. become.

Then, in the cases of Example 4, Example 5, and Example 6, in particular, as shown in the equation (92), the mapping unit 306A in FIGS. 3 and 4 has u × s1 (t), and the mapping unit 306B has v × s2. In some cases, (t) may be output, and the power change unit may be omitted in either case. In this case, the method of regularly changing the phase of the precoded modulated signal for the mapped signal u × s1 (t) and the mapped signal v × s2 (t) shall be applied. become.

Note that F shown in equations (89) to (92) is a precoding matrix used for time t, and y (t) has a phase change value. The receiving device will perform demodulation (detection) using the relationship between r1 (t), r2 (t) and s1 (t), s2 (t) shown above (Embodiment 1 and the like). It can be done in the same way as explained in). However, in the equation shown above, distortion components such as noise component, frequency offset, and channel estimation error are not represented in the equation, and demodulation (detection) is performed in a form that includes these. .. Regarding the values of u and v used by the transmitter to change the power, the transmitter transmits information about these or uses the transmission mode (transmission method, modulation method, error correction method, etc.). ) Is transmitted, and the receiving device can know the values of u and v used by the transmitting device by obtaining the information, thereby deriving the relational expression shown above and demodulating (detecting). Will be done.

In the present embodiment, a case where the phase change value is switched for the modulated signal after precoding in the time axis direction has been described as an example, but as in the description of the other embodiments, a multi-carrier such as the OFDM method has been described. When transmission is used, the same can be performed for the case of switching the phase change value for the modulated signal after precoding in the frequency axis direction. At this time, t used in this embodiment is replaced with f (frequency ((sub) carrier)).

Therefore, when switching the phase change value for the modulated signal after precoding in the time axis direction, z1 (t) and z2 (t) at the same time are from different antennas at z1 (t) and z2 (t). , Will be transmitted using the same frequency. Then, when switching the phase change value for the modulated signal after precoding in the frequency axis direction, z1 (f) and z2 (f) of the same frequency (same subcarrier) at z1 (f) and z2 (f). Will be transmitted from different antennas using the same time.

Further, the case where the phase changing method is switched for the modulated signal after precoding in the time-frequency axis direction can also be carried out in the same manner as described in the other embodiments. The method of switching the phase changing method with respect to the modulated signal after precoding in the present embodiment is limited to the method of switching the phase changing method with respect to the modulated signal after precoding described in the present specification. is not it.

Also, regular phase changes and precoding are applied to the two-stream baseband signals s1 (i) and s2 (i) (where i represents the order (time or frequency (carrier))). In the baseband signals z1 (i) and z2 (i) after both signals processed, the baseband signals z1 (i) after both signals are generated. In-phase I component I₁(i) Q for orthogonal components₁Let (i) be the common mode I component of the baseband signal z2 (i) after processing both signals.₂(i) Q for orthogonal components₂Let it be (i). At this time, the baseband components are replaced, and the in-phase component of the baseband signal r1 (i) after replacement is changed to I.₁(i) Q for orthogonal components₂(i), I the in-phase component of the baseband signal r2 (i) after replacement₂(i) Q for orthogonal components₁As (i), the modulated signal corresponding to the replaced baseband signal r1 (i) is transmitted from the transmitting antenna 1, and the modulated signal corresponding to the replaced baseband signal r2 (i) is transmitted from the transmitting antenna 2 at the same time. The modulated signal corresponding to the replaced baseband signal r1 (i) and the replaced baseband signal r2 (i) are transmitted from different antennas at the same time using the same frequency, such as transmitting using the frequency. You may send it. In addition, . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i), I the orthogonal component₂(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₁(i) Q for orthogonal components₂(i) . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i), I the orthogonal component₁(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₁(i) Q for orthogonal components₂(i) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i), I the orthogonal component₂(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i), I the orthogonal component₁(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i) Q for orthogonal components₂(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₁(i), I the orthogonal component₂(i) . Q for the in-phase component of the baseband signal r1 (i) after replacement₂(i), I the orthogonal component₁(i), I the in-phase component of the baseband signal r2 (i) after replacement₂(i) Q for orthogonal components₁(i) . Q for the in-phase component of the baseband signal r1 (i) after replacement₂(i), I the orthogonal component₁(i) Q for the in-phase component of the baseband signal r2 (i) after replacement₁(i), I the orthogonal component₂(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i), I the orthogonal component₂(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₁(i) Q for orthogonal components₂(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₂(i), I the orthogonal component₁(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₁(i) Q for orthogonal components₂(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i), I the orthogonal component₂(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₂(i), I the orthogonal component₁(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i) Q for orthogonal components₂(i), I the in-phase component of the baseband signal r1 (i) after replacement₂(i) Q for orthogonal components₁(i) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i) Q for orthogonal components₂(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₁(i), I the orthogonal component₂(i) . Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i), I the orthogonal component₁(i), I the in-phase component of the baseband signal r1 (i) after replacement₂(i) Q for orthogonal components₁(i) . Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i), I the orthogonal component₁(i) Q, the in-phase component of the baseband signal r1 (i) after replacement₁(i), I the orthogonal component₂It may be (i). Further, in the above, both signals are processed for the signals of two streams, and the replacement of the in-phase component and the orthogonal component of the signals after the signal processing of both is described, but the present invention is not limited to this and is more than two streams. It is also possible to perform both signal processing on the signal and replace the in-phase component and the orthogonal component of the signal after both signal processing.

In addition, the following signals may be exchanged. For example: . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i) Q for orthogonal components₂(i), I the in-phase component of the baseband signal r2 (i) after replacement₁(i) Q for orthogonal components₁(i) Note that this replacement can be realized by the configuration shown in FIG. 55.

Further, in the above example, the replacement of the baseband signals at the same time (same frequency ((sub) carrier)) is described, but the replacement of the baseband signals at the same time does not have to be performed. As an example, it can be described as follows: . The in-phase component of the baseband signal r1 (i) after replacement is described as I.₁(i + v), Q for orthogonal component₂(i + w), I the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i + v), I the orthogonal component₂(i + w), Q the in-phase component of the baseband signal r2 (i) after replacement₁(i + v), Q for orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r2 (i) after replacement₁(i + v), Q for orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i + v), I the orthogonal component₂(i + w), Q the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r1 (i) after replacement.₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r1 (i) after replacement.₁(i + v), Q for orthogonal component₂(i + w), Q the in-phase component of the baseband signal r2 (i) after replacement₁(i + v), I the orthogonal component₂(i + w) . Q for the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), I the orthogonal component₁(i + v), I the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . Q for the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r2 (i) after replacement₁(i + v), I the orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i + v), I the orthogonal component₂(i + w), Q the in-phase component of the baseband signal r1 (i) after replacement₁(i + v), Q for orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r2 (i) after replacement.₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r1 (i) after replacement₁(i + v), Q for orthogonal component₂(i + w) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i + v), I the orthogonal component₂(i + w), Q the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r2 (i) after replacement.₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i + v), Q for orthogonal component₂(i + w), I the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . I set the in-phase component of the baseband signal r2 (i) after replacement.₁(i + v), Q for orthogonal component₂(i + w), Q the in-phase component of the baseband signal r1 (i) after replacement₁(i + v), I the orthogonal component₂(i + w) . Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), I the orthogonal component₁(i + v), I the in-phase component of the baseband signal r1 (i) after replacement₂(i + w), Q for orthogonal component₁(i + v) . Q for the in-phase component of the baseband signal r2 (i) after replacement₂(i + w), I the orthogonal component₁(i + v), Q the in-phase component of the baseband signal r1 (i) after replacement₁(i + v), I the orthogonal component₂(i + w) In addition, the following signals may be exchanged. For example: . Baseband signal r after replacement₁The in-phase component of (i) is I₂(i + w), Q for orthogonal component₂(i + w), baseband signal after replacement r₂The in-phase component of (i) is I₁(i + v), Q for orthogonal component₁(i + v) This can also be realized by the configuration shown in FIG. 55.

FIG. 55 is a diagram showing a baseband signal replacement unit 5502 for explaining the above description. As shown in FIG. 1, in the baseband signals z1 (i) 5501_1 and z2 (i) 5501_2 after both signal processing, the in-phase I component of the baseband signal z1 (i) 5501_1 after both signal processing is I.₁(i) Q for orthogonal components₁Let (i) be the common mode I component of the baseband signal z2 (i) 5501_2 after processing both signals.₂(i) Q for orthogonal components₂Let it be (i). Then, I set the in-phase component of the baseband signal r1 (i) 5503_1 after replacement._r1(i) Q for orthogonal components_r1(i), I the in-phase component of the baseband signal r2 (i) 5503_2 after replacement_r2(i) Q for orthogonal components_r2If (i), the in-phase component I of the baseband signal r1 (i) 5503_1 after replacement_r1(i), Orthogonal component Q_r1(i), Baseband signal after replacement r2 (i) In-phase component I of 5503_2_r2(i) Q for orthogonal components_r2(i) shall be represented by any of the above. In this example, the replacement of the baseband signal after processing both signals at the same time (same frequency ((sub) carrier)) has been described, but as described above, different times (different frequency ((sub) carrier)) have been described. )) The baseband signal may be exchanged after processing both signals.

Further, in the above-mentioned replacement, the replacement method may be regularly switched.

For example, at time 0, the in-phase component of the replaced baseband signal r1 (0) is I.₁(0), Q for orthogonal component₁(0), I the in-phase component of the baseband signal r2 (0) after replacement₂(0), Q for orthogonal component₂(0) At time 1, the in-phase component of the baseband signal r1 (1) after replacement is changed to I.₂(1), Q for orthogonal components₂(1), I the in-phase component of the baseband signal r2 (1) after replacement₁(1), Q for orthogonal components₁(1) ... may be set, that is, when the time is 2k (k is an integer), the in-phase component of the baseband signal r1 (2k) after replacement is I.₁(2k), Q for orthogonal component₁(2k), I the in-phase component of the baseband signal r2 (2k) after replacement₂(2k), Q for orthogonal component₂Let it be (2k), and when the time is 2k + 1 (k is an integer), the in-phase component of the baseband signal r1 (2k + 1) after replacement is I.₂(2k + 1), Q for orthogonal component₂(2k + 1), I the in-phase component of the baseband signal r2 (2k + 1) after replacement₁(2k + 1), Q for orthogonal component₁It may be (2k + 1).

Also, when the time is 2k (k is an integer), the in-phase component of the baseband signal r1 (2k) after replacement is I.₂(2k), Q for orthogonal component₂(2k), I the in-phase component of the baseband signal r2 (2k) after replacement₁(2k), Q for orthogonal component₁Let it be (2k), and when the time is 2k + 1 (k is an integer), the in-phase component of the baseband signal r1 (2k + 1) after replacement is I.₁(2k + 1), Q for orthogonal component₁(2k + 1), I the in-phase component of the baseband signal r2 (2k + 1) after replacement₂(2k + 1), Q for orthogonal component₂It may be (2k + 1).

Similarly, it may be switched in the frequency axis direction. That is, when the frequency ((sub) carrier) is 2k (k is an integer), the in-phase component of the baseband signal r1 (2k) after replacement is I.₁(2k), Q for orthogonal component₁(2k), I the in-phase component of the baseband signal r2 (2k) after replacement₂(2k), Q for orthogonal component₂Let it be (2k), and when the frequency ((sub) carrier) is 2k + 1 (k is an integer), the in-phase component of the baseband signal r1 (2k + 1) after replacement is I.₂(2k + 1), Q for orthogonal component₂(2k + 1), I the in-phase component of the baseband signal r2 (2k + 1) after replacement₁(2k + 1), Q for orthogonal component₁It may be (2k + 1).

Also, when the frequency ((sub) carrier) is 2k (k is an integer), the in-phase component of the baseband signal r1 (2k) after replacement is I.₂(2k), Q for orthogonal component₂(2k), I the in-phase component of the baseband signal r2 (2k) after replacement₁(2k), Q for orthogonal component₁Let it be (2k), and when the frequency ((sub) carrier) is 2k + 1 (k is an integer), the in-phase component of the baseband signal r1 (2k + 1) after replacement is I.₁(2k + 1), Q for orthogonal component₁(2k + 1), I the in-phase component of the baseband signal r2 (2k + 1) after replacement₂(2k + 1), Q for orthogonal component₂It may be (2k + 1).

(Regarding cyclic Q delay) The application of Cyclic Q Delay described in this specification is described. Non-Patent Document 10 describes an outline of Cyclic Q Delay. In the following, a specific example of how to generate s1 and s2 when Cyclic Q Delay is used will be described.

FIG. 102 shows an example of the arrangement of signal points in the common mode I-quadrature Q plane when the modulation scheme is 16QAM. When the input bits are b0, b1, b2, b3, b0 b1 b2 b3 is one of the values from 0000 to 1111. For example, when b0 b1 b2 b3 is represented by 0000, the signal point 10201 in FIG. 102 is selected. Then, the value of the in-phase component based on the signal point 10201 is used as the in-phase component of the baseband signal, and the value of the orthogonal component based on the signal point 10201 is used as the orthogonal component of the baseband signal. Similarly, when b0 b1 b2 b3 has other values, the in-phase component and the orthogonal component of the baseband signal are generated.

Figure 103 shows the modulated signals s1 (t) (t: time) (or s1 (f), f: frequency) and s2 (t) (t: time) from the (binary) data when the cyclic Q delay is applied. ) (Or, s2 (f), f: frequency) is shown as an example of the configuration of the signal generator for generating.

When the data 10301 and the control signal 10306 are input to the mapping unit 10302 and a modulation method based on the control signal 10306, for example, 16QAM is selected as the modulation method, the mapping unit 10302 performs mapping according to the rule of FIG. 102 and maps. The in-phase component 10303_A and the quadrature component 10303_B of the later baseband signal are output. The modulation method is not limited to 16QAM, and other modulation methods can be implemented in the same manner.

At this time, the data at time point 1 corresponding to b0, b1, b2, and b3 in FIG. 102 shall be represented by b01, b11, b21, and b31. The mapping unit 10302 outputs the in-phase component I1 and the orthogonal component Q1 of the baseband signal of the time point 1 based on the data of the time point 1 based on b01, b11, b21, and b31. Similarly, the mapping unit 10302 outputs the in-phase component I2 and the orthogonal component Q2, ... Of the base band signal at time point 2.

The storage and signal replacement unit 10304 receives the in-phase component 10303_A and the orthogonal component 10303_B of the baseband signal and the control signal 10306 as inputs, and stores the in-phase component 10303_A and the orthogonal component 10303_B of the baseband signal based on the control signal 10306, and rearranges the signals. Is performed, and the modulation signal s1 (t) (10305_A) and the modulation signal s2 (t) (10305_B) are output. The method of generating the modulated signals s1 (t) and s2 (t) will be described in detail below.

As described in the specification, the modulated signals s1 (t) and s2 (t) are precoded and phase-changed. At this time, as shown in the present specification, signal processing such as phase change, power change, and signal replacement may be performed at any stage. The modulated signals r1 (t) and r2 (t) obtained by precoding and phase changing the modulated signals s1 (t) and s2 (t) have the same frequency at the same (common) time. It is transmitted using the band.

In the above, although the time axis t has been described, when a multi-carrier transmission method such as OFDM is used, s1 (t) and s2 (t) are changed to s1 (f) and s2 (f) (f: (sub). ) Carrier). At this time, the modulated signals r1 (f) and r2 (f) obtained by applying the precoding method of regularly switching the precoding matrix to the modulated signals s1 (f) and s2 (f) are the same. It is transmitted at (common) time (naturally, r1 (f) and r2 (f) are signals in the same frequency band). Further, as shown in the present specification, s1 (t) and s2 (t) can be considered as s1 (t, f) and s2 (t, f).

Next, a method of generating the modulated signals s1 (t) and s2 (t) will be described. FIG. 104 is a first example of a method of generating s1 (t) and s2 (t) when a cyclic Q delay is used.

FIG. 104 (a) shows the in-phase component and the orthogonal component of the baseband signal obtained by the mapping unit 10302 of FIG. 103. As shown in FIG. 104 (a), and as described in the mapping section 10302 of FIG. 103, the in-phase component I1 and the orthogonal component Q1 of the baseband signal at time point 1 and the baseband signal at time point 2 In this order, the in-phase component I2 and the quadrature component Q2, the in-phase component I3 and the quadrature component Q3 of the baseband signal at time point 3, and so on, the mapping unit 10302 outputs the in-phase component and the quadrature component of the baseband signal.

FIG. 104 (b) shows an example of a set of in-phase components and orthogonal components of the baseband signal when the signals are exchanged in the storage and signal exchange unit 10304 of FIG. 103. In FIG. 104 (b), time point 1 and time point 2, time point 3 and time point 4, time point 5 and time point 6, that is, time point 2i + 1 and time point 2i + 2 (i is an integer greater than or equal to 0) are set in the set. For example, at time point 1 and time point 2, the orthogonal components of the baseband signal are exchanged.

Therefore, since the in-phase components of the baseband signal are not interchanged, the in-phase component of the baseband signal at time point 1 is I1, the in-phase component of the baseband signal at time point 2 is I2, and the in-phase component of the baseband signal at time point 3 is in-phase. The ingredients are I3, ...

Since the orthogonal components of the baseband signal are interchanged within the set, the orthogonal component of the baseband signal at time point 1 is Q2, and the orthogonal component of the baseband signal at time point 2 is Q1 and the base at time point 3. The orthogonal component of the band signal is Q4, the orthogonal component of the baseband signal at time point 4 is Q3, and so on.

FIG. 104 (c) shows an example of the configuration of the modulated signals s1 (t) and s2 (t) before precoding when applying the method of precoding and phase changing. For example, as shown in FIG. 104 (c), the baseband signals generated as shown in FIG. 104 (b) are alternately assigned to s1 (t) and s2 (t). Therefore, the first slot of s1 (t) is (I1, Q2), and the first slot of s2 (t) is (I2, Q1). The second slot of s1 (t) is (I3, Q4), the second slot of s2 (t) is (I4, Q3), and so on.

Although FIG. 104 describes the time axis direction as an example, the same can be performed even in the frequency axis direction (as described above). At this time, it is described as s1 (f) and s2 (f).

Then, precoding and phase change are performed on s1 (t) of the Nth slot and s2 (t) of the Nth slot, and the signals r1 (t) and r2 (after the precoding and phase change of the Nth slot) are performed. t) will be obtained. This point is as described herein.

FIG. 105 shows a configuration method different from that of FIG. 103 for obtaining s1 (t) and s2 (t) of the Nth slot of FIG. 104. The mapping unit 10502 takes the data 10501 and the control signal 10504 as inputs, performs mapping based on the modulation method based on the control signal 10504, for example, considering the replacement of FIG. 104, and the mapped signal (in-phase component of the baseband signal and (Orthogonal component) is generated, and the modulated signal s1 (t) (10503_A) and the modulated signal s2 (t) (10503_B) are generated from the mapped signal and output. The modulated signal s1 (t) (10503_A) is the same as the modulated signal 10305_A in FIG. 103, and the modulated signal s2 (t) (10503_B) is the same as the modulated signal 10305_B in FIG. 103. As shown in (c). Therefore, the first slot of the modulated signal s1 (t) (10503_A) is (I1, Q2), the first slot of the modulated signal s2 (t) (10503_B) is (I2, Q1), and the modulated signal s1 (t) ( The second slot of 10503_A) is (I3, Q4), the second slot of the modulation signal s2 (t) (10503_B) is (I4, Q3), and so on.

As a supplement, the first slot (I1, Q2) of the modulated signal s1 (t) (10503_A) and the first slot (I2, Q1) of the modulated signal s2 (t) (10503_B) in the mapping unit 10502 of FIG. The generation method of is described.

In FIG. 105, 10501 is data, but the data at time point 1 is b01, b11, b21, b31, and the data at time point 2 is b02, b12, b22, b32. The mapping unit 10502 of FIG. 105 generates I1, Q1, I2, and Q2 described above from b01, b11, b21, b31 and b02, b12, b22, and b32. Then, the mapping unit 10502 of FIG. 105 can generate the modulation signals s1 (t) and s2 (t) from I1, Q1, I2, and Q2.

FIG. 106 shows a configuration method different from that of FIGS. 103 and 105 for obtaining s1 (t) and s2 (t) of the Nth slot of FIG. 104. The mapping unit 10601_A takes the data 10501 and the control signal 10504 as inputs, performs mapping based on the modulation method based on the control signal 10504, for example, considering the replacement of FIG. 104, and performs the mapping, and the signal after mapping (in-phase component of the baseband signal and (Orthogonal component) is generated, and the modulated signal s1 (t) (10503_A) is generated from the mapped signal and output. The mapping unit 10601_B takes the data 10501 and the control signal 10504 as inputs, performs mapping based on the modulation method based on the control signal 10504, for example, considering the replacement of FIG. 104, and performs the mapping, and the signal after mapping (in-phase component of the baseband signal and (Orthogonal component) is generated, and the modulated signal s2 (t) (10503_B) is generated from the mapped signal and output.

The data 10501 that is the input of the mapping unit 10601_A and the data 10501 that is the input of the mapping unit 10601_B are, of course, the same data. Further, the modulation signal s1 (t) (10503_A) is the same as the modulation signal 10305_A in FIG. 103, and the modulation signal s2 (t) (10503_B) is the same as the modulation signal 10305_B in FIG. 103. As shown in (c).

Therefore, the first slot of the modulated signal s1 (t) (10503_A) is (I1, Q2), the first slot of the modulated signal s2 (t) (10503_B) is (I2, Q1), and the modulated signal s1 (t) ( The second slot of 10503_A) is (I3, Q4), the second slot of the modulation signal s2 (t) (10503_B) is (I4, Q3), and so on.

As a supplement, a method of generating the first slot (I1, Q2) of the modulated signal s1 (t) (10503_A) in the mapping unit 10601_A of FIG. 106 will be described. In FIG. 106, 10501 is data, but the data at time point 1 is b01, b11, b21, b31, and the data at time point 2 is b02, b12, b22, b32. The mapping unit 10601_A of FIG. 106 generates I1 and Q2 described above from b01, b11, b21, b31 and b02, b12, b22, and b32. Then, the mapping unit 10601_A in FIG. 106 can generate the modulation signal s1 (t) from I1 and Q2.

A method of generating the first slot (I2, Q1) of the modulated signal s2 (t) (10503_B) in the mapping unit 10601_B of FIG. 106 will be described. In FIG. 106, 10501 is data, but the data at time point 1 is b01, b11, b21, b31, and the data at time point 2 is b02, b12, b22, b32. The mapping unit 10601_B of FIG. 106 generates I2 and Q1 described above from b01, b11, b21, b31 and b02, b12, b22, and b32. Then, the mapping unit 10601_B in FIG. 106 can generate s2 (t) from I2 and Q1.

Next, FIG. 107 shows a second example different from FIG. 104 in the method of generating s1 (t) and s2 (t) when the cyclic Q delay is used. In FIG. 107, the same symbols as those in FIG. 104 (the in-phase component and the orthogonal component of the baseband signal) are attached.

FIG. 107 (a) shows the in-phase component and the orthogonal component of the baseband signal obtained by the mapping unit 10302 of FIG. 103. Since FIG. 107 (a) is the same as FIG. 104 (a), the description thereof will be omitted.

FIG. 107 (b) shows the configuration of the in-phase component and the orthogonal component of the baseband signals of s1 (t) and s2 (t) before the signal replacement, and in FIG. 107 (b), the time point 2i + 1 The baseband signal of is assigned to s1 (t), and the baseband signal of time point 2i + 2 is assigned to s2 (t) (i is an integer greater than or equal to 0).

FIG. 107 (c) shows an example of a set of in-phase components and orthogonal components of the baseband signal when the signals are exchanged in the storage and signal exchange unit 10304 of FIG. 103. The feature of FIG. 107 (c) (a difference from FIG. 104) is that the signal is exchanged in s1 (t) and the signal is exchanged in s2 (t).

Therefore, in FIG. 107 (c), Q1 and Q3 are exchanged in s1 (t), and Q5 and Q7 are exchanged with respect to FIG. 107 (b), and the same exchange is performed thereafter. Further, in FIG. 107 (c), Q2 and Q4 are exchanged in s2 (t) with respect to FIG. 107 (b), and Q6 and Q8 are exchanged, and the same exchange is performed thereafter.

Therefore, the in-phase component of the baseband signal in the first slot of s1 (t) is I1, the orthogonal component is Q3, the in-phase component of the baseband signal in the first slot of s2 (t) is I2, and the orthogonal component is Q4. .. The in-phase component of the baseband signal in the second slot of s1 (t) is I3 and the orthogonal component is Q1, the in-phase component of the baseband signal in the second slot of s2 (t) is I4, and the orthogonal component is Q2. .. The third and fourth slots are represented as shown in FIG. 107 (c), and the same applies to the subsequent slots.

Then, precoding and phase change are performed on s1 (t) of the Nth slot and s2 (t) of the Nth slot, and the signals r1 (t) and r2 (after the precoding and phase change of the Nth slot) are performed. t) will be obtained. This point is as described herein.

FIG. 108 shows a configuration method different from that of FIG. 103 for obtaining s1 (t) and s2 (t) of the Nth slot of FIG. 107. The mapping unit 10502 takes the data 10501 and the control signal 10504 as inputs, performs mapping based on the modulation method based on the control signal 10504, for example, considering the replacement of FIG. 107, and the mapped signal (in-phase component of the baseband signal and (Orthogonal component) is generated, and the modulated signal s1 (t) (10503_A) and the modulated signal s2 (t) (10503_B) are generated from the mapped signal and output. The modulated signal s1 (t) (10503_A) is the same as the modulated signal 10305_A in FIG. 103, and the modulated signal s2 (t) (10503_B) is the same as the modulated signal 10305_B in FIG. 103. As shown in (c). Therefore, the first slot of the modulated signal s1 (t) (10503_A) is (I1, Q3), the first slot of the modulated signal s2 (t) (10503_B) is (I2, Q4), and the modulated signal s1 (t) ( The second slot of 10503_A) is (I3, Q1), the second slot of the modulation signal s2 (t) (10503_B) is (I4, Q2), and so on.

As a supplement, in the mapping section 10502 of FIG. 108, the first slot of the modulated signal s1 (t) (10503_A) is (I1, Q3), and the first slot of the modulated signal s2 (t) (10503_B) is (I2, Q4), the second slot of the modulation signal s1 (t) (10503_A) is (I3, Q1), and the first slot of the modulation signal s2 (t) (10503_B) is (I4, Q2).

In FIG. 108, 10501 is data, but the data at time point 1 is b01, b11, b21, b31, the data at time point 2 is b02, b12, b22, b32, and the data at time point 3 is b03, b13, b23, b33, Let the data at time point 4 be b04, b14, b24, b34. The mapping section 10502 of FIG. 108 is from b01, b11, b21, b31 and b02, b12, b22, b32 and b03, b13, b23, b33 and b04, b14, b24, b34 to I1, Q1, I2 described above. , Q2, I3, Q3, I4, Q4. Then, the mapping unit 10502 of FIG. 108 can generate modulation signals s1 (t) and s2 (t) from I1, Q1, I2, Q2, I3, Q3, I4, and Q4.

FIG. 109 shows a configuration method different from that of FIGS. 103 and 108 for obtaining s1 (t) and s2 (t) of the Nth slot of FIG. 107. The distribution unit 10901 receives the data 10501 and the control signal 10504 as inputs, distributes the data based on the control signal 10504, and outputs the first data 10902_A and the second data 10902_B. The mapping unit 10601_A takes the first data 10902_A and the control signal 10504 as inputs, performs mapping based on the modulation method based on the control signal 10504, for example, considering the replacement of FIG. 107, and performs mapping in consideration of the replacement of FIG. The component and orthogonal component) are generated, and the modulation signal s1 (t) (10503_A) is generated from the mapped signal and output. The mapping unit 10601_B takes the second data 10902_B and the control signal 10504 as inputs, performs mapping based on the modulation method based on the control signal 10504, for example, considering the replacement of FIG. 107, and performs the mapping, and the signal after mapping (the same phase of the baseband signal). The component and orthogonal component) are generated, and the modulation signal s2 (t) (10503_B) is generated from the mapped signal and output.

The first slot of the modulated signal s1 (t) (10503_A) is (I1, Q3), the first slot of the modulated signal s2 (t) (10503_B) is (I2, Q4), and the modulated signal s1 (t) (10503_A). The second slot of is (I3, Q1), the second slot of the modulation signal s2 (t) (10503_B) is (I4, Q2), and so on.

As a supplement, a method of generating the first slot (I1, Q3) and the second slot (I3, Q1) of the modulated signal s1 (t) (10503_A) in the mapping unit 10601_A of FIG. 109 will be described. In FIG. 109, 10501 is data, but the data at time point 1 is b01, b11, b21, b31, the data at time point 2 is b02, b12, b22, b32, and the data at time point 3 is b03, b13, b23, b33, Let the data at time point 4 be b04, b14, b24, b34. The distribution unit 10901 outputs the data at time point 1 as b01, b11, b21, b31 and the data at time point 3 as the first data 10902_A, and the data at time point 2 as b02, b12, b22, The data of b32 and time point 4 are output as the second data 802_B of b04, b14, b24, and b34. The mapping unit 10601_A in FIG. 109 generates (I1, Q3) and the second slot (I3, Q1) from b01, b11, b21, b31 and b03, b13, b23, and b33. The same operation is performed for the third and subsequent slots.

A method of generating the first slot (I2, Q4) and the second slot (I4, Q2) of the modulated signal s2 (t) (10503_B) in the mapping unit 10601_B of FIG. 109 will be described. In the mapping section 10601_B of FIG. 109, the data at time point 2 is from b02, b12, b22, b32 and the data at time point 4 are from b04, b14, b24, b34, the first slot is (I2, Q4), and the second slot (I4). , Q2) will be generated. The same operation is performed for the third and subsequent slots.

The two cyclic Q delay methods have been described above. However, as shown in FIG. 104, when signals are exchanged in the slots, the number of candidate signal points can be suppressed in the demodulation (detection) section of the receiving device. Therefore, there is an advantage that the calculation scale (circuit scale) can be reduced. On the other hand, as shown in FIG. 107, when the signals are exchanged in the signal of s1 (t) and the signal of s2 (t), the number of candidate signal points increases in the demodulation (detection) section of the receiving device. , Time diversity gain (frequency diversity gain when interchanged on the frequency axis) can be obtained, and there is an advantage that the reception quality of data may be further improved.

In the above explanation, the example is when the modulation method is 16QAM, but the description is not limited to this, and the modulation methods such as QPSK, 8QAM, 32QAM, 64QAM, 128QAM, and 256QAM are also used. It can be carried out in the same way.

Further, the cyclic Q delay method is not limited to the above two methods. For example, in both of the above two examples, the orthogonal components of the baseband signal are exchanged, but the in-phase components may be exchanged. Also, the swapping is performed at two time points (for example, the orthogonal components of the baseband signal are swapped at time points 1 and 2), but at multiple time points, the in-phase components of the baseband signal or ("and" The signals of the orthogonal components may be exchanged. Therefore, when the in-phase component and the orthogonal component of the baseband signal are generated and the cyclic Q delay is performed as shown in FIG. 104 (a), "the in-phase component of the baseband signal after the cyclic Q delay at time point i is Ii. , The orthogonal component of the baseband signal after the cyclic Q delay at time point i has a symbol representing Qj (i j) ", or" the in-phase component of the baseband signal after the cyclic Q delay at time point i Is Ij, and the orthogonal component of the baseband signal after the cyclic Q delay at time point i has a symbol that represents Qi (i j). "Or" The baseband signal after the cyclic Q delay at time point i. There is a symbol that expresses the in-phase component as Ij and the orthogonal component of the baseband signal after the cyclic Q delay at time point i as Qk (i j, i k, j k). "

Then, the modulated signal s1 (t) (or s1 (f) or s1 (t, f)) obtained by applying the cyclic Q delay described above, and the modulated signal s2 (t) (or Precoding and phase change will be applied to s2 (f) or s2 (t, f)). (However, as shown in the present specification, signal processing such as phase change, power change, and signal replacement may be performed at any stage.) At this time, it is obtained by applying cyclic Q delay. As a method of applying the precoding and the phase change to be applied to the modulated signal, it is possible to apply all the methods of applying the precoding and the phase change described in the present specification.

The present invention can be widely applied to a wireless system that transmits different modulated signals from a plurality of antennas, and is suitable for application to, for example, an OFDM-MIMO communication system. It also applies to the case of performing MIMO transmission in a wired communication system having multiple transmission points (for example, PLC (Power Line Communication) system, optical communication system, DSL (Digital Subscriber Line) system). At this time, a plurality of modulated signals as described in the present invention will be transmitted by using the plurality of transmission points. Further, the modulated signal may be transmitted from a plurality of transmission points.

302A, 302B Encoder

304A, 304B Interleaver

306A, 306B Mapping part

314 Signal processing method Information generation unit

308A, 308B Weighting synthesizer

310A, 310B Wireless section

312A, 312B antenna

317A, 317B Phase change section

402 Encoder

404 Distribution department

504 # 1,504 # 2 Transmitting antenna

505 # 1,505 # 2 Receiving antenna

600 Weighting synthesizer

701_X, 701_Y Antenna

703_X, 703_Y Wireless section

705_1 Channel fluctuation estimation unit

705_2 Channel fluctuation estimation unit

707_1 Channel fluctuation estimation unit

707_2 Channel fluctuation estimation unit

709 Control information decoder

711 Signal processing unit

803 INNER MIMO detector

805A, 805B Log likelihood calculation unit

807A, 807B Deinterriver

809A, 809B Log likelihood ratio calculation unit

811A, 811B Soft-in / soft-out decoder

813A, 813B Interleaver

815 Memory

819 Coefficient generator

901 Soft-in / soft-out decoder

903 Distribution department

1201A, 1201B OFDM method related processing unit

1302A, 1302A Serial-parallel converter

1304A, 1304B Sorting part

1306A, 1306B Inverse fast Fourier transform part

1308A, 1308B Wireless section