Method and device for determination of roll angle of rotating launched body

The present invention relates to a method for determination of the roll angle φ of a rotating body such as a shell, utilizing sensors for detection of rotation signals in a body-fixed coordinate system, in which the body-fixed rotation signals emitted by the sensors are filtered. The invention also relates to a device for determination of the roll angle φ of a rotating body, such as a shell, comprising in the rotating body body-fixed sensors for detection of rotation signals in a body-fixed coordinate system, and a filter device for filtration of interference in the detected rotation signals.

A shell that moves in a ballistic path, see Figure 2, will rotate the speed vector around an axis that lies in a horizontal plane. The rotation of the speed vector will take place around a plane-fixed y-axis y_PF. The plane-fixed coordinate system is defined in such a way that its origin follows the centre of gravity of the shell. The plane-fixed x-axis points forward in the shell along the axis of symmetry. The plane-fixed y-axis points to the right, viewed from the back, and lies in a plane that has the g-vector (g = gravitation) as a perpendicular. Finally, the plane-fixed z-axis points in such a way that the coordinate system has a right-hand rotation.

When rotation sensors are mounted in the shell, it is convenient to define a body-fixed coordinate system by the designation BF (Body Fixed), see Figure 1. When the shell rotates around the axis of symmetry, an angle arises between the y-axis and z-axis of the plane-fixed coordinate system and the respective y-axis and z-axis of the body-fixed coordinate system. This angle is designated ״φ״ in Figure 1 and is called m the following the roll angle.

If three rotation-measuring sensors are mounted in the 5 shell in such a way that they measure the rotation around respective body-fixed coordinate axes directly or via a linear combination, the inertial rotation vector can be expressed in the rotational directions ω_χΒΕ, m_yBFr ω,ΒΕ of the body-fixed coordinate system.

The rotation around the plane-fixed y-axis can then be expressed as measurement signals from the body-fixed rotation sensor signals and the roll angle can thereafter be calculated.

^_Bf=^f־^cosW ^_BF ־^sinW ®yBF ,

However, the shell is acted upon not only by the g vector but also by the atmosphere and, in particular, by wind turbulence in the atmosphere. This gives rise to moment interferences around the coordinate axes y־r and z־r. This, in turn, gives rise to rotations in and 0>_־bf. These rotations can be greater by the power of than the rotation ffl_yPP caused by the effect of the g vector on the path. In practice, therefore, the simple formula above can not be used to calculate the roll angle directly. In order to handle the body-fixed rotation sensor signals, the signals. are therefore filtered It has, however, proved difficult to filtei effectively measurement signals that are non-linear. For example, linear filters of the Kalman type have proved to be difficult to use.

³⁵ . 4.

The object of the present invention is to achieve method and a device for the determination of roll angle that eliminates the rotation signal interferences | caused by moment interferences that arise around the body's body-fixed coordinate axes co_yBF and m_zBF in a more effective and a simpler way. The object of the 5 invention is achieved by a method characterized in that a useful measurement signal in the sensors' rotation signals is mixed down to zero in frequency and in that the rotation signals are thereafter low-pass filtered, and a device characterized in that the filter device ,.10 ך comprises a mixer for mixing down a useful measurement signal in the sensors' rotation signals to zero in frequency and a low-pass filter for thereafter low-pass filtering the down-mixed rotation signals with useful

O measurement signal. By means of the invention, a method and a device for the determination of roll angle are achieved that estimate the roll angle in an effective way utilizing a smart non-linear filtration in a manageable low frequency range.

The filter device advantageously comprises a phaselocking filter. In addition to a low-pass filter, the , phase-locking filter can comprise sine- and cosine operators, multiplier and amplification regulator.

O 25 According to another advantageous embodiment, the filter device comprises a Δφ-eliminator. By this means, a constant error Δφ in the roll angle can be ׳ ) eliminated.

In a suitable embodiment, the Δφ-eliminator calculates _y .= LP_cos(Δφ)*sin(φ+Δφ) - LP_sin(Δφ) *cos(φ+Δφ) _x = LP_sin(Δφ)*sin(φ+Δφ) + LP_cos(Δφ)*cos(φ+Δφ) and 35 atan (y/x) in order to obtain φ + W1, where φ is the roll angle, Δφ is a constant error in the roll angle, LP_ indicates that the next sine or cosine function is low-pass filtered and W! indicates the noise level of the output signal.

The invention will be described below in greater detail with reference to the attached drawings, in which:

Figure 1 shows definitions of coordinate axes and rotations.

Figure 2 shows an example of a ballistic shell path.

Figure 3 shows the frequency content of the measurement signals OyBF, ®zbf in an initial position.

Figure 4 shows the frequency content of the measurement signals m_yBF, ω_ζΒΓ after down-mixing to zero in frequency.

Figure 5 shows a filter device comprised in the device according to the invention.

Figure 6 shows an example of a Δφ-eliminator that can be comprised in the filter device according to Figure

5.

Figure 7 shows a phase-locking filter comprised in the filter device according to Figure 5.

Figures 1 and 2 have already been discussed in the introduction to the description and there are therefore only some supplementary details to be discussed here. The shell shown in Figures 1 and 2 has been given the reference numeral 1 and follows a ballistic path 2.

The function of the filter device is illustrated in d0, . , . _י ,

Figures 3 and 4. The useful signal is originally at the frequency co_xBf and is surrounded by interferences 3, 4 on each side of this frequency, see Figure 3.

After down-mixing, the useful signal is at the frequency zero and the interferences now designated 5 are now superimposed at somewhat higher frequencies than zero. The interferences 5 have now been brought to 5 such a level as far as frequency is concerned that they can be filtered out by means of a low-pass filter.

The down-mixing of the useful signal can be described by the following two equations that are input signals 10 to the lower and upper low-pass filter respectively, see Figure 7.

LP_in = . cosU) . 003(¢ + Δ<0+ — sin W . 3111(¢ + Δ^) = cos(A0) lower / ^x_LP 003(¢) . sin^ + Δ^- 3111(¢) . 003(¢ + Δφ) = -^-- 8111^¢) ¹'*in _upper ^vr' ^v Qt ^UL

The roll angle is designated ¢ and Δ¢ is the constant error in the roll angle.

By dividing these two signals above and thereafter applying the inverse tangent function, the phase position error Δφ is obtained. This error is amplified by a factor K and the result is a compensation term for o_xBF that means that the filter homes in on zero in phase error irrespective of whether the error is positive or negative at the start of the .filtering process. When there is a constant measurement error in the aw-signal, it results in a constant phase error directly out from the phase-locking part of the filter.

This constant phase error can be eliminated in a subsequent mathematical processing of the output signal by means of a Δφ-eliminator.

For a description of the function of the filter device with reference to Figures 5-7, block diagrams are used.

Βθ

It can thus be noted that is negatively related to (✓.׳ the ro_yBF־axis ®_־BF-axis, which means that the measurement signal for to,»r is to be given a minus sign and that the sign is positive for ω_ζΒΓ.

The filter device 6 according to Figure 5 comprises a phase-locking filter 7 and a Δφ-eliminator 8. At the input of the filter device, there are three measurement signals emitted by sensors (not shown) that measure the 10 rotation around the three body-fixed coordinate axes co_xBF, co_yBF, (Ozbf. The filter device has also two output signals, of which the upper signal (φ+W!) does not have any constant error term, but on the other hand the noise level W! is higher than for the lower output 15 signal. The lower output signal contains a constant error Δφ. This error arises when the sensor for ©_xBF has a constant error. The noise W₂ of the lower output signal is, however, lower than the upper output signal. Which output signal is selected is dependent upon which 20 requirements with regard to noise and constant error are made for the estimated roll angle.

Figure 6 shows the construction of the Δφ-eliminator 8.

In the Δφ-eliminator there is a calculation unit that 25 calculates:

_y= LP_cos(Δφ)*sin (φ+Δφ) - LP_sin(Δφ)*cos(φ+Δφ) _x= _LP_sin(Δφ)*sin (φ+Δφ) + LP_cos(Δφ)*cos(φ+Δφ) and ³⁰ 1 atan (y/x) in order to obtain φ+ W!,

The calculation unit can consist of a microprocessor that carries out mathematical operations shown in the 35 blocks 9, 10 and 11. The input signals to the Δφeliminator are obtained from the phase-locking filter 7 shown in Figure 7, where (1), (2), (3) and (4) show where the signals are available.

- ר The phase-locking filter 7 in Figure 7 comprises the following blocks, namely a sign-changing block 12, two low-pass filters 13,14, sine- and cosine operators 1518, multipliers 19-22, adders 23-25, inverse tangent function 26, amplifier 27 with amplification factor K and an integrating block 28.

The low-pass filters 13 and 14 that are shown in Figure ך are adapted for the application in question. If rapid homing-in by the filter device is required, the low-pass filters 13 and 14 are set as high as possible in frequency, but with the requirement that the total phase-locking filter is stable. If, on the other hand, small errors and low noise are required, the low-pass filters 13 and 14 are designed with narrow bandwidth and of high order, but with the requirement that the phase-locking filter is to be stable. The amplification of the phase-locking filter (speed) can be set by varying the amplification factor K. Normally, the amplification factor K should be adjusted when the lowpass filters 13 and 14 are adapted to the application in question.