Decade band tapered slot antenna and methods of making and configuring same

DECADE BAND TAPERED SLOT ANTENNA, AND METHODS OF MAKING AND CONFIGURING SAME

DECADE BAND TAPERED SLOT ANTENNA, AND METHODS OF MAKING AND CONFIGURING SAME

TECHNICAL FIELD OF THE INVENTION

This invention relates in general to tapered slot antennas and, more particularly, to a method and apparatus for obtaining wide band performance in a tapered slot antenna.

BACKGROUND OF THE INVENTION

EP 0343322 discloses an improved conformal antenna array assembly having a strip conductor and a ground plane separated from and lying parallel to the strip conductor. The disclosed ground plane has a slot extending transverse to the strip conductor and a conductive planar element which is positioned across the slot and orthogonal tp the ground plane. The conductive planar element has curved surfaces extending upwardly and outwardly from the slot. The strip conductor and the ®Jot-containing ground plane are separated by a dielectric material.

US 6,008,770 discloses a tapered slot plane antenna apparatus for a millimeter wave radio communication system which provides a tapered pattern composed by utilizing a Fermi-Diac distribution function so as to consider an impedance matching and a directivity of the antenna apparatus. Supporting layers and protection layers may be utilized to provide sufficient strength for implementation in a compact millimeter wave radio communication system.

la

Chio, et al., Large Wideband Dual-Polarized Array of Vivaldi Antennas with Radome, 1999 Asia Pacific Microwave Conference (Singapore), IEEE, Piscataway, New Jersey, Nov. 30, 1999, pp. 92-95, discloses a wideband , widescan, dual polarized Vivaldi antenna element shown to provide about 4.5:1 bandwidth for a scan volume of 45° and VSWR of less than 2.

During recent decades, antenna technology has experienced an increase in the use of antennas that utilize an array of antenna elements, one example of which is a phased array antenna. Antennas of this type have many applications in commercial and defense markets, such as communications and radar systems. In many of these applications, broadband performance is desirable. Some of these antennas are designed so that they can be switched between two or more discrete frequency bands. Thus, at any given time, the antenna is operating in only one of these multiple bands. However, in order to achieve true broadband operation, the antenna needs to be capable of satisfactory operation in a single wide frequency band, without the need to switch between two or more discrete frequency bands.

One type of antenna element that has been found to work well in an array antenna is often referred to as a tapered slot antenna element. The spacing between antenna elements in an array antenna is typically determined by the frequency at which the antenna operates, and a tapered slot antenna element fits comfortably within the space available for an antenna element in many array antennas.

Existing tapered slot antenna elements typically have a bandwidth of about 3:1 to 4:1, although some have a bandwidth that approaches 6:1. While these existing tapered slot antenna elements have been generally adequate for their intended purposes, they have not been satisfactory in all respects. In this regard, there are applications in which it is desirable for a tapered slot antenna element to provide broadband performance involving a bandwidth in the neighborhood of 10:1, or even larger. Existing designs and design techniques have not been able to provide a tapered slot antenna element which approaches this desired level of broadband performance.

SUMMARY OF THE INVENTION

The present invention relates to an antenna element having a dielectric layer, an electrically, conductive layer, and an elongate conductive element, wherein:

the dielectric layer has a hole therethrough;

the electrically conductive layer is disposed adjacent one surface of said dielectric layer, said conductive layer having a recess etched therein which includes a balun portion and a tapered slot portion, said slot portion having a narrow end communicating with said balun portion, and said balun portion being aligned with said hole through said dielectric layer; and

2a the elongate conductive element being directly connected to and in the same plane as said conductive layer, said conductive layer extending generally transversely with respect to said slot portion in the region of said narrow end thereof , wherein said hole through said dielectric layer has substantially the same size and shape as said balun portion of said recess in said conductive layer, the element including a further conductive layer which has therein a further recess, . said further recess including a further balun portion and including a further slot portion which communicates at one end with said further balun portion, said slot portions of said recesses being of similar size and shape and being substantially aligned with each other, and said further balun portion having substantially the same size and shape as, and being aligned with, said hole through said dielectric layer.

The present invention further relates to a method, comprising the steps of:

creating a hole through a dielectric layer;

fabricating an electrically conductive layer adjacent one surface of said dielectric layer, said conductive layer haying a recess etched therein which includes a balun portion and a slot tapered portion, said slot portion having a narrow end communicating with said balun portion, and said balun portion being aligned with said hole through said dielectric layer; and forming an elongate conductive element in direct contact with and in the same plane as said conductive layer said elongate conductive element extending generally transversely with respect to said slot

2b portion in the region of said narrow end wherein said creating step is carried out so that . said hole through said dielectric layer has substantially the same size and shape as said balun portion of said recess in said conductive layer, the method including the step of fabricating a further conductive layer which has therein a further recess, said further recess including a further balun portion and including a further slot portion which communicates at one end with said further balun portion, said slot portions of said recesses being of similar size and shape and being substantially aligned with each other, and said further balun portion having substantially the same size and shape as, and being aligned with, said hole through said dielectric layer.

From the foregoing, it may be appreciated that a need has arisen for a method and apparatus that contribute, in a tapered slot antenna element, to broadband performance exhibiting a substantially greater bandwidth than is available in pre-existing tapered slot antenna elements.

One form of the present invention involves: a dielectric layer having a hole therethrough; an electrically conductive layer disposed adjacent one side of the dielectric layer, the conductive layer having a recess therein which includes a balun portion and a slot portion, the slot portion communicating at one end with the balun portion, and the balun portion being aligned with the hole through the dielectric layer; and an elongate conductive element which extends generally

WO 03/021715 transversely with respect to the slot portion in the region of the one end thereof.

A different form of the present invention involves: a conductive section having a recess which includes a 5 balun portion, and a slot portion, the slot portion communicating at one end with the balun portion, the balun portion having a shape which facilitates a large and abrupt discontinuity in impedance between the slot portion and the balun portion, the shape of the balun 10 portion being such that the balun portion_has an approximately straight side, and the slot portion having one end which communicates with the balun portion at a location between the ends of the straight side of the balun portion; and an elongate conductive element which 15 extends generally transversely' with respect to the slot portion in the region of the one end thereof, and which - has an end which is directly electrically coupled to the conductive section in the region of the one end of the slot portion.

20. Yet another form of the present invention involves:

first and second dielectric layers which extend approximately parallel to each other; first, second and third conductive layers which extend approximately parallel to each other and to the dielectric layers, the 25 first dielectric layer being located between the first and second conductive layers, and the second dielectric layer being located between the second and third dielectric layers, the conductive layers each having therein, a recess' which includes a. balun portion and a 30 slot portion communicating at one end with the balun portion, the slot portions in each', of the. conductive layers being of similar size and shape and being

WO 03/021715 substantially aligned with each other, and the balun portions in each of the conductive layers being of similar size and shape and being aligned with each other; a plurality of conductive vias which extend . through openings in the dielectric layers to electrically couple the conductive layers to each other; and an elongate conductive element which extends generally transversely with respect to the slot portion in the region of the one end thereof.

Still another form of the present invention involves: a conductive section having a recess which includes a balun portion and a slot portion., the slot portion communicating at one end with the balun portion, and the slot portion having edges on opposite sides thereof which each follow a predetermined curve other than a first-order exponential curve; and an elongate conductive element which extends generally transversely with respect to the slot portion in the region of the one end thereof, and which can carry an electrical signal.

A different form of the present invention involves modeling operational characteristics of an apparatus which includes a conductive section having a recess with

1 ,־.«־־ a slot portion, including: modeling the slot portion as a plurality of segments of electrically conductive material 25 which collectively, have a shape' that approximates a shape of the slot portion; and evaluating a characteristic of the slot portion by separately evaluating.the characteristic for each of the segments and then combining the evaluations for the segments.

Another form of the ־־present invention involves:, a conductive section having a recess which includes a balun portion and a slot portion, the slot portion

WO 03/021715 PCT/US02/28108 communicating at one end with the balun portion, and having a width which is narrowest in a first section of the slot portion located near the one end thereof, the slot portion having second and third sections which are disposed on Opposite sides of the first section and which each have a width larger than the width of the first section; and an elongate conductive element which extends generally transversely with respect to the slot portion in the region of the one' end thereof.

Yet another form of the present invention involves:

an electrically conductive layer having a recess therein which includes a balun portion and a slot portion, the slot portion communicating at one end with the balun portion; a dielectric layer disposed adjacent one side of the conductive layer, the dielectric layer having an opening therethrough in the region of a further end of the slot portion remote from the one end thereof; and an elongate conductive element which extends generally transversely with respect to the slot 'portion in the region of the one end thereof.

Still another form of the present invention involves: an electrically conductive plate having a balun hole and a slot, extending transversely therethrough, the slot opening at one end into the balun hole; and an 25 elongate conductive element which extends generally transversely with respect to the. slot in the region .of the one end Of the slot. .

A different form of the present invention involves: .־ a conductivesection having a recess which includes a balun portion and a slot portion, the slot portion communicating at one end with the balun portion, and having a further end remote from the one end thereof; an

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elongate conductive element which extends generally transversely with respect to the slot portion in the region of the one end thereof; and a refracting layer extending approximately perpendicular to a centerline of the slot portion at a location beyond the further end of the slot portion, the refracting layer being made of a material which is transmissive to and effects refraction of electromagnetic signals in a selected frequency range that travel in one of two opposite directions along the slot.

BRIEF DESCRIPTION OF THE DRAWINGS .

A better understanding of the present invention will be realized from the detailed description which follows, 15 taken in conjunction with the accompanying drawings, in which:

FIGURE 1 is a diagrammatic fragmentary front view of an apparatus embodying. aspects of the present invention, including an antenna element and part of a radome;

20. . FIGURE 2 is a diagrammatic fragmentary rear view .of the apparatus 10;

FIGURE 3 is a diagrammatic sectional view taken along the-section line 3-3 in FIGURE 1;

FIGURE 4 is a diagrammatic fragmentary sectional .25 front view of ^r the' apparatus of FIGURE 1, taken along a center plane thereof;

FIGURE .5 is a graph showing the shape of one edge of a slot portion which is part of the antenna element of FIGURE 1;

FIGURE 6 is׳ a diagrammatic fragmentary perspective view showing a portion of the rear side of the antenna element 12 in an enlarged scale;

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FIGURE 7 is a diagrammatic fragmentary perspective view showing in an enlarged scale an outer end portion of the apparatus of FIGURE 1;

FIGURE 8 is a highly diagrammatic view of the apparatus of FIGURE 1, showing a refraction characteristic effected by certain dielectric layers in the radome thereof; .

FIGURE 9 is a graph showing' return loss in E-plane scan as a function of frequency for the apparatus of

FIGURE 1;

FIGURE 10 is a graph showing return loss in H-plane scan as a function of frequency for the apparatus of . FIGURE 1;

FIGURE 11 is a block diagram showing functional sections of the apparatus of FIGURE 1;

FIGURE 12. is a diagrammatic view of a segmented transmission line which serves as a model for analyzing, a slotline present in the apparatus of FIGURE 1;

FIGURE 13 is a diagrammatic view, in an enlarged scale, of the end portions of. four of the transmission line segments of FIGURE 12, and also shows in- broken lines how the number of segments can be tripled through interpolation;

FIGURE 14' is a diagrammatic view of. one of the transmission line segments of FIGURE 12, represented in theoretical form;

FIGURE 15 is a flowchart which summarizes an optimization technique used in designing the apparatus of' FIGURE 1;.

FIGURE 16 is a diagrammatic front view of an antenna element which is an alternative embodiment of the.antenna element of FIGURE 1;.

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־ 8 '

FIGURE 17 is a diagrammatic perspective view of an antenna element which is still - another alternative embodiment of the antenna element of FIGURE 1;

FIGURE 18 is a diagrammatic sectional view taken 5 along the section line 18-18 in FIGURE 17; and

FIGURE 19 is a diagrammatic fragmentary sectional top . view of. a coaxial striplirie which is a component of the antenna.element of FIGURE 17.

DETAILED DESCRIPTION OF THE INVENTION

FIGURE 1 is a diagrammatic fragmentary front view of an apparatus 10 which includes an antenna element 12 arid part of a radome 13. In the disclosed embodiment, the apparatus 1.0 is configured for use in a not-illustrated 15 . phased array antenna system. The antenna system includes a plurality of the antenna elements 12 arranged in a twodimensional array of rows and columns, and includes a radome which extends over all the antenna elements, a portion of this radome being shown at 13 in FIGURE 1.

FIGURE 2 is a diagrammatic fragmentary rear view of the apparatus 10, and FIGURE 3 is. a diagrammatic sectional, view taken along . the section line 3-3 in FIGURE 1. As best seen in FIGURE 3, the antenna element 12 includes two adjacent and parallel layers 17 arid 18 of 25 a.dielectric material. In this, disclosed embodiment, the dielectric layers each have a dielectric constant (Er) of approximately 3.0. The dielectric layers 17' and 18 are bonded to each other by a thin layer 19 of bond film, which is of a type well known in the art. The dielectric 30 layers 17 and 18 are each approximately .20 mils thick. The bond film 19׳ is approximately 2-3 mils thick.

WO 03/021715 '

FIGURE 4 is a diagrammatic fragmentary sectional front view of the apparatus 10, taken along a ,central plane which extends between the dielectric layers17 ׳ and 18, with the bond film 19 omitted for clarity. The 5 dielectric layer 17 has on the front side thereof a first ground plane 26. (FIGURE 1), the dielectric layer 18 has on the rear side thereof a second ground plane 27 (FIGURE 2), and the dielectric layer 18 has on. the front side thereof a third ground plane defined by three 10 . separate portions 28A, 28B and 280 (FIGURE 4)., which are sometimes referred to _ע collectively herein as a ground plane 28.

The ground planes 26 and 27 are each electrodeposited metal layers with a thin gold plating on the 15 outer side thereof to resist corrosion. The ground planes 26 and 27 each have an overall thickness which is approximately 1-2 mils. The ground plane 28 is an electro-deposited metal layer which is approximately 0.5-1 mils thick.

The ground plane 26 has a recess etched through it, and this recess includes a balun portion 36 and . a slot portion 37. The balun portion 36 of the recess ,is approximately rectangular, except that it has corners which are slightly rounded. It' has׳ a length dimension 25 38, and a width dimension39 ׳. In the disclosed embodiment, the length dimension 38 is one-quarter of a wavelength of interest. The embodiment of FIGURES 1-4 is optimized for use in a frequency range of approximately 1.8 GHz to 18 GHz, and the length dimension 38 is 30 approximately one-quarter of the wavelength of a.center frequency of about 10 GHz. The width dimension 3 9 in. the disclosed embodiment is in the range of approximately

WO 03/021715 one-quarter of this wavelength to approximately threeeighths of this wavelength. That is, the width dimension 39 is at least as large as the length dimension 38, but is kept somewhat short of one-half, wavelength in order to 5 avoid potentially undesirable operational characteristics.

In general, it is desirable that the width dimension 39 should be as large as possible within these stated constraints. As a practical matter, however, when the 10 frequency of operation of a phased array antenna system progressively increases, . the size of the array must progressively decrease, because the space available for each antenna element is approximately one-half of the wavelength of the highest frequency of operation. Thus, 15 as the space available for each antenna element 12 progressively decreases, the maximum amount of space available for the width dimension 39 of the balun portion .36 also progressively decreases. Thus, in FIGURE 1, the width dimension 39 is about 5% longer than the length 20 dimension 38, but is not 50% to 70% longer, due to space limitations imposed by the operational frequency range of the antenna system,

Turning to the slot portion 37 of the recess in ground plane 26, the slot portion 37. has a narrow end 25 which communicates with the balun portion 36 along one of the linear sides of the balun portion 36, at a location spaced from each, end of that linear side. The. opposite end of the slot portion 37 is significantly wider than .־the narrow end. The shapes of the edges of. the slot 30 portion 37 will be discussed in more detail with reference to FIGURE 5.

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More specifically, FIGURE 5 is a graph showing the shape of one edge of the slot portion 37, where the ;horizontal axis represents the centerline of the slot, from the end. at the balun portion 36 to the end at the 5 radome 13. The vertical axis in FIGURE 5 represents the half-width of the slot, or in other words, the distance from the edge of. the slot to the centerline. The edges of the slot portion 3 7 are mirror images of each other with respect to the centerline of the slot, and therefore 10 only one of these edges is depicted in the graph of FIGURE 5.- i

It will be noted from FIGURE 5 that the edges of the slot portion 37 do not follow a pure first-order exponential curve. Instead, the slot edges have a shape 15 which has been carefully configured to minimize reflections and reduce return loss in a manner facilitating'a wide bandwidth in excess of 10:1. The technique used to configure the shape of the slot edge is .described in detail later. For the moment, it is sufficient to note certain characteristics of the specific shape shown in FIGURE 5 for the slot portion 37. More specifically, it can be seen that the narrowest part 41 of¹ the slot portion 37 is not precisely at the end of the slot portion which opens into the balun portion 36, 25 but instead is spaced a small distance from this end. This narrow part 41 provides a , region of increased capacitance. Also, toward the opposite end of the slot portion 37, there is. a significant discontinuity 42, J which is discussed later. Further, each edge of the slot 3 0 portion 37 is somewhat wavy in the section from the balun portion 36 to .the discontinuity 42, which is not a random meandering, but instead is a carefully configured

WO 03/021715 shape that reduces reflections and return loss in order to increase bandwidth and improve performance.

Roughly speaking, the curve shown in FIGURE 5 might be described as approximately a first-order exponential 5 curve that has at least one. higher-order characteristics superimposed on the first-order characteristic, and in fact the particular curve of FIGURE 5 has a number of higher-order characteristics superimposed on the firstusing well-known curve shown in of the following equation are set order characteristic. In curve-fitting techniques, FIGURE 5 can be expressed equation, where the coefficients for the forth in Table 1.

this regard, the specific in the form ²¹ . halfwidth(x) =—a,x' ,=0

TABLE 1 ־ COEFFICIENTS

<td> i</td><td> a!</td>

<td> 0</td><td> 15.56616 ’</td>

<td> 1</td><td> 3.540443</td>

<td> 2 .</td><td>.2724377</td>

<td> 3</td><td> 8.41E-03</td>

<td> 4</td><td>.46E-04</td>

<td> 5</td><td> 1.63E-06</td>

<td> 6.</td><td>.25E-08</td>

<td> 7</td><td> 6.95E-11</td>

<td> 8</td><td>.88E-13</td>

<td> 9</td><td> 9.09E-16</td>

<td> 10</td><td>.23E-18</td>

<td> 11</td><td> 4.27E-21</td>

WO 03/021715

<td> 12</td><td>.46E-24</td>

<td> 13</td><td> 7.73E-27</td>

<td> 14</td><td>.30E-30</td>

<td> 15</td><td> 5.41E-33</td>

<td>¹⁶</td><td>.11E-36</td>

<td> 17</td><td> 1.35E-39</td>

<td> 18 '</td><td> 4.32־E-43</td>

<td> 19</td><td> 9.54E-47</td>

<td> 20</td><td>.30E-50</td>

<td> 21</td><td> 8.21E-55</td>

Referring again to FIGURES 2 and 4, the ground plane 27 has . therethrough a recess which includes a balun .־ portion 43 and a slot portion 44, and the ground plane 28 has therethrough a recess which includes a balun portion ^J 46 and a slot portion 47. The slot portions 37, 44 and all have the same size and shape, in particular the shape described above in association with FIGURE 5.

• 10 . Further, the slot portions 37, 44 and 47 are all precisely aligned with each other. In a similar manner, the balun portions 36, 43 and 46 all have the same size and shape, and are precisely aligned with each -other. The dielectric Cavers 17 andUL^ each have therethrough an 15 approximately rectangular opening, which has the same size and shape as the balun portions 36, 43 and 46, and which is aligned with the balun portions 36, 43 and '46. Collectively, these aligned openings of approximately rectangular shape , in the three. groundplanes and the two 20 dielectric layers define a balun hole 49 of approximately rectangular shape, which extends completely through the antenna element 12.

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FIGURE 6 is diagrammatic fragmentary perspective view showing a portion of the rear side of the antenna element 12 in an enlarged scale. The balun opening 4 9 through the antenna element 12 is plated with an 5 electrically conductive material, such that a strip 51 of this conductive material extends along the edges of the balun hole. The ends of the strip' 51 are spaced so as to define a slot 52 aligned with the narrow ends of the slot portions 37, 44 and 47. The strip 51 extends between and 10 is electrically coupled to the ground planes 26 and 27, and is also .in electrical contact with' the ground plane 28A.

The antenna element 12 also has its opposite side edges plated with an electrically conductive material, 15 . such that respective strips 53 and 54 of this conductive material extend the full length of the dielectric ׳elements 17-18, and also extend between and are electrically coupled to each of the ground planes 26 and 27. The strip 53 is. also in electrical contact with the 20 , ground plane 28A along its entire length, and the strip 54 is in electrical contact with each of the ground planes 28B and 28C.

The dielectric layers 17 and 18 have' respective wedge-shaped openings' 57 and 58. therethrough, which are 25 identical size and'shape and are aligned with each other. The openings 57 and 58. begin at the outer ends of the dielectric elements 17 and 18, and decrease progressively in width in a direction ’ toward the balun hole 49. The tapering sides of the openings 57 and 58 are spaced 30 inwardly from the tapering edges of the slot portions 37״ 44 and 47. In a direction along the centerline of the J slot portions 37, 44 and 47, the inner ends of . the

WO 03/021715 openings 57 and 58 are approximately aligned with the . discontinuity 42 (FIGURE 5). The discontinuity 42 compensates to some extent for an impedance discontinuity caused within the dielectric material by the start of the 5 openings 57 and 58 at their left ends. The layer 19 of bond film (FIGURE 3) has a wedge-shaped opening through it which, is identical in size and shape to the openings •57 and 58, and which is aligned with the openings 57 and 58.

. The ground plane 28 (FIGURE 4) has, in' addition to the recess which includes the balun portion 46 and the

ל slot portion 47, a.further recess 66 which is an elongate channel that extends, from an inner end of the dielectric - k . layer 18 around the. balun portion 46, and opens into the 15 narrow end of the slot portion 47. . The channel 66 communicates along one side with the balun portion 46, but it would alternatively be possible for a portion of the groundplane 28A to extend between them.

An elongate conductive strip 67 extends through the 20 channel 66, such that one end is disposed at the inner end of the dielectric layer 18 located at the left side of FIGURE 1, and the other end extends across the narrow end of the slot portion 47 and is shorted directly to the ground plane 28A. The conductive strip 67 and the ground 25 plane 28A are discussed herein as if they are physically separate parts, because they serve different operational functions in the antenna element 12. However, as a practical matter, the ground plane 28A and the conductive strip 67 are just different integral portions of the same 30 conductive layer.

With . reference to FIGURE 1, an. approximately semicircular cutout 71 is provided through the ground plane

WO 03/021715 and the dielectric layer 17, in order to expose an end portion of the conductive strip 67, . and an end portion of each of the portions 28A and 28C of the ground plane .28. This permits a contact of a not-illustrated connector 5 arrangement to respectively engage the strip 67 and the ground plane portions 28A and 28C, in order to electrically couple . the conductive strip 67 of the antenna element 12 .to antenna system.circuitry which is known in the art and therefore not shown in the drawings. 10 In׳ the case of the antenna element 12 shown in FIGURE 1, the not-illustrated . antenna system. circuitry is electrically coupled to the arrangement of interconnected ground planes through direct engagement of a metal chassis of the antenna system with one or more of the 15 . outer ground planes 26-27 and the conductive strips 53-54. a.

The conductive strip 67 . serves as. a conductive element of the type which is commonly referred in the art as a stripline, and carries signals that are being 20 transmitted from or received by the antenna element 12.

The direct connection between the ground plane 28A and an end of the stripline 67 ' represents an electrical termination of that end of the stripline 67. Since the stripline 67 terminates directly into the groundplane 28, 25 reactances are minimized where the stripline 67 extends across the slot portion 47., .in comparison to pre-existing devices where the stripline is coupled by a via to a groundplane on the opposite side of a dielectric layer, or where the stripline, terminates into some form of 30 standalone termination structure designed to produce a standing wave resonance.

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A plurality of vias extend through both of the dielectric layers 17 and 18 at a number of different locations, so as to. electrically couple all three of the ground planes 26-28. Three of these vias are identified 5 with reference numerals 76, 77 and 78. The vias facilitate precise control over impedance characteristics within the slot portions 37, 44 and 47 and ' along the stripline 67, and also help to reduce or eliminate the extent to which electromagnetic fields can form parallel 10 plate and waveguide modes within the dielectric material. One of the illustrated vias is identified by reference numeral 79, and is slightly larger in diameter than the rest of the, vias. The via 79 is disposed closely adjacent the point at which one end of the stripline 67 .- 15 terminates directly into the ground plane portion-28 ־A, and serves to. ensure that this end of the stripline 67 is directly and reliably terminated to not only the center groundplane . 28,- but also the two outer groundplanes 2627. It will be noted that a respective row of the vias 20 extends adjacent each edge of. the slot portions 37, 44 and 47, with approximately uniform spacing from each via to the edge of the slot portions, and with approximately uniform spacing between adjacent vias. Behind each of these rows, along most of the length thereof, -is .a 25 further row of vias.

FIGURE .7 is a diagrammatic fragmentary perspective view of the outer end portion of the apparatus 10, in an • . enlarged scale. As best seen in FIGURE 7-, the radome 13 includes a dielectric layer 91 which is fixedly coupled 30 to an outer -end of the antenna element 12 by a bond film 92, a second dielectric' layer 93 which is fixedly coupled to the dielectric layer 91 by a bond film 94, and a third

WO 03/021715 dielectric layer 97 which is fixedly coupled to the dielectric layer 93 by a bond film 98. The bond films 92; 94 and 98 are materials of a type known in the art. The dielectric layer' 97 is relatively thin, and serves 5 primarily as a protective outer cover.

In the embodiment. of FIGURE 7, the dielectric layers 91, '93 and 97 have respective.thickness of 120 mils, 60 mils and 2 mils, and have respective dielectric constants (Er) of 1.08, 1.3, and 3.6. Alternatively, the dielectric 10 ' layers 91,' 93 and 97 could have respective thicknesses of mils, 120 mils and 2 mils, and respective dielectric constants of 1.3, 1.08 and 3.6. The dielectric layers 91 and 93 are transmissive to. radiation which is being transmitted from or received by the antenna element 12. 15 Further, the dielectric layers 91 and 93 effect a degree of refraction of this radiation, as discussed in more detail below. The dielectric, layers .91 and 93 can also ־; effect a small degree of impedance matching between the adjacent wide end of the slot portions located on . one 20 side thereof, and the free space located on the other side thereof..

In this regard, and with reference to FIGURE 4,. when an electrical signal is applied to the left end of the stripline 67, the signal travels through the stripline to 25 its opposite end, where the stripline extends transversely across the slot portion 47. Here, the electrical signal generates an electromagnetic field around the stripline, which tends to . try to travel in opposite directions within the slotline defined by the 30 slot portions 37, 44 and 47. The slotline increases approximately . progressively in impedance from the left end thereof toward the right end thereof, from an

WO 03/021715 ‘ PCT/US02/28108

I ¹⁹ impedance of approximately 50 ohms in the region of the stripline 67 to an impedance of approximately 340 to 350 ohms at the wide outer end. The stripline. 67 and the not-illustrated antenna system circuitry to which it is 5 coupled are matched, so as to provide a substantial uniform impedance of approximately 50 ohms from the circuitry through the stripline 67 to the slotline. Free space' beyond the right end of the apparatus 10 has an , impedance of approximately 377 ohms, for a two10 dimensional square unit cell representing uniform spacing in both directions of the two-dimensional array of antenna elements 12 within the phased array antenna system. The slotline effects an impedance transformation from a value of approximately 50 ohms at the left end, 15 which is matched to the impedance of the stripline 67, to a value of approximately 360-370 ohms at the right־ end, which closely approaches the impedance of free space.

The use of three groundplanes 26-28 provides more conductive material along the edges of the slotline, than 2 0 . in pre-existing arrangements that have only one' or two groundplanes, which in turn provides . increased capacitance within the slotline. The increased capacitance permits.the narrow. end of the slotline to be slightly wider than in pre-existing, devices, while. still 2-5 achieving, an impedance of 50 ohms which is ,matched to the impedance of the stripline 67. To the extent that the narrower end of the slotline can be wider, fabrication of the ground planes .26-28 is easier, due. to the fact that ' tolerances, involved in the etching techniques for the 30 . groundplanes are fixed.

The wedge-shaped openings 57 and 58 within the dielectric layers 17 and 18, and the congruent wedge

WO 03/021715 shaped opening within the bond film layer 19, help facilitate this impedance transformation, by reducing the amount of dielectric and. bond film material disposed within the slotline at the right end thereof. Thus, at

5' the right end of the antenna element 12, the. impedance within the .slotline will- more closely approach the impedance of the free'space located beyond the right end of the apparatus 10 than would be the case if the openings 57 and 58 were omitted and the right end of the slotline was completely filled with dielectric material.

This is due to the fact that air has a somewhat higher impedance than the dielectric material, arid the provision of the openings 57 and 58 substitutes, air for what would otherwise be dielectric material.

As mentioned above, the balun hole 4 9 is designed so that the width dimension 39 (FIGURE 1) is as large as possible in the region where the slotline opens into the balun hole 49, up to about three-eighths of a wavelength of interest. This is intended to provide the largest 20 possible impedance discontinuity, between the balun hole 49 and the narrow end of the slotline. This large discontinuity is facilitated by the fact, that the slot line opens into the balun hole 49 through a side of the balun hole 49 which is approximately linear, and at a 25 location spaced from both ends of this linear side.

In the disclosed embodiment, the balun hole has an ' impedance of approximately 300 ohms, which represents a relatively large- discontinuity in relation to the 50 ohm impedance of the adjacent end of the slotline. As noted 30 . above, electromagnetic fields generated by the stripline 67 where it crosses the slotline will tend to want to travel in both directions along the slotline. However,

WO 03/021715 the large impedance discontinuity between the balun hole 49 and the left end of . the slotline, will cause the majority of this electromagnetic energy to travel rightwardly rather than leftwardly along the slotline, 5 and to be transmitted into free space. To the extent that a small portion of the electromagnetic energy, travels leftwardly, the balun hole 49 has a length dimension which is approximately one-quarter wavelength (as discussed above) , and this creates^ an open circuit 10 standing wave which also tends to cause ׳electromagnetic ״.energy to travel rightwardly within the slotline.

As discussed'earlier in association with FIGURE 6, the inner edge of the balun hole 49 is plated with- a conductive strip 51, except at the slotline. The strip 15 51 helps to keep electromagnetic fields present within the_ ba 1 un _ho 1 e 49 from entering the dielectric material ~ ” ¹ «ill—» III - ———-——.**ד־ — ד—»11 — of layers 17 and 18, which helps to increase system bandwidth. . Consequently, the strip 51 helps establish the standing wave or resonant condition with respect to 20 electromagnetic energy within the balun hole.49, which in turn helps to direct electromagnetic energy rightwardly within the slotline. In a sense, the balun hole 49 is a _tuned inductive hole, which can operate over a 10:1 bandwidth without electrical or structural adjustment. On .. .. . ...... ! ! ! mm — — ...—,

In the disclosed embodiment, the balun hole 49 does not have any dielectric material within it. Thus, the balun'hole 49 _is filled with air, rather than dielectric material. For a given frequency, the wavelength of electromagnetic radiation is longer in air than it would be .in dielectric material. Consequently, to the extent the balun hole 49 is made as wide as possible in order to maximize the impedance discontinuity between the balun׳

WO 03/021715 hole and the adjacent end of the slotline, a given width will be further below one-half wavelength when the balun hole is filled with air than would be the case if the balun hole was -filled with dielectric material.

When electromagnetic radiation reaches the right end of the antenna element12 ־, it passes through the radome 13 and is emitted into free space. As mentioned above, the dielectric layers 91 and 93 of the radome 13 impart a degree of refraction to this electromagnetic radiation.

This refraction occurs with respect to wavefronts transmitted ,or received by the antenna system that are oriented at' an angle with respect to the antenna system boresight, which is parallel to the centerlines of the slot portions of the antenna elements. Wavefronts which are perpendicular to the antenna system boresight, and thus perpendicular to the centerlines of the' slot portions in the antenna elements, are not subject to refraction, or in other words can be viewed as undergoing refraction of O’. The following discussion of refraction 20 assumes that the wavefronts involved are oriented at an angle to the antenna system boresight and the centerlines of.the clot portions of the antenna elements.

In this regard, FIGURE 8 is a highly diagrammatic view of the apparatus 10, including both the antenna 25 element 12 and the radome 13. Arrow 111 represents electromagnetic radiation which is traveling outwardly through the slotline. As this, radiation passes through the interface between the antenna element 12' and the . dielectric layer 91, it is refracted to a degree, so that 30 it travels in a־ slightly different direction,, as indicated diagrammatically in FIGURE 8 by the arrow 112. Similarly, as this radiation passes through the interface

WO 03/021715 between dielectric layer 91 and dielectric 93, it experiences a further degree of refraction which further increases its angle, as indicated diagrammatically by arrow 113. Then, as this radiation passes through 'the 5 interface between dielectric layer 93 and free space, it is refracted a little further, so that it travels at a slightly greater angle, as indicated diagrammatically by arrow 114. This refraction within the'radome 13 permits the apparatus 10 to operate more effectively over awider 10 . scan angle, which, in the disclosed embodiment approaches about 50° to 60°. In a sense, the refraction causes a portion of the radiation transmitted at each edge of the scan angle to have a higher effective power level than would be the case without such refraction.־

The provision.of the wedge-shaped openings '57 and 58

- in the dielectric layer of the antenna element 12 permit the use of lower dielectric constants ' for the dielectric layers 91 and 93 of the radome 13 than would otherwise be the case. This in turn reduces the extent to which 20 electromagnetic energy is diverted into transverse surface waves within the dielectric layers, for example as indicated diagrammatically by a broken line arrow 117, which in turn reduces or avoids an effect that is sometimes referred to as scan blindness.

. ' Although the foregoing discussion of refraction was presented in. the context, of, transmitted radiation, persons skilled in the art will recognize that received radiation is also subject to refraction. In־ FIGURE 8,' for example^ reference numeral 121 diagrammatically 30 represents radiation which is approaching the antenna element 12 at an angle to the centerline of the slot portions in the antenna element 12. As this radiation

WO 03/021715

24.

passes through the radome 13 and enters the antenna element 12, the radiation is progressively refracted, as indicated diagrammatically by arrows 122, 123 and 124, until the radiation is traveling through the slot portion 5 of the antenna element 12 approximately parallel to the . centerline.

;FIGURE 9 is a graph showing return loss as a function of frequency for the embodiment of FIGURES 1-8, for what is known in the art as E-plane scan. Since return loss is a standard way of expressing the amount of reflection, it is desirable that return loss be as low as possible. It will be noted that the apparatus 10 provides a return loss which is continuously below -lOdB for a scan width of 60° across a bandwidth from 15⁷ approximately 1.8 GHz to approximately 17.5 GHz. Persons skilled in the art will recognize that,. expressed according to another industry standard, the embodiment of FIGURES 18־ provides a bandwidth of at least 10:1 for -9.5dB (VSWR less than 2).

. FIGURE 10 is a graph similar to FIGURE 9, but showing return loss for what is commonly known in the art as H-plane scan. FIGURE 10 shows that the apparatus 10 provides a return loss of -lOdB across a scan width of 45° to 50° from a frequency of about 3.5 GHz to a frequency in 25 excess of 18 GHz.

Although the foregoing discussion has been presented primarily in the context of.־signals that are being transmitted by the apparatus 10 of FIGURE 1, the apparatus 10 is' equally suitable for use in receiving 30 electromagnetic signals. Persons skilled in the art will understand from the foregoing discussion of signal

WO 03/021715 transmission how the apparatus 10 would function for purposes of signal reception.

Advantageous performance characteristics, such as those reflected by FIGURES 9 and 10, are due in part to 5 the shape determined for the edges of the slot portions 37, 44 and 47, which .collectively serve as the slotline of the antenna . element Ί2. An explanation will now be provided of how the. shape for the edges of the slot portions is determined,.

in this regard, and with reference to FIGURES 1 and

4, the apparatus 10 is conceptually broken into, three functional sections for purposes of carrying . out an analysis which determines an optimum shape for the edges of the slot. portions. More specifically, one functional 15 section is referred to as the balun, and corresponds roughly to the balun hole 49 and the conductive stripline 67. The next functional section is referred to as the slot, and corresponds roughly to .the part of the . slot portion which extends from the balun hole 49 to the 20 discontinuity 42 at the left end of the wedge-shaped openings _57 and 58. The third functional section 203 is referred to as the end piece, and corresponds roughly to the part of the apparatus 10 located to the right of the discontinuity 42, in particular from the left end of the 25 wedge-shaped openings 57-58 to the right side of the outer dielectric layer '97.

FIGURE 11 is a diagram showing three blocks 201-203, which respectively represent the , three . functional sections discussed above, namely the balun, slot and end 30 piece sections. Collectively, blocks 201-203 represent the apparatus 10 of FIGURE 1, as indicated diagrammatically by a broken line in FIGURE 11. Each of

WO 03/021715 PCT/US02/28108 the blocks 201-203 is depicted as a two-port element, including one port with two terminals on the left side, and another port with two terminals on the right side. Adjacent ports of the adjacent blocks are coupled to each 5 other. The end piece 203 has the port on the right side coupled to a further block 208, which diagrammatically represents the impedance of the free space disposed beyond the right end of the apparatus 10 in FIGURE 1.

As is known in the art, two-port blocks such as 10 those depicted at 201-203 can each be represented by what is commonly referred to as ah [ABCD] matrix. For example, focusing on the block 202 in FIGURE 11, which represents the slot, the left port has a voltage V_x and current I_x and the right port has a. voltage V_Y and current 15 I_Y. The relationship between these, ports can be. expressed by the following equation, where the subscript S identifies the.slot section:

Λ

Jx

Λ [V_r

<img file="IL160680A_D0001.tif" />

MJ

Similarly, and still referring to FIGURE 11, the overall transfer function for the apparatus 10 can be represented by, a single [ABCD] matrix, as follows:

/w. S' D. APP JpS where '^A H _\^A

Γ/4 B

D * C D

Jo I- Jo

EP

WO 03/021715 and where the subscripts APP,. B, S and EP respectively refer to the apparatus 10, the balun section 201, the slot section 202, and the end piece section 203.

Before attempting to determine an optimum shape for 5 the edges of the slot, the balun and end piece (which correspond .to blocks 201 and 203) are designed so as to achieve appropriate design goals. For example, as discussed- above, the balun׳ hole 49 (FIGURE 1) has various aspects, such as shape, size and the absence of 10 dielectric material, which are intended to. achieve the. design goal of a large impedance discontinuity between the balun hole and. slotline,., which in turn supports a wide bandwidth for the antenna element 12. Possible design configurations for both the balun and end piece 15 can be rigorously analyzed with an existing software program . . to determine expected operational characteristics. One suitable software program for this ' task is available under the tradename High Frequency Structure Simulator (HFSS), and can be commercially 20 obtained from Ansoft Corporation of Pittsburgh, Pennsylvania.

Once the physical design of the balun section and the end piece section have . been completed, several, appropriate [ABCD] matrixes are determined for each. In 25 this regard, ׳the apparatus 10 is designed for use across a frequency range . of ׳ interest. 'The operational characteristics of the balun section will be different at different frequencies, and the operational characteristics of the end piece section will be 30 different at different frequencies. Accordingly, several predetermined frequencies are selected, which are. spread throughout the frequency range of interest. Then, a

WO 03/021715 respective different [ABCD] matrix is determined for the balun section . 201 for each selected frequency, and a respective different [ABCD] matrix is determined for the end piece section 203 for each such frequency.

Appropriate techniques for determining an [ABCD] matrix from a physical design are known in the art. As one example, parameters representing the physical design can be provided to a known software program, which can then calculate a form of transfer function known in the 10 art as an [S] matrix. The HFSS computer program mentioned above is suitable for this task. . Thereafter, the [S] matrix can be converted into a corresponding [ABCD] matrix, using known mathematical techniques.

Turning to the slot section 202 of. FIGURE 11, one 15 aspect of the present invention is the provision of a technique where the portion of the slotline corresponding to the block 202 is represented by a model which is a transmission line having the same size and shape as the slot, the transmission line being in the form of a number 20 of. contiguous ’ transmission line segments. For example, FIGURE 12 is a ’diagrammatic view of a model which is a transmission line 241, made up. of a plurality of N contiguous rectangular segments SEG1, .SEG2, SEG3,. SEGN. In FIGURE 12 there are 40 segments, and thus 25 N = 40. The centerline of the slot is' indicated diagrammatically at 243, and the׳ outer ends of the N segments collectively represent the edges of the slot. The segments all have same length in a direction parallel to the centerline 243, but have a variety, of different 30 widths in a direction transverse to the centerline 243.׳ The segments in FIGURE 12 do not necessarily represent the precise slot shape shown in FIGURE 5, but instead can

WO 03/021715 be considered representative of one of a number of different shapes that are evaluated to determine which shape should serve as the optimum shape shown -in FIGURE 5.

In order to determine an optimum shape for the edges of the slot, the common length value for all of the segments SEG1 through S.EGN and also the N respective width values are varied selectively and. independently, and the performance of the apparatus 10 is evaluated for 10 each such configuration of the segmented transmission line, in a manner explained in more . detail below. It should be noted that the number N of segments is not varied. Consequently, to. the extent that the common length value for the segments is varied, the overall 15 length of the segmented transmission line, and thus the overall length of the slot it represents, will vary. Thus, part of what is optimized is the length.of the slot itself.

Since the common length and the respective widths of 20 the N segments are varied independently, the optimization process becomes progressively more complex and time consuming if the value of N is increased. As a result, competing considerations are involved in the selection, of the value of N. In particular, it is desirable, on one 25 hand to have a relatively large value of N so that the ends of the segments provide good resolution in the definition of the slot edges. On. the other hand, it is desirable to have a relatively small value of N in order to reduce the computational complexity involved in 30 evaluating different configurations of the segmented transmission line model. For an antenna element of the type disclosed at 12 in the embodiment of FIGURES 1-8, it

WO 03/021715 /

has been found that a value of N in the range of approximately 40 to 60 provides a good balance between these two competing considerations.

Various existing techniques are known for effecting 5 . the independent variation of a number of parameters in a selective manner so as to optimize a specified characteristic. One such .technique is commonly known in the art as the Nelder-Mead technique. There are commercially available software programs which implement 10 the Nelder-Mead technique, one example of which is the program MATLAB® available from The MathWorks of Natick, Massachusetts., ,Programs of this type provide generic Nelder-Mead capability, and can be provided with input data for a specific application which cause the program 15 to apply the generic principles to that specific application. Since Nelder-Mead techniques are known in the art, they are not described in detail here. Instead, to facilitate an understanding of the present invention, a brief overview is provided.

In particular, a program which implements NelderMead techniques is capable of varying multiple parameters in an intelligent manner according to Nelder-Mead principles, while evaluating a characteristicwhich is to be optimized. Generally speaking, configurations of 25 parameters which , tend to improve the specified characteristic are favored over configurations which do not improve the characteristic, and the favored configurations are used to predict other - new configurations that may possibly provide even greater 30 improvement in the specified characteristic.

. In the context of the present invention, an. initial slot shape is selected, for example where the edges of

WO 03/021715 the slot simply follow a first-order exponential curve. Then, a segmented transmission line model of the type shown in FIGURE 12 is used to model this initial slot shape, using N segments where N is roughly 40 to 60. The 5 ' respective widths . of the segments and also the common length .of the segments are then independently varied using Nelder-Mead techniques in order to come up with a plurality of different configurations of the segmented transmission line, which each represent a different slot 10 shape. For each such configuration, performance of that configuration is evaluated.

In this regard, in order to evaluate performance, the number of segments in the model is tripled through I .

interpolation. For example, FIGURE 13 is a . diagrammatic 15 view, in an enlarged scale, of the end portions of four of the transmission line segments shown in the upper right portion of FIGURE 12. The solid lines in FIGURE 13 correspond directly -to the segments which are shown in FIGURE 12. The broken lines in FIGURE 13 show how the 20 overall number of line segments is' tripled from N to 3N. ׳

For example, two points 261 and 262 are identified through interpolation at uniformly spaced locations along a straight line extending between two points 263 and 264,. which are at respective corners׳ of two of. the N segments 25 shown in FIGURE 12. Each of the points 261-264 then becomes a corner of a respective new segment having a length which is one-third the length of each of the N segments shown in FIGURE 12. It should be noted that, although 3N segments are now available for purposes of 30 evaluating performance, the Nelder-Mead techniques are not used to independently vary the widths of all 3N segments, but only the widths of the N segments shown in

WO (»3/021715

FIGURE 12. The other two-thirds of the segments have widths that are directly dependent on the original N widths, rather than widths determined through completely independent variation.

For 'a given configuration of 3N segments, for example as represented by broken lines in FIGURE 13, the performance of the system is evaluated in the following manner. Each of the 3N segments is treated as a separate transmission, line. With reference to FIGURE 14־, a 10 theoretical transmission line has a׳ length i,. which corresponds to the uniform dimension of each of the 3N . segments in a direction parallel to the centerline 243 (FIGURE 12) of the slot. Further,, the theoretical transmission line in. FIGURE 14 has an impedance Z_SEg and, 15 in the case of ' each of the ' 3N segments shown in FIGURE 13, this impedance depends on one or more different factors. First, it depends on the width of the segment in a direction transverse to the centerline 243. Further, and with reference to the apparatus 10 shown in 20 FIGURE 1, it depends on whether there is material within the slot and, if so, the characteristics of ' that material.

For example, the embodiment of FIGURE 1 has portions. ' of the dielectric layers 17 and. 18 which are־, disposed 25 within the slot, and the dielectric layers, have impedance characteristics that vary with frequency״ even for a given . width. In contrast, if the portions . of the. dielectric layers 17 and 18 located within the slot were removed, such; that the slot was filled with air, the 30 impedance . characteristic would vary with width but not frequency, because the impedance of air does not vary with frequency.

WO 03/021715

As evident from FIGURE 14, the theoretical transmission line can be modeled as a two-port element of the type discussed earlier, and its characteristics can thus can be represented by an [ABCD] matrix. In the case of one of the 3N rectangular segments shown in FIGURE 14, the [ABCD] matrix for a particular lossless ideal segment would be defined as follows:

^SEG where

In these equations, it should be noted that the value of the wavelength λ can vary not only as a function of frequency, but also as function of the type of material present within the slot. For example, for a given frequency, the wavelength will be one value if there is dielectric material within the. slot (as is the case, in the embodiment of FIGURE 1), but will be a different value if the slot contains air rather than dielectric material.

For a selected frequency, a respective [ABCD] matrix is determined for each of the 3N segments. Then, an [ABCD] matrix is determined for the entire segmented transmission line, as follows:

WO 03/021715

X..X

A B

CD

Then, referring to FIGURE 11, an [ABCD] matrix can be determined in the following manner for the' entire apparatus of FIGURE 1,. identified by the subscript APP, including the antenna element 12 and the radome portion 13. ,

Still referring to FIGURE 11, it will be recognized that this [ABCD] matrix for the antenna element can be expressed in the following standard form:.

AB x

APP

This matrix equation can be rewritten in the form of two non-matrix equations, as follows:

V!n ⁼ AVpg + BIps

I in = CV_FS + Dips where A, B, C and D are from

Still referring to FIGURE 11, and in particular to the block 208 at theright end thereof, it is well known

WO 03/021715 that voltage equals current times impedance. Thus, V_FS = l_PS . Z_FS. Substituting this into the two preceding equations for V!n and I!n yields the following:

V!n = Ifs (AZfs + B)

I in = Ifs (CZps + D) where A,.B, C and D are from

A B

C ^D.

Assume now . that Z_Sys’ represents the impedance of the entire system shown in FIGURE 11, including both the apparatus. 10 and the block 208, as viewed, from the port at the left side of FIGURE 11. It will be recognized that:

- - ^FS ⁺ F ^srs־I CZ +D where A, B,

C and D are from

As mentioned above, the antenna element 12 . of

FIGURE 1 is coupled to a not-illustrated antenna system, for example through a cable. The antenna system supplies electrical signals to and from the input port at the left side of FIGURE 11. Assume that Z_o represents the 25 characteristic impedance of the not-illustrated cable and other circuitry of the antenna system. It is customary in the art to design this circuitry and cable so that the impedances are all matched, to thereby provide a line of effectively constant impedance, with no reflection. In

WO 03/021715 the disclosed embodiment, this characteristic impedance Z_ohas a value of 50 ohms.

For a system of the type shown in 'FIGURE, 11, it is known in the art that the ratio of the reflected voltage 5 to the incident voltage into the port can be expressed by the following equation: I . ‘

7-7 7+7

1θ It is also well known in the art that, using a reflection value R determined from the preceding equation, the associated return loss RL can be determined from the following equation:

¹⁵ M20־tog,_״(|A|)

The performance evaluation.procedure discussed above is specific to a particular frequency. For a given slot shape, this evaluation needs to be carried out separately 20 for each of a number of- .different frequencies spread across a frequency range Of interest. This will result in. a number of different, values of return loss RL calculated for that particular slot shape at respective different frequencies, and these.values of return loss RL 25 can then be presented in the Torm of graph similar to FIGURES 9 and10 ־.

Further, the foregoing discussion has focused on how to evaluate one proposed slot shape. In order to come up with an optimum shape, a number of different slot shapes 30 need to be evaluated in a similar manner, and the results of these evaluations are then compared in order to

WO 03/021715 determine which slot shape provides the optimum performance. Various different criteria can be used to make this evaluation, and these criteria may be used either separately or in combination. Some examples of 5 such criteria will now be discussed, but it should be recognized that the present invention is not limited to these particular criteria. .

A' first criteria involves, a determination of the maximum value of return loss RL. calculated for a given 10 slot shape. The slot shape having the׳ lowest maximum value of RL could be selected as the optimum design. Alternatively, all evaluated slot shapes with a maximum . value of return loss RL.׳ lower than a specified value (such as -lOdB) could be identified, and the shapes in 15 this group could then be comparatively evaluated using other criteria.

A second criteria would be to determine the maximum value, for each slot shape, of the absolute value of the . calculated reflection R. The slot design with the lowest 20 such maximum value could be selected as the optimum design. Alternatively, all evaluated slot shapes for which this calculated maximum value is less than a specified value could be selected,. and the slot shapes in this group could then be comparatively evaluated using 25 other criteria.

The two criteria discussed above tend to focus on any single point, maximum for the reflection R or the return loss . RL. Other criteria could take more of an averaging approach to performance, across the frequency 30 range of interest. For example, a third criteria would be to sum the absolute values of reflection R calculated

WO 03/021715 at various frequencies for a given slot design, as follows:

fmn ., . .ΣΝ

A fourth criteria, which is a variation of the third criteria, would be. to sum the squares of the absolute values of reflection R calculated, at various frequencies for a given slot shape, as follows:

/ 2 /ma» ,,

ΣΝ /*”/mm ~ . FIGURE 15 is. a flowchart, which . summaries the optimization technique discussed above. More

ו

15:. specifically, in block 301, the designs of the balun and end piece are each optimized and finalized. Then, transfer functions are determined for each of. the balun

כ * and end piece at each of a plurality of predetermined frequencies spread across a frequency range of interest.

As discussed above, each of these transfer functions can be represented in the form of an [ABCD] matrix.

Next, at block 302, an initial slot shape, is selected in order to seed the optimization routine. In the disclosed embodiment, the initial slot shape is 25. selected to be a pure first-order exponential curve, but it would alternatively be possible to use some other initial slot shape. Next, at block 303, the. selected slot shape *is modeled as ־a segmented transmission line, in the manner discussed above in association with FIGURES

WO 03/021715 and 13. Then, at block 306, . the lowest of the predetermined frequencies in the range is selected.

Next, at block 307, a respective transfer function is determined at the selected frequency for each of the 5 segments of the segmented transmission line. In the disclosed embodiment, each such transfer function can be in the form of an [ABCD] matrix, as discussed above. These various transfer functions ׳ for the different segments are then combined to obtain a single transfer־ 10 function for the entire segmented transmission line. . In the disclosed embodiment, this is also an [ABCD] matrix, as discussed above.

Control then proceeds from block 307 to block 308. ..For the current slot shape and the selected frequency, 15 the transfer functions, for the balun section, slot section and end piece section are used to calculate and save a reflection value and a return loss value, in a manner discussed previously. Then, at block 311, a determination is made of whether the currently selected

. .' . ־ ע frequency is the highest frequency in the range. If not, the next highest of. the predetermined frequencies is selected at block 312, and control returns to block 307 to analyze the performance of the current slot design at .׳ this newly-selected frequency.

in contrast, if it is determined at block 311 that the current slot ^v shape has been evaluated for all predetermined frequencies in the range, control proceeds to block 313, where all of the reflection values. and return loss values for the current slot shape are used to 30 evaluate the performance of the system for that slot shape. These evaluations are then saved.

WO 03/021715

Next, at block 316, an evaluation is made of whether the optimum shape has been found. This determination involves use of performance criteria of the type discussed above. Further, it depends on the extent to which the Nelder-Mead techniques discussed above have reached a point’ where a variety of different slot shapes have been evaluated and it appears that the optimum shape is likely to be a shape that has already been evaluated, rather than a shape that has yet been evaluated. In 10 . general, a number of slot shapes will be evaluated before a decision' is made at block 316 that the optimum slot shape has been identified.

When a determination is made in . block 316 that an optimum slot shape has not yet been located, control 15 proceeds to block 317, where a new and different slot shape is selected for evaluation, through variation of the widths of the N segments and/or the common . length- of the N segments. . The blocks 316 and 317 basically represent a particular application for the known'Nelder20 Mead techniques that . were discussed earlier. In contrast, if at some point it is determined at block 316 that an optimdm slot shape has been determined, the evaluation process is finished, and ends at block 318.

FIGURE 16 is a diagrammatic front view of an. antenna 25 element 412 which is alternative embodiment of the antenna element 12 of FIGURE 1. The antenna element 412 of FIGURE 16 would normally be used with a radome of the type shown at 13 in FIGURE 1, but the radome is omitted ., from FIGURE 16. The antenna element 412 of FIGURE 16 is 30 substantially, identical to the antenna element 12 of FIGURE 1, except for the differences which are discussed below.

WO 03/021715

More specifically, the two dielectric layers and the bond film of the antenna element 412 each extend outwardly beyond the ends of the three ground planes, one of the dielectric layers being visible at 417; and one of the ground planes being visible at 426. The upper and lower side edges . of the antenna element 412 each have plating which extends from the left end of. the antenna element to the right ends of the ground planes. This edge plating does not extend the rest of the way to the right end of the antenna element 412.

The dielectric -layers each have a’, wedge-shaped opening therein, one of which is visible at 457. It will be'noted that the left end of each wedge-shaped opening is located rightwardly of the right ends of the ground .

planes, including the ground plane426־. In other words,, the wedge-shaped openings in the dielectric layers are not disposed within the slotline defined by the slots in the ground planes. Consequently, the edges of the slot portions in the antenna element 412. do not have a discontinuity comparable to that shown at 42 in FIGURE 1, because the discontinuity 42 is due to the fact that ,the wedge-shaped opening 57 in FIGURE 1 is disposed within the slotline.

Although.it is not readily visible in FIGURE 16, the 25 edges of the slot portions of the ground planes do not follow a first-order exponential curve, but instead have higher-order effects which give them a somewhat wavy shape, in a manner similar to that described above in association with the embodiment of FIGURE 1. The

0 procedure used to determine the shape of the slot edges for the embodiment of FIGURE 16 is similar to the procedure described above for the embodiment of FIGURE 1,

WO 03/021715 . and is therefore not described again in detail here. Further, the operation of the embodiment of FIGURE 16 is similar to the operation of the embodiment of FIGURE 1, and is. therefore not explained again in detail here.

FIGURE 17 is a diagrammatic perspective view of an antenna . element 512 which is a further alternative embodiment of the antenna element 12 of FIGURE 1. The antenna element 512 includes a body 514 which is made from a single' metal plate. A recess is provided through 10 the metal plate, and includes a balun portion 536 in the' shape of a rectangular. hole, and an elongate slot portion 537 which communicates at its narrow end with the balun portion 536. In general, the balun portion 536 and the slot portion 537 have sizes and shapes that are 15 comparable to those discussed above in association with the embodiment of FIGURE 1. In this regard, the edges of the slot portion 537 do not follow merely a first-order exponential curve, but instead, include higher-order effects which give the edges a somewhat wavy shape. The 20 shape of the edges is determined by a procedure similar . to that discussed above ' id association with the embodiment of FIGURE 1, and this procedure is not described again in detail here.

One significant difference is that the slot portion 25 537 contains air rather than a dielectric material. The effects of having air in. the slot portion, rather than a dielectric material, have already been discussed above in detail. The .antenna element. 512 includes a coaxial stripline. 561, which has an' electrically conductive 30 exterior sheath that is fixedly secured to the front of the plate 514 by a conductive epoxy adhesive of a known type .

WO 03/021715

43>

FIGURE 18 is a diagrammatic sectional view of the coaxial stripline 561, taken along the section line 18-18 in FIGURE 17. As shown in- FIGURE 18, the coaxial stripline 561 includes two adjacent dielectric layers 563 5 and 564, with a conductive stripline 567 disposed between them. Along most of its length, the stripline 567 has a width which is substantially less than the width of the dielectric layers 563 and 564, so that the dielectric layers 563 and 564 serve as a layer of insulating 10 material which extends coaxially around the stripline 567.

A' sheath 569 of an electrically conductive material extends completely around the dielectric layers 563 and 564. As mentioned above, the sheath 569 is physically 15 and electrically coupled, to the metal plate 514 in FIGURE 17 by a conductive epoxy adhesive of a known type, which is not separately shown in the drawings.

FIGURE 19 is a diagrammatic fragmentary sectional top view of the coaxial stripline '561, taken along a 20 plane defined by the top surface of the stripline 567, - ' *s and showing an end portion of the coaxial stripline 561 which is located in the region of the narrow end of the slot portion 537 (FIGURE 17) . With reference tO FIGURES 17 and 19, the conductive sheath 569 has an annular gap 25 572 which extends completely around the coaxial stripline.

561. The gap 572is aligned with the slot portion 537, and permits current within the stripline 567 to generate electromagnetic fields that can escape the sheath 569 and extend.into the slot portion 537.

Approximately . halfway across the gap 572, the stripline 567 begins expanding progressively, in width, which serves as a , transition to an approximately

WO 03/021715 PCT/US02/28108 (

rectangular end portion 573, three sides of which electrically engage the sheath 569. A via at 574 extends through the conductive stripline between opposite sides of the sheath 569, and is electrically coupled to the end 5 portion 573 of the stripline 567. Thus, in effect, the end of the stripline 567 is shorted directly to. a ground plane defined by the metal plate 514 (FIGURE 17), in order to effect electrical . termination of the stripline 567.

One technique for fabricating the coaxial stripline

561 is as follows. The dielectric material 564. is fabricated, and then a layer, of metal is deposited on. top of it. The metal layer is then photqlithographically. etched in a known manner, in order to remove selected 15 portions of it, such that the remaining portions define the stripline 567 with its end portion 573., Then, the dielectric layer 563 is formed over the dielectric layer 564 and the stripline 567. Next, a cylindrical hole is created through the dielectric layers and the metal 20׳ layer, at a' location where the via 574 is to be formed.

Then, this arrangement is immersed in an electroless plating tank, in order to form the sheath 569.over the entire exterior thereof, and in order to form the via 574 within the cylindrical hole. The annular mask prevents 25 conductive material from being plated within the, region of the gap 572. .After the'plating is completed, the mask . is removed in order to expose the gap 572. The resulting assembly is then secured to the metal plate 514, using a conductive epoxy adhesive, as discussed above.

The operation of the antenna element .512 of FIGURES

17-19 is generally similar, to that of the antenna element 12 . of FIGURE 1. Therefore,, a separate detailed

WO 03/021715 discussion of the operation of the antenna element 512 is believed to be unnecessary, and is omitted. here.

The present invention provides a number of technical advantages. One such technical advantage results from 5 the absence of dielectric material in the balun hole, such that the hole contains air. Since air has a lower dielectric constant than dielectric material, air has a higher impedance ^;than a dielectric material, and the wavelength of a given frequency is longer in air than in 10 a dielectric material. Consequently, for a given physical width of the balun hole,, the effective electrical width is smaller for air than for a dielectric material. This in turn means that the effective electrical width is farther below 8/2 for air.than for a 15 dielectric material, which reduces undesirable effects. A further advantage results where the' inner edge of the balun hole is conductive, . for example due -to the provision of plating, because, it helps to increase the bandwidth of the balun hole by containing electrical 20 fields to the hole, In the case of an antenna element with layers of a dielectric material, the conductive edge of the hole prevents electric fields from extending into the dielectric material aroundthe hole.

Still another advantage is realized where the balun 25 hole has a generally rectangular shape, because it helps . to.create an abrupt impedance discontinuity between the balun hole and the associated end of -the slotline. With an abrupt discontinuity in impedance, electric fields in the region of the narrow end of the. slot see the balun 30 hole as approximately an open circuit across a frequency range of. interest, which gives the balun hole a relatively wide bandwidth. A related advantage is

WO 03/021715 realized where dielectric material is omitted within the rectangular balun hole, and the edge of the balun hole is conductive, because the bandwidth of the balun hole is further enhanced. ׳ The resulting balun hole is 5 effectively a tuned conductive hole.

Still another advantage results from the provision of more than two ground planes, and the termination of the stripline directly into one of these ground planes, because this facilitates a relatively wide bandwidth for 10 the balun hole. Where the balun hole is approximately rectangular, contains no dielectric material, has conductive edges, is associated with-two or more ground planes, and is associated with a stripline termination into a ground plane, the standalone bandwidth of the' 15 balun hole can approach about 8:1.

Still another advantage involving increased .bandwidth results where such a balun hole is used with a, slot having a shape that has been optimized using techniques according to the invention. At low 20 ׳ frequencies, the balun hole is inductive and the slot is capacitive. But where the optimization technique is used to achieve conjugate matching of the balun hole and slot,, they cooperate to provide good performance even at low &lt; frequencies., in a manner somewhat analogous to resonance in a tuned RLC circuit. In particular, they can provide c ' .

a decade .(10:1) bandwidth capable of a +60° E-plane and ±50° H-plane scan. volume.

The provision of three or more ground planes can also provide another advantage., by helping to minimize 30 . reactances at the stripline to slotline transition.

Further, providing three or more ground planes increases the amount of conductive material present along the edges . WO 03/021715 of the slot, thereby increasing capacitance, which in turn allows the narrow end of the slot be wider. Where the narrow end of the slot is wider, it. is easier to fabricate the slot while still achieving a low impedance 5 of approximately 50 ohms for the narrow end; of the slot.

This is because the tolerances for etching are basically fixed, and etching the narrow end' of the slot becomes progressively easier as the width of the slot is progressively increased.

Still another advantage results .where the striplirie terminates directly into one of the ground, planes, because this effectively provides an actual physical short circuit to a ground plane/ in comparison to preexisting techniques that essentially seek to emulate or approximate a physical short circuit by creating a standing wave resonance. The disclosed antenna elements provide a striplirie to slotline transition with a transformer ratio that is close to unity,_r and with minimal stray reactances.

Although selected embodiments have been.illustrated and described in detail, it will be understood that various substitutions and alterations are possible without departing from the spirit and scope of the present invention, as defined by the following claims.