Radio communication device and constellation control method
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15 claims: 11 independent, 4 dependent
- 1Claims 1. A rádió communication apparátus (200); including:a spreading unit (215) configured to spread a response signal representing ACK or NACK with a sequence defined by one of cyclic shift values;characterized by further including: a scrambling unit (214) configured to multiply the response signal by 1 or eiá /2 ) depending on whether an index of a physical uplink control channel used fór transmission of the response signal is odd or even, wherein the cyclic shift value is determined from the index of the physical uplink control channel;and a transmitting unit (220) configured to transmit the response signal spread and multiplied by 1 or eiW 2 ).
- 4The rádió transmission apparátus according to one of claims 1-3 further comprising a second spreading unit configured to secondarily spread the response signal spread and multiplied by 1 or eiá /2 ) with one of orthogonal sequences, wherein said transmitting unit transmits the secondarily spread response signal, and the orthogonal sequence is determined from the index of the physical uplink control channel.
- 7The rádió transmission apparátus according to one of claims 4-6, wherein said scrambling unit selects 1 and eiá /2 ) alternately each time the cyclic shift value is shifted by a predefined amount in a plurality of the physical uplink control channels from which the same orthogonal sequence is determined.
- 8The rádió transmission apparátus according to one of claims 4-7, wherein said scrambling unit selects 1 in one of two physical uplink control channels and selects eiV /2 ) in the other of the two physical uplink control channels, wherein the same orthogonal sequence is determined from the two physical uplink control channels, and two cyclic shift values that are closest to each other are respectively determined from the two physical uplink control channels.
- 14The rádió transmission apparátus according to one of claims 1-13, further comprising a modulating unit configured to modulate the response signal with BPSK or QPSK, wherein said spreading unit spreads the modulated response signal and said scrambling unit multiplies the modulated response signal by 1 or βΚ π/2 ).
- 15A constellation controlling method; including the step of:spreading a response signal representing ACK or NACK with a sequence defined by a cyclic shift value;characterized by further including the steps of: multiplying the response signal by 1 or βΚ π/2 ) depending on whether an index of a physical uplink control channel used fór transmission of the response signal is odd or even, wherein the cyclic shift value is determined from the index of the physical uplink control channel ;and transmitting the response signal spread and multiplied by 1 or βΚ π/2 ).
Independent claims11
284 paragraphs in 3 sections, as filed
(56)
References cited:
EP-A2- 0 982 892 JP-A- 2005 027 336 US-A1-2007 242 764
WO-A1-2008/093774 US-A1-2004 032 838 (43) (60)
Date of publication of application:
14.07.2010 Bulletin 2010/28
Divisional application:
12154691.5/2 475 118
15201169.8
15201172.2 (73)
Proprietor: Panasonic Intellectual Property
Corporation of America
Torrance, CA 90503 (US) (72) (74)
ΕΡ 2 207 289 Β1
Inventors:
Seigo, Nakao
Osaka-shi, Osaka 540-6207 (JP)
Daichi, Imamura
Osaka-shi, Osaka 540-6207 (JP)
Representative: Grünecker Patent- und
Rechtsanwálte
PartG mbB
LeopoldstraBe 4
80802 München (DE)
PANASONIC: R1-073616 Signalling parameters fór ULACK/NACKresources, WWW.3GPP.ORG, 19 August 2007 (2007-08-19), XP008123371, NAKAO S. ET AL.: ’Evolved ÚTRA Nobori Seigyo Channel ni Okeru Scramble no lehikento’ IEICE TECHNICAL REPORT vol. 108, no. 249, 15 October 2008, pages 55 - 60, XP008123464 ’3GPP TSG RAN WG1 Meeting #52 R1-080978’, 11 February 2008 artiele PANASONIC: ’NTT DoCoMo, Necessity of the scrambling fór ACK/NACK on PUCCH’, pages 1 - 6, XP050109449 ’3GPP TSG RAN WG1 Meeting #50 R1-073616’, 20 August 2007 artiele PANASONIC: ’Signaling parameters fór UL ACK/NACK resources’, pages 1 - 3, XP008123371 ’3GPPTSG RAN WG1 Meeting #50 R1-073621’, 20 August 2007article PANASONIC:’VariablePhase Definition ofthe Reference Signal fór CQI in PUCCH’, pages 1 - 5, XP050107219
SHOGO NAKAO ET AL.: ’Kosoku Fading Kankyoka no Evolved ÚTRA Nobori Seigyo Channel Seino Ka ízen’ IEICE TECHNICAL REPORT vol. 108, no. 188,20 August 2008, pages 49-54, XP008123461 ’3GPP TSG RAN WG1 Meeting #52 R1-080979’, 11 February 2008 artiele PANASONIC, NTT DOCOMO: 'Necessity of the Scrambling fór the Reference Signal of CQI in PUCCH’, pages 1-5,
XP008123370
Note: Within nine months ofthe publication ofthe mention ofthe grant ofthe European patent in the European Patent Bulletin, any person may give notice to the European Patent Office of opposition to that patent, in accordance with the Implementing Regulations. Notice of opposition shall nőt be deemed to have been filed until the opposition fee has been paid. (Art. 99(1) European Patent Convention).
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ΕΡ 2 207 289 Β1 • '3GPPTSG RAN WG1 Meeting#49bis R1-073149’, 25 June 2007 article SAMSUNG: ’CycIic Shift Hopping of UL ACK Channels’, pages 1-6, XP008123369
ΕΡ 2 207 289 Β1
Description
Technical Field [0001] The present invention relates to a rádió communication apparátus and constellation control method.
Background Art [0002] In mobile communication, ARQ (Automatic Repeat Request) is applied to downlink data from a rádió communication base station apparátus (hereinafter abbreviated to base station) to rádió communication mobile station apparatuses (hereinafter abbreviated to mobile stations). That is, mobile stations feed back response signals representing errordetection results of downlink data, to the base station. Mobile stations perform a CRC (Cyclic Redundancy Check) of downlink data, and, if CRC=OK is found (i.e. if no error is found), feed back an ACK (ACKnowiedgement), and, if CRC=NG is found (i.e. if error is found), feed back a NACK (Negative ACKnowiedgement), as a response signal to the base station. These response signals are transmitted to the base station using uplink control channels such as a PUCCH (Physical Uplink Control CHannel).
[0003] Alsó, the base station transmits control information fór carrying resource allocation results of downlink data, to mobile stations. This control information is transmitted to the mobile stations using downlink control channels such as L1/L2 CCH’s (L1/L2 Control CHannels). Each L1/L2 CCH occupiesoneora plurality ofCCE’s (Control Channel Elements) based on the coding rate of control information. Fór example, when a L1/L2 CCH fór carrying control information coded by a rate of 2/3 occupies one CCE, a L1/L2 CCH fór carrying control information coded by a rate of 1/3 occupies two CCE’s, a L1/L2 CCH fór carrying control information coded by a rate of 1/6 occupies four CCE’s and a L1/L2 CCH fór carrying control information coded by a rate of 1/12 occupies eight CCE’s. Alsó, when one L1/L2 occupies a plurality of CCE’s, the CCE’s occupied by the L1/L2 CCH are consecutive. The base station generates a L1/L2 CCH on a per mobile station basis, assigns CCE’s to be occupied by L1/L2 CCH’s based on the number of CCE’s required by control information, and maps the control information on physical resources corresponding to the assigned CCE’s and transmits the control information.
[0004] Alsó, studies are underway to map between CCE’s and PUCCH’s on a one-to-one basis, to use downlink communication resources efficiently without signalling from a base station to mobile stations to report the PUCCH’s to be used fór transmission of response signals, (see Non-Patent Document 1). According to this mapping, each mobile station can decide the PUCCH to use to transmit response signals from the mobile station, from the CCE’s corresponding to physical resources on which control information fór the mobile station is mapped. Therefore, each mobile station maps a response signal from the mobile station on a physical resource, based on the CCE corresponding to a physical resource on which control information directed to the mobile station is mapped. Fór example, when a CCE corresponding to a physical resource on which control information directed to the mobile station is mapped, is CCE #0, the mobile station decides PUCCH #0 associated with CCE #0 as the PUCCH fór the mobile station. Alsó, fór example, when CCE’s corresponding to physical resources on which control information directed to the mobile station is mapped are CCE #0 to CCE #3, the mobile station decides PUCCH #0 associated with CCE #0, which is the smallest number in CCE #0 to CCE#3, as the PUCCH fór the mobile station, and, when CCE’s corresponding to physical resources on which control information directed to the mobile station is mapped are CCE #4 to CCE #7, the mobile station decides PUCCH #4 associated with CCE #4, which is the smallest number in CCE #4 to CCE#7, as the PUCCH fór the mobile station. [0005] Alsó, asshown in FIG.1, studies are underway to perform code-multiplexing byspreading a plurality of response signals from a plurality of mobile stations using ZAC (Zero Autó Correlation) sequences and Walsh sequences (see Non-Patent Document 1). In FIG.1, [W<sub>o</sub>, W<sub>1</sub>, W<sub>2</sub>, W<sub>3</sub>] represents a Walsh sequence with a sequence length of 4. As shown in FIG.1, in a mobile station, first, a response signal of ACK or NACK is subject to first spreading to one Symbol by a ZAC sequence (with a sequence length of 12) in the frequency domain. Next, the response signal subjected to first spreading is subject to an IFFT (Inverse Fást Fourier Transform) in association with W<sub>o</sub> to W<sub>3</sub>. The response signal spread in the frequency domain by a ZAC sequence with a sequence length of 12 is transformed to a ZAC sequence with a sequence length of 12 by this IFFT in the time domain. Then, the signal subjected to the IFFT is subject to second spreading using a Walsh sequence (with a sequence length of 4). That is, one response signal is allocated to each of four SC-FDMA (Single Carrier-Frequency Division Multiple Access) symbols S<sub>o</sub> to S<sub>3</sub>. Similarly, response signals of other mobile stations are spread using ZAC sequences and Walsh sequences. Here, different mobile stations use ZAC sequences of different cyclic shift values in the time domain (i.e., in the cyclic shift axis) or different Walsh sequences. Here, the sequence length of ZAC sequences in the time domain is 12, so that it is possible to use twelve ZAC sequences of cyclic shift values 0 to 11, generated from the same ZAC sequence. Alsó, the sequence length of Walsh sequences is 4, so that it is possible to use four different Walsh sequences. Therefore, in an ideál communication environment, it is possible to code-multiplex maximum forty-eight (12x4) response signals from mobile stations.
[0006] Alsó, as shown in FIG.1, studies are underway fór code-multiplexing a plurality of reference signals (e.g. pilot
ΕΡ 2 207 289 Β1 signals) from a plurality of mobile stations (see Non-Patent Document 2). As shown in FIG.1, in the case of generating three symbols of reference signals R<sub>o</sub>, R<sub>1</sub> and R<sub>2</sub>, similar to the case of response signals, first, the reference signals are subject to first spreading in the frequency domain by a sequence having characteristics of a ZAC sequence (with a sequence length of 12) in the time domain. Next, the reference signals subjected to first spreading are subject to an IFFT in association with orthogonal sequences with a sequence length of 3, [F<sub>o</sub>, F<sub>1</sub>, F<sub>2</sub>], such as a Fourier sequence. The reference signals spread in the frequency domain are converted by this IFFT to ZAC sequences with a sequence length of 12 in the time domain. Further, these signals subjected to IFFT are subject to second spreading using orthogonal sequences [F<sub>o</sub>, F<sub>2</sub>j. That is, one reference signal is allocated to three SC-FDMA symbols R<sub>o</sub>, R<sub>1</sub> and R<sub>2</sub>. Similarly, other mobile stations allocate one reference signal to three symbols R<sub>o</sub>, R<sub>1</sub> and R<sub>2</sub>. Here, different mobile stations use ZAC sequences of different cyclic shift values in the time domain or different orthogonal sequences. Here, the sequence length of ZAC sequences in the time domain is 12, so that it is possible to use twelve ZAC sequences of cyclic shift values 0 to 11, generated from the same ZAC sequence. Alsó, the sequence length of an orthogonal sequence is 3, so that it is possible to use three different orthogonal sequences. Therefore, in an ideál communication environment, it is possible to code-multiplex maximum thirty-six (12X3) reference signals from mobile stations.
[0007] As shown in FIG.1, seven symbols of S<sub>o</sub>, S<sub>1</sub>, R<sub>o</sub>, R-|, R<sub>2</sub>, S<sub>2</sub> and S<sub>3</sub> form one Symbol.
[0008] Here, there issubstantially nocrosscorrelation between ZAC sequences of different cyclic shift values generated from the same ZAC sequence. Therefore, in an ideál communication environment, a plurality of response signals subjected to spreading and code-multiplexing by ZAC sequences of different cyclic shift values (0 to 11), can be separated in the time domain substantially without inter-code interference, by correlation Processing in the base station.
[0009] However, due to an influence of, fór example, transmission timing difference in mobile stations and multipath delayed waves, a plurality of response signals from a plurality of mobile stations do nőt always arrive at a base station at the same time. Fór example, if the transmission timing of a response signal spread by the ZAC sequence of cyclic shift value 0 is delayed from the correct transmission timing, the correlation peak of the ZAC sequence of cyclic shift value 0 may appear in the detection window fór the ZAC sequence of cyclic shift value 1.
[0010] Further, if a response signal spread by the ZAC sequence of cyclic shift value 0 has a delay wave, an interference leakage due to the delayed wave may appear in the detection window fór the ZAC sequence of cyclic shift value 1. That is, in these cases, the ZAC sequence of cyclic shift value 1 is interfered with by the ZAC sequence of cyclic shift value 0. On the other hand, if the transmission timing of a response signal spread by the ZAC sequence of cyclic shift value 1 is earlier than the correct transmission timing, the correlation peak of the ZAC sequence of cyclic shift value 1 may appear in the detection window fór the ZAC sequence of cyclic shift value 0. That is, in this case, the ZAC sequence of cyclic shift value 0 is interfered with by the ZAC sequence of cyclic shift value 1. Therefore, in these cases, the separation performance degrades between a response signal spread by the ZAC sequence of cyclic shift value 0 and a response signal spread by the ZAC sequence of cyclic shift value 1. That is, if ZAC sequences of adjacent cyclic shift values are used, the separation performance of response signals may degrade.
[0011] Therefore, up till now, if a plurality of response signals are code-multiplexed by spreading using ZAC sequences, a sufficient cyclic shift value difference (i.e. cyclic shift interval) is provided between the ZAC sequences, to an extent that does nőt cause inter-code interference between the ZAC sequences. Fór example, when the difference between cyclic shift values of ZAC sequences is 2, only six ZAC sequences of cyclic shift values 0, 2, 4, 6, 8 and 10 or cyclic shift values 1, 3, 5, 7, 9 and 11amongst twelve ZAC sequences of cyclic shift values 0 to 12, are used fór first spreading of response signals. Therefore, if a Walsh sequence with a sequence length of 4 is used fór second spreading of response signals, it is possible to code-multiplex maximum twenty-four (6x4) response signals from mobile stations.
[0012] However, as shown in FIG.1, the sequence length of an orthogonal sequence used to spread reference signals is 3, and therefore only three different orthogonal sequences can be used to spread reference signals. Consequently, when a plurality of response signals are separated using the reference signals shown in FIG.1, only maximum eighteen (6X3) response signals from mobile stations can be code-multiplexed. That is, three Walsh sequences are required amongst four Walsh sequences with a sequence length of 4, and therefore one Walsh sequence is nőt used.
[0013] Also,the1 SC-FDMAsymbol shown in FIG.1 may be referred to as 1 LB (Long Block). Therefore, a spreading code sequence that is used in spreading in Symbol units or LB units, is referred to as a block-wise spreading code sequence.
[0014] Alsó, studies are underway to define eighteen PUCCH’s as shown in FIG.2. Normally, the orthogonality of response signals does nőt collapse between mobile stations using different block-wise spreading code sequences, as long as the mobile stations do nőt move fást. Bút, especially if there is a large difference of received power between response signals from a plurality of mobile stations at a base station,, one response signal may be interfered with by another response signal between mobile stations using the same block-wise spreading code sequence. Fór example, in FIG.2, a response signal using PUCCH #1 (cyclic shift value = 2) may be interfered with by a response signal using PUCCH #0 (cyclic shift value = 0).
[0015] Alsó, studies are underway to use the constellation shown in FIG.3 when BPSK is used as the modulation
EP 2 207 289 Β1 scheme fór response signals, and the constellation shown in FIG.4 when QPSK is used as the modulation scheme fór response signals (see Non-Patent Document 3).
Non-Patent Document 1: Implicit Resource Allocation of ACK/NACK Signal in E-UTRA Uplink (ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/TSGR1_49/Docs/R1-07243 9.zip)
Non-Patent Document 2: Multiplexing capability of CQIs and ACK/NACKs form different UEs (ftp://ftp.3gpp.org/TSG_RAN/WG1_RL1/TSGR1_49/Docs/R1-072315.zip)
Non-Patent Document 3: 3GPP TS 36.211 V8.0.0, Physical Channels and Modulation (Release 8), Sep. 2007 (ftp://ftp.3gpp.org/Specs/2007-09/Rel-8/36_series/36211-800.zip)
Disclosure of Invention
Problems to be Solved by the Invention [0016] An example case will be described below where the constellation shown in FIG.3 is used to modulate a response signal. Alsó, an example case will be described below where one mobile station #1 transmits a response signal using PUCCH #1 (in FIG.2) and another mobile station #2 transmits a response signal using PUCCH #0 (in FIG.2). In this case, the base station performs the above-described correlation Processing to distinguish between the response signal from mobile station #1 and the response signal from mobile station #2. At this time, components of the response signal from mobile station #2 may leak in the correlation output to récéivé the response signal of mobile station #1, and interfere with the response signal of mobile station #1.
[0017] Then, when mobile station #1 and mobile station #2 both transmit an ACK and the base station receives the response signal from mobile station #1, interference given from the response signal of mobile station #2 to the response signal of mobile station #1 is as follows.
[0018] That is, when the ACK and reference signal transmitted from mobile station #1 are received by the base station v ia a channel, in the base station, a response signal represented by (-1 -j)h1/Ö2 and reference signal represented by (1 +j)h 1 /42 are found as a correlation output of mobile station #1. Here, h1 is an effective channel in a case where the signals from mobile station #1 pass a channel between mobile station #1 and the base station, and are found, as a correlation output, in the detection window fór mobile station #1 in the base station.
[0019] Alsó, when the ACK and reference signal transmitted from mobile station #2 are received by the base station via a channel, in the base station, a component represented by (-1 -j)h2/Ó2 is found as interference to the response signal of mobile station #1 and a component represented by (1 +j)h2/\2 is found as interference to the reference signal of mobile station #1 in the correlation output of mobile station #1. Here, h2 is an effective channel in a case where the signals from mobile station #2 passes a channel between mobile station #2 and the base station, and leak, as the correlation output, in the detection window fór mobile station #1 in the base station.
[0020] When there is little delay on a channel and no transmission timing difference at a mobile station, such a leak does nőt occur. Bút, depending on conditions, h2 may be non-negligibly high fór h1. Therefore, when an ACK from mobile station #1 and ACKfrom mobile station #2 are code-multiplexed, in the base station, a response signal represented by (-1 -j)(h1 +h2)/é2 and reference signal represented by (1 +j)(h 1 +h2)/é2 are found in the correlation output of mobile station #1.
[0021] Therefore, the interference component given from the ACK of mobile station #2 to the ACK of mobile station #1 (i.e. the Euclidean distancefrom (-1 -j)/Ö2) by the synchronous detection in the base station, is represented by equation 1. That is, when both mobile station #1 and mobile station #2 transmit an ACK, there is no inter-code interference between the ACK of mobile station #1 and the ACK of mobile station #2.
[1]
<img file="HUE030438T2_D0001.tif" />
= 0... (Equation 1) [0022] Alsó, when mobile station #1 transmits a NACK, mobile station #2 transmits an ACK and the base station receives the response signal from mobile station #1, interference from the response signal of mobile station #2 to the response signal #1 is as follows.
[0023] That is, when the NACK and reference signal transmitted from mobile station #1 are received by the base station via a channel, in the base station, a response signal represented by (1 +j)h 1/Ö2 and reference signal represented by (1 +j)h 1Ó2 are found as a correlation output of mobile station # 1.
[0024] Alsó, when the ACK and reference signal transmitted from mobile station #2 are received by the base station
ΕΡ 2 207 289 Β1 via a channel, in the base station, a component represented by (-1 -j)h2/Ü2 isfound as interference to the response signal of mobile station #1 and a component represented by (1 +j)h2/\2 is found as interference to the reference signal of mobile station #1 in the correlation output of mobile station #1.
[0025] Therefore, when the NACK from mobile station #1 and the ACK from mobile station #2 are code-multiplexed, in the base station, a response signal represented by (1+j)(h1-h2)/72and reference signal represented by (1+j)(h1+h2)/72 are found in the correlation output of mobile station #1.
[0026] Therefore, the interference component given from the ACK of mobile station #2 to the NACK of mobile station #1 (i.e. the Euclideán distancefrom (1 +j)/72) by the synchronousdetection in the base station, is represented by equation 2. That is, when mobile station #1 transmits a NACK and mobile station #2 transmits an ACK, significant inter-code interference may be given from the ACK of mobile station #2 to the NACK of mobile station #1.
[2] (1 + 7)
A,-A? A, + A<sub>2 ?</sub> + 7)
2h,
...(Equation 2) [0027] Similarly, when mobile station #1 and mobile station #2 both transmit a NACK signal, as shown in equation 3, inter-code interference does nőt occur between the NACK of mobile station #1 and the NACK of mobile station #2. Alsó, when mobile station #1 transmits an ACK and mobile station #2 transmits a NACK, as shown in equation 4, significant inter-code interference may be given from the NACK of mobile station #2 to the ACK of mobile station # 1.
[3] [4] (1 + 7) /
1h<sub>2</sub>' *, + *2, = 0...(Equation 3) (1 + 7)f <sub>}</sub> ~h,+h<sub>2</sub><sup>y </sup>72 t a,+a<sub>2</sub> , (1 + 7) ' -2h<sub>2</sub>
Λ + <sup>Λ</sup>2
...(Equation 4) [0028] Here, taking intő account that ARQ is applied to downlink data, 3GPP-LTE defines that the target error rate per downlink data transmission is around 1 to 10%. That is, in ARQ of downlink data, the ACK occurrence rate is significantly higher than the NACK occurrence rate. Fór example, in a mobile communication system in which the target error rate per downlink data transmission is set to 10%, the ACK occurrence rate is 90%, while the NACK occurrence rate is 10%. Therefore, in the above example, there is a high possibility that a response signal of mobile station #2 that interferes with a response signal of mobile station #1 is an ACK. That is, there is a high possibility that, when mobile station #1 transmits a NACK, significant inter-code interference (represented by equation 2) is given from a response signal of mobile station #2 to this NACK, while there is a low possibility that, when mobile station #1 transmits an ACK, significant inter-code interference (represented by equation 4) is given from a response signal of mobile station #2 to this ACK. That is, there is a possibility that a NACK is more influenced by interference than an ACK. Consequently, the possibility of an increased error rate by interference becomes larger in a NACK than an ACK. Therefore, up till now, there is a possibility that a large difference is produced between NACK received quality and ACK received quality and a NACK is received in much poorer quality than an ACK.
[0029] The document fór discussion and decision titled, Signaling parameters fór UL ACK/NACK resources, 3GPP TSG RAN WG 1 Meeting #50, R1-073616, on August20, 2007 discusses signaling parameters fór uplink ACK/NACK, and proposes to signal most of the parameters implicitly to achieve the effect of inter-cell interference randomization. [0030] In viewofthe above, it is therefore an objectofthe present invention to provide a rádió communication apparátus and constellation control method that can make ACK received quality and NACK received quality equal.
Means fór Solving the Problem [0031] The rádió communication apparátus of the present invention employs a configuration having: according to claim 1.
ΕΡ 2 207 289 Β1 [0032] The constellation control method of the present invention includes the features of claim 15.
Advantageous Effect of Invention [0033] According to the present invention, it is possible to make ACK received quality and NACK received quality equal.
Brief Description of Drawings [0034]
FIG.1 is a diagram showing a spreading method of a response signal and reference signal (prior art);
FIG.2 is a diagram showing the definition of PUCCH (prior art);
FIG.3 illustrates a BPSK constellation (prior art);
FIG.4 illustrates a QPSK constellation (prior art);
FIG.5 is a block diagram showing the configuration of a base station according to Embodiment 1 of the present invention;
FIG.6 is a block diagram showing the configuration of a mobile station according to Embodiment 1 of the present invention;
FIG.7 is a diagram showing a constellation change according to Embodiment 1 of the present invention;
FIG.8 illustrates a BPSK constellation according to Embodiment 1 of the present invention;
FIG.9 illustrates a QPSK constellation according to Embodiment 1 of the present invention;
FIG.10 is a diagram showing scrambling Processing according to Embodiment 1 of the present invention;
FIG.11 is a diagram showing a constellation change according to Embodiment 2 of the present invention;
FIG.12 is a block diagram showing the configuration of a mobile station according to Embodiment 3 of the present invention;
FIG.13 is a diagram showing scrambling Processing according to Embodiment 4 of the present invention;
FIG.14 is a block diagram showing the configuration of a mobile station according to Embodiment 4 of the present invention;
FIG.15 is a diagram showing a constellation change according to Embodiment 5 of the present invention;
FIG.16 is a diagram showing a constellation change according to Embodiment 6 of the present invention;
FIG.17 illustrates a BPSK constellation according to Embodiment 6 of the present invention;
FIG.18 illustrates a BPSK constellation according to Embodiment 6 of the present invention;
FIG.19 illustrates a QPSK constellation according to Embodiment 6 of the present invention;
FIG.20 illustrates a QPSK constellation according to Embodiment 6 of the present invention;
FIG.21 illustrates a QPSK constellation according to Embodiment 8 of the present invention;
FIG.22 is a diagram showing a Q-axis amplitude in a case where the synchronous detection output of mobile station #1 is rotated to the right direction by 45 degrees, according to Embodiment 9 of the present invention; and FIG.23 is a diagram showing a Q-axis amplitude in a case where the synchronous detection output of mobile station #1 is rotated to the right direction by 45 degrees when all mobile stations use the same constellation.
Best Mode fór Carrying out the Invention [0035] Embodiments of the present invention will be explained below in detail with reference to the accompanying drawings.
(Embodiment 1) [0036] FIG.5 illustrates the configuration of base station 100 according to the present invention, and FIG.6 illustrates the configuration of mobile station 200 according to the present embodiment.
[0037] Here, to avoid complicated explanation, FIG.5 illustrates components associated with transmission of downlink data and components associated with reception of uplink response signals to downlink data, which are closely related to the present invention, and i11ustration and explanation of the components associated with reception of uplink data will be omitted. Similarly, FIG.6 illustrates components associated with reception of downlink data and components associated with transmission of uplink response signals to downlink data, which are closely related to the present invention, and illustration and explanation of the components associated with transmission of uplink data will be omitted.
[0038] Alsó, a case will be described with the following explanation, where ZAC sequences are used forfirst spreading and block-wise spreading code sequences are used fór second spreading. Here, forfirst spreading, it is equally possible to use sequences, which can be separated from each other because of different cyclic shift values, other than ZAC
EP 2 207 289 Β1 sequences. Fór example, fór first spreading, it is possible to use a GCL (Generated Chip like) sequence, CAZAC (Constant Amplitude Zero Autó Correlation) sequence, ZC (Zadoff-Chu) sequence or PN sequence such as a M sequence and orthogonal Gold code sequence. Alsó, as block-wise spreading code sequences fór second spreading, it is possible to use any sequences as long as these sequences are orthogonal orsubstantially orthogonal to each other. Fór example, it is possible to use Walsh sequences orFourier sequences as block-wise spreading code sequences fór second spreading.
[0039] Alsó, in the following explanation, twelve ZAC sequences with sequence length of 12 and of cyclic shift values 0 to 11 are referred to as ZAC #0 to ZAC #11, and three block-wise spreading code sequences with a sequence length of 4 and of sequence numbers 0 to 2 are referred to as BW #0 to BW #3. Here, the present invention is nőt limited to these sequence lengths.
[0040] Alsó, in the following explanation, the PUCCH numbers are determined by the cyclic shift values of ZAC sequences and the sequence numbers of block-wise spreading code sequences. That is, a plurality of resources fór response signals are determined by ZAC #0 to ZAC #11, which can be separated from each other because of different cyclic shift values, and BW #0 to BW #2, which are orthogonal to each other.
[0041] Alsó, in the following explanation, the CCE numbers and the PUCCH numbers are associated on a one-to-one basis. That is, CCE #0 is mapped to PUCCH #0, CCE #1 is mapped to PUCCH #1, CCE #2 is mapped to PUCCH #2..., and so on.
[0042] In base station 100shown in FIG.5, control Information generating section 101 and mapping section 104 récéivé as input a resource allocation result of downlink data. Alsó, control Information generating section 101 and encoding section 102 receives as input a coding rate of control Information to report the resource allocation result of downlink data, on a per mobile station basis, as coding rate Information. Here, in the same way as above, the coding rate of the control Information is one of 2/3, 1/3, 1/6 or 1/12.
[0043] Control Information generating section 101 generates control Information to carry the resource allocation result, on a per mobile station basis, and outputs the control Information to encoding section 102. Control Information, which is provided per mobile station, includes mobile station ID Information to indicate to which mobile station the control Information is directed. Fór example, control Information includes, as mobile station ID Information, CRC bits masked by the ID number of the mobile station, to which control Information is reported. Further, according to the coding rate Information received as input, control Information generating section 101 allocates a L1/L2 CCH to each mobile station based on the number of CCE’s required to report the control Information, and outputs the CCE number corresponding to the allocated L1/L2 CCH to mapping section 104. Here, in the same way as above, a L1/L2 CCH occupies one CCE when the coding rate of control Information is 2/3. Therefore, a L1/L2 CCH occupies two CCE’s when the coding rate of control Information is 1/3, a L1/L2 CCH occupies four CCE’s when the coding rate of control Information is 1/6, and a L1/L2 CCH occupies eight CCE’s when the coding rate of control Information is 1/12. Alsó, in the same way as above, when one L1/L2 CCH occupies a plurality of CCE’s, the CCE’s occupied by the L1/L2 CCH are consecutive.
[0044] Encoding section 102 encodes control Information on a per mobile station basis according to the coding rate Information received as input, and outputs the encoded control Information to modulating section 103.
[0045] Modulating section 103 modulates the encoded control Information and outputs the result to mapping section 104.
[0046] On the other hand, encoding section 105 encodes the transmission data fór each mobile station (i.e. downlink data) and outputs the encoded transmission data to retransmission control section 106.
[0047] Upon initial transmission, retransmission control section 106 holds the encoded transmission data on a per mobile station basis and outputs the data to modulating section 107. Retransmission control section 106 holds transmission data until retransmission control section 106 receives as input an ACK of each mobile station from deciding section 117. Further, upon receiving as input a NACK of each mobile station from deciding section 117, that is, upon retransmission, retransmission control section 106 outputs the transmission data associated with that NACK to modulating section 107.
[0048] Modulating section 107 modulates the encoded transmission data received as input from retransmission control section 106, and outputs the result to mapping section 104.
[0049] Upon transmission of control Information, mapping section 104 maps the control Information received as input from modulating section 103 on a physical resource based on the CCE number received as input from control Information generating section 101, and outputs the result to IFFT section 108. That is, mapping section 104 maps control Information on the subcarrier corresponding to the CCE number in a plurality of subcarriers comprised of an OFDM Symbol, on a per mobile station basis.
[0050] On the other hand, upon transmission of downlink data, mapping section 104 maps the transmission data, which is provided on a per mobile station basis, on a physical resource based on the resource allocation result, and outputs the result to IFFT section 108. That is, based on the resource allocation result, mapping section 104 maps transmission data on a subcarrier in a plurality of subcarriers comprised ofan OFDM Symbol, on a per mobile station basis. [0051] IFFT section 108 generates an OFDM Symbol by performing an IFFT of a plurality of subcarriers on which
ΕΡ 2 207 289 Β1 control information ortransmission data is mapped, and outputsthe OFDM Symbol to CP (Cyclic Prefix) attaching section 109.
[0052] CP attaching section 109 attaches the same signal as the signal at the tail end part of the OFDM Symbol, to the head ofthe OFDM Symbol as a CP.
[0053] Rádió transmitting section 110 performs transmission Processing such as D/A conversion, amplification and up-conversion on the OFDM Symbol with a CP and transmits the resultfrom antenna 111 to mobile station 200 (in FIG.6). [0054] On the other hand, rádió receiving section 112 receives a response signal or reference signal transmitted from mobile station 200 (in FIG.6), via antenna 111, and performs receiving Processing such as down-conversion and A/D conversion on the response signal or reference signal.
[0055] CP removing section 113 removes the CP attached to the response signal or reference signal subjected to receiving Processing.
[0056] Despreading section 114 despreads the response signal by a block-wise spreading code sequence that is used fór second spreading in mobile station 200, and outputs the despread response signal to correlation Processing section 115. Similarly, despreading section 114 despreads the reference signal by an orthogonal sequence that is used to spread the reference signal in mobile station 200, and outputs the despread reference signal to correlation Processing section 115. [0057] Correlation Processing section 115 finds the correlation value between the spread response signal, spread reference signal and ZAC sequence that is used fór first spreading in mobile station 200, and outputs the correlation value to descrambling section 116.
[0058] Descrambling section 116 descrambles the correlation value by the scrambling code associated with the cyclic shift value ofthe ZAC sequence, and outputs the descrambled correlation value to deciding section 117.
[0059] Deciding section 117 detects a response signal on a per mobile station basis, by detecting a correlation peak on a per mobile station basis using detection Windows. Fór example, upon detecting a correlation peak in the detection window fór mobile station #1, deciding section 117 detects a response signal from mobile station #1. Then, deciding section 117 decides whether the detected response signal is an ACK or NACK by the synchronous detection using the correlation value ofthe reference signal, and outputs the ACK or NACK to retransmission control section 106 on a per mobile station basis.
[0060] On the other hand, in mobile station 200 shown in FIG.6, rádió receiving section 202 receives the OFDM Symbol transmitted from base station 100 (in FIG.5), via antenna 201, and performs receiving Processing such as down-conversion and A/D conversion on the OFDM Symbol.
[0061] CP removing section 203 removes the CP attached to the OFDM Symbol subjected to receiving Processing. [0062] FFT (Fást Fourier Transform) section 204 acquires control information or downlink data mapped on a plurality ofsubcarriers by performing a FFT ofthe OFDM Symbol, and outputsthe control information or downlink data to extracting section 205.
[0063] Extracting section 205 and decoding section 207 receives as input coding rate information indicating the coding rate ofthe control information, that is, information indicating the number of CCE’s occupied by a L1 /L2 CCH.
[0064] Upon reception ofthe control information, based on the coding rate information, extracting section 205 extracts the control information from the plurality ofsubcarriers and outputs it to demodulating section 206.
[0065] Demodulating section 206 demodulates the control information and outputs the demodulated control information to decoding section 207.
[0066] Decoding section 207 decodes the control information based on the coding rate information received as input, and outputs the decoded control information to deciding section 208.
[0067] On the other hand, upon receiving the downlink data, extracting section 205 extracts the downlink data directed to the mobile station from the plurality of subcarriers, based on the resource allocation result received as input from deciding section 208, and outputs the downlink data to demodulating section 210. This downlink data is demodulated in demodulating section 210, decoded in decoding section 211 and received as input in CRC section 212.
[0068] CRC section 212 performs an error detection of the decoded downlink data using a CRC, generates an ACK in the case of CRC=OK (i.e. when no error is found) and a NACK in the case of CRC=NG (i.e. when error is found), as a response signal, and outputs the generated response signal to modulating section 213. Further, in the case of CRC=OK (i.e. when no error is found), CRC section 212 outputs the decoded downlink data as received data.
[0069] Deciding section 208 performs a blind detection of whether or nőt the control information received as input from decoding section 207 is directed to the mobile station. Fór example, deciding section 208 decides that, if CRC=OK is found (i.e. if no error is found) as a result of demasking by the ID number of the mobile station, the control information is directed to the mobile station. Further, deciding section 208 outputs the control information fór the mobile station, that is, the resource allocation result of downlink data fór the mobile station, to extracting section 205.
[0070] Further, deciding section 208 decides a PUCCH to use to transmit a response signal from the mobile station, from the CCE number associated with subcarriers on which the control information directed to the mobile station is mapped, and outputs the decision result (i.e. PUCCH number) to control section 209. Fór example, in the same way as above, when the CCE corresponding to subcarriers, on which control information directed to the mobile station is mapped,
ΕΡ 2 207 289 Β1 is CCE #0, deciding section 208 decides PUCCH #0 associated with CCE #0 as the PUCCH fór the mobile station. Alsó, fór example, when CCE’s corresponding to subcarriers on which control Information directed to the mobile station is mapped are CCE #0 to CCE #3, deciding section 208 decides PUCCH #0 associated with CCE #0, which is the smallest number in CCE #0 to CCE #3, as the PUCCH fór the mobile station, and, when CCE’s corresponding to subcarriers on which control information directed to the mobile station is mapped are CCE #4 to CCE #7, deciding section 208 decides PUCCH #4 associated with CCE #4, which is the smallest number in CCE #0 to CCE #3, as the PUCCH fór the mobile station.
[0071] Based on the PUCCH number received as input from deciding section 208, control section 209 Controls the cyclic shift value of a ZAC sequence that is used forfirst spreading in spreading section 215 and a block-wise spreading code sequence that is used forsecond spreading in spreading section 218. That is, control section 209 selects a ZAC sequence of the cyclic shift value corresponding to the PUCCH number received as input from deciding section 208, amongst ZAC #0 to ZAC #11, and sets the selected ZAC sequence in spreading section 215, and selects the blockwise spreading code sequence corresponding to the PUCCH number received as input from deciding section 208, amongst BW #0 to BW #2, and sets the selected block-wise spreading code sequence in spreading section 218. That is, control section 209 selects one of a plurality of resources defined by ZAC #0 to ZAC #11 and BW #0 to BW #2. Alsó, control section 209 reports the selected ZAC sequence to scrambling section 214.
[0072] Further, control section 209 Controls a block-wise spreading code sequence that is used forsecond spreading in spreading section 223. That is, control section 209 sets the block-wise spreading code sequence corresponding to the PUCCH number received as input from deciding section 208, in spreading section 223.
[0073] Modulating section 213 modulates the response signal received as input from CRC section 212 and outputs the result to spreading section 214. Modulation Processing in modulating section 213 will be described later in detail. [0074] Scrambling section 214 multiplies the modulated response signal (i.e. response Symbol) by a scrambling code 1 or β<sup>_</sup>Κ<sup>π/2</sup>) depending on to the ZAC sequence selected in control section 209, and outputs the response signal multiplied by the scrambling code to spreading section 215. Here, by multiplication of the scrambling code e’iW<sup>2</sup>, the constellation of the response signal is rotated by -90 degrees. Thus, scrambling section 214 functions as a rotation means to rotate the constellation of a response signal. Scrambling Processing in scrambling section 214 will be described later in detail.
[0075] Spreading section 215 performs first spreading of the response signal and reference signal (i.e. reference Symbol) by the ZAC sequence set in control section 209, and outputs the response signal subjected to first spreading to IFFT section 216 and the reference signal subjected to first spreading to IFFT section 221.
[0076] IFFT section 216 performs an IFFT ofthe response signal subjected to first spreading, and outputs the response signal subjected to IFFT to CP attaching section 217.
[0077] CP attaching section 217 attaches the same signal as the signal at the tail end part of the response signal subjected to an IFFT, to the head ofthe response signal as a CP.
[0078] Spreading section 218 performs second spreading ofthe response signal with a CP by the block-wise spreading code sequence set in control section 209, and outputs the response signal subjected to second spreading, to multiplexing section 219.
[0079] IFFT section 221 performs an IFFT ofthe reference signal subjected to first spreading, and outputs the reference signal subjected to IFFT to CP attaching section 222.
[0080] CP attaching section 222 attaches the same signal as the signal at the tail end part of the reference signal subjected to IFFT, to the head ofthe reference signal.
[0081] Spreading section 223 performs second spreading ofthe reference signal with a CP by the block-wise spreading code sequence set in control section 209, and outputs the reference signal subjected to second spreading, to multiplexing section 219.
[0082] Multiplexing section 219 time-multiplexes the response signal subjected to second spreading and the reference signal subjected to second spreading in one siót, and outputs the result to rádió transmitting section 220.
[0083] Rádió transmitting section 220 performs transmission Processing such as D/A conversion, amplification and up-conversion on the response signal subjected to second spreading orthe reference signal subjected to second spreading, and transmits the resulting signal from antenna 201 to base station 100 (in FIG.5).
[0084] Next, modulation Processing in modulating section 213 and scrambling Processing in scrambling section 214 will be explained in detail.
[0085] In a plurality of response signalssubjectto second spreading by the same block-wise spreading code sequence, inter-code interference on the cyclic shift axis is the largest between the response signals that are located on the closest positions to each other on the cyclic shift axis. Fór example, in six response signals subject to second spreading by BW #0 in FIG.2, the response signal that is transmitted using PUCCH #1 is subject to the largest interference from the response signal that is transmitted using PUCCH #0 and the response signal that is transmitted using PUCCH #2. [0086] Alsó, the ACK occurrence rate is significantly higher than the NACK occurrence rate, and, consequently, when a NACK is transmitted using an arbitrary PUCCH, there is a high possibility that a response signal that gives interference
ΕΡ 2 207 289 Β1 to the PUCCH is an ACK. Therefore, to improve the error rate performance of a NACK, it is im portant to reduce interference from an ACK.
[0087] With the present embodiment, as shown in FIG.7, the constellation of each response signal is rotated on the cyclic shit axis.
[0088] To be more specific, referring to six response signals subject to second spreading by BW #0 in FIG.7, the constellation acquired by rotating the constellation of a response signal that is transmitted using PUCCH #0, by -90 degrees, is used as the constellation of a response signal that is transmitted using PUCCH #1, and the constellation acquired by rotating the constellation of the response signal that is transmitted using PUCCH #1, by +90 degrees, is used as the constellation of a response signal that is transmitted using PUCCH #2. The same applies to PUCCH #2 to PUCCH #5. Fór example, when the modulation scheme of response signals is BPSK, constellation #1 of PUCCH #0, PUCCH #2 and PUCCH #4 is as shown in FIG.3, while constellation #2 of PUCCH #1, PUCCH #3 and PUCCH #5 is as shown in FIG.8. Alsó, fór example, when the modulation scheme of response signals is QPSK, constellation #1 of PUCCH #0, PUCCH #2 and PUCCH #4 is as shown in FIG.4, while constellation #2 of PUCCH #1, PUCCH #3 and PUCCH #5 is as shown in FIG.9.
[0089] Thus, according to the present embodiment, in ZAC #0, ZAC #2, ZAC #4, ZAC #6, ZAC #8 and ZAC #10 that are used fór first spreading of response signals subject to second spreading by BW #0, response signals subject to first spreading by ZAC #0, ZAC #4 and ZAC #8 form the first response signal group, and response signals subject to first spreading by ZAC #2, ZAC #6 and ZAC #10 form the second response signal group. That is, according to the present embodiment, the response signals belonging to the first response signal group and the response signals belonging to the second response signal group are alternately allocated on the cyclic shift axis. While the constellation of the first response signal group is referred to as constellation #1 (in FIG.3 and FIG.4), the constellation of the second response signal group is referred to as constellation #2 (in FIG.8 and FIG.9). That is, according to the present embodiment, the constellation of the second response signal group is rotated by -90 degrees with respect to the constellation of the first response signal group.
[0090] Alsó, according to the present embodiment, as shown in FIG.10, the rotation of constellation is performed by scrambling Processing in scrambling section 214.
[0091] That is, when the modulation scheme of response signals is BPSK, modulating section 213 modulates the response signals using constellation #1 shown in FIG.3. Therefore, the signal point of an ACK is (-1/92, -1/92), and the signal point of a NACK is (1/92, 1/92). Alsó, the signal point of a reference signal received as input from spreading section 215 is the same as the signal point of a NACK, (1/92, 1/92).
[0092] Then, in response signals subject to second spreading using BW #0, scrambling section 214 multiplies a response signal subject to first spreading using ZAC #0, ZAC #4 or ZAC #8 by scrambling code 1, and multiples a response signal subject to first spreading using ZAC #2, ZAC #6 or ZAC #10 by scrambling code Therefore, fór the response signal subject to first spreading by ZAC #0, ZAC #4 or ZAC #8, the signal point of an ACK is (-1/92, -1/92) and the signal point of a NACK is (1/92, 1/92). That is, the constellation of the response signal. subject to first spreading by ZAC #0, ZAC #4 orZAC#8 is constellation #1 (in FIG.3). On the other hand, fór the response signal subject to first spreading by ZAC #2, ZAC #6 or ZAC #10, the signal point of an ACK is (-1/92, 1/92) and the signal point of a NACK is (1/92, -1/92). That is, the constellation of the response signal subject to first spreading by ZAC #2, ZAC #6 or ZAC # 10 is constellation #2 (in FIG.8).
[0093] Thus, according to the present embodiment, by scrambling Processing in scrambling section 214, the constellation of the second response signal group is rotated by -90 degrees with respect to the constellation of the first response signal group.
[0094] As described above, an example case will be described below where mobile station #1 transmits a response signal using PUCCH #1 (in FIG.7) and another mobile station #2 transmits a response signal using PUCCH #0 (in FIG.7). Here, constellation #2 (in FIG.8) is used fór the response signal of mobile station #1, and constellation #1 (in FIG.3) is used fór the response signal of mobile station #2.
[0095] When mobile station #1 and mobile station #2 both transmit an ACK and the base station receives the response signal from mobile station #1, interference given from the response signal of mobile station #2 to the response signal of mobile station #1 is as follows.
[0096] That is, when the ACK and reference signal transmitted from mobile station #1 are received by the base station via a channel, in the base station, a response signal represented by (-1 +j)h1/92 and reference signal represented by (1 +j)h 1 /92 are found as a correlation output of mobile station #1.
[0097] Alsó, when the ACK and reference signal transmitted from mobile station #2 are received by the base station via a channel, in the base station, a component represented by (-1 -j)h2/92 is found as interference to the response signal of mobile station #1 and a component represented by (1 +j)h2/92 is found as interference to the reference signal of mobile station #1 in the correlation output of mobile station #1.
[0098] Therefore, when the ACK from mobile station #1 and the ACK from mobile station #2 are code-multiplexed, in the base station, a response signal represented by (1 +j)(jh 1 -h2)/92 and reference signal represented by (1 +j)(h1 +h2)/92
ΕΡ 2 207 289 Β1 are found in the correlation output of mobile station #1.
[0099] Therefore, the interference component given from the ACK of mobile station #2 to the ACK of mobile station #1 (i.e. the Euclideán distancefrom (-1 +j)A/2) by thesynchronousdetection in the base station, is represented by equation 5.
[5]
O + OÍ- jhy~<sup>h</sup>2 72 <sub>ς</sub> h<sub>}</sub>+h<sub>2</sub> (1 + 7)
7Σ + 7)V /ι, + Λ<sub>2 ?</sub>
...(Equation 5) [0100] Alsó, when mobile station #1 transmits a NACK, mobile station #2 transmits an ACK and the base station receives the response signal from mobile station #1, interference given from the response signal of mobile station #2 to the response signal of mobile station #1 is as follows.
[0101] That is, when the NACK and reference signal transmitted from mobile station #1 are received by the base station via a channel, in the base station, a response signal represented by (1 -j)h 1/72 and reference signal represented by (1 +j)h1/72 are found as a correlation output of mobile station #1.
[0102] Alsó, when the ACK and reference signal transmitted from mobile station #2 are received by the base station via a channel, in the base station, a component represented by (-1 -j)h2/72 is found as interference to the response signal of mobile station #1 and a component represented by (1 +j)h2/72 is found as interference to the reference signal of mobile station #1 in the correlation output of mobile station #1.
[0103] Therefore, when the NACK from mobile station #1 and the ACK from mobile station #2 are code-multiplexed, in the base station, a response signal represented by (1 +j)(-jh1 +h2)/72 and reference signal represented by (1 +j)(h 1 +h2)/72 are found in the correlation output of mobile station #1.
[0104] Therefore, the interference component given from the ACK of mobile station #2 to the NACK of mobile station #1 (i.e. the Euclidean distancefrom (1 -j)/72) by thesynchronousdetection in the base station, is represented by equation 6. [6] (1 + 7)
7^
-7-Λ ~<sup>h</sup>2 h<sub>}</sub>+h<sub>2</sub> (1 + 7)
7Σ
0-7)¼ h, +h,
...(Equation 6) [0105] Similarly, according to the present embodiment, when both mobile station #1 and mobile station #2 transmit a NACK signal, the interference component given from the NACK of mobile station #2 to the NACK of mobile station #1 (i.e. the Euclidean distance from (1 -j)/72) by the synchronous detection in the base station, is as shown in equation 7. Alsó, according to the present invention, when mobile station #1 transmits an ACK and mobile station #2 transmits a NACK, the interference component given from the NACK of mobile station #2 to the ACK of mobile station #1 (i.e. the Euclidean distance from (-1 +j)/72) by the synchronous detection in the base station, is as shown in equation 8.
[7] (1 + 7) ,
-7¼ + ¼^ + h<sub>2</sub> , (1 + 7) f (-1-7)¼ 72 L a,+a<sub>2</sub>
...(Equation 7) [8] (1 + 7)
77¼ + h<sub>2 </sub>h, + h-y (1 + 7)
7Σ (-1 + 7)¼ //,+¼
...(Equation 8) [0106] When the interference components represented by equation 5 to equation 8 are compared, it is understood that the magnitudes of the interference components represented by equation 5 to equation 8 are the same. That is, according to the present embodiment, regardless ofthe ACK occurrence rate orthe NACK occurrence rate, it is possible to make the error rate of an ACK and the error rate of a NACK equal. Therefore, according to the present embodiment, it is possible to make ACK received quality and NACK received quality equal.
ΕΡ 2 207 289 Β1 [0107] Alsó, according to the present embodiment, scrambling section 214 may multiply a modulated response signal by a scrambling code of 1 or e^<sup>nl2</sup>\ and rotate the constellation ofthe second response signal group by +90 degrees with respect to the constellation ofthe first response signal group.
(Embodiment 2) [0108] With the present embodiment, fór example, while the constellation is rotated in cell #1 as shown in FIG.7, the constellation is rotated in cell #2 adjacent to cell #1 as shown in FIG.1 1. Therefore, fór example, referring to PUCCH #1, while constellation #2 (in FIG.8 and FIG.9) is used fór PUCCH #1 in cell #1, constellation #1 (in FIG.3 and FIG.4) is used fór PUCCH #1 in cell #2. Similarly, referring to PUCCH #2, while constellation #1 (in FIG.3 and FIG.4) is used fór PUCCH #2 in cell #1, constellation #2 (in FIG.8 and FIG.9) is used fór PUCCH #2 in cell #2.
[0109] That is, with the present invention, further to Embodiment 1, between two adjacent cells, the constellation of one of two response signals subject to first spreading by ZAC sequences ofthe same cyclic shift value, is rotated by 90 degrees with respect to the constellation of the other response signal.
[0110] By this means, between a plurality of adjacent cells, it is possible to randomize interference between a plurality of response signals subject to first spreading by ZAC sequences ofthe same cyclic shift value. That is, according to the present embodiment, it is possible to randomize and reduce inter-cell interference between response signals.
(Embodiment 3) [0111] With the present embodiment, the constellation is rotated upon modulation of response signals.
[0112] FIG.12 illustrates the configuration of mobile station 400 according to the present embodiment. Here, in FIG. 12, the same components as in FIG.6 (Embodiment 1) will be assigned the same reference numerals and their explanation will be omitted.
[0113] In mobile station 400, a ZAC sequence selected in control section 209 is reported to modulating section 401. [0114] Then, in response signals subject to second spreading using BW #0 shown in FIG.7, modulating section 401 modulates a response signal subject to first spreading by ZAC #0, ZAC #4 or ZAC #8 (i.e. first response signal group) using constellation #1 (in FIG.3 and FIG.4), and modulates a response signal subject to first spreading by ZAC #2, ZAC #6 or ZAC #10 (i.e. second response signal group) using constellation #2 (in FIG.8 and FIG.9).
[0115] Thus, according to the present embodiment, upon modulation Processing in modulating section 401, the constellation of the second response signal group is rotated by 90 degrees with respect to the constellation of the first response signal group. That is, according to the present embodiment, modulating section 401 functions as a modulating means that modulates a response signal and as a rotating means that rotates the constellation ofthe response signal. Therefore, the present embodiment does nőt require scrambling section 214 (in FIG.6) and descrambling section 116 (in FIG.5) in Embodiment 1.
[0116] Thus, by performing rotation Processing in modulating section 401 instead of scrambling section 214, it is possible to achieve the same effect as in Embodiment 1.
(Embodiment 4) [0117] Embodiments 1 to 3 rotate the constellation of a response signal without changing the constellation of a reference signal. By contrast with this, as shown in FIG.13, the present embodiment rotates the constellation of a reference signal without changing the constellation of a response signal.
[0118] FIG. 14 illustrates the configuration of mobile station 600 according to the present embodiment. Here, in FIG. 14, the same components as in FIG.6 (Embodiment 1) will be assigned the same reference numerals and their explanation will be omitted.
[0119] In mobile station 600, when the modulation scheme of response signals is BPSK, scrambling section 214 multiplies a reference signal subject to first spreading using ZAC #0, ZAC #4 orZAC #8 by 1, and multiples a reference signal subject to first spreading using ZAC #2, ZAC #6 orZAC # 10 by ei(<sup>nl2</sup>'>. Therefore, the signal point of a reference signal subject to first spreading by ZAC #0, ZAC #4 or ZAC #8 is (1/Ú2, 1/Ú2), and the signal point of a reference signal subject to first spreading by ZAC #2, ZAC #6 or ZAC #10 is (1/Ú2, -1/Ú2).
[0120] Thus, by scrambling Processing in scrambling section 214, the present embodiment rotates the constellation of a reference signal fór the second response signal group by -90 degrees with respect to the constellation of a reference signal fór the first response signal group.
[0121] Thus, by performing rotation Processing ofthe constellation of a reference signal in scrambling section 214, it is equally possible to achieve the same effect as in Embodiment 1.
[0122] Alsó, according to the present embodiment, scrambling section 214 may multiply a reference signal by a scrambling code of 1 or βί(<sup>π/2</sup>), and rotate the constellation of a reference signal fór the first response signal group
ΕΡ 2 207 289 Β1 by +90 degrees with respect to the constellation of a reference signal fór the second response signal group.
(Embodiment 5) [0123] If there is a large difference of received power between response signals from a plurality of mobile stations in a base station, response signals ofthe higher received power may interfere with response signals ofthe lower received power. Fór example, in response signals subject to second spreading using BW #0 shown in FIG.15, when the received power of a response signal that is transmitted using PUCCH #0 and received powerof a response signal that is transmitted using PUCCH #3 are higher, and the received power of response signals that are transmitted using the other PUCCH’s are lower, the response signal that is transmitted using PUCCH #0 and the response signal that is transmitted using PUCCH #3 give the largest interference to the response signals that are transmitted using the other PUCCH’s.
[0124] Therefore, in this case, in ZAC #0, ZAC #2, ZAC #4, ZAC #6, ZAC #8 and ZAC #10 that are used fór first spreading of response signals subject to second spreading using BW #0, the response signals subject to first spreading by ZAC #0 and ZAC #6 form the first response signal group, and the response signals subject to first spreading by ZAC #2, ZAC #4, ZAC #8 and ZAC #10 form the second response signal group. Then, while the constellation of the first response signal group is constellation #1 (in FIG.3 and FIG.4), the constellation ofthe second response signal group is constellation #2 (in FIG.8 and FIG.9). That is, the present embodiment rotates the constellation ofthe second response signal group of the lower received power by -90 degrees with respect to the constellation of the first response signal group ofthe higher received power.
[0125] Alsó, the present embodiment may rotate the constellation ofthe second response signal group ofthe lower received power by +90 degrees with respect to the constellation ofthe first response signal group ofthe higher received power.
[0126] Thus, according to the present embodiment, by rotating the constellation of a signal ofthe lower received power by 90 degrees with respect to the constellation of a response signal of the higher received power on the cyclic shift axis, it is possible to prevent an increased NACK error rate by inter-code interference from an ACK due to the received power difference, and, as in Embodiment 1, make the ACK error rate and NACK error rate equal.
(Embodiment 6) [0127] A case will be explained with the present embodiment where twelve PUCCH’s shown in FIG.16 are defined. [0128] In this case, referring to four response signals subject to second spreading by BW #0 in FIG.16, the constellation acquired by rotating the constellation of the response signal that is transmitted using PUCCH #0, by -90 degrees, is the constellation ofthe response signal that is transmitted using PUCCH #1, the constellation acquired by rotating the constellation of the response signal that is transmitted using PUCCH #1, by -90 degrees, is the constellation of the response signal that is transmitted using PUCCH #2, and the constellation acquired by rotating the constellation ofthe response signal that is transmitted using PUCCH #2, by -90 degrees, is the constellation ofthe response signal that is transmitted using PUCCH #3.
[0129] Fór example, when the modulation scheme of response signals is BPSK, constellation #1 in PUCCH #0 is as shown in FIG.3, constellation #2 in PUCCH #1 is as shown in FIG.8, constellation #3 in PUCCH #2 is as shown in FIG.17, and constellation #4 in PUCCH #3 is as shown in FIG.18. Alsó, when the modulation scheme of response signals is OPSK, constellation #1 in PUCCH #0 is as shown in FIG.4, constellation #2 in PUCCH #1 is as shown in FIG.9, constellation #3 in PUCCH #2 is as shown in FIG.19, and constellation #4 in PUCCH #3 is as shown in FIG.20.
[0130] Thus, the present embodiment rotates the constellation of each response signal by -90 degrees on the cyclic shift axis. That is, although two constellations are used in Embodiment 1, four constellations are used in the present embodiment. Therefore, according to the present embodiment, it is possible to further randomize interference between response signals than in Embodiment 1. That is, according to the present embodiment, it is further possible to make the ACK error rate and NACK error rate equal.
[0131] Alsó, the present embodiment may rotate the constellation of each response signal by +90 degrees on the cyclic shift axis.
(Embodiment 7) [0132] A case will be explained with the present embodiment where a base station detects that a mobile station fails to récéivé control information to carry the resource allocation result of downlink data.
[0133] The mobile station performs a blind detection of whether or nőt control information is directed to the mobile station as described above, and, consequently, if the mobile station fails to récéivé control information due to poor channel condition, the mobile station has no way of knowing whether or nőt downlink data directed to the mobile station has been transmitted from the base station. Therefore, in this case, the mobile station does nőt récéivé data nor transmit
EP 2 207 289 Β1 a response signal. Thus, when a response signal is nőt transmitted from the mobile station to the base station, the base station needs to detectwhether a response signal is nőt transmitted from the mobile station, in addition to decide whether the response signal is an ACK or a NACK.
[0134] Here, non-transmission of a response signal from a mobile station is referred to as DTX (discontinuous transmission).
[0135] Normally, a threshold decision is used to detect DTX. That is, the base station measures the received power of a PUCCH that is used to transmit a response signal from the mobile station, detect DTX if the received power is lower than a threshold, and decides that an ACK or a NACK is transmitted from the mobile station if the received power is equal to or higher than the threshold.
[0136] However, PUCCH’s are separated by using different cyclic shift values of ZAC sequences and block-wise spreading code sequences. If the delay in a channel is large, if the transmission timing of a mobile station involves error or if transmission power control involves error, interference is significant especially on the cyclic shift axis. Therefore, if the base station tries to decide whether or nőt DTX is detected by a threshold decision of power in these cases, decision error is caused due to interference of leaked power from another mobile station that transmits a response signal using the ZAC sequence of the adjacent cyclic shift value.
[0137] Fór example, if mobile station #1 transmits an ACK using ZAC #0 and mobile station #2 that should transmit a response signal using ZAC #1 fails to récéivé control Information and does nőt transmit a response signal, the power of the response signal from mobile station #1 may leak even after correlation Processing to detect a response signal from mobile station #2. In this case, a conventional technique cannot decide whether a response signal is transmitted using ZAC #1 or power leaks from ZAC #0.
[0138] Therefore, similarto Embodiment 1 (FIG.7), the present embodiment rotates the constellation of each response signal on the cyclic shift axis.
[0139] As in Embodiment 1, an example case will be described below where mobile station #1 transmits a response signal using PUCCH #1 (in FIG.7) and another mobile station #2 transmits a response signal using PUCCH #0 (in FIG.7). Alsó, an example case will be described below where the modulation scheme of response signals is BPSK. Here, constellation #2 (in FIG.8) is used fór a response signal of mobile station #1 and constellation #1 (in FIG.3) is used fór a response signal of mobile station #2.
[0140] When mobile station #1 and mobile station #2 both transmit an ACK and the base station receives the response signal from mobile station #1, interference given from the response signal of mobile station #2 to the response signal of mobile station #1 is as follows.
[0141] That is, when the ACK and reference signal transmitted from mobile station #1 are received by the base station via a channel, in the base station, a response signal represented by (-1 +j)h1/é2 and reference signal represented by (1 +j)h 1 /42 are found as a correlation output of mobile station #1.
[0142] Alsó, when the ACK and reference signal transmitted from mobile station #2 are received by the base station via a channel, in the base station, a component represented by (-1 -j)h2/é is found as interference to the response signal of mobile station #1 and a component represented by (1 +j)h2/\2 is found as interference to the reference signal of mobile station #1 in the correlation output of mobile station #1.
[0143] Therefore, when the ACK from mobile station #1 and ACK from mobile station #2 are code-multiplexed, in the base station, a response signal represented by (1 +j)(jh 1-h2)/Ö2 and reference signal represented by (1 +j)(h1 +h2)/é2 are found in the correlation output of mobile station #1. That is, in this case, the output of synchronous detection in the base station is as shown in equation 9.
[9] jh<sub>x</sub> - h<sub>2</sub>
... (Equation 9) [0144] Alsó, when mobile station #2 transmits an ACK and mobile station #1 fails to récéivé control Information and does nőt transmit a response signal, in the base station, a response signal represented by (1 +j)(-h2)/\2 and reference signal represented by (1 +j)(h2)/é2 are found in the correlation output of mobile station #1. Therefore, in this case, the output of synchronous detection in the base station is as shown in equation 10.
[10]
ΕΡ 2 207 289 Β1
...(Equation 10) [0145] Comparing equation 9 and equation 10, it is understood that, when a response signal is provided from mobile station #1, there are the quadrature component (i.e. the value on the Q axis or complex component) and in-phase component (i.e. the value on the I axis or reál number component) in the synchronous detection output, while, when a response signal is nőt provided from mobile station #1, there is no quadrature component bút is only the in-phase component in the synchronous detection output.
[0146] Alsó, another example case will be described where mobile station #1 transmits a response signal using PUCCH #2 (in FIG.7) and another mobile station #2 transmits a response signal using PUCCH #1 (in FIG.7). Here, constellation #1 (in FIG.3) is used fór the response signal of mobile station #1 and constellation #2 (in FIG.8) is used fór the response signal of mobile station #2.
[0147] When mobile station #1 and mobile station #2 both transmit an ACK and the base station receives the response signal from mobile station #1, interference given from the response signal of mobile station #2 to the response signal of mobile station #1 is as follows.
[0148] That is, when the ACK and reference signal transmitted from mobile station #1 are received by the base station via a channel, in the base station, a response signal represented by (-1-j)h1A/2 and reference signal represented by (1 +j)h 11^2 are found as a correlation output of mobile station #1.
[0149] Alsó, when the ACK and reference signal transmitted from mobile station #2 are received by the base station via a channel, in the base station, a component represented by (-1 +j)h2/A/2 is found as interference to the response signal of mobile station #1 and a component represented by (1 +j)h2/\2 is found as interference to the reference signal of mobile station #1 in the correlation output of mobile station #1.
[0150] Therefore, when the ACK from mobile station #1 and ACK from mobile station #2 are code-multiplexed, in the base station, a response signal represented by (1 +j)(-h1 +jh2)/Ú2 and reference signal represented by (1 +j)(h1 +h2)/Ú2 are found in the correlation output of mobile station # 1. That is, in this case, the output of synchronous detection in the base station is as shown in equation 11.
[11] ~ A + jh<sub>2</sub> h\+h<sub>2</sub> ...(Equation 11) [0151] Alsó, when mobile station #2 transmits an ACK and mobile station #1 fails to récéivé control Information and does nőt transmit a response signal, in the base station, a response signal represented by (1 +j)(jh2)/Ú2 and reference signal represented by (1 +j)(h2)/A/2 are found in the correlation output of mobile station # 1. Therefore, in this case, the output of synchronous detection in the base station is as shown in equation 12.
[12]
<img file="HUE030438T2_D0002.tif" />
...(Equation 12) [0152] Comparing equation 11 and equation 12, it is understood that, when a response signal is provided from mobile station #1, there are the quadrature component and in-phase component in the synchronous detection output, while, when a response signal is nőt provided from mobile station #1, there is no quadrature component bút is only the inphase component in the synchronous detection output.
[0153] Therefore, according to the present embodiment, a base station can decide whether or nőt DTX is detected fór a response signal from a mobile station, based on one ofthe magnitudeof the in-phase component and the magnitude of the quadrature component in the synchronous detection output. Alsó, a response signal that is transmitted from a mobile station using the ZAC sequence of an adjacent cyclic shift value, does nőt have a negative effect on the detection of DTX, so that, even when there is significant interference from a response signal transmitted from the mobile station using the ZAC sequence of the adjacent cyclic shift value, it is possible to identify DTX accurately.
ΕΡ 2 207 289 Β1 (Embodiment 8) [0154] Similar to Embodiment 7, a case will be explained with the present embodiment where a base station detects that a mobile station fails to récéivé control information to report a resource allocation result of downlink data.
[0155] Here, an example case will bedescribed with the present embodimentwhere the modulation schemeof response signals is QPSK. Alsó, as in Embodiment 1, an example case will be described where mobile station #1 transmits a response signal using PUCCH #1 (in FIG.7) and another mobile station #2 transmits a response signal using PUCCH #0 (in FIG.7). Alsó, with the present embodiment, constellation #2 (in FIG.21) is used fór the response signal of mobile station #1 and constellation #1 (in FIG.4) is used fór the response signal of mobile station #2.
[0156] When mobile station #1 and mobile station #2 both transmit a ACK/ACK and the base station receives the response signal from mobile station #1, interference given from the response signal of mobile station #2 to the response signal of mobile station #1 is as follows.
[0157] That is, when the ACK/ACK and reference signal transmitted from mobile station #1 are received by the base station via a channel, in the base station, a response signal represented -h1 and reference signal represented by (1+j)h1/é2 are found as a correlation output of mobile station # 1.
[0158] Alsó, when the ACK/ACK and reference signal transmitted from mobile station #2 are received by the base station via a channel, in the base station, a component represented by (-1 -j)h2/\2 is found as interference to the response signal of mobile station #1 and component represented by (1 +j)h2/é2 is found as interference to the reference signal of mobile station #1 in the correlation output of mobile station #1.
[0159] Therefore, when the ACK/ACK from mobile station #1 and ACK/ACK from mobile station #2 are codemultiplexed, in the base station, a response signal represented by {-é2h1-(1+j)h2}/é2 and reference signal represented by (1+j)(h1+h2)/é2 are found in the correlation output of mobile station #1. That is, in this case, the output ofsynchronous detection in the base station is as shown in equation 13.
[13]
- -J2h, - (l 4- 7)/1, (1 + ΑΛ,+Α,)
...(Equation 13) [0160] Alsó, when mobile station #2 transmits a ACK/ACK and mobile station #1 fails to récéivé control information and does nőt transmit a response signal, in the base station, a response signal represented by (1 +j)(-h2)/é2 and reference signal represented by (1 +j)(h2)/é2 are found in the correlation output of mobile station #1. Therefore, in this case, the output ofsynchronous detection in the base station is as shown in equation 14.
[14]
-h<sub>2</sub> = -l
...(Equation 14) [0161] Comparing equation 13 and equation 14, it is understood that, when a response signal is provided from mobile station #1, there are the quadrature component and in-phase component in the synchronous detection output, while, when a response signal is nőt provided from mobile station #1, there is no quadrature component bút is only the inphase component in the synchronous detection output. Therefore, the base station can identify DTX accurately by measuring how distant the synchronous detection output is from the I axis.
[0162] Alsó, another example case will bedescribed where mobile station #1 transmits a response signal using PUCCH #2 (in FIG.7) and another mobile station #2 transmits a response signal using PUCCH #1 (in FIG.7). Here, according tothe present embodiment, constellation #1 (in FIG.4) is used fór the response signal of mobile station #1 and constellation #2 (in FIG.21) is used fór the response signal of mobile station #2.
[0163] When mobile station #1 and mobile station #2 both transmit a ACK/ACK and the base station receives the response signal from mobile station #1, interference given from the response signal of mobile station #2 to the response signal of mobile station #1 is as follows.
[0164] That is, when the ACK/ACK and reference signal transmitted from mobile station #1 are received by the base station via a channel, in the base station, a response signal represented by (-1 -j)h 1/42 and reference signal represented by (1 +j)h 1/42 are found as a correlation output of mobile station # 1.
[0165] Alsó, when the ACK/ACK and reference signal transmitted from mobile station #2 are received by the base station via a channel, in the base station, a component represented by -h2 is found as interference to the response
ΕΡ 2 207 289 Β1 signal of mobile station #1 and a component represented by (1 +j)h2/é2 is found as interference to the reference signal of mobile station #1 in the correlation output of mobile station #1.
[0166] Therefore, when the ACK/ACK from mobile station #1 and ACK/ACK from mobile station #2 are codemultiplexed, in the base station, a response signal represented by {-(1+j)h1-é2h2}A/2 and reference signal represented by (1+j)(h1+h2)/é2 are found in the correlation output of mobile station #1. That is, in this case, the output of synchronous detection in the base station is as shown in equation 15.
[15]
- (í + y)/i, - T/a, (ι + Λα,+α,)
...(Equation
15) [0167] Alsó, when mobile station #2 transmits a ACK/ACK and mobile station #1 fails to récéivé control information and does nőt transmit a response signal, in the base station, a response signal represented by -h2 and reference signal represented by (1 +j)(h2)/é2 are found in the correlation output of mobile station #1. Therefore, in this case, the output of synchronous detection in the base station is as shown in equation 16.
[16]
-Jlh<sub>2</sub> _ -72 _ -1 + 7 (l + j)h<sub>2</sub> (1 + /) y/2
...(Equation 16) [0168] Comparing equation 15 and equation 16, when a response signal is nőt provided from mobile station #1, it is understood that power is provided only on the axis 45 degrees shifted from the I axis and O axis (i.e. 45-degree axis). Therefore, the base station can detect DTX accurately by measuring how distance the synchronous detection output is from the 45-degree axis.
(Embodiment 9) [0169] Similar to Embodiment 7, a case will be described with the present embodiment where a base station detects that a mobile station fails to récéivé control information to carry the resource allocation result of downlink data. Here, using the synchronous detection output of a received signal, the base station decides whether the response signal is an ACK or a NACK, and detects DTX at the same time.
[0170] In this case, the identification between ACK, NACK and DTX is performed by a threshold decision using the synchronous detection output. Here, as in Embodiment 1, an example case will be described where mobile station #1 transmits a response signal using PUCCH #1 (in FIG.7) and mobile station #2 transmits a response signal using PUCCH #0 (in FIG.7). Here, the modulation scheme of response signals is BPSK. Therefore, constellation #2 (in FIG.8) is used fór the response signal of mobile station #1 and constellation #1 (in FIG.3) is used fór the response signal of mobile station #2. Alsó, the signal point of a reference signal is the same as the signal point of a NACK in FIG.3, (1Λ/2, 1/é2). [0171] If mobile station #1 that transmits a desired signal is nőt interfered with by mobile station #2 átáll, the synchronous detection output takes a value close to (1/é2, -1/é2) when the desired signal is a NACK, and the synchronous detection output takes a value close to (-1/^2, 1Λ/2) when the desired signal is an ACK. Here, mobile station #1 is influenced by nőise, and, consequently, the synchronous detection output does nőt always concentrate on one point.
[0172] Inter-code interference from mobile station #2 to mobile station #1 will be described below. The magnitude of power of inter-code interference (i.e. in the power of a signal that is transmitted by mobile station #2, the power that leaks to the correlation output of mobile station #1) is lower than a desired power, and, consequently, as described above, the synchronous detection output takes a value close to (1/é2, -1/é2) when the desired signal is a NACK, and the synchronous detection output takes a value close to (-1/^2, 1Λ/2) when the desired signal is an ACK.
[0173] Bút, when mobile station #1 fails to récéivé control information to carry the resource allocation result of downlink data, mobile station #1 does nőt transmit a response signal, and therefore there are only the interference component from mobile station #2 and nőise in the correlation output of mobile station # 1. In this case, the base station performs a synchronous detection of a response signal of mobile station #2 using a reference signal that leaks from mobile station #2, and, consequently, the synchronous detection output takes a value close to (-1/^2, -1Λ/2) when the response signal of mobile station #2 is an ACK, and the synchronous detection output takes a value close to (1/é2, 1Λ/2) when the response signal of mobile station #2 is a NACK.
[0174] That is, it is understood that, when mobile station #1 transmits a response signal, the powerof the synchronous
EP 2 207 289 Β1 detection output of the base station is high in the line direction of -45 degree slope represented by Y=-X, and, when mobile station #1 does nőt transmit a response signal (i.e. in the case of DTX), the power is low in the line direction of -45 degree slope represented by Y=-X.
[0175] FIG.22 illustrates the probability distribution density of the Q axis amplitude when the synchronous detection output of mobile station #1 subject to interference is rotated to the right by 45 degrees on the IQ pláne. As understood from FIG.22, if the synchronous detection output is rotated to the right by 45 degrees, when the desired signal is an ACK, the synchronous detection output takes a value close to (0, 1), that is, the Q axis amplitude is close to 1, while, when the desired signal is a NACK, the synchronous detection output takes a value close to (0, -1), that is, the Q axis amplitude is close to -1.
[0176] Alsó, FIG.23 illustrates the probability distribution density of the Q axis amplitude when the synchronous detection output of mobile station #1 subject to interference is rotated to the right by 45 degrees on the IQ pláne, in a case where the constellation of each response signal is nőt rotated on the cyclic shift axis, that is, in a case where, fór example, all mobile stations use the same constellation #2 (in FIG.8).
[0177] In FIG.22 and FIG.23, mobile station #1 is interfered with by mobile stations that use other PUCCH’s (in FIG.7) in addition to mobile station #2. Here, thegreatest interference isgivenfrom mobile station #2 that uses theZAC sequence of the adjacent cyclic shift value, to mobile station #1. Alsó, in FIG.22 and FIG.23, the ACK occurrence rate and the NACK occurrence rate are equal in all mobile stations, that is, the relationship of ACK:NACK=1:1 holds.
[0178] In FIG.22, a and β represent thresholds fór deciding between ACK, NACK and DTX, and, consequently, the base station decides that: mobile station #1 transmits a NACK if the Q axis amplitude in the case of the synchronous detection output rotated to the right by 45 degrees is less than a; mobile station #1 transmits an ACK if the Q axis amplitude in the case of the synchronous detection output rotated to the right by 45 degrees is greater than β; and mobile station #1 does nőt transmit a response signal (i.e. DTX) if the Q axis amplitude in the case of the synchronous detection output rotated to the right by 45 degrees is equal to or greater than a and equal to or less than β.
[0179] In FIG.23, when the synchronous detection output in the case of the greatest interference (i.e. interference from mobile station #2) has power in the same axis direction as the synchronous detection output of the desired signal, and therefore it is difficult to identify between ACK, NACK and DTX using thresholds a and β. By contrast with this, in FIG.22, the synchronous detection output in the case of the greatest interference has power in the axis direction 90 degrees shifted from the synchronous detection output of the desired signal, and therefore it is possible to identify between ACK, NACK and DTX using thresholds a and β.
[0180] That is, in combination with, fór example, the scrambling shown in Embodiment 1, even when the ACK occurrence rate and NACK occurrence rate are equal, it is possible to improve the accuracy of identifying between ACK, NACK and DTX in a base station.
[0181] Embodiments of the present invention have been described above.
[0182] Alsó, a PUCCH used in the above-described embodiments is a channel to feed back an ACK or NACK, and therefore may be referred to as an ACK/NACK channel.
[0183] Alsó, it is possible to implement the present invention as described above, even when other control Information than a response signal is fed back.
[0184] Alsó, a mobile station may be referred to as a UE, MT, MS and STA (station). Alsó, a base station may be referred to as a node B, BS or AP. Alsó, a subcarrier may be referred to as a tone. Alsó, a CP may be referred to as a Gl (Guard Interval).
[0185] Alsó, the method of error detection is nőt limited to CRC.
[0186] Alsó, a method of performing transformation between the frequency domain and the time domain is nőt limited to IFFT and FFT.
[0187] Alsó, a case has been described with the above-described embodiments where the present invention is applied to mobile stations. Here, the present invention is alsó applicable to a fixed rádió communication terminál apparátus in a stationary state and a rádió communication relay station apparátus that performs the same operations with a base station as a mobile station. That is, the present invention is applicable to all rádió communication apparatuses.
[0188] Although a case has been described with the above embodiments as an example where the present invention is implemented with hardware, the present invention can be implemented with software.
[0189] Furthermore, each function block employed in the description of each of the aforementioned embodiments may typically be implemented as an LSI constituted by an integrated Circuit. These may be individual chips or partially or totally contained on a single chip. LSI is adopted here bút this may alsó be referred to as IC, system LSI, super LSI, or ultra LSI depending on differing extents of integration.
[0190] Further, the method of Circuit integration is nőt limited to LSI’s, and implementation using dedicated circuitry or generál purpose processors is alsó possible. After LSI manufacture, utilization ofan FPGA (Field Programmable Gate Array) or a reconfigurable processor where connections and settings of Circuit cells in an LSI can be reconfigured is alsó possible.
[0191] Further, if integrated Circuit technology comes out to replace LSI’s as a result of the advancement of semicon19
ΕΡ 2 207 289 Β1 ductor technology or a derivative other technology, it is naturally alsó possible to carry out function block integration using this technology. Application of biotechnology is alsó possible.
[0192] The disclosures of Japanese Patent Application No.2007-280796, filed on October29, 2007, Japanese Patent Application No.2007-339924, filed on December 28, 2007, and Japanese Patent Application No.2008-268690, filed on October 17, 2008, including the specifications, drawings and abstracts.
Industrial Applicability [0193] The present invention is applicable to, fór example, mobile communication systems.
Contents3
2 sheets
Sheet 1 Sheet 2
119 members in 13 offices
Priority claims12
| Document | Office | Kind | Date |
|---|---|---|---|
| 2007280796 | Japan | A | |
| 2007280796 | Japan | A | |
| 2007339924 | Japan | A | |
| 2007339924 | Japan | A | |
| 2008268690 | Japan | A | |
| 2008268690 | Japan | A | |
| 2007280796 | – | – | – |
| 2007339924 | – | – | – |
| 2008268690 | – | – | – |
| JP20070280796 | – | – | – |
| JP20070339924 | – | – | – |
| JP20080268690 | – | – | – |
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| US2010135359A1 | United States of America | A1 | |
| KR20100070363A | Republic of Korea | A | |
| EP2207289A1 | European Patent Office (EPO) | A1 | |
| CN101821975A | China | A | |
| JP2010200335A | Japan | A | |
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| RU2009149211A | Russian Federation | A | |
| EP2207289A4 | European Patent Office (EPO) | A4 | |
| US8144745B2 | United States of America | B2 | |
| AU2008320275B2 | Australia | B2 | |
| US2012140687A1 | United States of America | A1 | |
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| JP5878995B2 | Japan | B2 | |
| US9313009B2 | United States of America | B2 | |
| EP2207289B1 | European Patent Office (EPO) | B1 | |
| EP2475118B1 | European Patent Office (EPO) | B1 | |
| US9344253B2 | United States of America | B2 | |
| EP3024163A1 | European Patent Office (EPO) | A1 | |
| EP3026834A1 | European Patent Office (EPO) | A1 | |
| JP2016116234A | Japan | A | |
| US2016233988A1 | United States of America | A1 | |
| ES2581767T3 | Spain | T3 | |
| ES2582865T3 | Spain | T3 | |
| CN103546255B | China | B | |
| MY158911A | Malaysia | A | |
| HUE029305T2 | Hungary | T2 | |
| US9584264B2 | United States of America | B2 | |
| JP6091667B2 | Japan | B2 | |
| CN103501215B | China | B | |
| CN103546256B | China | B | |
| US2017149538A1 | United States of America | A1 | |
| HUE030438T2This record | Hungary | T2 | |
| JP2017118562A | Japan | A | |
| CN103546257B | China | B | |
| EP3024163B1 | European Patent Office (EPO) | B1 | |
| EP3026834B1 | European Patent Office (EPO) | B1 | |
| ES2643382T3 | Spain | T3 | |
| ES2644393T3 | Spain | T3 | |
| EP3249836A1 | European Patent Office (EPO) | A1 | |
| JP6276877B2 | Japan | B2 | |
| US2018069667A1 | United States of America | A1 | |
| MY165313A | Malaysia | A | |
| JP2018098802A | Japan | A | |
| US10014989B2 | United States of America | B2 | |
| US10284342B2 | United States of America | B2 | |
| JP6510085B2 | Japan | B2 | |
| EP3249836B1 | European Patent Office (EPO) | B1 | |
| US2019215108A1 | United States of America | A1 | |
| JP2019146217A | Japan | A | |
| EP3537636A1 | European Patent Office (EPO) | A1 |
Numbers
- Publication
- E030438
- Publication, DOCDB
- E030438
- Publication, EPODOC
- HUE030438T
- Application
- 8844054
- Application, DOCDB
- E08844054
- Application, EPODOC
- HUE08844054
Titles2
- English
- RADIO COMMUNICATION DEVICE AND CONSTELLATION CONTROL METHOD
- Hungarian
- Rádió összeköttetési készülék, és helyzet ellenõrzési eljárás
Classification
- CPC, 25
- H04J13/0003
- H04J13/22
- H04L27/18
- H04J13/0059
- H04J13/0074
- H04L1/1854
- H04L1/1861
- H04L5/0007
- H04L5/0053
- H04L25/03866
- H04L27/2613
- H04L27/2626
- H04L27/2602
- H04L5/006
- H04L5/0091
- H04L2001/125
- H04L5/0055
- H04L1/0061
- H04L1/18
- H04W72/20
- H04W72/21
- H04W72/23
- H04L1/1825
- H04L1/1893
- H04L1/1896
- IPC, 7
- H04B1 707
- H04J11 00
- H04B1 7097
- H04J13 00
- H04J13 16
- H04W24 02
- H04W72 04