Control of power ratios for in-phase and quadrature channels in a communications system

Apparatus and method for controlling power ratios for phase and quadrature channels in a communications system

BACKGROUND The invention relates to radio communication systems using I / Q modulation, and more particularly to the control of a power relationship between I- and Q- channels in said system.

10 Modulation schemes that use In-phase (I) and quadrature (Q) signal components are known. In some cases, transmissions such as uplink in the IMT 20000 Broadband Code (WCDMA) Multiple Access Radio Communications System Standard, proposed in Europe and Japan, IQ modulation is used in a way which different data channels are transmitted in the

fifteen components I and Q (mentioned throughout this description as channels "I-" and "Q-"). In the proposed WCDMA system, the common control channel (PCCH) is transmitted on the Q channel at a data rate of 16 kilobits per second using an expansion factor of 256, while the dedicated traffic and control channel ( PDCH) is transmitted on channel 1 at any data rate between 32 kilobits per second (128 expansion factor) and 1024 kilobits per second (4 expansion factor).

twenty The power requirements in each of these channels I and Q- are, of course, different from each other. Therefore, before applying expansion and disturbance, channels I- and Q-have different power levels. It could be assumed, first, that the power of the channel must be proportional to the data rate present in the channel. However, this is not necessarily the case since there are different service quality requirements in

25 The different channels. The PCCH channel has pilots that may require a quality of service that differs from those required for speech or multiplexed data services on the PDCH channel.

The power levels of channels I- and Q- are controlled by a common Power Control algorithm. This algorithm increases or decreases the power in order to keep the signal strength constant in the

30 receiver. To achieve this, the algorithm must follow the Rayleigh fade, the normal logarithmic fade or the loss of variable trajectory due to the variable distance between the terminal and the base station.

A problem encountered derives from the requirement that the terminals in the WCDMA system have a transmitter characterized by good modulation accuracy. To get the exact power difference, by

35 For example, of 3 dB between channels I and Q, the amplitude ratio in the terminal is required to be:

β = ----- = 0.707! 2

40 To carry out this power ratio, the data samples in the Q channel are multiplied by the value of β, and the resulting samples are supplied to complex expansion and modulation circuits, together with data samples for the I channel.

Four. Five The implementation of this exact power ratio is problematic because the representation of the number 0.707 requires that many bits necessarily participate in the multiplication that is performed on each sample to be transmitted. As is well known, the computational load imposed by a multiplication operation is related to the length of the operands involved. The increased computational load translates not only in a longer calculation time, but also in increased power requirements

fifty to carry out the calculation.

In addition, when a system, such as the WCDMA system described above, has been designed on the assumption that β values ​​may vary continuously, different system components (for example, terminals manufactured by different manufacturers) may introduce different quantization errors

55 when β is represented. As a result of these imbalances, the behavior of the system will be degraded.

US 5,784,402 describes a Feher BPSK transmitter that is compatible with conventional BPSK receivers. FBPSK modems are based on a quadrature structure in which the channel data

60 Q are inserted in quadrature with the data of channel I for certain applications. The Q channel data may be "deviated" from the I channel data in a selectable amount between zero and a specified time.

SUMMARY Therefore, an object of the present invention is to provide a relationship control strategy of

power that improves behavior compared to conventional techniques.

According to one aspect of the present invention, the above objects and other objects are achieved in methods and apparatus for use in a transmitter of a radiocommunication system such as the Broadband Division Multiple Access (WCDMA) Multiple Access communications system. .

According to a first aspect of the invention, an apparatus is provided for use in a transmitter. The apparatus comprises means for receiving digital data associated with an in-phase channel (I-); means for receiving digital data associated with a quadrature channel (Q-); means for generating a gain signal, β, which represents a gain value selected from a finite number of gain values ​​that are exactly representable by means of a predetermined number of bits; means for multiplying the digital data associated to the Q channel by the gain signal, β, in order to control a power relationship between the in-phase channel (I-) and the quadrature channel (Q-); wherein the gain signal, β, is a rounded function of a digital data data rate associated with the Q channel.

According to the second aspect of the invention, a method for use in a transmitter is provided. The method comprises the steps of: receiving digital data associated with an in-phase channel (I-); receive digital data associated with a quadrature channel (Q-); generate a gain signal, β, which represents a gain value selected from a finite number of gain values ​​that are exactly representable by a predetermined number of bits; multiply the digital data associated to the Q channel by the gain signal, β, in order to control a power relationship between the in-phase channel (I-) and the quadrature channel (Q-); wherein the stage of generating a gain signal comprises the steps of: rounding the gain signal, β, to a data rate function of the digital data associated with the Q channel.

BRIEF DESCRIPTION OF THE DRAWINGS The objects and advantages of the invention can be understood by reading the detailed description that follows along with the drawings, in which:

Figure 1 is a block diagram of a radio communication system transmitter that operates according to an aspect of the invention; Figure 2 is a set of graphs representing, for each of a number of candidate quantification amounts, the extra transmitted power required as a function of the desired β gain value; Figure 3 is a flow chart depicting an example of the techniques for selecting a β value according to another aspect of the invention; Figure 4 is a set of graphs showing, for each of a number of quantification levels, the resulting modulation accuracy represented as a function of the ideal gain parameter, βIDEAL.

DETAILED DESCRIPTION The various features of the invention will now be described with respect to the Figures, in which identical parts are identified with the same reference characters.

Figure 1 is a block diagram of a radio communication system transmitter operating according to the invention. The transmitter uses channels I and Q as described previously in the Background section. Samples of data associated with channel Q 103 are supplied to an input of a multiplier 105, whose other input receives a β value from a power ratio control circuit 107. The multiplier 105 multiplies the data of the Q channel by β in order to control the power ratio, as described above. The multiplied Q channel data, together with the data associated with the I 101 channel, is supplied to a complex expansion and modulation circuit 109. The signals of the resulting channels I and Q are supplied to a first and a second converter 111, 113 of respective digital to analog (D / A). The analog signals supplied by the first and second D / A converters 111, 113, are supplied to a respective first and second mixers 115, 117. The first mixer 115 uses a cosine signal for the mixture, while the second mixer 117 uses a sine signal for the mixture. The outputs from the first and second mixers 115, 117, are combined in combination means 119 (for example, an adder), whose output is supplied to a power amplifier 121 for amplification prior to transmission.

According to one aspect of the invention, the transmitter further includes a power ratio control unit 107 that generates values ​​for β in a manner to be described now. The principles on which the power ratio control unit 107 operates derives at least in part, from the fact that in a radiocommunication system such as the CDMA, all signals are transmitted simultaneously on the same carrier frequency. All signals other than the desired signal are seen as interference in the receiver. When they are received by the base station, all received signals must have approximately the same energy per bit transmitted in order to minimize interference from each user and thereby optimize the capacity of the cell.

In the uplink channel of an IQ modulated scheme such as the WCDMA system mentioned above, the expansion factor of the Q channel is set to 256, while the expansion factor of the I channel can be any of the following: 128, 64, 32, 16, 8 and 4. The purpose of the gain factor, β, is to ensure an optimization of the system capacity. In conventional systems, no restrictions are placed on possible values ​​of β (that is, in conventional systems, β is specified as a continuous parameter).

The selection of a value for β can have a great impact on system performance. For example, the speed measurement at which information is transmitted in a CDMA system is the "chip rate". In an example of a system, the main chip rate can be fc = 4,096 Mchip / s, with other chip rates of 1,024, 2,048, 8,192 and 16,384 Mchip / s being defined for use. With reference to Figure 1, the digital information signal supplied by the Q 103 channel may have an oversampling rate ("OS") of 4, each sample being represented by a number of bits Nb. Multiplying each of the resulting samples by β, then it will be required that fs = fc * OS = 16,385 Mops in the mode of 4,096 Mchip / s.

Each extra bit in the multiplier (ie, Nb · number of bits in β) makes each multiplication operation more complex, and also adds an extra bit per sample that needs to be transmitted and processed. Consequently, to achieve an efficient power design, the number of bits involved in multiplication must be minimized. This can be achieved by restricting β to values ​​that can be accurately represented with a relatively small number of bits. However, as mentioned above, the purpose of the gain factor, β, is to guarantee an optimization of the system capacity, and this cannot be done with any arbitrary value of β. Instead, an analysis is needed to determine adequate β values ​​that can reduce the computational complexity required associated with the multiplication operation, without overflowing that degrades the system's capacity.

An example of analysis is as follows. Suppose that in implementations of the transmitter example, β will be in the form of a signal having a finite number of bits. Consequently, where βIDEAL represents an "ideal" value that guarantees the optimized capacity of the system, the signal β represents the ideal value plus some quantization noise that is introduced by approximation to the ideal value with a finite number of bits. That is, β = βIDEAL + (quantization noise).

In the exemplary embodiment, the values ​​of β are chosen allowing β to represent exactly βIDEAL where possible (for example, where βIDEAL = 0.5, and β is represented by at least one bit to the right of the binary root point) , and in all other cases rounding β to the next highest representable number. The reason why rounding up is always preferred in front of rounding up to the nearest representable number (which can result in, in some cases, downward rounding) is because the downward rounding causes the power ratio of I over Q decrease. As a consequence, the power in channel I may have to be increased in order for its performance to be relatively good with respect to that of channel Q. With the consideration of this strategy for the selection of P values, the extra power transmitted when the value of β increases slightly, can be calculated for a number of candidate bit sizes representative for β.

Figure 2 is a set of graphs depicting, for each of a number of candidate quantization amounts (i.e., the number of bits that are being used to represent β), the required extra transmitted power (in decibels) as a function of the desired value of β. Graphs for representations of β of 3, 4, 5 and 6 bits have been shown. It can be seen from graphs that when a 3-bit representation is used, the extra transmitted power required in the worst case is approximately 0.5 dB. In comparison when a 4-bit representation is used, the extra transmitted power required in the worst case is only 0.25 dB, and in most cases it is much smaller. As the number of bits used to represent β increases, the amount of extra transmitted power required is reduced. For the determination of the value of β that is better to use, another factor that is considered is the minimum stage size for adjusting the transmission power. In many radio systems, transmission power settings can only be made for discrete quantities. In the example WCDMA system, the smallest possible transmission power setting is 0.25 dB. Therefore, even if the use of 5 or 6-bit representations of β requires only, at most, approximately 0.12 dB (see Figure 2) of extra transmission power, the radio system could, in practice, be forced , to increase the power by 0.25 dB, because smaller adjustments are impossible. Consequently, it is better to represent β using 4-bit values ​​in this case because the use of more than 4 bits only increases the complexity of the multiplication without resulting in any additional transmission power savings.

In view of the foregoing, an embodiment of the invention includes quantifying (ie, representing) β by that number of bits, Nβ, which results in the lowest maximum required extra transmission power, PEXTRA, which is not below a predetermined multiple, K, of the minimum power setting amount, ΔPADJ. In the example described above, K = 1, so that only the smallest possible power adjustment amount will be required as a result of the quantification of β. In some other cases, however it may be

It is desirable to choose a different K value where the benefits of keeping Nβ low outweigh the benefits of further reducing the extra transmission power required. One way to select a value of β, then, has been illustrated in the flow chart of Figure 3. In step 301, the quantization amount, Nβ, is initialized at the lowest possible value (i.e., 1) . Next, PEXTRA is determined as a function of the given value of Nβ (step 303). Next, the value of PEXTRA is compared with the amount K · ΔPADJ (decision block 305), and if it is greater than, or equal to (output “yes” path of decision block 305), then it is increased by one the value of Nβ (step 307). The logical basis behind this stage is to test another amount of quantification to see if the required extra transmission power can be reduced without falling below the desired minimum of K · ΔPADJ. After the Nβ adjustment, the execution is repeated again in step 303.

When a PEXTRA value is found that is less than K · ΔPADJ (output “no” path of decision block 305), then too many bits are being used to represent β. The Nβ value is accordingly adjusted again to its previous acceptable level (step 309), and the process of selecting a quantification level for β is completed.

Table 1 below illustrates an example of a set of β values ​​that are selected to be close to the data rate relationships. For each relationship, an ideal value, βIDEAL, has been shown along with the proposed value based on the use of 4-bit representations of β, as previously determined.

Table 1

<dl><dt>Channel I Rate (kbps) </dt><dd>Q channel rate (kbps) Relationship of symbol rates in channels I and Q Ideal value, βIDEAL Proposed gain, β, using 4-bit representation Stages β in dB </dd></dl>

<dl><dt>16 </dt><dd>0 0 0 Q channel disconnection </dd></dl>

<dl><dt>16 </dt><dd /><dt>16 </dt><dd> 1 1 1 </dd></dl>

<dl><dt>16 </dt><dd> 32 ½ 0,707 0,75 3,52 </dd></dl>

<dl><dt>16 </dt><dd> 64 ¼ 0,5 0,5 2,77 </dd></dl>

<dl><dt>16 </dt><dd> 128 1/8 0,354 0,375 2,49 </dd></dl>

<dl><dt>16 </dt><dd> 256 1/16 0,25 0,25 3,52 </dd></dl>

<dl><dt>16 </dt><dd> 512 1/32 0,177 0,1875 2,5 </dd></dl>

<dl><dt>16 </dt><dd> 1024 1/64 0,125 0,125 3,52 </dd></dl>

Another factor to consider in the selection of a quantification amount to represent β refers to the effect this has on the imprecision of modulation. In most cell phone systems, for example, the standards under which these systems can operate set limits on the amount of inaccuracy of modulation that should be acceptable for any given terminal. If a given radiocommunication system operates under a standard that does not place any restriction on the values ​​of β (that is, the system assumes that βIDEAL is being used), then a terminal using a quantized P value will present inaccuracy of modulation when compare with signals that the system could be expected to generate. Figure 4 is a set of graphs showing, for each of a number of quantification levels, the resulting inaccuracy of modulation represented as a function of the ideal gain parameter, βIDEAL. It can be seen that when 4-bit β values ​​are used, the inaccuracy of modulation is about 6%. That is a substantial amount of the usual acceptable total modulation imprecision, so that serious restrictions on other components in the radio terminal would have to be imposed in order to avoid exceeding the permissible modulation imprecision limitations.

According to another aspect of the invention, the problem of inaccuracy of modulation resulting from the quantification of β is addressed by the design of the complete radiocommunication system based on the quantified values ​​of β, rather than the ideal unrestricted values, βIDEAL. When each transmitter requires the use of equal, quantified values ​​of β (for example, Nβ = 4), the system no longer perceives any inaccuracy of modulation in relation to this quantification. This has the double effect of eliminating system imbalances that may occur when different manufacturers quantify differently, while making terminal design easier without sacrificing system capacity.

The techniques for the selection of values ​​for profit, β, have been described above. During use, these β values ​​may be generated by a power ratio control unit 107, as illustrated in Figure 1. The power ratio control unit 107 can be implemented, for example, by way of digital storage device that has stored in it the one or more necessary values ​​of β. Preferred criteria for selecting quantified values ​​of β have been described, with a particular value of β = 4 as being preferred for use in the WCDMA system of the example described above. However, those skilled in the art will recognize that other criteria can be used to select quantified values ​​of β. For example, it is not always necessary to try to find that Nβ value that produces the smallest PEXTRA value that satisfies the PEXTRA&gt; K · PADJ relationship. Where appropriate, there may be other trade-offs between modulation accuracy and extra required transmission power that might be desired in other cases. The invention also covers those aspects.

5 The invention has been described with reference to a particular embodiment. However, as will be readily apparent to those skilled in the art, it is possible to materialize the invention in specific ways other than the preferred embodiments described above. This can be done without departing from the scope of the invention as defined in the appended claims. The preferred embodiment is merely illustrative and should not be considered limiting in any way. The scope of the invention is given by the claims.

10 annexes instead of the preceding description, and all variations and equivalents that fall within the scope of the claims, are understood to be encompassed by it.