Electrosurgical apparatus with high speed energy recovery

<u>BACKGROUND</u>

Technical Field

0001The present disclosure relates to an electrosurgical system and method and, more particularly, to an electrosurgical generator configured to dynamically control energy output.

Background of Related Art

0002Electrosurgery involves application of high radio frequency electrical current to a surgical site to cut, seal, ablate, or coagulate tissue. In monopolar electrosurgery, a source or active electrode delivers radio frequency energy from the electrosurgical generator to the tissue and a return electrode carries the current back to the generator. In monopolar electrosurgery, the source electrode is typically part of a surgical instrument held by the surgeon and applied to the tissue to be treated. A patient return electrode is placed remotely from the active electrode to carry the current back to the generator.

0003In bipolar electrosurgery, a hand-held instrument typically carries two electrodes, e.g., electrosurgical forceps. One of the electrodes of the hand-held instrument functions as the active electrode and the other as the return electrode. The return electrode is placed in close proximity to the active (i.e., current supplying) electrode such that an electrical circuit is formed between the two electrodes. In this manner, the applied electrical current is limited to the body tissue positioned between the two electrodes.

0004Conventional electrosurgical generators include a high voltage direct current power supply connected to a radio frequency (RF) output stage that converts DC energy generated by the power supply into RF energy. The power supply includes an output filter which substantially eliminates undesirable frequencies (e.g., noise) from the DC energy and stores large amounts of energy. Rapid tissue desiccation during the application of RF energy creates a potential for patient burn hazards due to excess energy dosage at the tissue site when the power source fails to rapidly alter the supplied energy dosage in response with dynamic changes in tissue impedance. Rising tissue impedance levels caused by desiccation unload the energy source and sustain the energy delivered to the tissue due to the large amount of stored energy in the output filter.

0005<patcit id="pcit0001" dnum="EP1776929A1"><text>EP 1 776 929 A1</text></patcit> is concerned with a circuit for reducing stored energy in an electrosurgical generator.

<u>SUMMARY</u>

0006According to the present disclosure, a circuit for controlling the discharging of stored energy in an electrosurgical generator is provided according to claim 1.

0007According to another embodiment of the present disclosure, a circuit for controlling the discharging of stored energy in an electrosurgical generator is provided according to claim 10.

0008The present disclosure also provides a method for controlling the discharging of stored energy in an electrosurgical generator. The method includes applying energy stored in an output of a power supply to tissue. The method also includes generating at least one control signal based on at least one of a sensed tissue property and a sensed energy delivery property, (i.e. power, voltage, current, time etc.). The method also includes generating an error signal based on a comparison between the at least one control signal and the energy stored in the output. The method also includes discharging the stored energy to an inductive load in parallel with the output of the power supply based upon the comparison between the energy stored in the output and the control signal.

<u>BRIEF DESCRIPTION OF THE DRAWINGS</u>

0009Various embodiments of the present disclosure are described herein with reference to the drawings wherein: <ul id="ul0001" list-style="none"><li><figref idref="f0001">Fig. 1A</figref> is a schematic block diagram of a monopolar electrosurgical system in accordance with an embodiment of the present disclosure;</li><li><figref idref="f0001">Fig. 1B</figref> is a schematic block diagram of a bipolar electrosurgical system in accordance with an embodiment of the present disclosure;</li><li><figref idref="f0002">Fig. 2</figref> is a schematic block diagram of a generator in accordance with an embodiment of the present disclosure;</li><li><figref idref="f0003">Fig. 3</figref> is a circuit diagram of a power supply in accordance with an embodiment of the present disclosure; and</li><li><figref idref="f0004">Fig. 4</figref> is a flow chart diagram of a method for controlling the discharge of energy stored in an output of an electrosurgical generator according to an embodiment of the present disclosure.</li></ul>

<u>RETAILED DESCRIPTION</u>

0010Particular embodiments of the present disclosure are described hereinbelow with reference to the accompanying drawings. In the following description, well-known functions or constructions are not described in detail to avoid obscuring the present disclosure in unnecessary detail.

0011In general, the present disclosure provides for an electrosurgical generator including a power supply configured to rapidly re-direct stored output energy through inductive energy transfer utilizing a controlled switching circuit to regulate, in real-time, the level of power sourced to the RF energy delivered to tissue during treatment.

0012More specifically, when the generator senses increased impedance in tissue due to rapid tissue desiccation, the generator of the present disclosure can control, in real time, the amount of treatment energy applied to tissue through use of a so-called "discharge" circuit. The discharge circuit provides a rapid response and time rate control of the electrosurgical energy delivered to tissue by discharging energy stored in an output filter of the power supply into an inductive load based on a feedback signal generated by the controller. The feedback signal may be based on a sensed tissue property (e.g., impedance) and/or an energy property (e.g., voltage, output energy level, etc.). This control provides for more accurate application of target treatment energy levels to treat tissue.

0013The generator according to the present disclosure can perform monopolar and bipolar electrosurgical procedures, including vessel sealing procedures. The generator may include a plurality of outputs for interfacing with various electrosurgical instruments (e.g., a monopolar active electrode, return electrode, bipolar electrosurgical forceps, footswitch, etc.). Further, the generator includes electronic circuitry configured for generating radio frequency power specifically suited for various electrosurgical modes (e.g., cutting, blending, division, etc.) and procedures (e.g., monopolar, bipolar, vessel sealing, ablation).

0014<figref idref="f0001">Fig. 1A</figref> is a schematic illustration of a monopolar electrosurgical system according to one embodiment of the present disclosure. The system includes a monopolar electrosurgical instrument 2 including one or more active electrodes 3, which can be electrosurgical cutting probes, ablation electrode(s), etc. Electrosurgical RF energy is supplied to the instrument 2 by a generator 20 via a supply line 4, which is connected to an active terminal 30 (<figref idref="f0002">Fig. 2</figref>) of the generator 20, allowing the instrument 2 to coagulate, ablate and/or otherwise treat tissue. The energy is returned to the generator 20 through a return electrode 6 via a return line 8 at a return terminal 32 (<figref idref="f0002">Fig. 2</figref>) of the generator 20. The active terminal 30 and the return terminal 32 are connectors configured to interface with plugs (not explicitly shown) of the instrument 2 and the return electrode 6, which are disposed at the ends of the supply line 4 and the return line 8, respectively.

0015The present disclosure may be adapted for use with either monopolar or bipolar electrosurgical systems. <figref idref="f0001">Fig. 1B</figref> shows a bipolar electrosurgical system according to the present disclosure that includes an electrosurgical forceps 10 having opposing jaw members 50 and 55. The forceps 10 includes a shaft member 64 having an end effector assembly 40 disposed at the distal end thereof. The end effector assembly 40 includes two jaw members 50 and 55 movable from a first position wherein the jaw members 50 and 55 are spaced relative to another to a closed position wherein the jaw members 50 and 55 cooperate to grasp tissue therebetween. Each of the jaw members 50 and 55 includes an electrically conductive sealing plate 112 and 122, respectively, connected to the generator 20 that communicates electrosurgical energy through the tissue held therebetween.

0016Electrically conductive sealing plates 112 and 122, which act as active and return electrodes, are connected to the generator 20 through cable 23, which includes the supply and return lines coupled to the active and return terminals 30, 32 (<figref idref="f0002">Fig. 2</figref>). The electrosurgical forceps 10 is coupled to the generator 20 at the active and return terminals 30 and 32 (e.g., pins) via a plug 92 disposed at the end of the cable 23, wherein the plug includes contacts from the supply and return lines. Electrosurgical RF energy is supplied to the forceps 10 by generator 20 via a supply line connected to the active electrode and returned through a return line connected to the return electrode.

0017Forceps 10 generally includes a housing 60 and a handle assembly 74 that includes moveable handle 62 and handle 72 which is integral with the housing 60. Handle 62 is moveable relative to handle 72 to actuate the end effector assembly 40 to grasp and treat tissue. The forceps 10 also includes shaft 64 that has a distal end 68 that mechanically engages the end effector assembly 40 and a proximal end 69 that mechanically engages the housing 60 proximate a rotating assembly 80 disposed at a distal end of the housing 60.

0018With reference to <figref idref="f0001">Fig. 1B</figref>, the generator 20 includes suitable input controls (e.g., buttons, activators, switches, touch screen, etc.) for controlling the generator 20. In addition, the generator 20 includes one or more display screens for providing the surgeon with variety of output information (e.g., intensity settings, treatment complete indicators, etc.). The controls allow the surgeon to adjust power of the RF energy, waveform, and other parameters to achieve the desired waveform suitable for a particular task (e.g., coagulating, tissue sealing, division with hemostasis, etc.). Further, the forceps 10 may include a plurality of input controls which may be redundant with certain input controls of the generator 20. Placing the input controls at the forceps 10 allows for easier and faster modification of RF energy parameters during the surgical procedure without requiring interaction with the generator 20.

0019<figref idref="f0002">Fig. 2</figref> shows a schematic block diagram of the generator 20 having a controller 24, a power supply 27, an RF output stage 28, and a sensor module 22. The power supply 27 may provide DC power to the RF output stage 28 which then converts the DC power into RF energy and delivers the RF energy to the forceps 10. The controller 24 includes a microprocessor 25 having a memory 26 which may be volatile type memory (e.g., RAM) and/or non-volitile type memory (e.g., flash media, disk media, etc.). The microprocessor 25 includes an output port connected to the power supply 27 and/or RF output stage 28 which allows the microprocessor 25 to control the output of the generator 20 according to either open and/or closed control loop schemes.

0020A closed loop control scheme generally includes a feedback control loop wherein the sensor module 22 provides feedback to the controller 24 (i.e., information obtained from one or more sensing mechanisms that sense various tissue parameters such as tissue impedance, tissue temperature, output current and/or voltage, etc.). The controller 24 then signals the power supply 27, which then adjusts the DC power supplied to the RF output stage, accordingly. The controller 24 also receives input signals from the input controls of the generator 20 and/or forceps 10. The controller 24 utilizes the input signals to adjust the power output of the generator 20 and/or instructs the generator 20 to perform other control functions.

0021The microprocessor 25 is capable of executing software instructions for processing data received by the sensor module 22, and for outputting control signals to the generator 20, accordingly. The software instructions, which are executable by the controller 24, are stored in the memory 26 of the controller 24.

0022The controller 24 may include analog and/or logic circuitry for processing the sensed values and determining the control signals that are sent to the generator 20, rather than, or in combination with, the microprocessor 25.

0023The sensor module 22 may include a plurality of sensors (not explicitly shown) strategically located for sensing various properties or conditions, e.g., tissue impedance, voltage at the tissue site, current at the tissue site, etc. The sensors are provided with leads (or wireless) for transmitting information to the controller 24. The sensor module 22 may include control circuitry which receives information from multiple sensors, and provides the information and the source of the information (e.g., the particular sensor providing the information) to the controller 24.

0024More particularly, the sensor module 22 may include a real-time voltage sensing system (not explicitly shown) and a real-time current sensing system (not explicitly shown) for sensing real-time values related to applied voltage and current at the surgical site. Additionally, an RMS voltage sensing system (not explicitly shown) and an RMS current sensing system (not explicitly shown) may be included for sensing and deriving RMS values for applied voltage and current at the surgical site.

0025The measured or sensed values are further processed, either by circuitry and/or a processor (not explicitly shown) in the sensor module 22 and/or by the controller 24, to determine changes in sensed values and tissue impedance. Tissue impedance and changes thereto may be determined by measuring the voltage and/or current across the tissue and then calculating changes thereof over time. The measured and calculated values may be then compared with known or desired voltage and current values associated with various tissue types, procedures, instruments, etc. This may be used to drive electrosurgical output to achieve desired impedance and/or change in impedance values. As the surgical procedure proceeds, tissue impedance fluctuates in response to adjustments in generator output as well as removal and restoration of liquids (e.g., steam bubbles) from the tissue at the surgical site. The controller 24 monitors the tissue impedance and changes in tissue impedance and regulates the output of the generator 20 in response thereto to achieve the desired and optimal electrosurgical effect.

0026Referring to <figref idref="f0003">Fig. 3</figref>, there is shown a block diagram of the power supply 27 including a control circuit 100 in series with a switching circuit 145. The control circuit 100 includes a first comparator 110 (e.g., an operational amplifier) having positive and negative input pins +A1 and -A1, respectively. Positive input pin +A1 is configured to receive an applied control signal (e.g., a variable DC voltage) from the controller 24 based on any one or more tissue parameters provided by the sensor module 22. Negative input pin -A1 is configured to receive a proportionally scaled feedback voltage of the power source output (e.g., connected to the RF output stage 28) to match the applied control signal on input pin +A1, as will be discussed in further detail below.

0027When the power source output fails to match the applied control signal, the resulting voltage difference at positive and negative input pins +A1 and -A1 causes the first comparator 110 to output an analog error signal (e.g., analog voltage) to drive a pulse modulator ("PM") 115. PM may be, for example, a pulse width modulator, a phase shift modulator or any such device known in the art for converting the analog error signal to a digital pulse control signal. The PM 115 converts the analog error signal to a digital pulse control signal (e.g., digital voltage) to implement control of a full-bridge power stage 120 by phase shifting the switching of one half-bridge with respect to the other. It allows constant frequency pulse-width modulation to provide high efficiency at high frequencies and can be used either as a voltage mode or current mode controller. More specifically, an AC/DC converter 125 converts an available ac signal (e.g., from an ac line voltage) to a dc signal to drive the full-bridge power stage 120, the output of which is, in turn, controlled by the digital pulse control signal to reflect the applied control signal from the controller 24. The resulting controlled output of the full-bridge power stage 120 drives an output filter 130 (e.g., a low-pass filter), having an inductor 132 and an output capacitor 134, to generate a DC output voltage V_c across the output capacitor 134. The resulting output voltage V_c is converted to RF energy by the RF output stage 28 and output to the electrosurgical instrument. A feedback compensator 140 continuously monitors the output voltage V_c (e.g., input to the RF output stage 28) and, in turn, provides a proportionally scaled feedback of the power source output to input pin -A1 of the first comparator 110 to match the applied control signal from the controller 24.

0028With continued reference to <figref idref="f0003">Fig. 3</figref>, discharging of energy is achieved in real-time using an active discharge circuit (ADC) 145 - a component of the power supply 27 - that switches inductor 150 using a first switching component 160 in parallel with the output capacitor 134 to discharge the energy therefrom, as will be discussed in further detail below. The ADC 145 includes a second comparator 180 (e.g., an operational amplifier) having negative and positive input pins -A2 and +A2 operably coupled to the positive and negative input pins +A1 and -A2 of the first comparator 110, respectively. In this manner, the input pins -A2 and +A2 of the second comparator 180 continuously monitor the difference between the applied control signal from the controller 24 on positive input pin +A1 and the proportionally scaled feedback of the power source output on negative input pin -A1.

0029An inductive load 150 (e.g., an inductor) is connected in parallel with the output filter 130 and in series with the first switching component 160. The first switching component 160 is normally off and may be a transistor, such as a field-effect transistor (FET), metal-oxide semiconductor field-effect transistor (MOSFET), insulated gate bipolar transistor (IGBT), relay, or the like. A first resistive element 162 is in series with the first switching component 160 and with ground 168, which is known as a source follower circuit. The source follower limits the amount of current that flows through the first resistive element 162, the switching component 160, and the inductor 150.

0030In the case of the power source output being greater than the applied control signal (i.e., -A1 > +A1), the switching circuit 145 utilizes inductive energy transfer to rapidly re-direct the stored output energy of the power source 27 away from the RF output stage 28 until the power source output matches the applied control signal (i.e., -A1 = +A1). More specifically, the second comparator 180 provides a drive voltage sufficient to close the first switching component 160 to discharge the stored energy from the output capacitor 134 to the inductive load 150. The activation of the first switching component 160 causes a conduction current I_Q1 to discharge from the capacitor 134 to ground 168 through the inductive load 150 and the first resistive element 162 to generate corresponding voltages V_Lr and V_R1, respectively. That is, while the first switching component 160 is switched on, the inductive load 150 absorbs the energy discharged by the output capacitor 134 to rapidly decrease the output voltage V_c until the power source output again matches the applied control signal (i.e., -A1 = +A1). Under this match condition, the second comparator 180 no longer provides the sufficient drive voltage, resulting in the first switching component 160 to return to the normally off position to interrupt the flow of the conduction current I_Q1 through the inductive load 150. The interruption of current flow through the inductive load 150 causes the magnetic flux field on the inductive load 150 to collapse due to a back electromagnetic force of voltage thereacross (e.g., a so-called "back EMF effect"). The back EMF voltage turns on diode 155, connected in shunt with the inductive load 150, to become forward-biased, providing a path for the inductor 150 magnetic flux and conductive current to be reset to zero. In addition this process prevents the back EMF voltage from increasing to a level sufficient to cause damage and/or stress to other components of the ADC 145 (e.g., the first switching component 160, the first resistive element 162, etc.).

0031The ADC 145 includes a second normally off switching component 170 that provides so-called "turn-on limiting" of the first switching component 160 to control the flow of the conduction current I_Q1 through the inductive load 150. More specifically, the second switching component 170 operates to monitor the voltage drop V_R1 across the first resistive element 162 caused by the conduction current I_Q1. Resistors 164 and 166 establish the threshold for component 170 turn on limiting. As the conduction current I_Q1 through the first switching component 160 increases, the voltage drop V_R1 across the first resistive element 162 increases to drive the second switching component 170 on, when the threshold for turn on limiting of component 170 is reached. The turn on of the second switching component 170 effectively reduces the drive voltage applied to the first switching component 160 to a steady state value from the second comparator 180, thereby regulating the current flow through the first switching component 160. The resulting reduced drive voltage of the first switching component 160 stabilizes the flow of conduction current I_Q1 through the first switching component 160 and, thus, through the first resistive element 162 thereby regulating the voltage drop V_R1 thereacross. In this manner, the output voltage V_c across the output capacitor 134 discharges at an incremental time rate of change, represented by equation (1) below:<maths id="math0001" num="(1)"><math display="block"><mrow><mi mathvariant="normal">Vc</mi><mo>=</mo><mn mathvariant="normal">1</mn><mo>/</mo><mi mathvariant="normal">C</mi><mspace width="1em" /><mrow><mstyle displaystyle="true"><mrow><msubsup><mrow><mo>∫</mo></mrow><mn mathvariant="normal">0</mn><mspace width="1em" /></msubsup></mrow></mstyle></mrow><msub><mrow><mspace width="1em" /><mi mathvariant="normal">I</mi></mrow><mi mathvariant="normal">QI</mi></msub><mi mathvariant="normal">dt</mi></mrow></math><img file="EP2160992B1_D0001.tif" /></maths>

0032Where: <ul id="ul0002" list-style="none"><li>Vc is the output voltage across the capacitor 134;</li><li>C is the capacitance of the capacitor 134; and</li><li>I_Q1 is the conductive current through the inductive load 150.</li></ul>

0033In the illustrated embodiment, one or more resistive elements 164 and 166 are utilized to set the desired proportion of the voltage drop V_R1 across the first resistive element 162 sufficient to turn on the second switching element 170. That is, each of resistive elements 164 and 166 may be interchanged with resistive elements of various resistance values to vary the proportion of the voltage drop V_R1 across the first resistive element 162 at which the second switching component 170 turns on. For example, the resistance ratio provided by the combination of the resistive elements 164 and 166, adjusts the proportion of the voltage drop V_R1 necessary to turn on the second switching component 170. The resistive elements 164 and 166 of <figref idref="f0003">Fig. 3</figref> are illustrative only in that a single resistive element (not explicitly shown) or, alternatively, a plurality of resistive elements (not explicitly shown) in parallel and/or in series may replace the resistive elements 164 and 166 between the first switching component 160 and the second switching component 170 to achieve substantially the same purpose.

0034A buffer 172 (e.g., one or more resistors) between the first switching component 160 and the output of the second comparator 180 provides an isolation buffer therebetween when the second switching component 170 is turned on. As seen in <figref idref="f0003">Fig. 3</figref>, absent the buffer 172, the output of the second comparator 180 is shorted to ground 168 due to the closure of the second switching component 170. In this way, the buffer 172 operates to prevent a so called "over current" condition on the second comparator 180 during the closure of the second switching component 170.

0035<figref idref="f0004">Fig 4</figref> illustrates a method 200 for controlling the discharge of energy stored in an output of an electrosurgical generator. In step 210, energy is supplied to tissue. More specifically, the power supply 27 provides DC power to the RF output stage 28. The RF output stage 28 converts the DC power into RF energy and delivers the RF energy to tissue (e.g., via forceps 10). In step 220, the sensor module 22 generates a feedback signal to the controller 24 based on any one or more sensed tissue and/or energy properties. In step 230, a comparison is made between a control voltage generated by the controller 24 in response to the sensor feedback signal and the output voltage V_c sampled by feedback compensator 140. In step 240, based on the comparison of step 230, an error signal is generated by the first comparator 110 and provided to the PM 115. PM 115 drives the full bridge power stage 120 to develop the output voltage Vc on capacitor 134, based on any one or more sensed tissue and/or energy properties. In step 250, the switching circuit 145 controls the discharging of the output capacitor 134 by redirecting the power supply 27 stored energy using the inductive load 150 in response to a reduction of required RF energy delivered to the tissue, based on any one or more sensed tissue and/or energy properties. Sensor module 22 provides feedback to controller 24 regarding the reduced RF energy need, whereby controller 24 then communicates a reduced control voltage to the power supply 27. Comparator 180 automatically monitors the reduced control voltage, where -A2 is now less than +A2, to drive switch 160 on. The turn on of switch 160 redirects the stored energy of output capacitor 134. As a result, the redirected stored energy in the power supply 27 lowers the output voltage Vc and rapidly reduces the delivered RF energy of the RF output stage 28.

0036While several embodiments of the disclosure have been shown in the drawings and/or discussed herein, it is not intended that the disclosure be limited thereto, as it is intended that the disclosure be as broad in scope as the art will allow and that the specification be read likewise. Therefore, the above description should not be construed as limiting, but merely as exemplifications of particular embodiments. Those skilled in the art will envision other modifications within the scope of the claims appended hereto.