An antenna

0001The present invention relates to antennas and particularly, though not exclusively, to antennas arranged for transmitting and/or receiving brief pulses of radiation.

0002Pulsed electromagnetic (e/m) energy transmission and reception systems typically possess wide-band or ultra wide-band (UWB) transmission spectral band widths. This UWB characteristic stems from the pulsed nature of the e/m energy transmitted or received by such systems. The shape of such energy pulses in the time-domain is typically one of any number of approximations to a delta function, and generally has the property that the width of the frequency spectrum of such impulse increases as the time-domain "length" or duration of the pulse decreases. Thus, the more brief the pulse of radiation is the broader is its spectral bandwidth.

0003Thus, when an antenna is used employing such pulses in UWB applications, it is often found that the time-domain behaviour of the antenna is critical to the operation of the antenna. In particular, if an impedance mismatch or discontinuity occurs in such an antenna (such as at the open-circuit end of the antenna), the consequence is often the unwanted generation of a standing wave of e/m energy within the antenna's radiating element(s) caused by reflections within the antenna of the e/m energy to be transmitted.

0004This trapped energy not only reduces the efficiency of the transducer of which the antenna forms a part, but also masks, obscures or interferes with signals received by the transceiver while the trapped energy is still present within the antenna.

0005Thus, in any resonant structure, such as a dipole antenna, an impulse signal injected at the antenna input will typically be partially reflected from the open-circuited end of the dipole causing a residual reflected return signal to appear at the antenna input. This return reflection is often referred to as "ringing" or may be referred to as "aperture clutter" since it clutters/obscures the aperture of the antenna.

0006Pulsed UWB transceivers are often employed in applications such as short-distance positioning, or length measurement etc. where a pulsed e/m signal is transmitted from the transceiver and its reflection subsequently received after a very brief time period.

0007Such applications require that the entire e/m signal pulse has exited the antenna of the transceiver before any reflection of that signal is expected to be received. This aims to ensure that the transmitted signal does not interfere with its received reflections and thereby obscure the positioning/measurement process.

0008However, ringing/aperture clutter results in just such obscurement and is highly undesirable.

0009Prior art pulsed UWB transceiver systems have attempted to overcome this problem by adding e/m signal absorbing material to the ends of the dipole antennas thereof or by loading the antennas with a distributed series of resistors along their length in an attempt to dampen or attenuate the standing waves therein which cause aperture clutter. However, such solutions are generally of little effect or most likely result in undesirably excessive attenuation of received/transmitted signal energy.

0010Furthermore, short-range positioning antennas etc. are most desirably small in physical size so as to be not only portable but also useable at close quarters and in confined spaces. This requires the antenna to be as small as possible. However, reducing the size of an antenna has, in the prior art, typically resulted in a corresponding reduction of bandwidth. This is undesirable.

0011<patcit id="pcit0001" dnum="US20030020668A1"><text>US 2003/0020668 A1</text></patcit> discloses an antenna according to the preamble of claim 1.

0012The present invention aims to overcome at least some of the aforementioned deficiencies in the prior art, and is defined in the sole independent claim 1. The proposed invention, in any of its aspects, provides an antenna for use particularly, though not exclusively, at microwave e/m signal frequencies.

0013The present invention proposes, in one of its aspects, an antenna having a tapered radiating element possessing a slow-wave structure along a tapered radiating edge thereof. The tapered radiating element supports wide bandwidths while the slow-wave structures along radiating edges extends the physical length of the radiating edge in question without increasing the size of the radiating element. This increase in radiating edge length supports an increase in antenna bandwidth without increasing antenna size, or permits one to reduce antenna size without reducing (or without significantly reducing) the bandwidth of the antenna.

0014The "slow-wave" structure may be any non-linear and meandering slant edge which provides a meandering radiating edge to the radiating element, and therefore slows down the progress of a signal wave travelling along the slant edge by constraining the signal wave to progress along the longer meandering slant edge rather than to progress directly along a shorter linear slant edge. Non-linear/meandering edges include, for example; any corrugated or serrated formation of or in the slant edge; a jagged slant edge; a castellated/crenulated slant edge; a wavy/oscillating slant edge or the like. Most preferably, the meanders of the slant edge (e.g. serrations/corrugations/castellations/crenulations/waves/oscillations or jags) are shaped such that the Q-factor of the antenna is minimised thereby reducing aperture clutter by reducing the relative magnitude of a signal reaching the terminal (open-circuit) end of the slant edge where signal reflection tends to occur - this being the source of aperture clutter. The Q-factor of the antenna is proportional to the ratio of: the electromagnetic energy stored in the antenna due to the signal propagating within the antenna; and, the rate of loss of e/m energy from the antenna due to the signal propagating along the slant edge:<maths id="math0001"><math display="block"><mi mathvariant="italic">ʺQ</mi><mo>-</mo><mi mathvariant="italic">factorʺ</mi><mo>∝</mo><mfrac><mi mathvariant="italic">stored energy</mi><mi mathvariant="italic">rate of energy loss</mi></mfrac></math><img file="EP1517401B1_D0001.tif" /></maths>

0015Thus, the relative magnitude of a signal reaching the terminal outer end of the slant edge (i.e. relative to the magnitude of that signal at the input/beginning of the slant edge) is sensitively dependent upon the rate of loss of energy from the signal during propagation along the slant edge. By suitably shaping the meanders of the slow-wave structure, the present invention may enhance the rate of radiative energy loss of the propagating signal as it progresses along the slant edge. The result is a reduced signal magnitude at the terminal end of the slant edge and, therefore, a reduced reflection signal back along the slant edge (i.e. reduced aperture-clutter). This technique of reducing aperture clutter avoids the use of radiation attenuating materials (RAM) in reducing reflected signal magnitudes by simply causing signals to radiate from the slant edge more readily or rapidly and does not merely "damp" the signals as RAM would.

0016Accordingly, the slow-wave structure may comprise a series of saw-tooth serrations which may, for example, be formed by a series of straight edged tapering (e.g. triangular) notches which each extend into the radiating element at the slant edge thereby collectively rendering the slant edge into a jagged edge. However, other notch shapes could be employed, such as square notches or curved notches or the like. The notches may be contiguous such that the edge of one notch and the edge of a neighbouring notch meet at a convergence thereby collectively forming a serration point or end. Such contiguity helps increase the length of the slow-wave structure, particularly when the notch edges are straight, and so increases the bandwidth of the antenna.

0017In a first of its aspects, the present invention may provide an antenna comprising a radiating element having (e.g. at one end) a signal feed-point and two opposed slant edges which diverge with increasing distance from the antenna feed-point such that the radiating element tapers outwardly therefrom, wherein a slow-wave structure (e.g. a series of serrations) is formed in a slant edge so as to extend along the slant edge thereby to form a slow-wave structure for a signal propagating along the slant edge.

0018The signal Θ(x,t) propagating along a slant edge (e.g. dimension "x") at time "t" may be represented by the following equation:<maths id="math0002"><math display="block"><mi mathvariant="normal">Ψ</mi><mfenced><mi>x</mi><mi>t</mi></mfenced><mo>=</mo><mi>A</mi><mspace width="1em" /><mi>exp</mi><mfenced><mo>-</mo><mi>j</mi><mo>⁢</mo><mi mathvariant="normal">Φ</mi><mfenced><mi>x</mi><mi>t</mi></mfenced></mfenced></math><img file="EP1517401B1_D0002.tif" /></maths> where M(x,t) is the phase of the wave representing the signal, and: Φ(<i>x</i>,<i>t</i>)=β<i>x</i>-ω<i>t</i> where ? is the angular frequency of the signal and ∃ is the propagation factor which, for a given signal frequency ? is related to the phase velocity v_ph of the signal by the relation: V_ph = T/∃, thus, Φ(<i>x</i>,<i>t</i>)=ω(<i>x</i>/<i>v_ph</i> -<i>t</i>).

0019A slow-wave structure is formed in a slant edge by shaping the slant edge in such a way that, in response to changes in signal frequency, the rate (∂Φ/∂ω) of the resulting change in the phase of the wave at a given point along its propagation path (i.e. the slant edge) is reduced.

0020This signal phase manipulation may be applied to the serrated/corrugated slant edge(s) by shaping the corrugation/serrations of the slant edge to be either constant in size/scale, or to increase in size/scale with increasing distances (i.e. dimension "x") along the slant edge. For example, increasing distance "x" could be measured relative to the signal feed-point. A direct consequence of such signal phase manipulation has been found to be that the reactance of the radiating element changes much less in response to changes in signal frequency than would be the case where the slow-wave structure not shaped to implement the aforementioned signal phase manipulation. It has also been found that such a reduction in reactance changes is more significant when serrations increase in size/scale with increases in distance along the slant edge, especially when log-periodically scaled as discussed below. Thus, over a wide bandwidth of signal frequencies the radiating element may present substantially the same or at least similar reactance to signals with the consequence that where the antenna has been impedance-matched at a given signal frequency it will also tend to be impedance-matched (or nearly so) at many other signal frequencies within the bandwidth of the antenna. This near frequency-independence of reactance avoids or greatly reduces the degree of impedance mismatch in the antenna and so avoids or reduces the occurrence of the signal reflections which are caused by such mismatches and which are a source of aperture clutter. Hence, aperture clutter may be indirectly reduced by use of the aforesaid signal phase manipulation along the serrated slant edge of the radiating element of the antenna in the present invention. Furthermore, the near frequency-independence enables the overall antenna structure to be relatively small yet support a relatively large impedance matching bandwidth in spite of its small size.

0021Serrations in said series of serrations are preferably shaped to maximise or increase the rate of radiative loss of energy from a signal propagating along the slant edge. Preferably, the slow-wave structure is a series of serrations which may form a series of contiguous notches which extend into the radiating element from the slant edge. Serrations in the series may be shaped to terminate at the convergence of two tapering serration edges forming a single serration tip.

0022It is most preferable that successive serrations/ corrugations are shaped and/or arranged within the series such that each serration/corrugation of the series electromagnetically couples as little as possible to neighbouring serrations/corrugations of the series in response to a signal propagating along the slant edge. Minimising such coupling enables each notch/serration to perform its function almost independently (as far as possible) of the function of the notches/serrations neighbouring it.

0023This de-coupling, or minimal coupling, is preferably maintained or approached by shaping each serration to terminate in a serration tip formed by the convergence of two serration edges at an angle of between about 75° to about 105°. It has been found that such a tip angle reduces inter-serration e/m coupling without significantly reducing the other benefits of the invention (e.g. small size, low Q-factor, broad bandwidth etc). This is particularly so when serration edges are substantially straight.

0024Preferably, the series of serrations defines (or is defined by) a series of notches each of which is defined by neighbouring edges of successive serrations which extend into the radiating element from a slant edge.

0025At high signal frequencies, such as microwave frequencies, signals are known to preferentially propagate along the outer edges of an antenna's radiating elements. Thus, by locating the series of serrations along the slant edges of the radiating element, the present invention aims to ensure that the majority of the signal within the antenna passes along the serrations and through the series of notches formed by the serrations and thereby maximally experiences the structure responsible for enhanced radiative signal power loss and responsible for increased signal bandwidth. This series of serrations and notches not only reduces aperture clutter but may also reduce the size of the antenna radiating element required to achieve a given signal operating bandwidth. This size reduction may be achieved by providing at a selected property of any given notch of the series is determined according to the corresponding property of the proceeding notch in a series so as to provide a notch series which is log-periodically distributed in respect of the selected notch property. Thus, the ratio of: the magnitude of the selected property in respect of a given notch; and, the magnitude of the selected property in respect of the notch proceeding the given notch, is a fixed scaling factor shared by all such notch pairs in the series.

0026For example, the selected property may be the magnitude of a dimension(s) of, or associated with, a given notch of the series which is arranged to differ from the magnitude of the corresponding dimension(s) of the proceeding notch of the series according to a predetermined scaling factor thereby to form a log-periodic distribution in respect of the magnitude of the dimension(s) in question along the series. The dimension(s) may be one or more of: the position of a notch along the slant edge as measured from the feed-point; the physical depth of a notch; the width of a notch at the slant edge. Other notch properties may be log-periodically distributed in this way.

0027Serrations in said series of serrations are shaped such that corresponding dimensions of successive serrations increase log-periodically whereby the ratio of said corresponding dimensions in respect of (i.e. as between) successive such neighbouring serrations has a constant predetermined ratio value. Thus, since notch dimensions are defined by the dimension of neighbouring serrations, one may achieve a log-periodic scaling of notch dimensions by a suitable log-periodic scaling of serration dimensions.

0028For example, the length of an edge of any given serration of said series of serrations may exceed the length of the corresponding edge of the preceding serration of the series such that the ratio of said lengths in respect of successive serrations has a value substantially equal to said constant predetermined ratio value.

0029It is well known in the art that if the dimensions of a log-periodic antenna are scaled by a given proportion (e.g. doubled), and at the same time the wave length of signals in the antenna is scaled by the same proportion, the performance of the antenna will not substantially change. This property is known as "frequency independence" and arises because the property of the log-periodic antenna which gives it its log-periodicity is also invariant to changes of scale. Without such scaling invariants within the antenna radiating structure, it is difficult to achieve in a non-log-periodic antenna a performance (e.g. bandwidth) comparable to that of a log-periodic antenna structure without increasing the size of the non-log-periodic antenna radiating structure.

0030Preferably, the distance between the location of the feed-point and the location of successive serrations of the series increases log-periodically whereby the ratio of the said distance in respect of successive serrations has a constant predetermined ratio value.

0031Thus, preferably, the serrations of the series d serrations are arranged in a suitable fashion so as to provide a so-called "frequency independent" antenna radiating element (i.e. able to radiate effectively at any frequency within a broad band of frequencies) as discussed above. This may be achieved in the present invention by spacing the notches (which define the serrations) in the series of notches so as to form a log-periodic positioning of notches along the slant edge.

0032Each notch of the series of notches preferably extends into the radiating element from a respective location along the slant edge which location is spaced from the antenna feed-point by a distance chosen such that the ratio of such distances as between neighbouring notches has a constant predetermined ratio value. The distance by which a given notch or serration is spaced from the feed-point is preferably a distance measured along the slant edge of the antenna's radiating element but excluding the lengths of other notches/serrations of the series intermediate the feed-point and the given notch/serration (i.e. the distance being measured along the slant edge as if the/any intermediate notches/serrations, which have edges, were absent.

0033The location of a given notch/serration may be measured from the near most edge of the notch/serration at the slant edge, or from the far most edge thereof or from the midpoint between opposing edges of the notch/serration at the slant edge.

0034However one chooses to measure the aforesaid distance r_i; in respect of each slot/serration (i) in the series, the log-periodic nature of the series is such that: r_i+1/r_i = constant, as between a given notch/serration "i" at the successive neighbouring notch/serration "i+1" where the ratio value is a constant greater than 1 (one).

0035The widths of the notches/serrations of the series may be chosen to scale log-periodically along the series. That is to say, the width of any given notch/serration of the series (as measured between opposing points on opposing edges of a given notch/serration) may be chosen to exceed the width of the preceding notch/serration of the series (similarly measured) such that the ratio of widths as between those neighbouring notches/serrations has a value substantially equal to the aforesaid constant predetermined ratio value.

0036Each one of the two opposed slant edges of the radiating element preferably has a respective said series of serrations formed therein.

0037The opposed series of serrations may be arranged symmetrically such that one is the mirror image of the other along a line extending through the radiating element from the feed-point and between the two slant edges.

0038Divergent tapering of the radiating element from the antenna feed-point provides an antenna suitable for broadband signal transmission and reception as associated with pulsed UWB applications. The radiating element may be shaped to taper outwardly from an apex or point at the antenna feed-point. The radiating element may be triangular in shape (generally speaking), or may be in a shape of a segment of a circle with an arcuate distal peripheral edge bridging the terminal outermost ends of the two slant edges. However, this distal peripheral edge may be other than arcuate, and the radiating element may have an antenna feed-point at other than an apex or point, and the tapering edges may taper from other than a convergent apex/point i.e. the edges may never "meet".

0039The invention in a second of its aspects, may provide an antenna having a tapered radiating element one end of which is an antenna feed-point, the radiating element having two opposed slant edges which diverge with increasing distance from the slant edge such that the radiating element tapers outwardly thereform, wherein the radiating element has a distal peripheral edge bridging the terminal outermost ends of the two slant edges thereof which recedes towards the feed-point at the mid-region thereof so as to shape the radiating element into two symmetrical lobes which diverge with increasing distance from the feed-point.

0040The invention, in its second aspect, may also incorporate the features of the invention in its first aspect including none, some or all of the aforementioned variants, preferable features and alternative features of the first aspect of the invention. In its second aspect the radiating element may be combined with a ground plane conductor to form a monopole antenna.

0041At low signal frequencies, the radiating element of the invention in its second aspect behaves as a simple monopole (when combined with a ground plane). As the signal frequency rises, the symmetrical lobes of the radiating element tend to bifurcate the signal into two slant polarisations defined by the divergent orientations of the lobes. This has the beneficial effect of maintaining a wide elevation beam width of radiated signals and also introduces a radiated electrical field component along its geometrical axis of symmetry (i.e. the axis about which the divergent lobes have mirror symmetry). This produces a wide elevation beam width of radiated signals and a shallow radiation null along the direction of the geometrical symmetry axis of the radiating element, which one would not expect from a conventional monopole antenna (one would expect a complete, zero-signal, null along the axis of symmetry).

0042Preferably, the mid-region of the distal peripheral edge partially recedes towards the feed-point to form a V-shaped notch which extends into the radiating element with an apex angle less than about 90 degrees. However, other notch shapes are permissible which result in divergent symmetrical lobe shapes in the radiating element.

0043Constraining the apex angle of a v-shaped notch to less than about 90º has been found to cause the peripheral notch to preferentially suppress the occurrence of transverse signal modes which would otherwise tend to propagate along the distal peripheral edge of the radiating element and interfere with the operation and performance of the antenna undesirably.

0044The present invention may provide an antenna according to any of the first and second aspects of the invention having said radiating element and a ground plane conductor relative to which the radiating element extends substantially perpendicularly, or across which the face of the radiating element extends (e.g. parallel thereto or otherwise), thereby to form a monopole antenna. In the former case the monopole antenna so produced is preferably an omnidirectional antenna operable to radiate in all directions in the azimuthal plane, whereas in the latter case the resultant antenna is preferably unidirectional being more limited in its azimuthal range.

0045The radiating element is most preferably planar, in which case the radiating element may be arranged so that its plane is substantially perpendicular to that of the ground-plane from which (or relative to which) it extends, or may be plane parallel therewith.

0046In another aspect of the invention there may be provided a monopole antenna having a radiating element and a ground plane conductor structure defining a non-planar ground plane surface being deformed such that parts of the surface are displaced, relative to other parts thereof, towards the radiating element.

0047For example in a third of its aspects, the present invention may provide a monopole having a radiating element and a ground plane conductor defining a ground plane surface which includes: a substantially planar first surface portion arranged nearmost the radiating element to face the radiating element; and, a second planar surface portion extending away from the first surface portion so as to be non-coplanar therewith and so as to face generally towards the radiating element. In facing generally towards the radiating element, a normal to (and extending from) the second surface converges with a corresponding normal to the first surface portion. For example, the ground plane may be shaped to include two separate planar parts joined (e.g. integrally, at a fold in the ground plane structure) whereby the radiating element is arranged to extend substantially perpendicularly from one of the two planar parts of the (e.g. folded) ground plane and a face (e.g. plane) of the radiating element is arranged to extend across the other of the two planar parts thereof. The invention in its third aspect may also include the features of the invention in its first and/or its second aspects including some, none or all of the variants and preferably features of the first and second aspects as identified above.

0048By shaping the ground plane conductor in this way (e.g. folding or arranging a fold-like structure), the part of the ground plane across which a face (e.g. plane) of the radiating element extends acts to reflect radiation emanating towards it from the radiating element. Consequently the monopole antenna formed by the radiating element together with the ground plane conductor so shaped acts as a directional antenna having a directionality determined by the reflecting portion of the ground plane.

0049The face or plane of the radiating element may be substantially parallel to the plane of the other of the two planar parts of the (e.g. folded) ground plane. In this orientation, signals emanating from the radiating element towards the parallel ground plane part will be reflected directly back towards the formed by the latter.

0050Alternatively, the face or plane of the radiating element may be other than parallel to the plane of the other of the two planar parts of the (e.g. folded) ground plane, such that the separation between the face or plane of radiating element and the part of the ground plane across which it extends varies (e.g. increases) with increasing distance (e.g. along the radiating element) from the feed-point. This has the added advantage of greatly reducing signal cancellations which occur when the separation between the radiating element and the part of the ground plane across which it extends, is equal to one half of the wavelength of a radiated signal. In such cases the signal radiated by the antenna is slightly reduced in magnitude due to such cancellations since the cancelled part of the reflected signal no longer contributes to the whole signal. By varying the separation one ensures that such resonance occurs only at a very small region of the antenna where the half-wavelength separation only occurs regionally.

0051Preferably, the first part of the ground plane across which a face of the radiating element extends, and the second part relative to which it extends perpendicularly, meet each other at an angle of from 90 degrees to 120 degrees thereby resulting in a separation between the first part of the ground plane and the radiating element which is either constant (90° angle) or increases with increasing distance from the feed point (angles between 90° and 120°).

0052In a further aspect the present invention may provide a monopole antenna having a radiating element and a ground plane conductor structure defining a non-planar ground plane surface being deformed such that peripheral parts of the surface are displaced, relative to other parts thereof, away from the radiating element.

0053For example, in the fourth of its aspects, the present invention may provide a monopole antenna having a radiating element and ground plane conductor defining a ground plane surface which includes: a substantially planar central surface portion arranged nearmost the radiating element to face the radiating element; and, an outer surface portion which contains a peripheral part of the ground plane surface, wherein the outer surface portion extends away from the central surface portion so as to be non-coplanar therewith and to face generally away from the radiating element.

0054In facing generally away from the radiating element, the normal to (and extending from) any point on the outer surface portion does not intersect the radiating element, nor is it parallel to any corresponding normal to the central surface portion, but rather, it diverges therefrom.

0055This arrangement presents a generally convex ground plane conductor surface for the radiating element, the surface comprising the planar central surface portion presented towards the radiating element and the outer surface portion not presented towards the radiating element. The outer surface portion may also be planar or may be curved or may have curved regions contiguous with planar regions. For example, the outer surface portion may comprise a planar region extending away from the central surface portion and a contiguous curved region extending away from the planar region wherein the curved region contains a peripheral part of the ground plane surface. In this way, the outer surface portion may contain a curved region in which the peripheral surface in question is displaced to face away from the radiating element to an even greater extent than that to which the planar region of the outer surface portion is so displaced. The radiating element preferably extends/stands substantially perpendicularly relative to the central surface portion of the ground plane surface.

0056The non-coplanar surface portions, and the non-coplanar surface regions within the outer surface portion may be defined by, or joined at, e.g. by a fold/bend or other shaping in the ground-plane structure. This aspect of the invention may also include the features of the invention in any one of its first, second and third aspects including some, none, or all of the variants and preferably features thereof as discussed above in relation to those other aspects.

0057The electric field of the monopole antenna, in use, emanates from the radiating element and terminates at the upper surface of the ground plane conductor. However, when terminating at the peripheral edge of a ground plane conductor, such fields often induce stray currents which, in turn, may induce stray currents in the underside of the periphery of the ground plane. Consequently, stray electric fields which emanate from the stray currents at the ground plane underside may interfere with the antenna signal feed input at the underside of the ground plane. This is undesirable.

0058Such effects of stray electric fields may be reduced by increasing the size of the ground plane and thereby reducing the magnitude of the electric fields reaching its periphery. As a result, the stray induced currents and, thus, the stray electric fields they generate are accordingly reduced. However, to minimise antenna size yet produce the same effect, the invention, in its fourth aspect, proposes displacing the ground plane's peripheral edge (or parts of it) away from the plane of the ground plane and away from the radiating element. This geometry capitalises on the fact that the electric field lines terminating at the ground plane's upper surface must do so at an angle of 90° thereto. Hence, by displacing the upper surface of the peripheral parts of the ground plane away from the source of the electric field lines (i.e. the radiating element) one forces such field lines to loop outwardly in space in order that the field line may terminate at the displaced ground plane upper surface at an angle of 90° thereto.

0059This deforming effect not only causes the relevant electric field lines to traverse a greater distance in space thereby reducing their magnitude at their termination point (and hence the size of stray currents they induce), but also has the effect of increasing the proportion of electric field lines terminating at the upper surface of the undisplaced portion of the ground plane, with a consequent reduction in the proportion of field lines terminating at the upper surface of the displaced ground plane peripheral part, and a consequent reduction in the magnitude of stray currents inducible thereby. This ground plane geometry is equivalent to increasing the planar extent of a fully planar ground plane but obviates the need to do this thereby saving space.

0060Some or all of the periphery of the ground plane may possess radiation absorbing material (RAM) underneath the peripheral parts of the ground plane surface. Where the outer surface portion includes a non-planar region containing a peripheral part of the ground plane surface as discussed above, the non-planar region may be curved or folded through any angle up to and exceeding 180 degrees relative to the planar portion/region of the ground plane from which it extends (e.g. defining a semicircular surface). In such a case the ground plane structure may possess radiation absorbing material (RAM) located between those parts of the non-planar region which face in opposite directions, and most preferably the RAM extends across sufficient area of the underside of the ground plane conductor structure (i.e. the side opposite to, or reverse to, the aforesaid ground plane surface) that said peripheral edge portions of the non-planar region (or its underside) are not exposed to the underside of the outer surface portion of the ground plane surface at least.

0061Preferably, the outer surface portion extends away from the central surface portion at an angle of no more than 90° relative to the plane of the central surface portion (i.e. an angular displacement of the outer surface portion, relative to the central portion, not exceeding 90 degrees).

0062Increasing this angle beyond 90° reduces antenna gain since it results in displaced parts of the ground plane conductor at least partly extending across other parts of the ground plane conductor resulting in dipole-like behaviour which is undesirable in a monopole antenna.

0063The term "ground pane" herein refers to the functional aspect of a ground plane structure of a monopole antenna and includes planar structures as well as non-planar structures which perform this function.

0064The present invention may also provide a portable impulse transceiver apparatus, or an ultra wide-band (UWB) communications apparatus, comprising an antenna according to the invention in any of its aspects.

0065Non-limiting examples of the present invention shall now be described with reference to the accompanying drawings in which: <ul id="ul0001" list-style="none" compact="compact"><li><figref idref="f0001">Fig.1</figref> illustrates the radiating element of a monopole antenna upstanding from a ground plane conductor;</li><li><figref idref="f0001">Fig.2a</figref> illustrates the radiating element of a monopole antenna together with a ground plane conductor, being plane-parallel therewith;;</li><li><figref idref="f0001">Figs. 2b and 2c</figref> illustrate side views of the monopole antenna of <figref idref="f0001">Fig. 2a</figref>;</li><li><figref idref="f0002">Figs.3a, 3b, 3c, 3d and 3e</figref> each illustrate side views of a monopole antenna, with a ground plane conductor either flat or folded in different configurations;</li><li><figref idref="f0002">Fig. 4a</figref> illustrates a monopole antenna with a ground plane folded such that the radiating element extends perpendicularly from one part thereof, and the face of the antenna element extends across another part of the ground plane;</li><li><figref idref="f0002">Fig. 4b</figref> shows a side view of the antenna of <figref idref="f0002">Fig.4a</figref>;</li><li><figref idref="f0002">Fig.4c, 4d and 4e</figref> show side views of a monopole antenna having a fold or a fold like structure in the ground plane thereof which displaces a portion of the peripheral outer edge of the ground plane from the radiating element of the antenna.</li><li><figref idref="f0002">Fig. 4e and 4f</figref> illustrates sides use of the monopole antenna which the ground plane is folded, or has a fold like structure;</li><li><figref idref="f0003">Fig. 5a and 5b</figref> illustrate monopole antennas having a ground plane conductor a peripheral edge portion of which is folded away from the radiating element of the antenna;</li><li><figref idref="f0003">Fig. 6a and 6b</figref> illustrate monopole antennas of a variety illustrated in <figref idref="f0003">Figs. 5a and 5b</figref> respectively;</li><li><figref idref="f0003">Fig. 7</figref> shows a monopole antenna possessing a ground plane structure folded as in the antenna structure illustrated in <figref idref="f0002">Fig. 4a</figref> but with the outer peripheral edge of the portion of the ground plane conductor across which the face of the radiating element extends shaped into a semi- circular edge;</li><li><figref idref="f0004">Fig. 8</figref> illustrates a Smith Chart recording the impedance of a monopole antenna as a function of signal frequency.</li></ul>

0066In the figures like elements have been given the same reference sign for consistency.

0067Referring to <figref idref="f0001">Fig.1</figref> there is illustrated a monopole antenna 1 comprising a planar radiating element 2 comprising a substantially flat sheet of conductive material generally shaped as a segment having two opposed slant edges 6, which diverge outwardly from an apex of the segment. The antenna radiating element 2 has a signal feed-point 5 at the apex of the segment.

0068The two opposed slant edges 6 diverge with increasing distance from the antenna feed-point 5 such that the radiating element 2 tapers outwardly from the feed-point. The radiating element possesses a distal peripheral edge (8, 9 and 10) which bridges the terminal outermost ends of the two opposed slant edges and forms the curved outermost periphery of the radiating element.

0069The radiating element has two identical series of serrations 7b each formed within a respective one of the two opposed slant edges. Each serration of a given series of serrations is formed by a pair of successive angular (tapering) notches 7a which extend into the planar sheet of the radiating element 2 from the respective slant edge 6. Each tapering notch has notch edges which converge to terminate within the sheet 2 of the radiating element at a right-angled apex 7a. Consequently, at the portion of the radiating element in between such pairs of tapering notches there is formed one serration of the series of serrations 7b in the respective slant edge 6.

0070Each such serration, and the series of serrations collectively, presents a slow-wave structure to a signal propagating along the slant edge.

0071Successive serrations of each series of serrations are shaped to increase in size relative to the preceding serrations in a log-period manner. Thus, the serrations in a given series have a common shape. In this example the common shape is a straight-edged serration with two tapering edges extending from the body of the radiating element at predetermined angles and converging at increasing distance from the body of the radiating element to a terminal right-angular serration tip or apex.

0072The converging edges of a given serration may differ in length as in the example in <figref idref="f0001">Fig. 1</figref>, or may be equal in length as in the alternative example shown in <figref idref="f0001">Figs. 2a, 2b and 2c</figref>.

0073In either example, a successive serration in a given series of serrations possess two tapering edges which each extend from the body of the radiating element at the same predetermined angles as occurs in respect of the edges of the preceding serration of the series, and also converge at a right angular serration apex. The ratio of the lengths of the two tapering edges of any given serration is shared by all serrations in the same series since all serrations in a given series share the same general shape. However, due to log-periodic scaling, the lengths themselves increase by a predetermined scaling value such that the ratio of a serration edge length of a given serration and the corresponding edge length of the succeeding serration has a constant predetermining ratio value shared by all such neighbouring serrations.

0074Furthermore, each series of serrations 7b along a respective <figref idref="f0001">Fig. 1</figref> is arrange such that the distance between the location of the feed-point 5 of the radiating element and the location of the serration increase log-periodically as one encounters successive serrations of a given series. The result is that the ratio of the aforesaid distance, as between two neighbouring (successive) serrations, is equal to a constant predetermined ratio value shared by all such neighbouring serrations. The location of the serration may be considered to be the location of the apex or the tip of the serration in question, for example.

0075The antenna 1 also includes a ground plane conductor 3 seen inside-view in <figref idref="f0001">Fig. 1</figref> and perpendicular to the radiating element 2 which extends through an aperture within the centre of the ground plane to which the outer sheet 4 of a coaxial cable is connected. The inner core of the coaxial cable is connected to, and feeds, the antenna feed-point 5 of the antenna radiating element 2. The ground plane conductor 3 spans outwardly from the aperture in its centre in all directions perpendicular to the axis of symmetry of radiating element to form a flat conductor sheet which underlays all parts of the two slant edges 6 of the radiating element and beyond.

0076The distal peripheral edge (8, 9 and 10) of the radiating element bridging the terminal outermost ends of the two slant edges thereof is shaped to partially recede towards the feed-point 5 of the antenna at the mid-region of the outer peripheral edge. The result of this edge recession is the formation of a recess 8 being centred upon the axis of symmetry of the radiating element and being itself symmetrical in shape about that axis. Opposing edges of the recess are linearly shaped to converge inwardly in the direction of edge recession at equal angles (θ/2) relative to the symmetry axis and to converge at a point within the face/plane of the radiating element some distance from the feed-point.

0077The recess thereby not only forms a v-shaped notch having an apex angle θ ( θ &lt;90°) but also shapes the radiating element as a whole into two diverging lobes each being the mirror image of the other across the symmetry access.

0078This divergent lobe structure promotes bifurcation of signals within the radiating element along the divergent directions of the lobes. This has the beneficial effect of maintaining wide elevation beam width in radiated signals and induces a radiated electric field component along the geometrical symmetry axis of the radiating element (i.e. perpendicular to the ground plane) which removes any signal null in that direction and allows signal transmission/detection perpendicular to the ground plane.

0079<figref idref="f0001">Figs. 2a, 2b and 2c</figref> show a plan view and two side views, respectively, of an alternative monopole antenna arrangement 11 according to the present invention. In this alternative, the plane of the radiating element 12 of the antenna is arranged to extend across the ground plane 13 such that the plane of the former is spaced from, but is parallel to, the plane of the latter. Otherwise the structure and functional features of the antenna arrangement of <figref idref="f0001">Figs. 2a, 2b and 2c</figref> are substantially the same as the corresponding features illustrated in <figref idref="f0001">Fig. 1</figref> and discussed above. For example, a given feature of the antenna illustrated in <figref idref="f0001">Fig. 1</figref> assigned a particular reference number may be correspondingly identified in the antenna illustrated in <figref idref="f0001">Figs. 2a, 2b or 2c</figref> using a reference number which differs from the reference number of the corresponding feature in <figref idref="f0001">Fig. 1</figref> by a value of 10. Thus, for example, item 3 of <figref idref="f0001">Fig. 1</figref> and item 13 of <figref idref="f0001">Figs. 2a, 2b or 2c</figref> (i.e. 13 = 3 + 10) both correspond to the ground plane conductor of the respective antennas, while the items 6 of <figref idref="f0001">Fig. 1</figref> and item 16 of <figref idref="f0001">Figs. 2a - 2c</figref> both correspond to equivalent slant edges.

0080With this in mind, and with the exception of the discussion of the orientation of the radiating element 2 relative to the ground plane conductor 3, the reader is referred to the above text describing the antenna of <figref idref="f0001">Fig. 1</figref> for a discussion of the corresponding features of the antenna of <figref idref="f0001">Figs. 2a- 2c</figref>, reference numbers renumbered accordingly.

0081The side view of <figref idref="f0001">Fig. 2b</figref> is a view "edge-on" towards the edge A of the ground plane 13, being the same orientation or view as is used in <figref idref="f0001">Fig. 1</figref>. The side view of <figref idref="f0001">Fig. 2c</figref> is a view "edge-on" towards the edge B of the ground plane. As can be seen in these side views, the outer sheath of the coaxial cable 14 connecting with the ground plane 13 extends through the aperture in the ground plane where it connects to the ground plane, and extends beyond that aperture someway (about halfway) into a space between the ground plane and the feed-point 15 on the overlaying radiating element 12 thereby to provide an impedance matching section.

0082<figref idref="f0002">Fig. 3a</figref> illustrates a side view (edge-on) of a monopole antenna comprising a radiating element 30. The antenna radiating element 30 having a signal feed-point 32 positioned at the base of the radiating element and centred within an aperture arranged within the ground plane sheet 31 (seen edge-on in <figref idref="f0002">Fig. 3a</figref>) from which the radiating element 32 perpendicularly extends.

0083Electric fields emanating from the radiating element and terminating at the periphery of the ground plane upper surface may induce stray currents which, in turn, may induce currents and electric fields at the underside of the ground plane. Such induced electric fields are undesirable.

0084<figref idref="f0002">Figs. 3b and 3c</figref> show different embodiments of an aspect of the present invention which aim to address this undesirable situation. In each of these differing embodiments, a part of the outer peripheral edge 34 of the ground plane 33 is folded (by differing angles) away from the radiating element. This displacement reduces the magnitude of the common mode current induced in the outer periphery of the ground plane. The fold (35 or 36) may be a direct fold integrally formed within the structure and material of the ground plane conductor 33. Alternatively, the fold may be formed at the join of two separate but electrically connected ground plane conductor portions. Of course, it is to be understood that the displacement of the peripheral edge portion 34 of the ground plane conductor away from the radiating element may be achieved by other than a simple fold (35 or 36) and may be achieved by curving the outer regions of the ground plane smoothly and continuously with increasing proximity to the outer peripheral edge portion thereby to suitably displace the edge portion from the radiating element without forming a sharp fold 36.

0085The angular displacement ∀ of the outer peripheral edge portion 34, as measured from the plane of the central parts of the ground plane, is chosen to reduce the magnitude of stray currents induced in the peripheral edge of the ground plane. It is most preferable that the maximum displacement angle ∀ is 90° as illustrated in the example of <figref idref="f0002">Fig. 3c</figref>.

0086It is to be understood that either some or all of the outer peripheral edge of the ground plane may be displaced away from the radiating element of the antenna in the manner described above.

0087<figref idref="f0002">Figure 3e</figref> schematically illustrates the effect of displacing the outer peripheral portion 34 of the ground plane upon the shape of the electric field lines (E) emanating from the radiating element 30 and terminating at the displaced upper surface 34 of the ground plane. In the absence of ground plane displacement, an electric field line E emanating from a point A on the radiating element 30 may terminate at point C of a completely planar ground plane upper surface (33 and 34') the electric field line E impinges upon the upper ground plane surface perpendicularly thereto. Subsequent displacement of the outer surface portion 34 of the ground plane causes the electric field line in question to bulge outwardly so as to enable the field line to terminate at point B of the displaced peripheral surface portion 34 of the ground plane. As is indicated in <figref idref="f0002">Figure 3e</figref>, the deformed electric field line E' intercepts the plane containing the undisplaced central portion of the ground plane surface 33 adjacent the radiating element 30 at a point B' displaced outwardly from the point C at which the undeformed electric field line E previously terminated prior to displacement of the outer peripheral portion 34 of the ground plane surface. Consequently, not only is the length of the deformed electric field line E' greater than that of the undeformed electric field line E, and therefore of smaller magnitude at its point of termination (B), but also any stray electrical currents induced by that field at the peripheral portions of the ground plane surface will be correspondingly reduced.

0088<figref idref="f0002">Figure 3d</figref> schematically illustrates a monopole antenna the outer surface portions of which not only contain planar regions extending from a fold 35 in the ground plane, but also contain peripheral curved surface regions 80 extending from the aforementioned planar regions. The curved peripheral surface regions 80 curve through an angular displacement up to or exceeding 180 degrees with radiation absorbing material (RAM) 90 located between the terminal edge of the ground plane conductor and the opposing underside of the displaced portion of the ground plane conductor. This extreme deformation not only greatly reduces the magnitude of electric field lines emanating from the radiating element 30 and terminating at the extreme periphery of the ground plane conductor surface 80, thereby reducing the magnitude of electrical fields induced by stray currents thereat, but also significantly damps any such induced electrical fields.

0089Referring to <figref idref="f0002">Fig. 4a</figref> there is illustrated a monopole antenna comprising a radiating element 42 fed with signals at a feed-point 43 thereof and being arranged in conjunction with a ground plane conductor 40 to provide a monopole antenna. The ground plane conductor 40 is shaped to include two separate planar parts, 41 a and 41 b, joined at a fold 45 in the ground plane structure such that one of the planar parts 41 b of the ground plane structure extends perpendicularly from the other of the two planar parts 41 a thereof. The view of the antenna of <figref idref="f0002">Fig. 4a</figref> is a view taken "face-on" such that the face of the radiating element 42 is in full view. Conversely, only the edge of the planar part 41 b of the ground plane conductor from which the radiating element perpendicularly extends can be seen in the view provided by <figref idref="f0002">Fig. 4a</figref>. However, due to the folding of the other part 41 a of the two planar parts of the ground plane towards the radiating element 42, the view of <figref idref="f0002">Fig. 4a</figref> provides a complete "face-on" view of that upwardly folding ground plane part.

0090<figref idref="f0002">Fig. 4b</figref> provides a side view (with the antenna of <figref idref="f0002">Fig. 4a</figref> rotated through 90° about the axis of symmetry of the radiating element 42) in which the fold 45 in the structure of the ground plane conductor 40 can be seen. The face of the radiating element 42 is consequently arranged to extend across the face of the upwardly folded part 41 a of the ground plane conductor such that the plane of the radiating element and the plane of the upwardly folded ground plane conductor portion are parallel such that the separation "x" between any point on the face of the antenna structure 42 and any opposing point on the face of the upwardly extended ground plane conductor portion is constant in value.

0091The fold 45 formed in the structure of the ground plane conductor may be a direct and integrally formed fold in the material of the ground plane. Alternatively, the fold may be formed at the join or interconnection between two otherwise separate ground plane conductor portions (i.e. not integrally formed).

0092<figref idref="f0002">Figs. 4c and 4d</figref> illustrate further developments of the embodiment illustrated in <figref idref="f0002">Figs. 4a and 4b</figref>, and like features have been assigned like reference numerals. As can be seen in the embodiments of <figref idref="f0002">Figs. 4c and 4d</figref>, in addition to folding one portion 41 a of the ground plane conductor 40 towards the radiating element 42, the ground plane conductor structure possesses an additional fold, 46 or 49, which displaces an outer peripheral edge portion of the ground plane 47 or 50, away from the radiating element 42 through a displacement angle α of up to 90°. The form, structure and purpose of this displacement of the outer peripheral edge portions, 47 or 50, is as described with regard to the corresponding edge displacements illustrated in <figref idref="f0002">Fig. 3b, 3c and Fig. 3d</figref>.

0093The fold, 46 or 49, about which the outer peripheral edge portion, 47 or 50 respectively, is displaced is a linear fold running parallel to the linear edge of the displaced outer peripheral edge portion in question. Similarly, the fold 45 about which the upwardly folding planar part 41 a of the ground plane structure is upwardly displaced is also a linear fold and runs parallel to the fold, 46 or 49, in the other of the two planar parts, 41 b, about which the aforementioned outer peripheral edge, 47 or 50, is displaced.

0094<figref idref="f0002">Figs. 4e and 4f</figref> illustrate a side view of a monopole antenna comprising a radiating element 42 and a ground plane conductor structure 40 through which the radiating element 42 extends and is fed at a feed-point 43. As in the monopole antenna structures illustrated in <figref idref="f0002">Fig. 4a - 4d</figref>, the ground plane conductor structure 40 is shaped to include two separate planar parts joined at a fold 51 in the ground plane structure 40. The radiating element 42 of the monopole antenna is arranged to extend substantially perpendicularly from one part 41 b of the two planar parts of the folded ground plane structure and the face of the radiating element is arranged to extend across the other part 41 a of the two planar parts of the ground plane. However, the face of the radiating element 42 is other than parallel to the plane of the other part 41 a of the two planar parts of the folded ground plane structure 40, such that the separation "x" between the radiating element 42 and the part 41 a of the ground plane across which the face of the radiating element extends increases with increasing distance from the feed-point 43. This divergence in the separation of opposing faces of the ground plane conductor structure and the radiating element significantly reduces the effect of cancellations as between radiated signals emanating from the radiating element 42 towards the opposing face of the upwardly displaced planar part 41 a of the ground plane, and signals reflected from the latter propagating towards the former.

0095<figref idref="f0003">Figs. 5a and 5b</figref> each illustrates variants of the monopole antennas illustrated in <figref idref="f0002">Fig. 3b and Fig. 3c</figref> respectively. According to these variants, the monopole antenna, which comprises a planar radiating element 52 with serrated slant edges which taper outwardly from a feed-point 53 of the antenna, possesses a ground plane structure 54 possessing displaced outer peripheral edge portions, 56 or 58, which extend in the direction substantially perpendicular to the face of the radiating element 52 and the serrated slant edges thereof. A fold structure, 55 or 57, is formed in the ground plane conductor 54 as a linear fold extending in a direction perpendicular to the face of the radiating element 52, and therefore parallel to the displaced outer peripheral edge portion 56 or 58. The angle α about which the outer peripheral edge portion, 56 or 58, is displaced away from the radiating element 52 is any suitable value not exceeding 90º. In other embodiments all peripheral edge portions (e.g. all four edges of the ground planes illustrated in <figref idref="f0003">Figs.5a and 5b</figref> may be displaced by a suitable angle a.

0096Referring to <figref idref="f0003">Fig. 6a and Fig. 6b</figref> there are illustrated further variants of the embodiments illustrated in <figref idref="f0003">Fig. 5a and Fig. 5b</figref> respectively. In these embodiments, the ground plane is additionally folded along a linear fold running parallel to the face/plane of the radiating element 52 thereby defining two separate but electrically joined planar portions, 60a and 60b, of the ground plane which are perpendicular to each other. This ground plane folding is the same as the folding 45 referred to in conjunction with <figref idref="f0002">Fig. 4b - 4d</figref> and consequently results in the face of the radiating element 52 extending across the face of the upwardly folded portion 60a of the ground plane at a constant separation thereform. Consequently, the antenna embodiments illustrated in the <figref idref="f0003">Fig. 6a and Fig. 6b</figref> each possess a ground plane displaying three fold structures, two of which (items 61 or 63) run parallel to each other and perpendicular to the face of the radiating structure and serve to displace a peripheral edge portion of the ground plane from the view of the radiating element, while a third fold (not shown) runs perpendicular to the aforementioned two parallel folds and parallel to the plane of the radiating element 52 and serves to displace a planar portion of the ground plane 60a towards the face of the radiating element such that the latter extends across the former.

0097<figref idref="f0003">Fig. 7</figref> illustrates a variant in the structure of the antenna illustrated in <figref idref="f0002">Fig. 4a and Fig. 4b</figref> in which the ground plane structure 70 of the antenna is folded along a linear fold to produce two planar ground plane parts, 65a and 65b, whereby the plane of one of the planar parts 65b is perpendicular to the plane of the radiating element 52 whereas the plane of the other of the planar parts 65a is parallel with and directly facing the plane of the radiating elements being spaced therefrom by a constant separation "x". In this variant, the outer peripheral edge 75 of the planar part of the ground plane structure across which the radiating element 52 extends is semi-circular. This shape reduces overall antenna size without any significant reduction in performance.

0098Thus, the present invention, for example, as shown in the above embodiments, may provide an ultra wide-band (UWB) electromagnetic impulse transceiver for applications in short range communications and/or positioning systems. The invention may be implemented in the form of a monopole antenna thereby obviating the need for a balun within the antenna circuitry. The antenna according to the present invention in any of its embodiments has the important benefit of being sufficiently small for use as a portable impulse transceiver.

0099Furthermore, monopole antennas structured according to the present invention in its first aspect display up to a decade of bandwidth, have reduced aperture clutter with moderate signal loss and have relatively small physical size.

0100<figref idref="f0004">Figure 8</figref> illustrates a Smith Chart 85 displaying the change in impedance of a monopole antenna having a radiating element possessing log-periodically scaled slant edge serrations such as is illustrated in <figref idref="f0001">Figs.1, 2a</figref>, <figref idref="f0002">4a</figref>, <figref idref="f0003">5a, 5b, 6a, 6b and 7</figref>.

0101The Smith Chart illustrates the variation in antenna impedance across a bandwidth of signal frequencies extending from T₀=0.045GHZ to T₂=20GHZ. Starting at near an open circuit impedance at low signal frequency To, the impedance trace 80 of the serrated radiating element in question initially follows a clockwise looping trajectory which converges towards the "zero-reactance axis" 86 of the Smith Chart in a manner similar to that expected from prior art monopole antennas.

0102The trajectory 81 illustrated in <figref idref="f0004">Figure 8</figref> provides a representative example of the spiralling trajectory one typically expects of prior art large diameter monopole antennas, and has been included in <figref idref="f0004">Figure 8</figref> for the purposes of comparison.

0103However, at an intermediate frequency value of T₁=3.6GHZ the trajectory 80 of the impedance of the present monopole antenna begins to diverge from the spiralling trajectory form typically expected. As can be seen, the reactive component of the impedance begins to stabilise upon a constant value as the signal frequency increases further. Indeed, across the signal frequency range T=T to T=T", the impedance trajectory 80 is almost completely constrained to follow a path of constant reactance (of a low value).

0104As is well known in the art, the nature of a Smith Chart is that the axis of the chart include circular segments such as segments 87, 88 and 89 which each separately define a locus of impedance values in which only the resistive component of the impedance changes along the line, while the reactive component remains constant. Indeed, the axis 86 represents a special case of this in which the reactive impedance component is 0.

0105Thus, it can be seen that the portion of the trajectory 80 located between signal frequency values T' and T" closely follows a constant reactance line of the Smith Chart just below the zero-reactance line 86. This near constancy in the reactance of the antenna greatly assists in reducing the occurrence of impedance mismatches arising within the antenna over frequency values ranging from T to T" at least.

0106The antennas illustrated in <figref idref="f0001">Fig.1</figref>, <figref idref="f0002">Fig.3a to 3c</figref> and <figref idref="f0003">Figs.5a and 5b</figref> are "omnidirectional" being unlimited in their azimuthal direction of radiation. For a particular embodiment of this invention, it was found that the 140 degree (10 dB) elevation beamwidth extends from about -60 degrees to about +80 degrees relative to the position of the ground plane. The antenna illustrated in <figref idref="f0001">Figures 2a to 2c</figref> and <figref idref="f0002">4a to 4f</figref> and <figref idref="f0003">Figures 6a, 6b and 7</figref> show different types of "unidirectional" antenna which are designed to radiate in a specific (limited) range of directions.

0107It is to be understood that variants of the above described examples of the invention in its various aspects, such as would be readily apparent to the skilled person, may be made without departing from the scope of the invention in any of its aspects.