Angle modulated signal receiving apparatus.

The present invention relates to a wireless receiver set which has the facility to measure the receive frequency for automatic frequency control in a communication system using angle modulated signals (ie.frequency or phase modulated signals). The present invention is particularly applicable to a mobile subscriber set using a narrow band in UHF band.

The drift of carrier frequency degrades the transmission characteristics considerably. The frequency drift deteriorates the distortion, frequency response characteristics, and/or error rate in the passband and furthermore, that frequency drift increases the undesirable leakage power to adjacent channels. In order to prevent the effect of the frequency drift, one of the following must be taken. <ul id="ul0001" list-style="none"><li>a) The communication system is designed so that the interval of the radio channels is considerably large as compared with the bandwidth of each channel.</li><li>b) A local oscillator and/or modulator which might cause the frequency drift is sufficiently stable.</li><li>c) The frequency drfit is measured, and the drift is compensated for automatically.</li></ul>

Among them, the first one is not practical, since the wireless channels are limited in number and bandwidth.

The second proposal is also not practical in case of a mobile subscriber set, although it is useful for a fixed base station which may install a highly stable standard oscillator, since a small subscriber set must be simple in structure and can not have a highly stable standard oscillator. A TCXO (Temperature Compensated Crystal Oscillator) has been known for compensating frequency drift of carrier frequency due to temperature change. However, when a TCXO is installed in a mobile subscriber set, the frequency stability is practically up to 1-1.5 ^ppm (I PPm=10^-6).

Further, a DTCXO system (Digitally Temperature Compensated Crystal Oscillator) is proposed in IEEE Proc. 37th Frequency control symposium pp434-441, by T.Uno et al, in which a memory stores the frequency change by temperature change, and a capacitance array is adjusted according to the measured temperature and the content of the memory, has been proposed. However, that DTCXO system can not compensate secular change of an oscillator, although it can provide the stability up to I ppm.

The above third proposal is classified into two methods.

a) AFC (Automatic Frequency Control)

FigJ shows a block diagram of an automatic frequency control system which has been used in a prior FM receiver. An FM signal received by an antenna 1.1 is frequency converted by a mixer 1.3 which receives a local frequency of a local oscillator 1.2. The IF signal (Intermediate Frequency signal) which is the output of the mixer 1.3 is applied to a frequency discriminator 1.5 through an IF amplifier 1.4. The demodulated speech signal is obtained at the output 1.6 of the frequency discriminator 1.5. Since the frequency discriminator 1.5 provides a DC voltage which is proportional to frequency error of an input frequency, or the error of the input frequency from the center frequency of the frequency discriminator, that DC voltage is applied to a variable capacitance diode 1.8 through a level converter 1.7 which adjusts the voltage level of that DC voltage to the proper voltage for the operation of the variable capacitance diode 1.8. The variable capacitance diode 1.8 is a component of a resonant circuit of a local oscillator. When the local frequency of the variable frequency oscillator 1.2 drifts, the IF frequency then drifts, and the amount of the drift induces the DC voltage at the output of the discriminator 1.5. That DC voltage is applied to the variable capacitor diode 1.8 so that the DC voltage or the frequency error is decreased.

However, the prior system of FigJ has the disadvantage that the frequency stability is not enough for narrow band mobile communication, since the error of the center frequency of a frequency discriminator can not be less than 0.5 kHz on the condition of massproduction. In other words, the frequency error of the local oscillator can not be less than the error of the center frequency of a discriminator. Therefore, the system of FigJ can not be used in an application which requires very small frequency drift.

b) Phase lock of a local oscillator to receive frequency

Fig.2 shows a block diagram of another prior art (Japanese patent publication 1544/65), in which a local oscillator is phaselocked to a receive frequency which is sufficiently stable. In Fig.2, the numeral 2.1 is a reception antenna, 2.2 is a first receiver for communication, 2.3 is a second receiver for frequency control for receiving a reference frequency from a base station. The second receiver 2.3 provides the received reference frequency to the phase detector 2.4. The numeral 2.5 is a voltage controlled crystal oscillator, output of which is applied to the phase detector 2.4. The output of the phase detector 2.4 is applied to the oscillator 2.5. Thus, the output frequency of the oscillator 2.5 is locked to the reference frequency from the base station.

The local oscillator for the first receiver 2.2 has another phase detector 2.6, a voltage controlled oscillator 2.7 and a frequency divider 2.8. The output of the crystal oscillator 2.5 is compared with the output of the voltage controlled oscillator 2.7 through the frequency divider 2.8, and the output of the phase detector 2.6 controls the voltage controlled oscillator 2.7 so that the oscillator 2.7 is locked to the crystal oscillator 2.5. Therefore, the accuracy or the stability of the oscillator 2.7 is the same as that of the base station. Since the reference frequency from the base station is supposed to be accurate enough, the local frequency in the configuration of Figure 2 is also accurate.

However, the system of Figure 2 has the following two disadvantages. First the receive side requires not only a first receiver 2.2 for communication, but also a second receiver merely for receiving reference frequency. Thus, the structure of the receiver set is complicated. Further, the transmission of the reference frequency merely for frequency control of a receiver is not desirable in view of the use of a valuable frequency band. Secondly, when the fading is severe, and the receive level is low, it suffers from much phase change, the phase lock loop would not operate correctly, and the regeneration of the reference frequency would be impossible.

In accordance with the present invention, angle modulated receiving apparatus comprises a standard oscillator; at least one frequency mixer for converting a received radio frequency signal to a first intermediate frequency signal by using the local frequency from the oscillator; a limiter for limiting the amplitude of the first intermediate frequency signal; a discriminator coupled to the output of the limiter for demodulating the angle modulated signal; monitoring means including a digital frequency counter coupled with the output of the limiter to monitor the first intermediate frequency; and control means provided for adjusting the frequency of the oscillator depending upon the output of the digital frequency counter.

The invention provides a receiver such as a mobile subscriber set which is free from distortion, data transmission error, and leakage power to adjacent radio channels.

The main concept of the present invention is to measure intermediate frequency at a mobile subscriber set based upon the facts that (I) it is possible to use an amplitude limiter to suppress receive level change in angle modulation system, (2) a noise generated in the limiter may be removed simply by using a bandpass filter or a phase locked loop, (3) an error of a local frequency of a receiver is kept in an intermediate frequency even when a radio receive frequency is converted to the intermediate frequency by a plurality of frequency mixers, (4) an intermediate frequency which is relatively low frequency accurately by using a digital counter, (5) a time base signal for operating the digital counter has not to be a highly accurate one when the frequency to be measured is low, (6) the structure of the digital counter is simple, and is implemented merely by a single middle scale integration circuit.

Thus the intermediate frequency of the receiver is measured based upon the above facts and the assumption that the transmit frequency of for example a mobile base station is accurate in order to detect an error of a local frequency of a receiver.

Further, when a receiver is a multi-conversion receiver, the error of the measurement due to the error of a second local frequency is compensated by calculating the intermediate frequency with a time base signal by a first local frequency, and other local frequencies.

Some examples of apparatus in accordance with the present invention and some known apparatus are illustrated in the accompanying drawings, in which:- <ul id="ul0002" list-style="none"><li>Figure 1 is a block diagram of a prior AFC circuit,</li><li>Figure 2 is a block diagram of a prior receiver which has an oscillator locked to a high precision frequency standard,</li><li>Figure 3 is a block diagram of an example of a receiver according to the present invention,</li><li>Figure 4 illustrates the variation of measured frequency with receive level obtained by the experiment,</li><li>Figure 5 is a block diagram of another embodiment of the receiver according to the present invention,</li><li>Figure 6 is a block diagram of still another embodiment of the present invention,</li><li>Figure 7 is a block diagram of still another embodiment of the present invention,</li><li>Figure 8 is a block diagram of still another embodiment of the present invention,</li><li>Figure 9 is a block diagram of still another embodiment of the present invention, and</li><li>Figure 10 is a block diagram of still another embodiment of the present invention.</li></ul>

In Figure 3 the numeral 3.1 is a frequency standard oscillator using a temperature compensated quartz crystal oscillator (TXCO). The numeral 64 comprises a frequency synthesizer with a phase detector 3.2, a voltage controlled oscillator (VCO) 3.3 and a frequency divider 3.4. The frequency synthesizer 64 provides the first local frequency FL for the first mixer 3.6. It should be appreciated that the output of the frequency synthesizer is locked or has some relation with the standard frequency of the oscillator 3.1. The receive signal from the antenna 3.5 is applied to the first frequency mixer 3.6 which converts the receive frequency to the first intermediate frequency using the first local frequency FL1 which is the output of the frequency synthesizer 64 (or the output of the voltage controlled oscillator 3.3). The mixer 3.6 provides the sum and the difference of the receive frequency and the first local frequency. The first intermediate frequency filter 3.7 selects one of them as a first intermediate frequency. The first intermediate frequency F_if is applied to the second mixer 3.9 which converts the input frequency Fi_fby using the second local frequency F_L2 from an oscillator and provides the sum and the difference of F_I1 and F_L2. The second intermediate frequency (IF) filter 3.10 selects one of them as the second intermediate frequency. The second IF frequency is for instance 455 kHz.

In a mobile communication system using VHF/UHF band, a double conversion receiver is used because carrier frequency is considerably higher than a reasonable intermediate frequency, and an intermediate frequency cannot be so high since a high gain amplifier in that high intermediate frequency can not be obtained. Therefore, the present embodiment takes a double conversion receiver.

The output of the second IF filter 3.10 is applied to an amplitude limiter 3.11 which limits or amplifies an input signal so that the amplifier saturates or the amplitude of the signal is limited. The discriminator 3.12 coupled with output of the limiter 3.11 demodulates angle modulated signal to a baseband signal, which is provided to an output terminal 3.15.

Simultaneously, the output of the limiter 3.11 is applied to the digital frequency counter 3.14 through the noise canceller 3.13, which is implemented for instance by a bandpass filter so that wideband noise generated by the limiter is cancelled.

The timebase signal for the digital counter 3.14 is provided by the frequency standard oscillator 3.1 such as a quartz oscillator through a frequency divider 3.17, and the oscillation frequency of the oscillator 3.1 is controlled by the measured result from the counter 3.14 through the control circuit 3.16. The control circuit 3.16 compares the measured result from the counter 3.14 with a reference value, and provides the control analog voltage to the oscillator 3.1 depending upon the error which is the difference between said reference frequency and the measured frequency. The time base signal applied to the counter 3.14 operates the counter 3.14 so that the counter 3.14 counts input pulses during a gate signal defined by a time base signal. The time base signal from a standard frequency oscillator in a mobile subscriber receiver is enough for high precision measurement when the intermediate frequency is around 455 kHz, because the error is less than 45.5 Hz when the accuracy of the standard oscillator is 10-⁴, which is obtained easily.

The measurement accuracy when the time base signal by the standard oscillator 3.1 is used is now analyzed.

It is assumed in Fig.3 that the receive frequency frcm the antenna 3.5 is F_a, the first intermediate frequency is F_i1, the first local frequency is F_L1, the second intermediate frequency is Fi₂, the second local frequency is F_L2, the error of the standard oscillator (TCXO) which is used for the first local frequency is ε₁, the error of the second local frequency is s₂, the measured second intermediate frequency is Then, the following equation is satisfied.<maths id="math0001" num=""><img file="EP0253680A2_D0001.tif" /></maths>

When the error of the standard oscillator (TCXO) is ε₁, the first local frequency <o>F</o>_<o>L1</o><o></o>becomes as follows.<maths id="math0002" num=""><img file="EP0253680A2_D0002.tif" /></maths>

Assuming that the error s₂ of the second local frequency is zero, the second intermediate frequency <o>F</o>_<o>i2</o><o></o>is as follows.<maths id="math0003" num=""><img file="EP0253680A2_D0003.tif" /></maths>

The measured second intermediate frequency is as follows when the standard oscillator TCXO is used as a time base sianal.<maths id="math0004" num=""><img file="EP0253680A2_D0004.tif" /></maths>

The measurement error ΔF_i2 is shown by the equation (5).<maths id="math0005" num=""><img file="EP0253680A2_D0005.tif" /></maths>

The calculated examples of the value ΔF_i2 is shown in the table I where F_a=872.5 MHz, F_L1 =782.5 MHz, F_L2=89.455 MHz, Fi_l =90 MHz, and Fi₂=455 kHz. <tables id="tabl0001" num="0001"><img file="EP0253680A2_D0006.tif" /></tables>

The ppm means the error of 10-⁶.

It should be noted that the error of the local frequency is kept in the intermediate frequency even when the radio frequency is converted to the intermediate frequency. So, high accurate measurement is possible by measuring the second intermediate frequency which is considerably lower than the radio frequency and/or the first local frequency.

Fig.4 shows the curves showing the effect of the fading to the measured result, in which the maximum Doppler frequency is 40 Hz which corresponds to the moving speed of approximate 50 km/hour in 800 MHz. In Fig.4, the vertical axis shows the measured frequency, the horizontal axis shows the receive signal level, and the figures in the curves show the standard deviation (Hz). The modulation signal in Fig.4 is a pseudo speech signal having the average modulation index 1.5 (rad/s) and the split phase coded PN data signal multiplexed under said speech signal spectrum with the maximum frequency deviation 0.6 kHz. The gate time of the time base signal of the counter is 1.0 second. The sensitivity of the receiver (12 dB SINAD) is 0 dBµ, and the passband is 8 kHz. Fig.4 shows that the standard deviation of the measured value under fading is only 10 Hz when the receive signal level is 10 dBp.. So, it should be noted that this provides sufficient measurement accuracy.

Fig.5 shows a block diagram of another embodiment of the present invention, in which the measurement error due to the drift of the second local frequency is compensated.

In the figure, the numeral 50 is an antenna, 52 is a receiver which includes a first mixer, a second mixer, a first IF filter, a second IF filter, a limiter, and a second local oscillator, so 52 corresponds to 3.6, 3.7, 3.8, 3.9, 3.10 and 3.11 in Fig.3. The numeral 54 is a noise canceller, and corresponds to 3.13 in Fig.3. The numeral 58 is a digital frequency counter corresponding to 3.14 in Fig.3. The numeral 60 is a control corresponding to 3.16 in Fig.3. The numeral 62 is a frequency divider corresponding to 3.17 in Fig.3. The numeral 64 is a frequency synthesizer corresponding to 64 (3.2, 3.3 and 3.4) in Fig.3. The numeral 66 is a standard oscillator such as a quartz crystal oscillator corresponding to 3.1 in Fig.3. The numeral 56 is a switch for selecting an input of the counter 58 between an output of the noise canceller 54 and the second local frequency of the receiver 52 according to the output of the control 60. The output of the counter 58 is applied to the control 60 which performs the calculation for the compensation of the second local frequency, and is simply implemented by a single chip micro-processor. Other structure of Fig.5 is the same as that of Fig.3. The output of the synthesizer 64 may also be used as a transmit frequency.

The compensation of the error in the second local frequency is analyzed below.

The second local frequency is measured by the counter 58 with the time base signal from the standard oscillator 66 through the frequency divider 62, as is the case of the embodiment of Fig.3.

The measured value is:<maths id="math0006" num=""><img file="EP0253680A2_D0007.tif" /></maths>

When the switch 56 is switched to the second local freauencv. the measured value is;<maths id="math0007" num=""><img file="EP0253680A2_D0008.tif" /></maths>

Those two measured values are added to each other.<maths id="math0008" num=""><img file="EP0253680A2_D0009.tif" /></maths>

It should be noted that the equation (8) does not include (s₂) which is the error of the second local frequency. Since Fi₂ and F_L2 are known, and F_L1 is determined when the receive channel is determined, the error (₈₁) of the first local frequency is given as follows from the equation (8).<maths id="math0009" num=""><img file="EP0253680A2_D0010.tif" /></maths>Thus, the error of the first local frequency, or the error of the receive frequency is measured, irrespective of the error of the second local frequency.

The equation (6) has the assumption that the second local frequency is the lower local frequency. When the second local frequency is the upper local frequency, the equation (6) is changed as follows.<maths id="math0010" num=""><img file="EP0253680A2_D0011.tif" /></maths>

When the equation (7) which is the measurement result of the second local frequency is subtracted from the equation (10), the error (si) which is free from the error of the second local frequency is given as follows.<maths id="math0011" num=""><img file="EP0253680A2_D0012.tif" /></maths>

The control 60 connects the counter 58 to the noise canceller 54, by controlling the switch 56, then, connects the counter 58 to the second local frequency by switching the switch 56. Then, the equation (9) or (II) is calculated in the control 60.

Fig.6 shows a block diagram of another embodiment of the present invention. The feature of the embodiment of Fig.6 is that the second local frequency is obtained by multiplying or dividing the standard frequency. The same numerals in Fig.6 show the same members as those in Fig.3. When necessary, the output of the synthesizer 64 is used for the frequency for a transmitter of a mobile subscriber set.

The numeral 3.8a is a frequency multiplier coupled with the output of the standard frequency oscillator 3.1 and the second mixer 3.9 so a multiple frequency of n times the basic frequency Fs is obtained. Thus, the second local frequency F_L2=n•Fs is obtained, where Fs is the output frequency of the standard oscillator (TCXO) 3.1.

When the second local frequency is n.Fs (n is an integer), the second IF (Intermediate Frequency) is as follows.<maths id="math0012" num=""><img file="EP0253680A2_D0013.tif" /></maths>So, accuracy of the second local frequency is the same as that of first local frequency, but can not select arbitrary. However, it should be noted that said restriction of the second local frequency is not serious.

When the second local frequency is locked to the first local frequency, it becomes possible to control the second local frequency itself.

When a multiple channel synthesizer is used as a first local oscillator, the equation (12) is chanqed to;<maths id="math0013" num=""><img file="EP0253680A2_D0014.tif" /></maths>where K is the lowest frequency of the first local frequencies, and Ch is the channel number, M is the ratio of the standard frequency to the phase comparison frequency of the frequency synthesizer.

Thus, it should be appreciated in the equation (13) that the error of the second local frequency depends upon only the error of the standard oscillator.

Assuming that both the first local and the second local use the lower locals, when the standard frequency has the error so that the standard frequency is lower than the desired frequency, the second IF frequency is simultaneously lowered. Therefore, the control 3.16 intends to compensate the error so that the standard frequency is increased, depending upon the difference between the desired nominal second IF frequency and the measured second IF frequency (equation (4)). The control is performed until the measured second IF frequency coincides with the nominal frequency or the error becomes less than an allowable value. Similarly, when the standard frequency is higher than the nominal value, the measured second frequency F_L2 becomes higher than the nominal value, and so the control 3.16 controls the standard oscillator so that the output frequency is lowered.

Therefore, it should be appreciated that the error of the second local frequency is removed, although that error of the second local frequency can not be removed in the prior art.

The first local frequency and the second local frequency may be the higher frequencies. However, the combination in which the first local frequency is the higher one, and the second local frequency is the lower one, and/or the combination that the first local frequency is the lower one and the second local frequency is the higher one is impossible in the structure of Fig.3.

As for the restriction of the second local frequency, it is not serious. For instance, when the first IF is 90 MHz which is popular in mobile communication, and the standard frequency of TCXO is 12.8 MHz, the second IF may be 400 KHz, by selecting the second local frequency to be 7 times of the standard frequency (7 x 12.8) and to be the lower local frequency.

Fig.7 is a block diagram of still another embodiment of the present invention. In Fig.7, the same numerals as those in Fig.5 show the same members as those in Fig.5. The feature of the embodiment of Fig.7 is that the receiver 52m is able to provide the receiver input level, the control 60a accepts the receiver input level signal, and the presence of the sample hold circuit 70.

The control 60a carries out the control as described in accordance with Fig.5 only when the receiver input level is higher than a predetermined value by applying the TCXO control signal to the sample hold circuit 70. When the receiver input level is lower than the predetermined level, the control 60a does not provide said TCXO control signal but provides the sample hold control signal.

The sample hold circuit 70 operates as follows. When the TCXO control signal is active, that signal is transferred to the standard oscillator 66 to control the same. When the control of the standard oscillator 66 finishes, the TCXO control signal stops, and the sample hold circuit 70 keeps the control signal just before the TCXO signal stops. Then, the control of the standard oscillator is carried out by the signal kept in the sample hold circuit 70. When the receiver input level is lower than the predetermined value, the control of the standard oscillator 66 is of course performed by the control signal kept in the sample hold cirucit 70.

The embodiment of Fig.7 is advantageous since the control is performed only when the receiver input level is higher than a predetermined value, and therefore, the control is not disturbed by noise in case of deep fading. Further, it should be appreciated that the TCXO is so stable that no continuous control is necessary, but an intermittent control, for instance once a year is enough for keeping frequency stability.

Preferably, the sample hold circuit 70 has a battery power source which operates even when a main switch of a mobile subscriber set is off so that the frequency is accurate when the receiver set is switched on next time.

Fig.8 is a block diagram of still another embodiment according to the present invention. The same numerals in Fig.8 as those in Fig.5 show the same members as those in Fig.5.

The feature of the embodiment of Fig.8 as compared with that of Fig.5 is that the embodiment of Fig.8 has a pair of receivers 52a and 52b, each of which is the same as the receiver 52m in Fig.7 which provides the receive signal level information. The embodiment of Fig.8 has also a level comparator 80 which compares the receive level of each receiver, and a switch 82 to select one of the receivers so that the receiver with the higher receive level is selected.

Therefore, the configuration of Fig.8 is a so-called space diversity system having a pair of antennas 50a and 50b, and a pair of receivers 52a and 52b, together with the level comparator 80 and the switch 82. Other portions of Fig.8 are the same as the embodiment of Fig.5.

The embodiment of Fig.8 has the advantage that the frequency control is carried out depending upon the higher receive signal, and therefore, the frequency control is not disturbed by noise when the receive signal level is low because of fading.

Fig.9 is a block diagram of still another embodiment according to the present invention. The feature of the embodiment of Fig.9 is that both the second IF frequency and the second local frequency are measured and those two measured values are calculated to compensate the error of the first local frequency.

The same numerals in Fig.9 as those in Fig.3 show the same members as those in Fig.3. The numeral 52 is a receiver which includes the first mixer, the second mixer, the first IF filter, the second IF filter, and the amplitude limiter. The receiver 52 provides not only the second IF output signal, but also the second local frequency. The embodiment of Fig.9 has a pair of digital frequency counters 3.14 and 3.14a, a calculator 90 for calculating the outputs of those counters, a reference data 94 which provides the correct value of the first IF frequency, and a comparator 92 for comparing the output of the calculator 90 with the output of the reference data 94. The output of the comparator 92 is applied to the control 3.16 which controls the standard oscillator (TCXO) 3.1.

It is assumed that the receive frequency at the antenna 3.5 is F_a, the first local frequency is FL 1, the first IF frequency is Fi₁, the second local frequency is F_L2, and the second IF frequency is Fi₂. Then, the relationship of the table 2 are satisfied. <tables id="tabl0002" num="0002"><img file="EP0253680A2_D0015.tif" /></tables>

When we intend to compensate the first local frequency based upon the measurement of the second IF frequency, the error of the second local frequency must be compensated. If the first IF frequency is measured, it would be possible to compensate the first local frequency based upon the meaured first IF frequency. However, since the first IF signal is low in level, so it would be difficult to measure the first IF frequency directly. Therefore, the present embodiment measures both the second IF frequency and the second local frequency, instead of the first IF frequency, and provides the equivalent first IF frequency through the calculation based upon said table 2.

The first local frequency is calculated from the second local frequency and the second IF frequency as shown in the table 2. Therefore, the measurement of the second IF frequency and the second local frequency is enough for providing the error of the first local frequency.

In Fig.9, the calculator 90 provides the sum (when the second local frequency is the lower one) or the difference (when the second local frequency is the upper one) of the second local frequency and the second IF frequency to provide the first local frequency. It should be noted that when the second local frequency has some error, that error appears in the result of the calculator 90. The comparator 92 compares the output of the calculator 90 (measured first local frequency) with the reference first local frequency from the reference data 94, and the difference between those two values is applied to the control 3.16, which controls the standard oscillator 3.1 so that the output of the comparator 92 becomes zero. Thus, the frequency synthesizer 64 is adjusted considering the error of the second local frequency.

Fig.10 is a block diagram of still another embodiment according to the present Invention. The feature of the embodiment of Fig,10 is that the frequency error of a subscriber set is measured in a base station, and the measured result is transmitted to the subscriber set through radio channel. Then, the subscriber set adjusts the error according to the error information from the base station.

The transmit frequency F2 of the subscriber set is received by the receiver 120 in the base station through the antenna 122. The frequency counter 118 which Is a digital frequency counter measures the IF frequency in the receiver of the base station. When the result of the measurement by the counter 118 has the error higher than the allowable value, the error which the subscriber set must remove is coded In the calculation coding circuit 116, and the coded information is transmitted to the subscriber set through the modulator 110, the transmitter 108, and the antenna 106, with the transmit, frequency FI.

It should be appreciated that the measurement in the base station using the standard oscillator 114 and the frequency synthesizer 112 is quite accurate, since the base station is a fixed large station, and so, can use the best available standard oscillator with the good temperature compensation.

The subscriber set receives that error information by the receiver 52 through the antenna 50. The demodulator 100 demodulates the coded error information. And, the control 60 decodes the signal, and controls the standard oscillator (TCXO) 66 according to the decoded error signal. So, it is supposed that the output of the control 60 is essentially the same as the output of the 3.16 in Fig.3.

The measured data in the base station is transmitted to the subscriber station through one of the following means. <ul id="ul0003" list-style="none"><li>a) Data signal transmission multiplexed in the lower side of a speech band.</li><li>b) Data transmission through common control signal, which is used at the initial stage of a mobile communication including channel switching, identification of a subscriber set, and/or a channel number. The measured data is carried in that common control signal.</li><li>c) Data transmission through common control signal during speech. When the error compensation must be carried out during speech, the speech must be interrupted for a short while. The base station sends the particular tone signal, and then, sends the common control signal which carries the measured frequency error information. The subscriber set recognizes the measured error signal, which follows the particular tone signal which functions a trigger signal of the frequency compensation operation.</li></ul>

As a modification of the present invention, when a subscriber set has separate independent local oscillators for a receiver and a transmitter, respectively, both the local oscillators can be adjusted. First, a local oscillator for a receiver is adjusted as mentioned in accordance with Fig.3, or one of Figs.5 through 10. Then, an input of a synthesizer of a receiver is switched to an output of a standard oscillator of a transmitter so that the reception is carried out using a standard oscillator of a transmitter. So, as in the case of the adjustment of a receiver, the measurement of IF frequency and the adjustment of a standard oscillator according to the measured result provides the adjustment of the standard oscillator of a transmitter. After the adjustment, the standard oscillator of a transmitter is coupled with a synthesizer of a transmitter.