Plug/jack system having pcb with lattice network

(54) Title: JACK FOR USE IN ONE (57) Summary:

PLUG-JACK COMBINATION IN A COMMUNICATION SYSTEM (30) Unionist Priority: 3/18/2008 us 12/050550, 3/20/2007 US 60/895853 (73) Owner (s): Panduit Corp.

(72) Inventor (s): Masud Bolouri-Saransar, Ronald A. Nordin, Wayne C. Fite (74) Attorney (s): Momsen, Leonardos & CIA.

(86) International Order: pct US2OO8O57413 of 19/03/2008 (87) International Publication: wo 2008 / 115945of 25/09/2008

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“JACK FOR USE IN A PLUG-JACK COMBINATION IN A COMMUNICATION SYSTEM”

REFERENCE TO OTHER ORDERS

The present application claims priority for US Patent Application No. 12 / 050,550, filed on March 18, 2008 and US Provisional Patent Application No. 60 / 895,853, filed on March 20, 2007, both of which are incorporated herein by reference. in its entirety. This application incorporates by reference in its entirety US Patent No. 7,153,168, issued on December 26, 2006 and entitled “Electrical Plug / Jack System with Improved Crosstalk Compensation”.

BACKGROUND OF THE INVENTION

1. Technical Field

The present application relates to a plug / jack system and, in particular, a plug / jack system containing a lattice to reduce crosstalk in the plug / jack system.

2. Description of the Prior Art

In the communications industry, as data transmission rates have steadily increased, crosstalk due to capacitive and inductive couplings between conductors in parallel closely spaced inside a jack and / or plug has become increasingly problematic. Plug / jack systems with improved crosstalk performance have been designed to meet increasingly demanding standards. Many of these improved plug / jack systems have included designs described in US Patent No. 5,997,358, the entirety of which is incorporated herein by reference. In particular, the recent plug / jack systems introduced predetermined amounts of crosstalk compensation, to cancel offending crosstalk. Two or more compensation zones are used to be responsible for the phase shifts between compensation and crosstalk. As a result, the magnitude and phase of the offending crosstalk is compensated by the compensation which, together, has an equal magnitude, but opposite phase.

Recent transmission rates have exceeded the capabilities of the techniques described in US Patent No. 5,997,358. Thus, improved compensation techniques were needed.

SUMMARY f

A multi-zone plug / jack system is provided. These zones include a contact zone, a compensation zone and a crosstalk zone. In the contact zone, the plug contacts of a plug connect with the jack spring contacts of a jack at the plug / jack interfaces of the jack spring contacts. The contact zone provides crosstalk in the plug / jack system. The trim zone provides a trim signal that compensates for crosstalk in the plug / jack system. The jack's crosstalk zone adds delayed crosstalk in phase. A PCB connected to the jack spring contacts contains a crosstalk zone. The compensation zone can be provided, for example, in the PCB containing the crosstalk zone, in a PCB arranged between the plug / jack interfaces and in the PCB containing the crosstalk zone and / or by forming the jack spring contacts. The conductors of the compensation and crosstalk zones are connected to the jack spring contacts. At least one of the compensation and crosstalk zones contains a coupling between first and second conductor pairs, which can be modeled as a lattice network. The truss network includes a crosstalk circuit component and a compensation circuit component, each of which has a different coupling rate vs. frequency. In one embodiment, the truss network includes an LC circuit in series between a first conductor of the first conductor pair and a first conductor of the second conductor pair and an LC circuit in series between a second conductor of the first conductor pair and a second conductor from the second conductor pair. The truss network also contains a shunt capacitor between the first conductor of the first conductor pair and the second conductor of the second conductor pair and a derivation capacitor between the second conductor of the first conductor pair and the first conductor of the second pair of conductors. conductors. The coupling frequency response slope of the truss network is designed to be higher or lower than the coupling frequency response slope of a first order coupling (such as a purely capacitive coupling), depending on the zone in question. that the lattice is arranged.

BRIEF DESCRIPTION OF THE DRAWINGS

Exemplary embodiments are described below with reference to the accompanying drawings.

Figs. 1A and IB are simplified block diagrams of a plug / jack compensation system.

Fig. 2 illustrates a schematic model of the three-zone plug / jack system of Figs. 1A and IB, showing only wires 3, 4, 5 and 6.

Figs. 3 (i), 3 (ii) and 3 (iii) show a circuit model schematic having only capacitive coupling, only mutual inductive coupling and a lattice network, respectively, in the compensation zone.

Figs. 4 (i), 4 (ii) and 4 (iii) show a schematic of the circuit model having capacitive coupling and mutual inductive coupling, LC circuit coupling in series and a lattice network, respectively, in the crosstalk zone.

Figs. 5A and 5B are simulations of the magnitude response and phase shift, respectively, of networks operating in the crosstalk zone.

Figs. 6A and 6B are simulations of the magnitude response and phase shift, respectively, of a lattice network and a first order coupling operating in the compensation zone.

Figs. 7A and 7B illustrate a simplified vector model of a three-zone RJ45 plug and jack system at various frequencies, when a first order coupling and a lattice, respectively, are used in the compensation zone.

Figs. 8A and 8B illustrate a simplified vector model of a three-zone plug and jack system at various frequencies, when a first order coupling and a lattice, respectively, are used in the crosstalk zone.

Fig. 9 is a simulation of end-crosstalk close to a plug / jack system, comparing a first-order coupling and a lattice in the crosstalk zone.

Fig. 10 is a simulation of end-crosstalk close to a plug / jack system, comparing a first-order coupling and a lattice in the crosstalk zone.

Figs. 11A and 1 IB show near end crosstalk (Fig. 11A) and distant end crosstalk (Fig. 1 IB) for an RJ45 10 GbE jack, having a lattice in the crosstalk zone.

Figs. 12A - 12F show positive and negative mutual inductance between conductor pairs and a simulation of the coupling vs. frequency for each setting.

Figs. 13A and 13B show two embodiments employing positive and negative mutual inductance in a lattice; Fig. 13C is a simulation of the lattice vs. frequency for each configuration of Figs. 13A and 13B.

Figs. 14A and 14B show other embodiments employing positive and negative mutual inductance in a lattice network; Fig. 14C is a simulation of the lattice vs. frequency for each configuration of Figs. 14A and 14B, compared to a capacitive coupling.

Fig. 14 shows a jack containing an LC circuit in series with negative mutual inductance in the compensation zone and with positive mutual inductance in the crosstalk zone.

Figs. 16 - 19 show various jack configurations with lattice networks containing positive or negative mutual inductance in the compensation and crosstalk zones.

Figs. 20 - 21 shows jacks containing a parallel resonant circuit containing positive mutual inductance in the compensation and crosstalk zones.

Figs. 22 - 23 show double lattice networks having crosstalk vectors and compensation vectors, respectively, with different frequency characteristics.

DETAILED DESCRIPTION OF METHODS

The data transmission rates used in communications systems are continually increasing. This increase has increased crosstalk in the plug / jack system. Therefore, several methods were used to decrease the net crosstalk in the system. One of these methods includes providing at least one printed circuit board (PCB) in the jack to compensate for crosstalk, reduce net near end crosstalk (NEXT) in the system. According to some embodiments, reducing the net NEXT in a plug / jack system also results in a reduction in net far-end crosstalk (FEXT).

A type of electrical connector typically used in a communications system is an RJ45 connector. The standard pin configuration for an eight-wire RJ45 plug / jack system contains multiple conductive pairs. These multiple pairs include a split pair (conductors 3 and 6) that straddle an intermediate pair (conductors 4 and 5). The signals introduced in the split pair are capacitively and inductively coupled to the intermediate pair due to the physical proximity of the conductors to both the plug and the jack. The unintentional coupling inserted into the jack in the vicinity of the plug / jack interface is crosstalk. The area in which this coupling occurs is referred to below as the contact zone.

To compensate for the crosstalk resulting from the above coupling, capacitive and inductive coupling between the different conductor pairs is intentionally introduced in different zones along the transmission path of the plug / jack system. Figures IA and IB illustrate cross-sectional views of different embodiments of a plug / jack system. Both in Figs. IA as IB the plug contacts of the plug connect with the jack spring contacts of the jack in plug / jack interfaces of the jack spring contacts of Zone A (contact zone). The jack spring contacts extend from the plug / jack interfaces to connect with a PCB containing Zone C (hereinafter referred to as the crosstalk zone). Conductive tracks on the PCB extend between the jack spring contacts and the insulation displacement contacts (IDCs) attached to the PCB. As shown in Fig. IA, Zone B (hereinafter referred to as the compensation zone) is arranged between the contact zone and the crosstalk zone. The compensation zone can be created using a PCB or individual elements attached to the jack spring contacts and / or by changing the shape of the jack spring contacts. The connector PCBs according to at least some embodiments can be rigid PCBs, flexible PCBs or combinations of the two. As shown in Fig. IB, the compensation zone (Zone B ') can also be arranged on the PCB containing the IDCs. Zone B 'is electrically closer to the contact zone than the crosstalk zone (Zone C) is to the contact zone.

As discussed above, crosstalk is unintentionally introduced into the contact zone. The compensation zone introduces compensation, which compensates for the combined crosstalk of the contact and crosstalk zones. The addition of crosstalk in the crosstalk zone allows the jack compensation zone to better compensate for crosstalk in the contact zone by introducing delayed crosstalk in phase to the jack / plug system, as more fully described below and in US Patent No. 7,153,168. Although the embodiment shown in Fig. IA or Fig. IB can be used, the effectiveness of the compensation in the compensation zone increases with the increasing proximity of the contact zone, due to the decreased phase delay between the crosstalk introduced in the contact zone and the compensation introduced in the compensation zone.

The coupling of each zone is modeled as a network between the conductors. The networks contain circuits between coupled conductor pairs. Each circuit contains one or more circuit elements. Conductors may include jack spring contacts or conductive tracks on the PCB. The capacitive and inductive coupling of each of the compensation and crosstalk zones can be provided by distributed elements, such as PCB tracks that run parallel to each other or to the jack spring contacts, or by individual physical components between the spring contacts. jack or tracks. If capacitive and inductive couplings are provided by distributed elements, the coupling of a particular section can be modeled as a circuit containing heaped elements, as long as the section is small compared to the wavelength of the maximum frequency to be analyzed. Generally, the physical section size should be less than about 1/20 the wavelength of the signal using this approach. For example, if a purely distributed capacitive coupling or a purely distributed inductive coupling exists between a pair of conductors, such coupling can be modeled by the use of a single capacitor or inductor, respectively, between the conductive pair. The contact zone contains a combination of a distributed mutually inductive coupling and a capacitive coupling distributed between the pairs of conductors, which results in multiple first order couplings, as shown in Fig. 2. The magnitude of a first order coupling, such as a purely capacitive coupling, has a frequency dependency of approximately 20 dB per decade. The grouped element model is suitable for the normal operating frequency range of the plug / jack system. Thus, the grouped element model will be used to describe the circuit elements of various circuits examined here.

Figure 2 illustrates a schematic model of the three zone plug / jack system of Figs. IA and IB, showing only conductors 3, 4, 5 and 6 for clarity. Each of the three zones includes capacitive and inductive circuit elements, shown in the compensation and crosstalk zones as a block containing a network. The contact zone includes capacitive and inductive coupling of the plug wires and contacts (112 in Fig. IA), capacitive coupling resulting from the jack spring contacts extending from the plug / jack interface to the end of the jack spring contacts away from the PCB (114 in Fig. IA) and capacitive and inductive coupling of the spring contacts jack extending from the plug / jack interface towards the PCB (116 in Fig. IA). These elements are shown as capacitive and inductive mutual coupling between conductors 3 and 4 and between conductors 6 and 5. The amount of each of the mutual capacitance and inductance can be different between the two coupled pairs. Similar coupling can occur between the conductors of the compensation zones and the crosstalk zones.

The coupling shown in the contact zone of Fig. 2 is a first order coupling. Although the use of similar first order couplings in the compensation and crosstalk zones may provide some capacity to reduce crosstalk, such couplings have limitations in reducing crosstalk. Other networks can be used to better reduce crosstalk. In particular, a lattice network having multi-frequency dependent couplings can be used in the compensation and / or crosstalk zones, to provide compensation and crosstalk coupling.

An embodiment of a truss network contains a series inductance and capacitance (i.e., an LC series circuit) between two sets of conductor pairs and a tap capacitance between two other sets of conductor pairs. This embodiment of a truss network is modeled as two LC circuits in series of a crosstalk configuration (one between conductor pair 3-4 and the other between conductor pair 56) and two branch capacitors in a compensation configuration ( one between conductor pair 3 - 5 and the other between conductor pair 4-6). The truss network can be used in one or the other or in both the compensation zone and the crosstalk zone.

Comparing the lattice to first order couplings: the slope of the lattice frequency response is tunable and can be higher or lower, the phase shift of the lattice changes with frequency to a greater extent and the resonant frequency of the truss network can be designed as desired. Similarly, by comparing the truss network with an LC circuit in series only in a crosstalk configuration: the slope of the truss network's frequency response can be adjusted more flexibly, the phase shift of the truss network changes with the frequency to a greater extent and the inductance used in the truss network may be less than the physical layout of the tracks on the PCB allows, causing the inductance to be reduced in size. The use of the truss network allows for improved frequency conformation of the crosstalk response of the plug / jack system.

Figures 3 and 4 show schematic of the SPICE circuit model (Simulation Program with Integrated Circuit Emphasis) for various forms of netting in the compensation zone and the crosstalk zone, respectively. As above, in one embodiment, each file of the networks of Figs. 3 and 4 can be provided by tracks on a PCB, with the coupling between the tracks represented as individual circuit elements. More specifically. Figs. 3 (i) and 3 (ii) illustrate the use of purely capacitive or purely mutually inductive couplings, respectively. between conductors 3 and 5 and between conductors 4 and 6 in the compensation zone. -Each-of-these-couplings éniTõdélãdo ”by a single element, a capacitor (C_çie C \₂) or a mutual inductor (M_V| in_&lt;2) between the drivers of each pair. Figure 4 (i) illustrates a combination of capacitors (C_xd and C_xl2) and mutual inducers (M_xtie M_xl2) coupling conductors 3 and 4 and coupling conductors 5 and 6 in the crosstalk zone, while Fig. 4 (ii) shows an inductor-capacitor (LC) circuit between conductors 3 and 4 and between conductors 5 and 6 in the crosstalk zone.

The LC circuit in series between each pair of conductors in Fig. 4 (ii) contains a capacitor, C_si, in series with a self-inductance, L_s], between conductive pairs 3 and 4. Also, C_s2 is in series with L_s2 between conductor pairs 5 and 6. An LC circuit in series has a resonant frequency = 1 / (2 π * a / LC). For frequencies below the resonance frequency, the coupling provided by the LC circuit in series increases as a function of the frequency. For frequencies above the resonance frequency, the coupling provided by the LC circuit in series decreases as a function of the frequency.

Figures 3 (iii) and 4 (iii) show embodiments of the truss network of the compensation zone and the crosstalk zone, respectively. As illustrated, the truss network includes a pair of IC circuits in series together with shunt capacitances. A series LC circuit (Lu and Cu in Fig. 3 (iii) and L_X| and C \ i in Fig. 4 (iii&gt; is connected in a crosstalk configuration between conductors 3 and 4 and the other LC circuit in series (I_d2 and C₎₂ in Fig. 3 (iii) and L_x2 and C_x2 in Fig. 4 (iii)) is connected in a crosstalk configuration between conductors 5 and 6. In addition, a shunt capacitor (C13 in Fig. 3 (iii) and C_x3 in Fig. 4 (iii)) is connected in a compensation configuration between conductors 3 and 5 and the other tap capacitor (C14 in Fig. 3 (iii) and C_x4 in Fig. 4 (iii)) is connected in a compensation configuration between conductors 4 and 6. In an embodiment of Fig. 3 (iii), capacitors C13 and C14 are equal to each other and have a greater capacitance than capacitors Cn and C12, which are also the same. In an embodiment of Fig. 4 (iii), capacitors C_x3 and C_x4 are equal to each other, but have a lower capacitance than C capacitors_xt and C_x2, which are also the same. A lattice network can be implemented in the crosstalk zone, as shown in Fig. 4 (iii), for example, when the contact zone vector and the crosstalk vector are not balanced with respect to the compensation zone vector , as shown in Fig. 8A. This can happen when the magnitudes of the contact and crosstalk vectors are not the same and / or when the phase differences between the compensation vector and the contact and crosstalk vectors are not the same.

The capacitance and inductance of the LC series circuit alone and the truss network can be designed so that the LC series circuit alone and the truss network do not play a significant role in coupling at lower frequencies (eg, lower than about 100 MHz) but play an increasingly significant role at higher frequencies (eg, greater than about 100 MHz), due to the presence of the series inductor. As an example, Figs. 5A and 5B illustrate the responses of the different networks in the crosstalk zone of the RJ45 plug / jack system. More specifically, Figs. 5A and 5B compare the magnitude and phase shift, respectively, of a first order coupling (capacitance only), an LC series circuit (as shown in Fig. 4 (ii)) and a crosstalk zone lattice ( as shown in Fig. 4 (iii)). The capacitance used in the simulation of the first order coupling and the LC series circuit is 1 pF. Each crosstalk capacitance used in the lattice network simulation (that is, the capacitance of the LC series circuit of the lattice network) is 1 pF and each compensating capacitance (that is, the derivation capacitance of the lattice network) is 2 pF. Each inductance used in the simulations of the LC series circuit and the lattice network is 20 nH. The capacitance and inductance values ​​given are for low frequencies (below about 50 MHz). An operating frequency range characteristic of the plug / jack system is shown in Figs. 5 A and 5B as the dashed region entitled “area of ​​interest” and extends from about 200 MHz to about 500 MHz. In the graph in Fig. 5A, the first order coupling response has a slope of approximately 20 dB per decade in the area of ​​interest. The LC series circuit has a resonance at approximately 1.1 GHz. Below the resonance, the LC series circuit response has a slope of about 25 dB per decade. The response slope of the truss network under the resonance is greater (at about 30 dB per decade) than the response slope of the series LC circuit.

The phase shifts of the first order coupling, the LC circuit in series and the lattice of the crosstalk zone, as a function of frequency, are illustrated in Fig. 5B. The phase shifts of the first order coupling and the LC series circuit of the area of ​​interest are approximately equal. The phase shift of the truss network often changes to a greater extent than the phase shift of the first order coupling or the LC circuit in series across the area of ​​interest. The difference in magnitude and phase displacement displayed by the truss network, in comparison with the first order coupling or the LC circuit in series, takes advantage when compensating for the plug / jack system. This is also shown in more detail using the vector diagrams in Figs. 7 and 8 and described in more detail below.

The magnitude response and phase shift of the networks operating in the compensation zone of the RJ45 plug / jack system are illustrated in Figs. 6A and 6B, respectively. In particular, Figs. 6A and 6B illustrate the magnitude response and phase shift, respectively, of the lattice network (shown in Fig. 3 (iii)) and the first order (capacitive) coupling (shown in Fig. 3 (i)). The values ​​of the circuit elements used in the simulations of Figs. 6A and 6B are the same used in Figs. 5A and 5B, except that each crosstalk capacitance used in the lattice simulation is 2 pF and each compensation capacitance is 1 pF. The magnitude of the first order coupling response shown in Fig. 6A has a slope of about 20 dB per decade. The magnitude of the lattice response in the area of ​​interest is less than that of the first order coupling and has a slope ranging from about 20 dB per decade at the lower end of the area of ​​interest to about 0 dB per decade in the highest end of the area of ​​interest. As shown in Fig. 6B, the phase shift of the truss network often changes to a greater extent than the phase shift of the first order coupling over the area of ​​interest. The magnitude and phase shift of the truss are capable of being more precisely adapted to better compensate for crosstalk than the first order coupling or the LC circuit in series.

Figures 7 and 8 illustrate vector models of a three zone plug / jack system. The compensation and crosstalk of the contact zone, the compensation zone and the crosstalk zone can be performed as a set of frequency-dependent vectors, separated by a phase difference from a reference plane (which is nominally located at the effective center of the compensation zone). The phase differences depend on the physical distances between the couplings and also on the materials through which the signals propagate. The contact zone contains multiple crosstalk terms that can be combined to form a single crosstalk vector that has a magnitude and a phase. Both the crosstalk of the contact zone and the crosstalk of the crosstalk zone have a phase difference in the compensation zone compensation. The vectors of the three zones can be added together to calculate frequency-dependent crosstalk.

The vector models of Figs. 7 and 8 compare a first order coupling with a lattice network implemented in the compensation zone and the crosstalk zone, respectively. The relative magnitudes of the vectors are shown at different frequencies. Note that these figures show the magnitudes of the vectors in relation to each other, the absolute magnitudes of the vectors often increases over the area of ​​interest. In Figs. 7 and 8, low frequency refers to frequencies below about 50 MHz, medium frequency refers to frequencies between about 50 MHz and 200 MHz and high frequency refers to frequencies above about 200 MHz. The relative magnitudes of the vectors are shown at different frequencies.

The implementation of a first order coupling in the compensation zone of Fig. 7A is compared with the implementation of a lattice in the compensation zone of Fig. 7B. The vector diaphragms of Figs. 7A and 7B assume that the plug / jack system is balanced, that is, the phase angle differences between the compensation and the crosstalk of the contact zone and between the compensation and crosstalk of the crosstalk are the same and that the crosstalk of the contact zone has the same magnitude as the crosstalk of the crosstalk zone. The crosstalk components are shown in Figs. 7A and 7B by the vectors pointing downwards (710, 711, 712, 720, 721, 722 in Fig. 7A and 750, 751, 752, 760, 761 and 762 in Fig. 7B). Cross-talk vectors are symmetrical around 0 ° (the compensation zone is taken as the reference plane in Figs. 7 and 8), as shown by the angles φ_ΐ5 φ₂, φ₃, of Fig. 7A and φ₄, φ₅, φ₆ in Fig. 7B. The angles represent the phase difference between the compensation zone and the contact and crosstalk zones. The relative magnitude of the crosstalk vector 720, 721, 722 of the contact zone is A_ml, A_m2, A_m3, respectively, and the relative magnitude of the crosstalk vector 710, 711, 712 in the crosstalk zone is C_mi, C_m2, Ç_m3, respectively, in Fig. 7A. Similarly, the relative magnitude of the crosstalk vector of contact zone 760, 761, 762 is A_m4, A_m5, A_m6, respectively, and the relative magnitude of the crosstalk vector 750, 751, 752 in the crosstalk zone is C_m4, Ç_m5, C_m6, respectively, in Fig. 7B. Crosstalk vectors often increase in relative magnitude and angle. Thus, (pi &lt;φ₂ &lt;φ₃ AND THE_ml = C_mj) &lt;(A_m2 = C_m2) &lt;(A_m3 = C_m3) in Fig. 7A and φ₄ &lt;φ₅ &lt;φ₆ and the_m4 = C_m4) &lt;(A_m5 = C_m5) &lt;(A_m6 = C_m6) in Fig. 7B.

Compensation of the compensation zone is provided to compensate for the crosstalk of the plug / jack system. The compensation vector (730, 731, 732 of Fig. 7A and 770, 771, 772 of Fig. 7B) of the compensation zone has a polarity opposite to that resulting from the crosstalk vectors. The resulting vector (740, 741, 742 in Fig. 7A and 780, 781, 782 in Fig. 7B) is the combination of the crosstalk and compensation vectors. Thus, the resulting vector represents the crosstalk remaining in the plug / jack system after compensation. The angles of each pair of crosstalk vectors (710 and 720, 711 and 721, 712 and 722 of Fig. 7A and 750 and 760, 751 and 761, 752 and 762 of Fig. 7B) of the reference plane are the same in a particular frequency across the frequency range shown in Figs. 7A and 7B. The sinusoidal components φ (that is, the horizontal components of Figs. 7A and 7B) of the crosstalk vectors of the crosstalk zones and contact zones of each frequency, that is, 710 and 720, 711 and 721, 712 and 722, 750 and 760, 751 and 761, 752 and 762, are canceled, leaving only the sinusoidal components φ (that is, the vertical components of Figs. 7A and 7B). Thus, the resulting vector overlaps the compensation vector (i.e. 740 overlay 730, 742 overlay 731, 742 overlay 732 in Fig. 7A, 780 overlay 770, 781 overlay 771, 782 overlay 772 in Fig. 7B).

In Fig. 7A, the magnitudes of the compensation and crosstalk vectors individually increase with frequency at a rate of about 20 dB per decade. This causes the resulting vector to increase relatively quickly frequently because the compensation vector increases more than the combined cosine dos components of the crosstalk and contact zone crosstalk vectors. Thus, without the use of the lattice, the crosstalk of the plug / jack system increases substantially with increasing frequency.

The vector diagrams in Fig. 7B illustrate a plug / jack system that employs a lattice in the compensation zone. The vectors in Fig. 7B are similar to those in Fig. 7A. However, in the plug / jack system shown in Fig. 7B, the compensation vector 770, 771, 772 often increases at a rate of less than 20 dB per decade, that is, less than that of the individual crosstalk vectors 750 , 751, 760, 761, 752, 762. The increase in the compensation vector 770, 771, 772 can be better matched to the increase in the combined cosine components dos of the respective crosstalk vectors 750 and 760, 751 and 761, 752 and 762. The resulting vector still has no displacement phase, but increases with frequency less than in the jack of Fig. 7 A.

A simplified vector model of a three-zone RJ 145 plug and jack system at different frequencies, in which a first order coupling is implemented in the crosstalk zone, is shown in Fig.8A and a vector model in which the network truss is implemented in the crosstalk zone is shown in Fig. 8B. Unlike the vector diagrams in Figs. 7A and 7B, the vector diagrams of Figs. 8A and 8B assume that the plug / jack system is not balanced. The differences in phase angle between compensation and crosstalk of the contact zone and between compensation and crosstalk of the crosstalk zone are not the same. As illustrated by the angles (Θ) in Fig. 8A, the crosstalk phase shift of the compensation crosstalk zone is less than the crosstalk phase shift of the compensation contact zone (ie θι&gt; 0₂, Θ3&gt; θ₄, Θ5&gt; Oô). The crosstalk of the contact zone nor the crosstalk of the crosstalk zone of Fig. 8A are of the same magnitude; the magnitude of the crosstalk of the contact zone is greater than the magnitude of the crosstalk of the crosstalk zone (ie, A_nl &gt; C_ni, An₂ &gt; C_n2, A_n3 &gt; C_n3).

In Fig. 8 A, similar to Fig. 7 A, the magnitudes of the individual crosstalk vectors 810, 811, 812, 820, 821, 822 increase with frequency at a rate of about 20 dB per decade (ie, A_n3 &gt; A_n2 &gt; A_nie C_n3 &gt; C_n2 &gt; C_ni). The magnitude of the compensation vector 830, 831, 832 also correspondingly increases with frequency at a rate of about 20 dB per decade. Due to the imbalance, the resulting vector 840, 841, 842 does not overlap the compensation vector 830, 831, 832. Thus, the resulting vector 840, 841, 842 grows in magnitude and phase delay with increasing frequency due to increased phase inequality. of the crosstalk vectors 810 and 820, 811 and 821, 812 and 822.

Using a lattice in the crosstalk zone, the relative magnitude of the resulting vector is reduced, as shown in Fig. 8B. Unlike Fig. 8A, the plug / jack system of Fig. 8B is effectively balanced, that is, the crosstalk vector 860, 861, 862, introduced in the contact zone and the crosstalk vector 850, 851, 852, introduced in the contact zone have the same relative magnitude (ie A_n4 = C_n4, A_n5 = C_n5, A_n6 = C_n6) and phase difference with respect to the compensation zone. When the frequency increases, the relative magnitude of the crosstalk vector 850, 851, 852 of the crosstalk zone, due to the lattice network, as shown in Fig. 8b, increases at a higher rate than the relative magnitude of the crosstalk vector 810 , 811, 812 of the crosstalk zone, due to a first order coupling, as shown in Fig. 8A. The relative magnitude of the resulting vector 880, 881, 882 of the plug / jack system implementing the truss network in the crosstalk zone thus increases with less frequency than in a plug / jack system implementing a first order coupling in the crosstalk zone. crosstalk.

SPICE simulations of a first order coupling and a lattice network implemented in the crosstalk zone are compared with the NEXT limit (standard ANSI / TIA / EIA-568B.2-1) in Fig. 9. In the simulation, below about 100 MHz, the NEXT of the plug / jack system, having a lattice in the 910 crosstalk zone, and the NEXT of the plug / jack system, having first order coupling in the 920 crosstalk zone, are almost identical. Between about 100 MHz and 220 MHz, the NEXT of the plug / jack system, having a lattice in the 910 crosstalk zone, is slightly larger than the NEXT of the plug / jack system having first order coupling in the crosstalk 920. Between about 250 MHz and 1 GHz, the NEXT of the plug / jack system, having a lattice in the 910 crosstalk zone, is significantly less than the NEXT of the plug / jack system having first order coupling of the crosstalk zone 920. In particular, the difference between the NEXT of the plug / jack system with the 910 truss network and the NEXT of the plug / jack system with the first order 920 coupling increases to 15 - 20 dB at about 500 MHz. The NEXT of the plug / jack system with both the 910 truss network and the 920 first order coupling are below the NEXT 930 limit for frequencies less than about 400 MHz. Above 400 MHz, the NEXT of the plug / jack system with the first order coupling 920 exceeds the NEXT 930 limit, while the NEXT of the plug / jack system with the 910 truss network remains below the NEXT 930 limit. Both the bandwidth of an RJ45 jack and the NEXT margin (the difference between the NEXT of the plug / jack system and the NEXT limit) are improved through a first order coupling, using a lattice in the crosstalk zone in the normal operating range of the plug / jack system.

The SPICE simulations of a first order coupling and a lattice network implemented in the compensation zone are compared with the NEXT limit in Fig. 10. As in the simulation of Fig. 9, the NEXT of the plug / jack system, having a lattice in the 1010 compensation zone, and the plug / jack system NEXT, having first order coupling in the 1020 compensation zone, are almost identical below about 100 MHz. Between about 100 MHz and 200 MHz, the NEXT of the plug / jack system, having a lattice in the 1010 compensation zone, is greater than the NEXT of the plug / jack system, having first order coupling in the compensation 1020. Between about 200 MHz and 600 MHz, the NEXT of the plug / jack system, having a lattice in the 1010 compensation zone, is significantly less than the NEXT of the plug / jack system having first order coupling in compensation zone 1020. In particular, the difference between the NEXT of the plug / jack system, with the 1010 truss network and the NEXT of the plug / jack system, with the first order 1020 coupling, increases to 23 - 24 dB at about 500 MHz The NEXT of the plug / jack system with both the 1010 truss network and the 1020 first order coupling is below the NEXT 1030 limit, for frequencies less than about 400 MHz. Above 400 MHz, the NEXT of the plug / jack system with the first order coupling 1020 exceeds the NEXT 1030 limit, while the NEXT of the plug / jack system with the 1010 truss network remains below the NEXT 1030 limit. As above, both the bandwidth of an RJ45 jack and the NEXT margin (the difference between the NEXT of the plug / jack system and the NEXT limit) are improved through a first order coupling, using a lattice network. in the compensation zone in the normal operating range of the plug / jack system.

Figures 11A and 11B show measurements of near-end crosstalk (NEXT) and far-end crosstalk (FEXT), respectively, of plug / jack systems, having first order coupling in the crosstalk zone and plug / jack systems. , employing a lattice network in the crosstalk zone. In both cases, an RJ45 plug, having the performance level of an “intermediate plug” specification, as defined by TIA568B, is used. As shown in Fig. 11 A, the NEXT performance of the jack using a 1120 lattice network is less than the NEXT performance of the jack using first order 1110 coupling at frequencies exceeding about 300 MHz. The NEXT performances of the jack having a 1120 lattice network and having a first order 1110 coupling are below the NEXT 10G 1130 requirement for frequencies below about 400 MHz, while only the NEXT performance of the jack having a 1120 lattice is below of the NEXT 10G 1130 requirement for frequencies above about 400 MHz. In Fig. 1 IB, while the FEXT performances of the jack having a 1150 lattice network and having a first order 1140 coupling are below the FEXT 10G 1160 requirement (ANSI / TIA / EIA-568B.2.1 standard) for frequencies below about 500 MHz, the FEXT performance of the jack having an 1150 lattice network is better than that of the jack having a first order 1140 coupling across all frequencies above 2 MHz.

Other network configurations can be used in addition to those illustrated above. For example, an inductor such as a self-inducting element can be used as a crosstalk circuit component (eg, between conductors 3 and 4 and between 5 and 6) of the truss. Figures 12 - 21 illustrate other networks that can be used.

Figures 12A and 12B show the use of negative and positive mutual inductance in a coupling between each pair of conductors. The only difference between these figures is that the L connection₂ is inverted, so that the

Fig. 12A has a negative mutual inductance and Fig. 12B has a positive mutual inductance. In these figures, the coupling between each pair of conductors includes a capacitor in series with an inductor. The mutual inductance, M, of the inductor varies with a mutual coupling constant, Κ. K varies between 0 and 1 (that is, 0 &lt;K&gt; 1). Each capacitor is 1 pF and the auto-inductance L_s of each inductor L_si, L_s2, L_s3, L_s4 is 20 nH in Figs. 12A and 12B. The inductance of each inductor in Fig. 12A varies so that Li = L_si + M = L_s + MeL2 = L_s2 + M = L_s + M, where M = - K * * L_s2 = -K * L_s, so that L] = L₂ = (1-K) * L_s. Thus, when K = 0, M = 0 and L | = L₂ = 20 nH. When K approaches 1, M approaches —L_s and the net inductance of each inductor (L_s + M) goes to 0. Thus, when K approaches 1, the response of the LC circuit in series between each pair of conductors approaches that of u only an ideal capacitive coupling. Similarly, the inductor in Fig. 12B varies so that Μ = K * L_s and L₃ = L₄ = (1 + K) * L_s. So, when K approaches 1, M approaches L_s and L₃ = L₄ = 2L_s.

Figures 12C - 12F are simulations of couplings using the circuits shown in Figs. 12A and 12B. More specifically, Fig. 12C is a simulation of the configuration of Fig. 12A, while Fig. 12D is an increase of Fig. 12C in the area of ​​interest between about 200 MHz and 500 MHz. Similarly, Fig. 12E is an simulation of the configuration of Fig. 12B, while Fig. 12F is an increase of Fig. 12E in the area of ​​interest. As illustrated in Figs. 12C and 12D, the coupling decreases at all frequencies within the area of ​​interest when the degree of negative mutual inductance increases. As illustrated in Figs. 12E and 12F, the coupling increases at all frequencies within the area of ​​interest when the degree of positive mutual inductance increases.

Figures 13A and 13B show the use of negative and positive mutual inductance in a lattice. The lattice of Fig. 13A has a negative mutual inductance and the lattice of Fig. 13B has a positive mutual inductance. As in the LC series circuit of Figures 12A and 12B, the auto inductance of each inductor in the LC series circuit of the truss network is 20 nH. The capacitance of each LC circuit in series is 1 pF and each tap capacitor has a capacitance of 2 pF. Fig. 13C is a simulation showing the coupling of a truss network using negative mutual inductance (Fig. 13A) or positive mutual inductance (Fig. 13B). As shown in Fig. 13C, using positive mutual inductance, the degree of coupling in the 200 - 500 MHz frequency range is reduced to a greater extent than using negative mutual inductance.

Figures 14A and 14B show a lattice network having positive and negative mutual inductance, respectively. As in the LC series circuit of Figs. 13A and 13B, the auto-inductance of each inductor of the LC circuit in series of the truss network is 20 nH. Unlike the configurations in Figs. 13 A and 13B, however, the capacitance of each LC circuit in series is 2 pF and each tap capacitor has a capacitance of 1 pF. Figure 14C is a simulation showing coupling to a lattice using negative mutual inductance (Fig. 14A) or positive mutual inductance (Fig. 14B). As shown in Fig. 14C, using positive mutual inductance increases the degree of coupling in the 200 - 500 MHz frequency range to a greater extent than using negative mutual inductance. The difference in the degree of coupling between Figs. 13 and 14 is a result of the relative differences between the capacitance of the LC series circuit and the shunt capacitance between the figures.

Figures 15 - 23 show several multizone configurations, which make use of negative or positive mutual inductance. Mutual inductance is used in both clearing and crosstalk zones, mutual inductance can be negative or positive in both zones or negative in one zone and positive in the other zone. Figures 15 - 19 illustrate ways of making three-zone jacks, in which the LC circuits in series are used in the compensation and crosstalk zones. Figures 20 and 21 illustrate embodiments of the three-zone jacks, in which parallel resonant circuits are employed in the compensation and crosstalk zones. Each parallel resonant circuit contains a parallel combination of an inductor and a capacitor. As with the LC series circuit configurations, the parallel resonant circuits can be in one or both of the compensation and crosstalk zones and can use a self-inductance only or can include a mutual inductance. The inductor of each resonant circuit parallel to the embodiments of Figs. 20 and 21 contain a mutual inductance. The coupling between each pair of conductors contains each parallel resonant circuit in series with a blocking capacitor. In general, a combination of parallel resonant circuits and LC circuit in series can be used in different zones or in the same zone of a jack. Figures 22 and 23 illustrate two lattice networks containing mutual inductances. As shown in Figs. 7 and 8, and discussed above, each lattice network provides a vector (compensation or crosstalk), depending on the configuration of the lattice network and the values ​​of the individual elements within the lattice. The duplication of a lattice network provides a double lattice vector, whose relative magnitude changes with frequency in a direction opposite to the relative magnitude of the lattice vector in the area of ​​interest. Thus, for example, if a particular truss network provides a crosstalk vector whose relative magnitude increases with increasing frequency in the area of ​​interest, the duplication of the particular truss network provides a double crosstalk vector, whose relative magnitude decreases with frequency growing.

The use of a lattice in the compensation zone and / or the crosstalk zone can increase the crosstalk performance of the jack. Each lattice network may include one or more LC circuit in series and / or one or more parallel resonant circuits. Truss network inductors can include self-inductance and / or mutual inductance. The lattice can be provided using tracks on a PCB, different components and / or conforming the jack spring contacts. The properties of the PCB material containing the lattice can be increased through the use of a high permeability material or a material with a frequency dependence on the PCB. The circuits of each truss network can be arranged in various crosstalk and compensation configurations and the values ​​of the circuit elements of the circuits can be selected to provide the desired jack characteristics.